FSP33035ND

BRUSHLESS DC MOTOR CONTROLLER FSP33035 FEATURES 10V to 30 V Operation Undervoltage Lockout 6.25V Reference Capable of Supplying Sensor Power Fully Accessible Error Amplifier for Closed Loop Servo Applications High Current Drivers Can Control External 3–Phase MOSFET Bridge Cycle–By–Cycle Current Limiting Pinned–Out Current Sense Reference Internal Thermal Shutdown Selectable 60°/300° or 120°/240° Sensor Phasings Can Efficiently Control Brush DC Motors with External MOSFET H–Bridge Top driver output current not more than 50mA Bottom driver output current not more than 100mA SOP24L and PDIP24L Packages GENERAL DESCRIPTION The FSP33035 is a high performance second generation monolithic brushless DC motor controller containing all of the active functions required to implement a full featured open loop, three or four phase motor control system. This device consists of a rotor position decoder for proper commutation sequencing, temperature compensated reference capable of supplying sensor power, frequency programmable sawtooth oscillator, three open collector top drivers, and three high current totem pole bottom drivers ideally suited for driving power MOSFETs. Also included are protective features consisting of undervoltage lockout, cycle–by–cycle current limiting with a selectable time delayed latched shutdown mode, internal thermal shutdown, and a unique fault output that can be interfaced into microprocessor controlled systems. Typical motor control functions include open loop speed, forward or reverse direction, run enable, and dynamic braking. The FSP33035 is designed to operate with electrical sensor phasings of 60°/300° or 120°/240°, and can also efficiently control brush DC motors. PIN CONFIGURATION 1/28 2007-3-16 BRUSHLESS DC MOTOR CONTROLLER FSP33035 PIN DESCRIPTION Pin Number 1, 2, 24 3 4, 5, 6 7 8 Pin Function These three open collector Top Drive outputs are designed to drive BT , AT , CT the external upper power switch transistors. Fwd/Rev The Forward/Reverse Input is used to change the direction of motor rotation. These three Sensor Inputs control the commutation sequence. SA, SB, SC A logic high at this input causes the motor to run, while a low causes it to Output Enable coast. Reference Output This output provides charging current for the oscillator timing capacitor CT and a reference for the error amplifier. It may also serve to furnish sensor power. Current Sense A 100 mV signal, with respect to Pin 15, at this input terminates output Noninverting Input switch conduction during a given oscillator cycle. This pin normally connects to the top side of the current sense resistor. Oscillator The Oscillator frequency is programmed by the values selected for the timing components, RT and CT. This input is normally connected to the speed set potentiometer. Error Amp Noninverting Input Error Amp This input is normally connected to the Error Amp Output in open loop Inverting Input applications. This pin is available for compensation in closed loop applications. Error Amp Out/PWM Input Fault Output This open collector output is active low during one or more of the following conditions: Invalid Sensor Input code, Enable Input at logic 0, Current Sense Input greater than 100 mV (Pin 9 with respect to Pin 15), Undervoltage Lockout activation, and Thermal Shutdown. Reference pin for internal 100 mV threshold. This pin is normally connected to the bottom side of the current sense resistor. This pin supplies a ground for the control circuit and should be referenced back to the power source ground. This pin is the positive supply of the control IC. The controller is functional over a minimum VCC range of 10 to 30 V. The high state (VOH) of the Bottom Drive Outputs is set by the voltage applied to this pin. The controller is operational over a minimum VC range of 10 to 30 V. These three totem pole Bottom Drive Outputs are designed for direct drive of the external bottom power switch transistors. The electrical state of this pin configures the control circuit operation for either 60° (high state) or 120°(low state) sensor electrical phasing inputs. A logic low state at this input allows the motor to run, while a high state does not allow motor operation and if operating causes rapid deceleration. Pin Name 9 10 11 12 13 14 15 16 17 18 Current Sense Inverting Input Gnd VCC VC 19, 20, 21 22 CB, BB, AB 60°/120 ° Select 23 Brake 2/28 2007-3-16 BRUSHLESS DC MOTOR CONTROLLER FSP33035 ELECTRICAL CIRCUIT 3/28 2007-3-16 BRUSHLESS DC MOTOR CONTROLLER FSP33035 ABSOLUTE MAXIMUM RATINGS Parameter Power Supply Voltage, VCC Digital Inputs (Pins 3, 4, 5, 6, 22, 23), Oscillator Input Current (Source or Sink), IOSC Error Amp Input Voltage Range (Pins 11, 12), VIR Error Amp Output Current (Source or Sink), Iout Current Sense Input Voltage Range (Pins 9, 15), Vsense Fault Fault Output Voltage, VCE(fault) Fault Output Sink Current, ISINK(fault) Top Drive Voltage (Pins 1, 2, 24), VCE(top) Top Drive Sink Current (Pins 1, 2, 24), ISINK(top) Bottom Drive Supply Voltage (Pin 18),Vc Bottom Drive Out put Current(Source or Sink, Pins19, 20, 21), IDRV Maximum Power Dissipation @ TA = 85°C, PD Thermal Resistance, Junction–to–Air, RQJA Operating Junction Temperature, TJ Operating Ambient Temperature Range, TA Storage Temperature Range, TSTG Rating 40 Vref 30 -0.3 to Vref 10 -0.3 to 5 20 20 40 50 30 100 867(PDIP24L) 650(SOP24L) 75(PDIP24L) 100(SOP24L) 150 -40 to 85 -65 to 150 Unit V V mA V mA V V mA V mA V mA mW °C/W °C °C °C ELECTRICAL CHARACTERISTICS (VC C = VC = 20 V, RT = 4.7 k, CT = 10 nF, TA = 25°C, unless otherwise noted.) PARAMETER SYMBOL TEST CONDITIONS REFERENCE SECTION Reference Output Voltage Line Regulation Load Regulation Output Short Circuit Current , Reference Under Voltage Lockout Threshold, ERROR AMPLIFIER Input Offset Voltage Input Offset Current Input Bias Current Input Common Mode Voltage Range Open Loop Voltage Gain Input Common Mode Rejection Ratio Power Supply Rejection Ratio Output Voltage Swing High level Output Voltage Swing Low level (Ire f = 1.0 mA), TA = 25°C (Ire f = 1.0 mA), TA = -40 to 85°C (VC C = 10 to 30 V, Ir e f = 1.0 mA), (Ir e f = 1.0 to 20 mA), MIN 5.9 5.82 TYP MAX 6.5 6.57 30 30 5.0 10 500 -1000 0~Vref (VO = 3.0 V, RL = 15 k) 70 55 (VCC=VC =10 to 30V) RL= 15 k to GND RL = 15 k to Vref 65 4.6 1.0 UNIT Vref V mV mV mA V mV nA nA V dB dB dB V Isc Vth Vio Iio Iib Vicr AVOL CMRR PSRR VOH VOL TA = -40 to 85°C TA = -40 to 85°C TA = -40 to 85°C 40 4.0 4/28 2007-3-16 BRUSHLESS DC MOTOR CONTROLLER FSP33035 ELECTRICAL CHARACTERISTICS(CONTINUED) (VC C = VC = 20 V, RT = 4.7 k, CT = 10 nF, TA = 25°C, unless otherwise noted.) PARAMETER SYMBOL TEST CONDITIONS OSCILLATOR SECTION Oscillator Frequency Frequency Change with Voltage Sawtooth Peak Voltage Sawtooth Valley Voltage LOGIC INPUTS Input Threshold Voltage (Pins 3, 4, 5, 6, 7, 22, 23)High State Input Threshold Voltage (Pins 3, 4, 5, 6, 7, 22, 23) Low State Sensor Inputs (Pins 4, 5, 6) High State Input Current Sensor Inputs (Pins 4, 5, 6) Low State Input Current Forward/Reverse, 60°/ 120 ° Select (Pins 3, 22, 23) High State Input Current Forward/Reverse, 60°/ 120 ° Select (Pins 3, 22, 23) Low State Input Current Output Enable High State Input Current Output Enable Low State Input Current CURRENT LIMIT COMPARATOR Threshold Voltage Input Bias Current fosc fosc/V Vosc(p) Vosc(v) VIH VIL IIHS IILS IIHF (VIH = 5.0 V) (VIL = 0 V) (VIH = 5.0 V) -150 -600 -75 MIN 22 (VCC = 10 to 30 V) 1.2 3.0 V 0.8 -20 uA -150 -10 uA IILF (VIL = 0 V) -300 -75 TYP MAX 28 5.0 4.5 UNIT kHz % V V IIHE IILE (VIH = 5.0 V) (VIL = 0 V) -60 -60 85 -10 uA -10 115 -5.0 1.5 100 300 ns 300 mV uA V uA Vthc Iibc OUTPUTS AND POWER SECTIONS Top Drive Output Sink VCE(sat) Saturation Top Drive Output Off–State IDRVleak Leakage Top Drive Output Switching Time , Rise Time trT Top Drive Output Switching Time ,Fall Time Bottom Drive Output Voltage, High State Bottom Drive Output Voltage, Low state Bottom Drive Output Switching Time Rise Time Bottom Drive Output Switching Time Fall Time Fault Output Sink Saturation Fault Output Off–State Leakage tfT VOHB VOHL trB tfB VCE(sat) IFLTleak (Isink = 25 mA) (VCE = 30 V) (CL = 47 pF, RL = 1.0 k) (CL = 47 pF, RL = 1.0 k) VCC = 20 V, VC = 30 V ( Isource = 50 mA) VCC = 20 V, VC = 30 V ( Isink = 50 mA) (CL = 1000 pF) (CL = 1000 pF) (Isink = 16 mA) (VCE = 20 V) VCC-2 V 2.0 200 ns 200 500 100 mV uA 5/28 2007-3-16 BRUSHLESS DC MOTOR CONTROLLER FSP33035 ELECTRICAL CHARACTERISTICS(CONTINUED) (VC C = VC = 20 V, RT = 4.7 k, CT = 10 nF, TA = 25°C, unless otherwise noted.) PARAMETER SYMBOL TEST CONDITIONS OUTPUTS AND POWER SECTIONS Under Voltage Lockout VTH(on) Drive Output Enabled Hysteresis, VH Power Supply Current, Pin 17 Power Supply Current, Pin 18 ICC MIN TYP MAX UNIT (VCC or VC Increasing) VCC = VC = 20 V VCC = 20 V, VC = 30 V VCC = VC = 20 V 8.2 0.1 10 0.3 16 V V mA 20 6.0 10 mA IC VCC = 20 V, VC = 30 V BLOCK DIAGRAM 6/28 2007-3-16 BRUSHLESS DC MOTOR CONTROLLER FSP33035 FUNCTION DESCRIPTION Rotor Position Decoder An internal rotor position decoder monitors the three sensor inputs (Pins 4, 5, 6) to provide the proper sequencing of the top and bottom drive outputs. The sensor inputs are designed to interface directly with open collector type Hall Effect switches or opto slotted couplers. Internal pull–up resistors are included to minimize the required number of external components. The inputs are TTL compatible, with their thresholds typically at 2.2 V. The FSP33035 series is designed to control three phase motors and operate with four of the most common conventions of sensor phasing. A 60°/120° Select (Pin 22) is conveniently provided and affords the FSP33035 to configure itself to control motors having either 60°, 120°, 240° or 300° electrical sensor phasing. With three sensor inputs there are eight possible input code combinations, six of which are valid rotor positions. The remaining two codes are invalid and are usually caused by an open or shorted sensor line. With six valid input codes, the decoder can resolve the motor rotor position to within a window of 60 electrical degrees. The Forward/Reverse input (Pin 3) is used to change the direction of motor rotation by reversing the voltage across the stator winding. When the input changes state, from high to low with a given sensor input code (for example 100), the enabled top and bottom drive outputs with the same alpha designation are exchanged (AT to AB , BT to BB , CT to CB ). In effect, the commutation sequence is reversed and the motor changes directional rotation. Motor on/off control is accomplished by the Output Enable (Pin 7). When left disconnected, an internal 25 µA current source enables sequencing of the top and bottom drive outputs. When grounded, the top drive outputs turn off and the bottom drives are forced low, causing the motor to coast and the Fault output to activate. Dynamic motor braking allows an additional margin of safety to be designed into the final product. Braking is accomplished by placing the Brake Input (Pin 23) in a high state. This causes the top drive outputs to turn off and the bottom drives to turn on, shorting the motor–generated back EMF. The brake input has unconditional priority over all other inputs. The internal 40 k: pull–up resistor simplifies interfacing with the system safety–switch by insuring brake activation if opened or disconnected. The commutation logic truth table is shown in Table below. A four input NOR gate is used to monitor the brake input and the inputs to the three top drive output transistors. Its purpose is to disable braking until the top drive outputs attain a high state. This helps to prevent simultaneous conduction of the top and bottom power switches. In half wave motor drive applications, the top drive outputs are not required and are normally left disconnected. Three Phase, Six Step Commutation Truth Table (Note 1) NOTES: 1. V = Any one of six valid sensor or drive combinations X = Don’t care. 2. The digital inputs (Pins 3, 4, 5, 6, 7, 22, 23) are all TTL compatible. The current sense input (Pin 9) has a 100 mV threshold with respect to Pin 15. A logic 0 for this input is defined as < 85 mV, and a logic 1 is > 115 mV. 3. The fault and top drive outputs are open collector design and active in the low (0) state. 4.With 60°/120 ° select (Pin 22) in the high (1) state, configuration is for 60° sensor electrical phasing 7/28 2007-3-16 BRUSHLESS DC MOTOR CONTROLLER FSP33035 inputs. With Pin 22 in low (0) state, configuration is for 120° sensor electrical phasing inputs. 5. Valid 60° or 120° sensor combinations for corresponding valid top and bottom drive outputs. 6. Invalid sensor inputs with brake = 0; All top and bottom drives off, Fault low. 7. Invalid sensor inputs with brake = 1; All top drives off, all bottom drives on, Fault low. 8. Valid 60° or 120° sensor inputs with brake = 1; All top drives off, all bottom drives on, Fault high. 9. Valid sensor inputs with brake = 1 and enable = 0; All top drives off, all bottom drives on, Fault low. 10. Valid sensor inputs with brake = 0 and enable = 0; All top and bottom drives off, Fault low. 11. All bottom drives off, Fault low. Error Amplifier A high performance, fully compensated error amplifier with access to both inputs and output (Pins 11, 12, 13) is provided to facilitate the implementation of closed loop motor speed control. The amplifier features a typical DC voltage gain of 80 dB, 0.6 MHz gain bandwidth, and a wide input common mode voltage range that extends from ground to Vref. In most open loop speed control applications, the amplifier is configured as a unity gain voltage follower with the noninverting input connected to the speed set voltage source. Oscillator The frequency of the internal ramp oscillator is programmed by the values selected for timing components RT and CT. Capacitor CT is charged from the Reference Output (Pin 8) through resistor RT and discharged by an internal discharge transistor. The ramp peak and valley voltages are typically 4.1 V and 1.5 V respectively. To provide a good compromise between audible noise and output switching efficiency, an oscillator frequency in the range of 20 to 30 kHz is recommended. Pulse Width Modulator The use of pulse width modulation provides an energy efficient method of controlling the motor speed by varying the average voltage applied to each stator winding during the commutation sequence. As CT discharges, the oscillator sets both latches, allowing conduction of the top and bottom drive outputs. The PWM comparator resets the upper latch, terminating the bottom drive output conduction when the positive–going ramp of CT becomes greater than the error amplifier output. The pulse width modulator timing diagram is shown in the Figure below. Pulse width modulation for speed control appears only at the bottom drive outputs. Pulse Width Modulator Timing Diagram Reference 8/28 2007-3-16 BRUSHLESS DC MOTOR CONTROLLER FSP33035 Current Limit Continuous operation of a motor that is severely over–loaded results in overheating and eventual failure. This destructive condition can best be prevented with the use of cycle–by–cycle current limiting. That is, each on–cycle is treated as a separate event. Cycle–by–cycle current limiting is accomplished by monitoring the stator current build–up each time an output switch conducts, and upon sensing an over current condition, immediately turning off the switch and holding it off for the remaining duration of oscillator ramp–up period. The stator current is converted to a voltage by inserting a ground–referenced sense resistor RS in series with the three bottom switch transistors (Q4, Q5, Q6). The voltage developed across the sense resistor is monitored by the Current Sense Input (Pins 9 and 15), and compared to the internal 100 mV reference. The current sense comparator inputs have an input common mode range of approximately 3.0 V. If the 100 mV current sense threshold is exceeded, the comparator resets the lower sense latch and terminates output switch conduction. The value for the current sense resistor is: The Fault output activates during an over current condition. The dual–latch PWM configuration ensures that only one single output conduction pulse occurs during any given oscillator cycle, whether terminated by the output of the error amp or the current limit comparator. Reference voltage source The on–chip 6.25 V regulator (Pin 8) provides charging current for the oscillator timing capacitor, a reference for the error amplifier, and can supply 20 mA of current suitable for directly powering sensors in low voltage applications. In higher voltage applications, it may become necessary to transfer the power dissipated by the regulator off the IC. This is easily accomplished with the addition of an external pass transistor as shown in Figure below. A 6.25 V reference level was chosen to allow implementation of the simpler NPN circuit, where Vref – VBE exceeds the minimum voltage required by Hall Effect sensors over temperature. With proper transistor selection and adequate heatsinking, up to one amp of load current can be obtained. Reference Output Buffers The NPN circuit is recommended for powering Hall or opto sensors, where the output voltage temperature coefficient is not critical. The PNP circuit is slightly more complex, but is also more accurate over temperature. Neither circuit has current limiting. Undervoltage Lockout A triple Undervoltage Lockout has been incorporated to prevent damage to the IC and the external power switch transistors. Under low power supply conditions, it guarantees that the IC and sensors are fully functional, and that there is sufficient bottom drive output voltage. The positive power supplies to the IC (VCC) and the bottom drives (VC) are each monitored by separate comparators that have their thresholds at 9.1 V. This level ensures sufficient gate drive necessary to attain low RDS(on) when driving standard power MOSFET devices. When directly powering the Hall sensors from the reference, improper sensor operation can result if the reference output voltage falls below 4.5 V. A third comparator is used to detect this condition. If one or more of the comparators detects an undervoltage condition, the Fault Output is activated, the top drives are turned off and the bottom drive outputs are held in a low state. Each of the comparators contains hysteresis to prevent oscillations when crossing their respective thresholds. 9/28 2007-3-16 BRUSHLESS DC MOTOR CONTROLLER FSP33035 Fault Output The open collector Fault Output (Pin 14) was designed to provide diagnostic information in the event of a system malfunction. It has a sink current capability of 16 mA and can directly drive a light emitting diode for visual indication. Additionally, it is easily interfaced with TTL/CMOS logic for use in a microprocessor controlled system. The Fault Output is active low when one or more of the following conditions occur: 1) Invalid Sensor Input code 2) Output Enable at logic [0] 3) Current Sense Input greater than 100 mV 4) Undervoltage Lockout, activation of one or more of the comparators 5) Thermal Shutdown, maximum junction temperature being exceeded This unique output can also be used to distinguish between motor start–up or sustained operation in an overloaded condition. With the addition of an RC network between the Fault Output and the enable input, it is possible to create a time–delayed latched shutdown for overcurrent. The added circuitry shown in the Figure makes easy starting of motor systems which have high inertial loads by providing additional starting torque, while still preserving overcurrent protection. This task is accomplished by setting the current limit to a higher than nominal value for a predetermined time. During an excessively long overcurrent condition, capacitor CDLY will charge, causing the enable input to cross its threshold to a low state. A latch is then formed by the positive feedback loop from the Fault Output to the Output Enable. Once set, by the Current Sense Input, it can only be reset by shorting CDLY or cycling the power supplies. Drive Outputs The three top drive outputs (Pins 1, 2, 24) are open collector NPN transistors capable of sinking 50mA with a minimum breakdown of 30 V. Interfacing into higher voltage applications is easily accomplished with the circuits shown in two Figures below. The three totem pole bottom drive outputs (Pins 19, 20, 21) are particularly suited for direct drive of N–Channel MOSFETs or NPN bipolar transistors. Each output is capable of sourcing and sinking up to 100mA. Power for the bottom drives is supplied from VC (Pin 18). This separate supply input allows the designer added flexibility in tailoring the drive voltage, independent of VCC. A zener clamp should be connected to this input when driving power MOSFETs in systems where VCC is greater than 20 V so as to prevent rupture of the MOSFET gates. The control circuitry ground (Pin 16) and current sense inverting input (Pin 15) must return on separate paths to the central input source ground. Thermal Shutdown Internal thermal shutdown circuitry is provided to protect the IC in the event the maximum junction temperature is exceeded. When activated, typically at 170°C, the IC acts as though the Output Enable was grounded. Timed Delayed Latched Over Current Shutdown 10/28 High Voltage Interface with NPN Power Transistors 2007-3-16 BRUSHLESS DC MOTOR CONTROLLER FSP33035 High Voltage Interface with N-Channel Power MOSFETS Current Waveform Spike Suppression MOSFET Drive Precautions Bipolar Transistor Drive 11/28 2007-3-16 BRUSHLESS DC MOTOR CONTROLLER FSP33035 High Voltage Boost Supply Current Sensing Power MOSFETs Differential Input Speed Controller Controlled Acceleration/Deceleration 12/28 2007-3-16 BRUSHLESS DC MOTOR CONTROLLER FSP33035 Digital Speed Controller Closed Loop Speed Control Closed Loop Temperature Control 13/28 2007-3-16 BRUSHLESS DC MOTOR CONTROLLER FSP33035 APPLICATION Three Phase Motor Commutation The three phase application shown in Figure below is a full–featured open loop motor controller with full wave, six step drive. The upper power switch transistors are Darlingtons while the lower devices are power MOSFETs. Each of these devices contains an internal parasitic catch diode that is used to return the stator inductive energy back to the power supply. The outputs are capable of driving a delta or wye connected stator, and a grounded neutral wye if split supplies are used. At any given rotor position, only one top and one bottom power switch (of different totem poles) is enabled. This configuration switches both ends of the stator winding from supply to ground which causes the current flow to be bidirectional or full wave. A leading edge spike is usually present on the current waveform and can cause a current–limit instability. The spike can be eliminated by adding an RC filter in series with the Current Sense Input. Using a low inductance type resistor for RS will also aid in spike reduction. Care must be taken in the selection of the bottom power switch transistors so that the current during braking does not exceed the device rating. During braking, the peak current generated is limited only by the series resistance of the conducting bottom switch and winding. If the motor is running at maximum speed with no load, the generated back EMF can be as high as the supply voltage, and at the onset of braking, the peak current may approach twice the motor stall current. The next figure shows the commutation waveforms over two electrical cycles. The first cycle (0° to 360°) depicts motor operation at full speed while the second cycle (360° to 720°) shows a reduced speed with about 50% pulse width modulation. The current waveforms reflect a constant torque load and are shown synchronous to the commutation frequency for clarity. Three Phase, Six Step, Full Wave Motor Controller 14/28 2007-3-16 BRUSHLESS DC MOTOR CONTROLLER FSP33035 Three Phase, Six Step, Full Wave Commutation Waveforms 15/28 2007-3-16 BRUSHLESS DC MOTOR CONTROLLER FSP33035 The figure below shows a three phase, three step, half wave motor controller. This configuration is ideally suited for automotive and other low voltage applications since there is only one power switch voltage drop in series with a given stator winding. Current flow is unidirectional or half wave because only one end of each winding is switched. Continuous braking with the typical half wave arrangement presents a motor overheating problem since stator current is limited only by the winding resistance. This is due to the lack of upper power switch transistors, as in the full wave circuit, used to disconnect the windings from the supply voltage VM. A unique solution is to provide braking until the motor stops and then turn off the bottom drives. This can be accomplished by using the Fault Output in conjunction with the Output Enable as an over current timer. Components RDLY and CDLY are selected to give the motor sufficient time to stop before latching the Output Enable and the top drive AND gates low. When enabling the motor, the brake switch is closed and the PNP transistor (along with resistors R1 and RDLY ) are used to reset the latch by discharging CDLY. The stator flyback voltage is clamped by a single zener and three diodes. Three Phase, Three Step, Half Wave Motor Controller 16/28 2007-3-16 BRUSHLESS DC MOTOR CONTROLLER FSP33035 Three Phase Closed Loop Controller The FSP33035, by itself, is only capable of open loop motor speed control. For closed loop motor speed control, the FSP33035 requires an input voltage proportional to the motor speed. Traditionally, this has been accomplished by means of a tachometer to generate the motor speed feedback voltage. Figure below shows an application whereby an MC33039, powered from the 6.25 V reference (Pin 8) of the FSP33035, is used to generate the required feedback voltage without the need of a costly tachometer. The same Hall sensor signals used by the FSP33035 for rotor position decoding are utilized by the MC33039. Every positive or negative going transition of the Hall sensor signals on any of the sensor lines causes the MC33039 to produce an output pulse of defined amplitude and time duration, as determined by the external resistor R1 and capacitor C1. The output train of pulses at Pin 5 of the MC33039 are integrated by the error amplifier of the FSP33035 configured as an integrator to produce a DC voltage level which is proportional to the motor speed. This speed proportional voltage establishes the PWM reference level at Pin 13 of the FSP33035 motor controller and closes the feedback loop. The FSP33035 outputs drive a TMOS power MOSFET 3–phase bridge. High currents can be expected during conditions of start–up, breaking, and change of direction of the motor. The system shown in the below Figure is designed for a motor having 120/240 degrees Hall sensor electrical phasing. The system can easily be modified to accommodate 60/300 degree Hall sensor electrical phasing by removing the jumper (J2) at Pin 22 of the FSP33035. Closed Loop Brushless DC Motor Control Using the FSP33035 and MC33039 17/28 2007-3-16 BRUSHLESS DC MOTOR CONTROLLER FSP33035 Sensor Phasing Comparison There are four conventions used to establish the relative phasing of the sensor signals in three phase motors. With six step drive, an input signal change must occur every 60 electrical degrees; however, the relative signal phasing is dependent upon the mechanical sensor placement. A comparison of the conventions in electrical degrees is shown in the figure in page 17. From the sensor phasing table, note that the order of input codes for 60° phasing is the reverse of 300°. This means the FSP33035, when configured for 60° sensor electrical phasing, will operate a motor with either 60° or 300° sensor electrical phasing, but resulting in opposite directions of rotation. The same is true for the part when it is configured for 120° sensor electrical phasing; the motor will operate equally, but will result in opposite directions of rotation for 120° for 240° conventions. Sensor Phasing Comparison Sensor Phasing Table In this data sheet, the rotor position is always given in electrical degrees since the mechanical position is a function of the number of rotating magnetic poles. The relationship between the electrical and mechanical position is: An increase in the number of magnetic poles causes more electrical revolutions for a given mechanical revolution. General purpose three phase motors typically contain a four pole rotor which yields two electrical revolutions for one mechanical. Two and Four Phase Motor Commutation The FSP33035 is also capable of providing a four step output that can be used to drive two or four phase motors. The truth table in page 19 shows that by connecting sensor inputs SB and SC together, it is possible to truncate the number of drive output states from six to four. The output power switches are connected to BT, CT, BB, and CB. The figure in page 20 shows a four phase, four step, full wave motor control application. Power switch transistors Q1 through Q8 are Darlington type, each with an internal parasitic catch diode. With four step drive, only two rotor position sensors spaced at 90 electrical degrees are required. The commutation waveforms are shown in the figure in page 21. Figure in page 22 shows a four phase, four step, half wave motor controller. It has the same features as the circuit in the figure in page 16, except for the deletion of speed control and braking. Two and Four Phase, Four Step, Commutation Truth Table 18/28 2007-3-16 BRUSHLESS DC MOTOR CONTROLLER FSP33035 Four Phase, Four Step, Full Wave Motor Controller 19/28 2007-3-16 BRUSHLESS DC MOTOR CONTROLLER FSP33035 Four Phase, Four Step, Full Wave Motor Controller 20/28 2007-3-16 BRUSHLESS DC MOTOR CONTROLLER FSP33035 Four Phase, Four Step, Half Wave Motor Controller 21/28 2007-3-16 BRUSHLESS DC MOTOR CONTROLLER FSP33035 H –Bridge Brush–Type Controller 22/28 2007-3-16 BRUSHLESS DC MOTOR CONTROLLER FSP33035 Brush Motor Control Though the FSP33035 was designed to control brushless DC motors, it may also be used to control DC brush type motors. Figure in page 22 shows an application of the FSP33035 driving a MOSFET H–bridge affording minimal parts count to operate a brush–type motor. Key to the operation is the input sensor code [100] which produces a top–left (Q1) and a bottom–right (Q3) drive when the controller’s forward/reverse pin is at logic [1]; top–right (Q4), bottom–left (Q2) drive is realized when the Forward/Reverse pin is at logic [0]. This code supports the requirements necessary for H–bridge drive accomplishing both direction and speed control. The controller functions in a normal manner with a pulse width modulated frequency of approximately 25 kHz. Motor speed is controlled by adjusting the voltage presented to the noninverting input of the error amplifier establishing the PWM’s slice or reference level. Cycle–by–cycle current limiting of the motor current is accomplished by sensing the voltage (100 mV) across the RS resistor to ground of the H–bridge motor current. The over current sense circuit makes it possible to reverse the direction of the motor, using the normal forward/reverse switch, on the fly and not have to completely stop before reversing. LAYOUT CONSIDERSIONS Do not attempt to construct any of the brushless motor control circuits on wire–wrap or plug–in prototype boards. High frequency printed circuit layout techniques are imperative to prevent pulse jitter. This is usually caused by excessive noise pick–up imposed on the current sense or error amp inputs. The printed circuit layout should contain a ground plane with low current signal and high drive and output buffer grounds returning on separate paths back to the power supply input filter capacitor VM. Ceramic bypass capacitors (0.1 µF) connected close to the integrated circuit at VCC , VC , Vref and the error amp noninverting input may be required depending upon circuit layout. This provides a low impedance path for filtering any high frequency noise. All high current loops should be kept as short as possible using heavy copper runs to minimize radiated EMI. TYPICAL PERFORMANCE CHARACTERISTICS 23/28 2007-3-16 BRUSHLESS DC MOTOR CONTROLLER FSP33035 TYPICAL PERFORMANCE CHARACTERISTICS(CONTINUED) 24/28 2007-3-16 BRUSHLESS DC MOTOR CONTROLLER FSP33035 TYPICAL PERFORMANCE CHARACTERISTICS(CONTINUED) 25/28 2007-3-16 BRUSHLESS DC MOTOR CONTROLLER FSP33035 TYPICAL PERFORMANCE CHARACTERISTICS(CONTINUED) ORDERING INFORMATION FSP33035XXX Package: S: SOP24L N: PDIP24L Packing: Blank: Tube or Bulk Temperature Grade: D: -40~85℃ MARKING INFORMATION FSP33035 YYWWXX Logo Part number Internal code Date code: YY: Year (01=2001) WW: Nth week (01~52) 26/28 2007-3-16 BRUSHLESS DC MOTOR CONTROLLER FSP33035 PACKAGE INFORMATION (1) SOP24L Symbol A A1 b C D E e H h L Y θ Dimensions In Millimeters Nom. Max. 2.54 2.64 0.20 0.30 0.406 0.48 0.254 0.31 15.29 15.60 7.50 7.60 1.27BSC 10.00 10.31 10.65 0.25 0.66 0.75 0.51 0.76 1.02 0.075 0º 8º Min. 2.36 0.10 0.35 0.23 15.20 7.40 Dimensions In Inches Nom. 0.102 0.008 0.016 0.010 0.612 0.300 0.051BSC 0.400 0.412 0.010 0.026 0.020 0.030 Min. 0.094 0.004 0.014 0.009 0.600 0.296 0º Max. 0.106 0.012 0.019 0.012 0.624 0.304 0.426 0.030 0.041 0.003 8º 27/28 2007-3-16 BRUSHLESS DC MOTOR CONTROLLER FSP33035 (2) PDIP24L Symbol A A1 A2 B B1 C D E E1 e L E2 Dimensions In Millimeters Min. Max. 3.710 4.310 0.510 3.200 3.600 0.360 0.560 1.524(Typ.) 0.204 0.360 29.250 29.850 6.200 6.600 7.620(Typ.) 2.540(Typ.) 3.000 3.600 8.200 9.400 Dimensions In Inches Min. Max. 0.148 0.172 0.020 0.128 0.144 0.014 0.022 0.061(Typ.) 0.008 0.014 1.170 1.194 0.248 0.264 0.305(Typ.) 0.102(Typ.) 0.120 0.144 0.328 0.376 28/28 2007-3-16