GS9005BCTJE3

GENLINX™ GS9005B Serial Digital Receiver DATA SHEET FEATURES DEVICE DESCRIPTION • The GS9005B is a monolithic IC designed to receive SMPTE 259M serial digital video signals. This device performs the functions of automatic cable equalization and data and clock recovery. It interfaces directly with the GENLINX™ GS9000B or GS9000S decoder, and GS9010A Automatic Tuning Subsystem. • • • • • • automatic cable equalization (typically 300m of high quality cable at 270Mb/s) fully compatible with SMPTE 259M and operational to 400 Mb/s adjustment free receiver when used with the GS9000B or GS9000S decoder and GS9010A Automatic Tuning Sub-system signal strength indicator selectable cable or direct digital inputs 28 pin PLCC packaging Pb-free and Green D E D S N E GN M SI M E O D C E R EW T N O N OR F The VCO centre frequencies are controlled by external resistors which can be selected by applying a two bit binary code to the Standards Select input pins. An additional feature is the Signal Strength Indicator output which provides a 0.5V to 0V analog output relative to VCC indicating the amount of equalization being applied to the signal. APPLICATIONS • 4ƒSC, 4:2:2 and 360 Mb/s serial digital interfaces The GS9005B is packaged in a 28 pin PLCC operating from a single +5 or -5 volt supply. ORDERING INFORMATION Part Number Package Temperature Pb-Free and Green GS9005BCPJ 28 Pin PLCC 0°C to 70°C No GS9005BCTJ 28 Pin PLCC Tape 0°C to 70°C No GS9005BCPJE3 28 Pin PLCC 0°C to 70°C Yes SPECIAL NOTE: RVCO1 and RVCO2 are functional over a reduced temperature range of TA=0° C to 50° C. RVCO0 and RVCO3 are functional over the full temperature range of TA=0° C to 70° C. This limitation does not affect operation with the GS9010A ATS. GS9005B 28 SIGNAL STRENGTH INDICATOR FILTER CONTROL 16 PEAK DETECTOR VOLTAGE VARIABLE FILTER CABLE 8,9 IN AGC 2 CAPACITOR OUTPUT 'EYE' MONITOR LOGIC COMPARATOR DC RESTORER Σ ANALOG DIGITAL SELECT EQUALIZER DIGITAL 5,6 IN 1 24 DATA LATCH A/D 25 SERIAL DATA SERIAL DATA 22 23 SERIAL CLOCK SERIAL CLOCK PHASE COMPARATOR CARRIER DETECT 19 CARRIER DETECT 10 ÷2 CHARGE PUMP LOOP FILTER 12 VCO STANDARD SELECT 20 21 ƒ/2 ENABLE SS0 SS1 PLL 13 14 15 17 Revision Date: November 2004 FUNCTIONAL BLOCK DIAGRAM Document No. 32466 - 1 GENNUM CORPORATION P.O. Box 489, Stn A, Burlington, Ontario, Canada L7R 3Y3 tel. (905) 632-2996 fax: (905) 632-5946 Gennum Japan: Shinjuku Green Tower Building 27F 6-14-1, Nishi Shinjuku Shinjuku-ku, Tokyo 160-0023 Japan Tel: +81 (03) 3349-5501 Fax: +81 (03) 3349-5505 ABSOLUTE MAXIMUM RATINGS PARAMETER VALUE / UNITS Supply Voltage CAUTION ELECTROSTATIC 5.5 V Input Voltage Range (any input) SENSITIVE DEVICES VCC+0.5 to VEE-0.5 V DC Input Current (any one input) DO NOT OPEN PACKAGES OR HANDLE EXCEPT AT A STATIC-FREE WORKSTATION 5 mA Power Dissipation 750 mW Operating Temperature Range Storage Temperature Range Lead Temperature (soldering, 10 seconds) 0°C TA 70°C -65°C TS 150°C 260°C D E D S N E GN M SI M E O D C E R EW T N O N OR F GS9005B RECEIVER DC ELECTRICAL CHARACTERISTICS VS = 5V, T A = 0°C to 70°C, R L = 100Ω to (VCC - 2V) unless otherwise shown. PARAMETER SYMBOL CONDITIONS Operating Range MIN TYP MAX UNITS 4.75 5.0 5.25 V NOTES Supply Voltage VS Power Consumption PD - 500 700 mW Supply Current (Total) IS - 122 160 mA Serial Data & - High V OH TA = 25°C -1.025 - -0.88 V with respect to V CC Clock Output - Low VOL TA = 25°C -1.9 - -1.6 V with respect to V CC see Figure13 Logic Inputs - High VIH MIN +2.0 - - V with respect to V EE (1, 10, 20, 21) - Low V IL MAX - - +0.8 V with respect to V EE - 0.2 0.4 V with respect to VEE Open 4.0 5.0 - V Collector - Active High -0.6 - 0 V with respect to VCC 200 - 2000 mVp-p Differential Drive TYP MAX UNITS NOTES Carrier Detect VCDL Output Voltage VCDH Signal Strength Indicator Output Direct Digital Input VSS RL = 10 kΩ to V CC See Note 2 VDDI Levels (5, 6) GS9005B RECEIVER AC ELECTRICAL CHARACTERISTICS VS = 5V, TA = 0°C to 70°C, RL = 100Ω to (V CC - 2V) unless otherwise shown. PARAMETER SYMBOL CONDITION MIN Serial Data Bit Rate BRSDO TA = 25°C 100 - 400 Mb/s Serial Clock Frequency ƒ SLK TA = 25°C 100 - 400 MHz see Figure11 Output Signal Swing VO TA = 25°C 700 800 900 mV p-p see Figure12 Serial Data to Serial Clock Synchronization td See Waveforms - -500 - ps Lock Times tLOCK See Note 1 - - 10 µs Equalizer Gain AVEQ TA = 25°C 30 36 - dB Jitter tJ TA = 25°C - ±100 - ps p-p Data lags Clock at 135 MHz see Figure15 0 metres, 270 Mb/s Input Resistance (SDI/SDI) R IN TA = 25½C 3k 5k - Ω Input Capacitance (SDI/SDI) C IN T A = 25½C - 1.8 - pF Output Eye Monitor VOEM RL = 50Ω to V CC 40 - mVp-p - see Figure14 see Figure14 NOTES: 1. Switching between two sources of the same data rate. 2. With weaker signals VSS approaches V CC . 2 of 13 32466 - 1 GS9005B Re - clocking Receiver - Detailed Device Description The GS9005B Reclocking Receiver is a bipolar integrated circuit containing a built-in cable equalizer and circuitry necessary to re-clock and regenerate the NRZI serial data stream. Packaged in a 28 pin PLCC, the receiver operates from a single five volt supply at data rates in excess of 400 Mb/s. Typical power consumption is 500 mW. Typical output jitter is ±100 ps at 270 Mb/s. Serial Digital signals are applied to either a built-in analog cable equalizer via the SDI and SDI inputs (pins 8,9) or via the direct digital inputs DDI and DDI (pins 5,6). A logical HIGH applied to the Analog/Digital Select input (1) routes the equalized signal while a logic LOW routes the direct digital signal to the reclocker. Phase Locked Loop The phase comparator itself compares the position of transitions in the incoming signal with the phase of the local oscillator (VCO). The error-correcting output signals are fed to the charge pump in the form of short pulses. The charge pump converts these pulses into a “charge packet” which is accurately proportional to the system phase error. D E D S N E GN M SI M E O D C E R EW T N O N OR F Cable Equalizer The Serial Digital signal is connected to the input either differentially or single ended with the unused input being decoupled. The equalized signal is generated by passing the cable signal through a voltage variable filter having a characteristic which closely matches the inverse cable loss characteristic. Additionally, the variation of the filter characteristic with control voltage is designed to imitate the variation of the inverse cable loss characteristic as the cable length is varied. The amplitude of the equalized signal is monitored by a peak detector circuit which produces an output current with a polarity corresponding to the difference between the desired peak signal level and the actual peak signal level. This output is integrated by an external AGC filter capacitor (AGC CAP pin 2), providing a steady control voltage for the voltage variable filter. A separate signal strength indicator output, (SSI pin 28), proportional to the amount of AGC is also provided. As the filter characteristic is varied automatically by the application of negative feedback, the amplitude of the equalized signal is kept at a constant level which is representative of the original amplitude at the transmitter. The equalized signal is then DC restored, effectively restoring the logic threshold of the equalized signal to its correct level irrespective of shifts due to AC coupling. As the final stage of signal conditioning, a comparator converts the analog output of the DC restorer to a regenerated digital output signal. An OUTPUT 'EYE' MONITOR (pin 16), allows verification of signal integrity after equalization but before reslicing. Analog/Digital Select A 2:1 multiplexer selects either the equalized (analog) signal or a differential ECL data (digital) signal as input to the reclocker PLL. The charge packet is then integrated by the second-order loop filter to produce a control voltage for the VCO. During periods when there are no transitions in the signal, the loop filter voltage is required to hold precisely at its last value so that the VCO does not drift significantly between corrections. Commutating diodes in the charge pump keep the output leakage current extremely low, minimizing VCO frequency drift. The VCO is implemented using a current-controlled multivibrator, designed to deliver good stability, low phase noise and wide operating frequency capability. The frequency range is design-limited to ±10% about the oscillator centre frequency. VCO Centre Frequency Selection The centre frequency of theVCO is set by one of four external current reference resistors (RVCO0-RVCO3) connected to pins 13,14,15 or 17. These are selected by two logic inputs SS0 and SS1 (pins 20, 21) through a 2:4 decoder according to the following truth table. SS1 SS0 Resistor Selected 0 0 RVCO0 (13) 0 1 RVCO1 (14) 1 0 RVCO2 (15) 1 1 RVCO3 (17) As an alternative, the GS9010A Automatic Tuning Subsystem and the GS9000B or GS9000S Decoder may be used in conjunction with the GS9005B to obtain adjustment free and automatic standard select operation (see Figure 20). With the VCO operating at twice the clock frequency, a clock phase which is centred on the eye of the locked signal is used to latch the incoming data, thus maximising immunity to jitter-induced errors. The alternate phase is used to latch the output re-clocked data SDO and SDO (pins 25, 24). The true and inverse clock signals themselves are available from the SCO and SCO pins 23 and 22. 3 of 13 32466 - 1 AGC VCC1 VEE1 CAP 4 SERIAL DATA OUT (SD0) SERIAL CLOCK OUT (SCK) A/D SSI VEE2 28 27 VCC4 tD tD 50% 3 2 26 DDI 5 25 SD0 DDI 6 24 SD0 VCC2 7 23 SC0 SDI 8 22 SC0 SDI 9 21 SS1 ƒ/2 EN 10 20 SS0 VEE3 11 19 CD 50% GS9005B TOP VIEW D E D S N E GN M SI M E O D C E R EW T N O N OR F Fig.1 Waveforms 12 13 14 15 16 17 18 LOOP RVCO0 RVCO1 RVCO2 OEM RVCO3 VCC3 FILT Fig. 2 GS9005B Pin Connections GS9005B PIN DESCRIPTIONS PIN NO. 1 SYMBOL A/D TYPE Input DESCRIPTION Analog/Digital Select. TTL compatible input used to select the input signal source. A logic HIGH routes the Equalizer inputs (pins 8 and 9) to the PLL and a logic LOW routes the Direct Digital inputs (pins 5 and 6) to the PLL. 2 3 4 5,6 AGC CAP Input AGC Capacitor. Connection for the AGC capacitor. VEE1 Power Supply. Most negative power supply connection. (Equalizer) VCC1 Power Supply. Most positive power supply connection. (Equalizer) DDI/DDI Input Direct Data Inputs (true and inverse). Pseudo-ECL, differential serial data inputs. These are selected when the A/D input (pin 1) is at logic LOW and are self biased to 1.2 volts below VCC. They may be directly driven from true ECL drivers when VEE = -5V and VCC= 0 V. 7 8,9 Power Supply. Most positive power supply connection. ( Phase detector, A/D select, carrier detect). VCC2 SDI/SDI Input Serial Data Inputs (true and inverse). Differential analog serial data inputs. Inputs must be AC coupled and may be driven single ended. These inputs are selected when the A/D input (pin 1) is logic HIGH. 10 11 12 13 ƒ/2 EN Input ƒ/2 Enable-TTL compatible input used to enable the divide by 2 function. VEE3 Power Supply. Most negative power supply connection. (VCO, Mux, Standard Select) LOOP FILT Loop Filter. Node for connecting the loop filter components. RVCO0 Input VCO Resistor 0. Analog current input used to set the centre frequency of the VCO when the two Standard Select bits (pins 20 and 21) are set to logic 0,0. A resistor is connected from this pin to VEE. 14 RVCO1 Input VCO Resistor 1. Analog current input used to set the centre frequency of the VCO when Standard Select bit 0 (pin 20) is set HIGH and bit 1 (pin 21) is set LOW. A resistor is connected from this pin to VEE. 15 RVCO2 Input VCO Resistor 2. Analog current input used to set the centre frequency of the VCO when Standard Select bit 0 (pin 20) is set LOW and bit 1 (pin 21) is set HIGH. A resistor is connected from this pin to VEE. 16 OEM Output Output Eye Monitor Analog voltage representing the serial bit stream after equalization but before reslicing. 17 RVCO3 Input VCO Resistor 3. Analog current input used to set the centre frequency of the VCO when the two Standard Select bits (pins 20 and 21) are set HIGH. A resistor is connected from this pin to VEE. 4 of 13 32466 - 1 GS9005B PIN DESCRIPTIONS cont. PIN NO SYMBOL 18 VCC3 19 CD TYPE DESCRIPTION Power Supply. Most positive power supply connection. (VCO, MUX, standards select). Carrier Detect. Open collector output which goes HIGH when a signal is present at either the Serial Output Data inputs or the Direct Digital inputs. This output is used in conjunction with the GS9000B or GS9000S in the Automatic Standards Select Mode to disable the 2 bit standard select counter. This pin should see a low impedance (e.g. 1nF to AC Gnd) 20,21 Standard Select Inputs. TTL inputs to the 2:4 multiplexer used to select one of four VCO centre SS0, SS1 Inputs D E D S N E GN M SI M E O D C E R EW T N O N OR F frequency setting resistors (RVCO0 - RVCO3). When both SS0 and SS1 are LOW, RVCO0 is selected. When SS0 is HIGH and SS1 is LOW, RVCO1 is selected. When SS0 is LOW and SS1 is HIGH, RVCO2 is selected and when both SS0 and SS1 are HIGH, RVCO3 is selected. These pins should see a low impedance (e.g. 1nF to AC Gnd) 22,23 SCO/SCO Outputs Serial Clock Outputs (inverse and true). Pseudo-ECL differential outputs of the extracted serial clock. These outputs require 390 Ω pull-down resistors to VEE. 24,25 SDO/SDO Outputs Serial Data Outputs (inverse and true). Pseudo-ECL differential outputs of the regenerated serial data. These outputs require 390 Ω pull-down resistors to VEE. 26 27 28 VCC4 Power Supply. Most positive power supply connection. (ECL outputs) VEE2 Power Supply. Most negative power supply connection. (Phase detector, A/D select, Carrier detect) SSI Signal Strength Indicator. Analog output which indicates the amount of AGC action. This output indirectly indicates the amount of equalization and thus cable length. INPUT / OUTPUT CIRCUITS VCC + - VCC 1.2V VCC 16µA 2k 2k 1k 1k VCC A/D Pin 1 DDI Pin 5 DDI Pin 6 50µA 380µA + 1.6V - Fig. 3 Pins 1, 5 and 6 5 of 13 32466 - 1 INPUT / OUTPUT CIRCUITS cont. I VCO (1.9 - 2.4V) LOOP FILTER (1.8 - 2.7V) D E D S N E GN M SI M E O D C E R EW T N O N OR F Pin 13 RVCO 0 Pin 14 RVCO 1 Pin 15 RVCO 2 Pin 17 RVCO 3 400 400 400 400 Fig. 4 Pins 13, 14, 15 and 17 VCC VCC4 200 200 10k 10k SDO or SCO Pin 25, 24 SDO or SCO Pin 23, 22 VCC VCC 3k 800 Fig. 5 Pins 25, 24, 23 and 22 6 of 13 32466 - 1 INPUT / OUTPUT CIRCUITS cont. VCC VCC 500 SSI Pin 28 AGC CAP Pin 2 VCC VCC 1.5k 5k VCC + - 2k 2V LOOP FILTER Pin 12 D E D S N E GN M SI M E O D C E R EW T N O N OR F 1k + - 0.4V 5k 5k 620 SDI Pin 8 SDI Pin 9 920µA 920µA Fig. 7 Pin 12 Fig. 6 Pins 28, 2, 8 and 9 VCC VCC 10k CD Pin 19 OEM Pin 16 200 5mA 5mA Fig. 9 Pin 19 Fig. 8 Pin 16 VCC VCC VCC 40µA 40µA VCC VCC 18µA SS1 Pin 21 ƒ/2 EN Pin 10 55µA 480µA + - 1.6V SSO Pin 20 Fig. 10 Pins 20, 21 and 10 7 of 13 32466 - 1 TYPICAL PERFORMANCE CURVES (VS = 5V, TA = 25°C) 900 500 850 400 SERIAL OUTPUTS (mV) FREQUENCY (MHz) 450 350 300 250 VS = 5.25V 800 VS = 5.00V 750 D E D S N E GN M SI M E O D C E R EW T N O N OR F ƒ/2 OFF 200 ƒ/2 ON 150 700 VS = 4.75V 650 100 50 1 2 3 4 5 6 7 8 9 600 10 0 10 20 30 40 50 FREQUENCY SETTING RESISTANCE (ký) TEMPERATURE (°C) Fig. 11 Clock Frequency Fig. 12 Serial Outputs 60 70 140 135 VS = 5.25V CURRENT (mA) 130 125 VS = 5.00V 120 VS = 4.75V 115 110 105 100 0 10 20 30 40 50 60 70 TEMPERATURE (°C) Fig. 13 Supply Current 8 of 13 32466 - 1 +5V +5V ANALOG 10µ + DIGITAL SSI 0.1µ +5V 0.1µ 390 VCC4 SSI VEE2 1 28 27 26 A/D 2 AGC 3 VEE1 ECL DATA INPUTS 5 DDI 6 DDI 7 VCC2 8 SDI VCC1 4 0.1µ SDO 390 25 100 DATA D E D S N E GN M SI M E O D C E R EW T N O N OR F 0.1µ INPUT 75 47p SDO SCO GS9005B SCO SS1 9 SDI VCC3 RVCO3 EYEOUT RVCO2 RVCO1 RVCO0 75 11 VEE3 LOOP 47p SS0 10 ƒ/2 CD 12 13 14 15 16 17 18 22n 24 100 DATA 23 100 CLOCK 22 100 CLOCK 21 +5V 390 20 390 19 10k +5V 113 CARRIER DETECT OUTPUT 0.1µ 5.6p 910 +5V 10n ÷2 ÷1 See Figure 18 STAR ROUTED LOOP VOLTAGE TEST POINT All resistors in ohms, all capacitors in microfarads, all inductors in henries unless otherwise stated. Fig.14 GS9005B Typical Test Circuit Using +5V Supply TEST SETUP Figure 14 shows a typical circuit for the GS9005B using a +5 volt supply. The four 0.1µF decoupling capacitors must be placed as close as possible to the corresponding VCC pins. When the Direct Digital Inputs are not used, one of these inputs should be connected to VCC to avoid picking up noise and unwanted signals. The loop voltage can be conveniently measured across the 10nF capacitor in the loop filter. Tuning procedures are described in the Temperature Compensation Section (page 11). The fixed value frequency setting resistors should be placed close to the corresponding pins on the GS9005B. The Carrier Detect is an open-collector active high output requiring a pull-up resistor of approximately 10 kΩ. The layout of the loop filter and RVCO components requires careful attention. This has been detailed in an application note entitled "Optimizing Circuit and Layout Design of the GS9005A/15A", Document No. 521 - 32 - 00. The SS0, SS1, CD pins should see a low AC impedance. This is particularly important when driving the SS0, SS1 pins with external logic. The use of 1 nF decoupling capacitors at these pins ensures this. Figure 15 shows the GS9005B connections when using a -5 volt supply. 9 of 13 32466 - 1 ANALOG + DIGITAL 10µ SSI -5V 0.1µ -5V 0.1µ 0.1µ -5V 4 3 2 390 1 28 27 26 -5V 0.1µ VCC4 SSI A/D AGC VEE1 VEE2 SCO GS9005B 8 SDI SCO SS1 9 SDI VCC3 11 VEE3 SS0 RVCO3 10 ƒ/2 EYEOUT 75 VCC2 RVCO2 47p SDO RVCO1 47p 390 SDO DDI RVCO0 -5V 75 7 LOOP INPUT 6 DDI VCC1 D E D S N E GN M SI M E O D C E R EW T N O N OR F ECL DATA INPUTS 5 CD 25 100 DATA 24 100 DATA 23 100 CLOCK 22 100 CLOCK 21 390 20 390 19 10k 12 13 14 15 16 17 18 113 22n CARRIER DETECT OUTPUT 0.1µ 5.6p 910 -5V 10n ÷2 ÷1 See Figure 18 -5V STAR -5V ROUTED LOOP VOLTAGE -5V All resistors in ohms, all capacitors in microfarads, all inductors in henries unless otherwise stated. Fig. 15 GS9005B Typical Test Circuit Using -5V Supply VCO Frequency Setting Resistors There are two modes of VCO operation available in the GS9005B. When the ƒ/2 ENABLE (pin 10) is LOW, any of the four VCO frequency setting resistors, RVCO0 through RVCO3 (pins 13, 14, 15 and 17) may be used for any data rate from 100 Mb/s to over 400 Mb/s. For example, for 143 Mb/s data rate, the value of the total RVCO resistance is approximately 6k8 and for 270 Mb/s operation, the value is approximately 3k5. The 5k potentiometers will then tune the desired data rate near their mid-points. Jitter performance at the lower data rates (143, 177 Mb/s) is improved by operating the VCO at twice the normal frequency. This is accomplished by enabling the ƒ/2 function which activates an additional divide by two block in the PLL section of the GS9005B. The selection is dependent upon the level of the STANDARD SELECT BIT, SS1 (pin 21). When SS1 is LOW, RVCO0 and RVCO1 (pins 13 and 14) are used for the higher data rates. When SS1 is HIGH, the VCO frequency is now twice the bit rate and its frequency is set by RVCO2 and RVCO3 (pins 15 and 17). For 143 Mb/s and 270 Mb/s operation, (the VCO is at 286 MHz and 270 MHz respectively) the total resistance required is approximately the same for both data rates. This also applies for 177 Mb/s and 360 Mb/s operation (the VCO is tuned to 354 MHz and 360 MHz respectively). This means that one potentiometer may be used for each frequency pair with only a small variation of the fixed resistor value. This halves the number of adjustments required. When the ƒ/2 ENABLE is HIGH two of the RVCO pins are assigned to data rates below 200 Mb/s and two are assigned to data rates over 200 Mb/s. 10 of 10 32466 - 1 Temperature Compensation Figure 16 shows the connections for the frequency setting resistors for the various data rates. The compensation shown for 360 Mb/s and 177 Mb/s with Divide by 2 ON, is useful to a maximum ambient temperature of 50°C. If the Divide by 2 function is not enabled by the ƒ/2 ENABLE input, no compensation is needed for the 143 Mb/s and 177 Mb/s data rates. The resistor connections are shown in Figure 17. In both cases, the 0.1 µF capacitor that bypasses the potentiometer should be star routed to VEE 3. 1k 10k 0.1µF VEE Divide by 2 is OFF 143Mb/s and 177 Mb/s using any RVCO0 pins D E D S N E GN M SI M E O D C E R EW T N O N OR F 5.6k 4.3k 1.3k 1N914 5k 0.1µF Fig. 17 1.3k 1N914 5k Non - Temperature Compensated Resistor Values for 143 Mb/s and 177 Mb/s 0.1µF Loop Bandwidth VEE The loop bandwidth is dependant upon the internal PLL gain constants along with the loop filter components connected to pin 12. In addition, the impedance seen by the RVCO pin also influences the loop characteristics such that as the impedance drops, the loop gain increases. VEE Divide by 2 is OFF Divide by 2 is ON 270 Mb/s using RVCO0 or RVCO1 143 Mb/s using RVCO2 or RVCO3 1k Applications Circuit 1k 1k 0.1µF 0.1µF Figure 18 shows an application of the GS9005B in an adjustment free, multi-standard serial to parallel convertor. This circuit uses the GS9010A Automatic Tuning Subsystem IC and a GS9000B or GS9000S Decoder IC. The GS9005B may be replaced with a GS9015B Reclocker IC if cable equalization is not required. 177 Mb/s using RVCO2 or RVCO3 The GS9010A ATS eliminates the need to manually set or externally temperature compensate the Receiver or Reclocker VCO. The GS9010A can also determine whether the incoming data stream is 4ƒsc NTSC,4ƒsc PAL or component 4:2:2. 1k 1N914 1N914 VEE VEE Divide by 2 is OFF 360 Mb/s using RVCO0 or RVCO1 Divide by 2 is ON Fig. 16 Frequency Setting Resistor Values & Temperature Compensation Temperature Compensation Procedure In order to correctly set the VCO frequency so that the PLL will always re-acquire lock over the full temperature range, the following procedure should be used. The circuit should be powered on for at least one minute prior to starting this procedure. Monitor the loop filter voltage at the junction of the loop filter resistor and 10 nF loop filter capacitor (LOOP FILTER TEST POINT). Using the appropriate network shown above, the VCO frequency is set by first tuning the potentiometer so that the PLL loses lock at the low end (lowest loop filter voltage). The loop filter voltage is then slowly increased by adjusting the the potentiometer to determine the error free low limit of the capture range. Error free operation is determined by using a suitable CRC or EDH measurement method to obtain a stable signal with no errors. Record the loop filter voltage at this point as VCL. Now adjust the potentiometer so that the loop filter voltage is 250 mV above VCL. The GS9010A includes a ramp generator/oscillator which repeatedly sweeps the Receiver VCO frequency over a set range until the system is correctly locked. An automatic fine tuning (AFT) loop maintains the VCO control voltage at it's centre point through continuous, long term adjustments of the VCO centre frequency. When an interruption to the incoming data stream is detected by the Receiver, the Carrier Detect goes LOW and opens the AFT loop in order to maintain the correct VCO frequency for a period of at least 2 seconds. This allows the Receiver to rapidly relock when the signal is reestablished. During normal operation, the GS9000B or GS9000S Decoder provides continuous HSYNC pulses which disable the ramp/oscillator of the GS9010A. This maintains the correct Receiver VCO frequency. 11 of 13 32466 - 1 Application Note - PCB Layout Special attention must be paid to component layout when designing high performance serial digital receivers. For background information on high speed circuit and layout design concepts, refer to Document No. 521-32-00, “Optimizing Circuit and Layout Design of the GS90005A/15A”. A recommended PCB layout can be found in the Gennum Application Note “EB9010B Deserializer Evaluation Board.” The use of a star grounding technique is required for the loop filter components of the GS9005B/15B. Controlled impedance PCB traces should be used for the differential clock and data interconnection between the GS9005B and the GS9000B or GS9000S. These differential traces must not pass over any ground plane discontinuities. A slot antenna is formed when a microstrip trace runs across a break in the ground plane. The series resistors at the parallel data output of the GS9000B or GS9000S are used to slow down the fast rise/fall time of the GS9000B or GS9000S outputs. These resistors should be placed as close as possible to the GS9000B or GS9000S output pins to minimize radiation from these pins. D E D S N E GN M SI M E O D C E R EW T N O N OR F SWF SSI VCC 0.1µ 10µ + DVCC +5V + 0.1µ DGND (1) 113 (2) 7 100 8 V SS1 21 CC SS0 20 390 9 390 10 19 CD SCI SCI SS1 910 (4) PD5 GS9000B or GS9000S PD4 SST DVCC 12 13 14 15 16 25 100 24 100 23 100 22 100 21 100 20 100 PD1 19 100 PD3 PD2 SS0 VCC 17 PARALLEL DATA BIT 8 PARALLEL DATA BIT 7 PARALLEL DATA BIT 6 PARALLEL DATA BIT 5 PARALLEL DATA BIT 4 PARALLEL DATA BIT 3 PARALLEL DATA BIT 2 PARALLEL DATA BIT 1 DVCC PARALLEL DATA BIT 0 PARALLEL CLOCK OUT 18 SYNC CORRECTION ENABLE 0.1µ 0.1µ 0.1µF 10n PD6 SDI 11 VSS 100 PD8 23 PD7 VDD 6 PARALLEL DATA BIT 9 28 27 26 PD9 100 SDI 1 PDO 24 VSS 5 2 HSYNC 100 3 PCLK VCC3 25 22 SCO RVCO3 RVCO0 VSS SSI VCC4 A/D VEE2 AGC VEE1 VCC1 SDO 12 13 14 15 16 17 18 5.6p 22n GS9005B 4 390 SCO VCC2 10 ƒ/2 11 VEE3 75 28 27 26 DDI 8 SDI 9 SDI 47p 390 SDO EYEOUT 47p 1 DDI LOOP 75 7 2 RVCO2 0.1µ 6 3 RVCO1 VCC 5 4 SYNC WARNING FLAG HSYNC OUTPUT DGND SWC DGND ECL DATA INPUT INPUT INPUT SELECTION 0.1µ SWF GND 100 DGND VCC VCC SCE 10µ VDD 10µ 100 3.3k 100 0.1µ + VDD VCC +5V 100 100 DGND DGND 1.2k DVCC VCC 1.2k (3) 0.1µ 68k 50k 22n VCC 120 STAR ROUTED DGND GS9010A 6.8µ + 1 (2) 6.8µ 2 + 3 4 3.3n 5 VCC P/N OUT IN- COMP LF 6 ƒ/2 7 VCC 8 SWF STDT 16 0.1µ 15 VCC 14 CD 13 HSYNC 12 GND 11 OSC 10 DLY 9 FVCAP VCC STANDARD TRUTH TABLE 100k 82n (2) 0.68µ All resistors in ohms, all capacitor in microfarads, all inductors in henries unless otherwise stated. VCC 0.1µ SWF 180n ƒ/2 P/N STANDARD 0 0 4:2:2 - 270 0 1 4:2:2 - 360 1 0 4ƒsc - NTSC 1 1 4ƒsc - PAL (1) Typical value for input return loss matching (2) To reduce board space, the two anti-series 6.8µF capacitors (connected across pins 2 and 3 of the GS9010A) may be replaced with a 1.0 µF non-polarized capacitor provided that: (a) the 0.68 µF capacitor connected to the OSC pin (11) of the GS9010A is replaced with a 0.33 µF capacitor and (b) the GS9005B/15B Loop Filter Capacitor is 10nF. (3) Remove this potentiometer if P/N function is not required, and ground pin 16 of the GS9010A. (4) The GS9000B will operate to a maximum frequency of 370 Mbps. The GS9000S will operate to a maximum frequency of 300 Mbps. Fig. 18 Typical Application Circuit REVISION NOTES New document. DOCUMENT IDENTIFICATION PRODUCT PROPOSAL This data has been compiled for market investigation purposes only, and does not constitute an offer for sale. ADVANCE INFORMATION NOTE This product is in development phase and specifications are subject to change without notice. Gennum reserves the right to remove the product at any time. Listing the product does not constitute an offer for sale. PRELIMINARY The product is in a preproduction phase and specifications are subject to change without notice. DATA SHEET The product is in production. Gennum reserves the right to make changes at any time to improve reliability, function or design, in order to provide the best product possible. For latest product information, visit www.gennum.com Gennum Corporation assumes no responsibility for the use of any circuits described herein and makes no representations that they are free from patent infringement. © Copyright July 2004 Gennum Corporation. All rights reserved. Printed in Canada. 12 of 13 32466 - 1 GS9005B Package Outline Drawing D E D N E NS M IG M S O E C D E R EW T N O N R O F REVISION NOTES November 2007 - Version 1 Added Package Outline Drawing (ECR #148311) For latest product information, visit www.gennum.com DOCUMENT IDENTIFICATION PRODUCT PROPOSAL This data has been compiled for market investigation purposes only, and does not constitute an offer for sale. ADVANCE INFORMATION NOTE This product is in development phase and specifications are subject to change without notice. Gennum reserves the right to remove the product at any time. Listing the product does not constitute an offer for sale. PRELIMINARY The product is in a preproduction phase and specifications are subject to change without notice. DATA SHEET The product is in production. Gennum reserves the right to make changes at any time to improve reliability, function or design, in order to provide the best product possible. Gennum Corporation assumes no responsibility for the use of any circuits described herein and makes no representations that they are free from patent infringement. © Copyright July 2004 Gennum Corporation. All rights reserved. Printed in Canada. 13 of 13 32466 - 1