HA9P2556-9

HA-2556 Data Sheet September 1998 File Number 2477.5 57MHz, Wideband, Four Quadrant, Voltage Output Analog Multiplier The HA-2556 is a monolithic, high speed, four quadrant, analog multiplier constructed in the Intersil Dielectrically Isolated High Frequency Process. The voltage output simplifies many designs by eliminating the current-to-voltage conversion stage required for current output multipliers. The HA-2556 provides a 450V/µs slew rate and maintains 52MHz and 57MHz bandwidths for the X and Y channels respectively, making it an ideal part for use in video systems. The suitability for precision video applications is demonstrated further by the Y Channel 0.1dB gain flatness to 5.0MHz, 1.5% multiplication error, -50dB feedthrough and differential inputs with 8µA bias current. The HA-2556 also has low differential gain (0.1%) and phase (0.1o) errors. The HA-2556 is well suited for AGC circuits as well as mixer applications for sonar, radar, and medical imaging equipment. The HA-2556 is not limited to multiplication applications only; frequency doubling, power detection, as well as many other configurations are possible. For MIL-STD-883 compliant product consult the HA-2556/883 datasheet. Features • High Speed Voltage Output . . . . . . . . . . . . . . . . . 450V/µs • Low Multiplication Error . . . . . . . . . . . . . . . . . . . . . . .1.5% • Input Bias Currents. . . . . . . . . . . . . . . . . . . . . . . . . . . 8µA • 5MHz Feedthrough. . . . . . . . . . . . . . . . . . . . . . . . . . -50dB • Wide Y Channel Bandwidth . . . . . . . . . . . . . . . . . . 57MHz • Wide X Channel Bandwidth . . . . . . . . . . . . . . . . . . 52MHz • VY 0.1dB Gain Flatness . . . . . . . . . . . . . . . . . . . . 5.0MHz Applications • Military Avionics • Missile Guidance Systems • Medical Imaging Displays • Video Mixers • Sonar AGC Processors • Radar Signal Conditioning • Voltage Controlled Amplifier • Vector Generators Ordering Information PART NUMBER HA3-2556-9 HA9P2556-9 HA1-2556-9 TEMP. RANGE (oC) -40 to 85 -40 to 85 -40 to 85 PACKAGE 16 Ld PDIP 16 Ld SOIC 16 Ld CERDIP PKG. NO. E16.3 M16.3 F16.3 Functional Block Diagram VX+ + VXHA-2556 VOUT A X - Pinout HA-2556 (PDIP, CERDIP, SOIC) TOP VIEW GND 1 REF VREF 2 VYIOB 3 VYIOA 4 VY+ 5 VY - 6 V- 7 VOUT 8 Σ Y X 1/SF + ∑ VY+ + Y Z VZ+ + - - VY16 VXIOA 15 VXIOB 14 NC 13 VX+ 12 VX11 V+ +Z VZ- NOTE: The transfer equation for the HA-2556 is: (VX+ -VX-) (VY+ -VY-) = SF (VZ+ -VZ-), where SF = Scale Factor = 5V; VX, VY, VZ = Differential Inputs. 10 VZ 9 VZ + 1 CAUTION: These devices are sensitive to electrostatic discharge; follow proper IC Handling Procedures. 1-888-INTERSIL or 321-724-7143 | Copyright © Intersil Corporation 1999 HA-2556 Absolute Maximum Ratings Voltage Between V+ and V- Terminals. . . . . . . . . . . . . . . . . . . . 35V Differential Input Voltage . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 6V Output Current . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . ±60mA Thermal Information Thermal Resistance (Typical, Note 1) θJA (oC/W) θJC (oC/W) PDIP Package . . . . . . . . . . . . . . . . . . . 77 N/A SOIC Package . . . . . . . . . . . . . . . . . . . 90 N/A CERDIP Package. . . . . . . . . . . . . . . . . 75 20 Maximum Junction Temperature (Ceramic Package) . . . . . . . 175oC Maximum Junction Temperature (Plastic Packages) . . . . . . 150oC Maximum Storage Temperature Range . . . . . . . . . . -65oC to 150oC Maximum Lead Temperature (Soldering 10s) . . . . . . . . . . . . 300oC (SOIC - Lead Tips Only) Operating Conditions Temperature Range . . . . . . . . . . . . . . . . . . . . . . . . . -40oC to 85oC CAUTION: Stresses above those listed in “Absolute Maximum Ratings” may cause permanent damage to the device. This is a stress only rating and operation of the device at these or any other conditions above those indicated in the operational sections of this specification is not implied. NOTE: 1. θJA is measured with the component mounted on an evaluation PC board in free air. Electrical Specifications PARAMETER MULTIPLIER PERFORMANCE Transfer Function VSUPPLY = ±15V, RF = 50Ω, RL = 1kΩ, CL = 20pF, Unless Otherwise Specified TEST CONDITIONS TEMP. (oC) MIN TYP MAX UNITS ( V X+ – V X- ) × ( V Y+ – V Y- ) V OUT = A ------------------------------------------------------------------- – ( V Z+ – V Z- ) 5 Note 2 25 Full 1.5 3.0 0.003 5 0.02 0.05 0.2 3 6 0.25 0.5 % % %/oC V % % % Multiplication Error Multiplication Error Drift Scale Factor Linearity Error VX, VY = ±3V, Full Scale = 3V VX, VY = ±4V, Full Scale = 4V VX, VY = ±5V, Full Scale = 5V AC CHARACTERISTICS Small Signal Bandwidth (-3dB) VY = 200mVP-P, VX = 5V VX = 200mVP-P, VY = 5V Full Power Bandwidth (-3dB) Slew Rate Rise Time Overshoot Settling Time Differential Gain Differential Phase VY 0.1dB Gain Flatness VX 0.1dB Gain Flatness THD + N 1MHz Feedthrough 5MHz Feedthrough SIGNAL INPUT (VX, VY, VZ) Input Offset Voltage 10VP-P Note 5 Note 6 Note 6 To 0.1%, Note 5 Notes 3, 8 Notes 3, 8 200mVP-P, VX = 5V, Note 8 200mVP-P, VY = 5V, Note 8 Note 4 200mVP-P, Other Ch Nulled 200mVP-P, Other Ch Nulled Full 25 25 25 25 25 25 25 25 25 25 25 25 25 25 25 25 25 25 420 4.0 2.0 - 57 52 32 450 8 20 100 0.1 0.1 5.0 4.0 0.03 -65 -50 0.2 0.3 - MHz MHz MHz V/µs ns % ns % Degrees MHz MHz % dB dB 25 Full - 3 8 45 8 12 15 25 15 20 mV mV µV/ oC µA µA Average Offset Voltage Drift Input Bias Current Full 25 Full 2 HA-2556 Electrical Specifications PARAMETER Input Offset Current VSUPPLY = ±15V, RF = 50Ω, RL = 1kΩ, CL = 20pF, Unless Otherwise Specified (Continued) TEST CONDITIONS TEMP. (oC) 25 Full Differential Input Resistance Full Scale Differential Input (VX, VY, VZ) VX Common Mode Range VY Common Mode Range CMRR Within Common Mode Range Voltage Noise (Note 9) f = 1kHz f = 100kHz OUTPUT CHARACTERISTICS Output Voltage Swing Output Current Output Resistance POWER SUPPLY +PSRR -PSRR Supply Current NOTES: 2. 3. 4. 5. 6. 7. 8. 9. 10. Error is percent of full scale, 1% = 50mV. f = 4.43MHz, VY = 300mVP-P, 0 to 1VDC offset, VX = 5V. f = 10kHz, VY = 1VRMS, VX = 5V. VOUT = 0 to ±4V. VOUT = 0 to ±100mV. VS = ±12V to ±15V. Guaranteed by characterization and not 100% tested. VX = VY = 0V. VX = 5.5V, VY = ±5.5V. Note 7 Note 7 Full Full Full 65 45 80 55 18 22 dB dB mA Note 10 Full Full 25 ±5.0 ±20 ±6.05 ±45 0.7 1.0 V mA Ω 25 25 25 25 Full 25 25 MIN ±5 65 TYP 0.5 1.0 1 ±10 +9, -10 78 150 40 MAX 2 3 UNITS µA µA MΩ V V V dB nV/√Hz nV/√Hz Simplified Schematic V+ VBIAS VBIAS VCC VX+ VX- VY+ VY VZ + OUT REF + VZ - - VXIO A VXIOB VYIO A GND VYIOB V- 3 HA-2556 Application Information Operation at Reduced Supply Voltages The HA-2556 will operate over a range of supply voltages, ±5V to ±15V. Use of supply voltages below ±12V will reduce input and output voltage ranges. See “Typical Performance Curves” for more information. To accomplish this the differential input voltages are first converted into differential currents by the X and Y input transconductance stages. The currents are then scaled by a constant reference and combined in the multiplier core. The multiplier core is a basic Gilbert Cell that produces a differential output current proportional to the product of X and Y input signal currents. This current becomes the output for the HA-2557. The HA-2556 takes the output current of the core and feeds it to a transimpedance amplifier, that converts the current to a voltage. In the multiplier configuration, negative feedback is provided with the Z transconductance amplifier by connecting VOUT to the Z input. The Z stage converts VOUT to a current which is subtracted from the multiplier core before being applied to the high gain transimpedance amp. The Z stage, by virtue of it’s similarity to the X and Y stages, also cancels second order errors introduced by the dependence of VBE on collector current in the X and Y stages. The purpose of the reference circuit is to provide a stable current, used in setting the scale factor to 5V. This is achieved with a bandgap reference circuit to produce a temperature stable voltage of 1.2V which is forced across a NiCr resistor. Slight adjustments to scale factor may be possible by overriding the internal reference with the VREF pin. The scale factor is used to maintain the output of the multiplier within the normal operating range of ±5V when full scale inputs are applied. Offset Adjustment X and Y channel offset voltages may be nulled by using a 20K potentiometer between the VYIO or VXIO adjust pin A and B and connecting the wiper to V-. Reducing the channel offset voltage will reduce AC feedthrough and improve the multiplication error. Output offset voltage can also be nulled by connecting VZ- to the wiper of a potentiometer which is tied between V+ and V-. Capacitive Drive Capability When driving capacitive loads >20pF a 50Ω resistor should be connected between VOUT and VZ+, using VZ+ as the output (see Figure 1). This will prevent the multiplier from going unstable and reduce gain peaking at high frequencies. The 50Ω resistor will dampen the resonance formed with the capacitive load and the inductance of the output at pin 8. Gain accuracy will be maintained because the resistor is inside the feedback loop. Theory of Operation The HA-2556 creates an output voltage that is the product of the X and Y input voltages divided by a constant scale factor of 5V. The resulting output has the correct polarity in each of the four quadrants defined by the combinations of positive and negative X and Y inputs. The Z stage provides the means for negative feedback (in the multiplier configuration) and an input for summation into the output. This results in the following equation, where X, Y and Z are high impedance differential inputs. 1 REF NC NC NC VY+ 2 3 4 5 6 -15V 7 8 50Ω + + The Balance Concept The open loop transfer equation for the HA-2556 is: ( V X+ -V X- ) x ( V Y+ – V Y- ) V OUT = A ------------------------------------------------------------------ - ( V Z+ -V Z- ) 5V where; A 5V = Output Amplifier Open Loop Gain = Fixed Scaled Factor VX, VY, VZ = Differential Input Voltages An understanding of the transfer function can be gained by assuming that the open loop gain, A, of the output amplifier is infinite. With this assumption, any value of VOUT can be generated with an infinitesimally small value for the terms within the brackets. Therefore we can write the equation: 16 15 14 13 12 11 Σ NC NC NC VX+ - - +- + 10 9 +15 V VZ VZ + 1kΩ VOUT 20pF ( V X+ -V X- ) x ( V Y+ -V Y- ) 0 = ---------------------------------------------------------------- - ( V Z+ -V Z- ) 5V which simplifies to: ( V X+ -V X- ) x ( V Y+ -V Y- ) = 5V ( V Z+ -V Z- ) FIGURE 1. DRIVING CAPACITIVE LOAD XxY V OUT = Z = ------------5 This form of the transfer equation provides a useful tool to analyze multiplier application circuits and will be called the Balance Concept. 4 HA-2556 Typical Applications Let’s first examine the Balance Concept as it applies to the standard multiplier configuration (Figure 2). VX+ A VX1/5V VY+ B VY+ + HA-2556 VOUT A X + ∑ W A VX+ + VXZ VZ + + HA-2556 A X + 1/5V VY+ VZ + Y ∑ Z VZ + + VOUT W Here the Balance equation will appear as: (A) x (A) = 5(W) - - Y - - - - - FIGURE 2. MULTIPLIER VY - VZ - Signals A and B are input to the multiplier and the signal W is the result. By substituting the signal values into the Balance equation you get: (A) x (B) = 5(W) FIGURE 4. SQUARE Which simplifies to: A2 W = -----5 And solving for W: AxB W = ------------5 Notice that the output (W) enters the equation in the feedback to the Z stage. The Balance Equation does not test for stability, so remember that you must provide negative feedback. In the multiplier configuration, the feedback path is connected to VZ+ input, not VZ-. This is due to the inversion that takes place at the summing node just prior to the output amplifier. Feedback is not restricted to the Z stage, other feedback paths are possible as in the Divider Configuration shown in Figure 3. VX+ + HA-2556 VOUT A X + 1/5V VY+ B VY+ ∑ W The last basic configuration is the Square Root as shown in Figure 5. Here feedback is provided to both X and Y inputs. VX+ + VXHA-2556 VOUT A X + ∑ W - 1/5V VY+ + Y Z VZ + + - - A VZ - VY- FIGURE 5. SQUARE ROOT (FOR A > 0) - VX- The Balance equation takes the form: ( W ) × ( –W ) = 5 ( –A ) Y Z VZ + + - - Which equates to: VZ A W= 5A FIGURE 3. DIVIDER Inserting the signal values A, B and W into the Balance Equation for the divider configuration yields: ( -W ) ( B ) = 5V x ( -A ) The four basic configurations (Multiply, Divide, Square and Square Root) as well as variations of these basic circuits have many uses. Frequency Doubler For example, if ACos(ωτ) is substituted for signal A in the Square function, then it becomes a Frequency Doubler and the equation takes the form: ( ACos ( ωτ ) ) × ( ACos ( ωτ ) ) = 5 ( W ) Solving for W yields: 5A W = -----B Notice that, in the divider configuration, signal B must remain ≥0 (positive) for the feedback to be negative. If signal B is negative, then it will be multiplied by the VX- input to produce positive feedback and the output will swing into the rail. Signals may be applied to more than one input at a time as in the Squaring configuration in Figure 4: And using some trigonometric identities gives the result: A2 W = ------ ( 1 + Cos ( 2 ωτ ) ) 10 5 HA-2556 Square Root The Square Root function can serve as a precision/wide bandwidth compander for audio or video applications. A compander improves the Signal to Noise Ratio for your system by amplifying low level signals while attenuating or compressing large signals (refer to Figure 17; X0.5 curve). This provides for better low level signal immunity to noise during transmission. On the receiving end the original signal may be reconstructed with the standard Square function. input was dedicated to a slow moving control function as is required for Automatic Gain Control. The HA-2556 is versatile enough for both. Although the X and Y inputs have similar AC characteristics, they are not the same. The designer should consider input parameters such as small signal bandwidth, AC feedthrough and 0.1dB gain flatness to get the most performance from the HA-2556. The Y channel is the faster of the two inputs with a small signal bandwidth of typically 57MHz versus 52MHz for the X channel. Therefore in AM Signal Generation, the best performance will be obtained with the Carrier applied to the Y channel and the modulation signal (lower frequency) applied to the X channel. Communications The Multiplier configuration has applications in AM Signal Generation, Synchronous AM Detection and Phase Detection to mention a few. These circuit configurations are shown in Figures 6, 7 and 8. The HA-2556 is particularly useful in applications that require high speed signals on all inputs. ACos(ωΑτ) Audio VXVX+ + HA-2556 VOUT A X + ∑ W Scale Factor Control The HA-2556 is able to operate over a wide supply voltage range ±5V to ±17.5V. The ±5V range is particularly useful in video applications. At ±5V the input voltage range is reduced to ±1.4V. The output cannot reach its full scale value with this restricted input, so it may become necessary to modify the scale factor. Adjusting the scale factor may also be useful when the input signal itself is restricted to a small portion of the full scale level. Here we can make use of the high gain output amplifier by adding external gain resistors. Generating the maximum output possible for a given input signal will improve the Signal to Noise Ratio and Dynamic Range of the system. For example, let’s assume that the input signals are 1VPEAK each. Then the maximum output for the HA-2556 will be 200mV. (1V x 1V)/(5V) = 200mV. It would be nice to have the output at the same full scale as our input, so let’s add a gain of 5 as shown in Figure 9. VX+ A + VXHA-2556 VOUT A X + 1/5V ∑ 1kΩ RF W - 1/5V CCos(ωCτ) Carrier VYVY+ + Y Z VZ + + - - VZ - AC W = -------- ( Cos ( ω C – ω A )τ + Cos ( ω C + ω A )τ ) 10 FIGURE 6. AM SIGNAL GENERATION VX+ + VXHA-2556 AM Signal VOUT A W - X + ∑ 1/5V Carrier VY+ + Y Z VZ+ + - - - VY- VZB VY+ + Y Z VZ + + LIKE THE FREQUENCY DOUBLER YOU GET AUDIO CENTERED AT DC AND 2FC. - - VY- VZ - FIGURE 7. SYNCHRONOUS AM DETECTION HA-2556 + VXVOUT A X + 1/5V ACos(ωτ+φ) VY+ + ∑ W RF ExternalGain = ------- + 1 RG FIGURE 9. EXTERNAL GAIN OF 5 250Ω RG ACos(ωτ) VX+ - One caveat is that the output bandwidth will also drop by this factor of 5. The multiplier equation then becomes: Z VZ + + Y 5AB W = ----------- = A × B 5 - - VY- A2 W = ------ ( Cos ( φ ) + Cos ( 2 ωτ + φ ) ) 10 VZ - Current Output Another useful circuit for low voltage applications allows the user to convert the voltage output of the HA2556 to an output current. The HA-2557 is a current output version offering 100MHz of bandwidth, but its scale factor is fixed and does not have an output amplifier for additional scaling. Fortunately the circuit in Figure 10 provides an output current that can be DC COMPONENT IS PROPORTIONAL TO COS(f) FIGURE 8. PHASE DETECTION Each input X, Y and Z has similar wide bandwidth and input characteristics. This is unlike earlier products where one 6 HA-2556 scaled with the value of RCONVERT and provides an output impedance of typically 1MΩ. The equation for IOUT becomes: A×B 1 I OUT = ------------- × ------------------------------5 R CONVERT Of course the HA-2556 is also well suited to standard multiplier applications such as Automatic Gain Control and Voltage Controlled Amplifier. A VX+ + 5K B 5K VYVXVY+ + HA-2556 W = 5(A2-B2) A X + Y ∑ 5K Z VZ + + Video Fader The Video Fader circuit provides a unique function. Here Ch B is applied to the minus Z input in addition to the minus Y input. In this way, the function in Figure 11 is generated. VMIX will control the percentage of Ch A and Ch B that are mixed together to produce a resulting video image or other signal. A VX+ + VXHA-2556 VOUT A X + 1/5V B VY+ + ∑ R1 5K Z VZ + + VXVX+ 1/5V VZ A VY+ RCONVERT IOUT - 1/5V - - - VZ - 5K FIGURE 12. DIFFERENCE OF SQUARES 95K R2 + HA-2556 VOUT A X + ∑ A-B W = 100 A - Y - - - VY- + Y Z VZ + + - - B VZ - FIGURE 10. CURRENT OUTPUT VY- The Balance equation looks like: ( V MIX ) × ( ChA – ChB ) = 5 ( V OUT – ChB ) R1 and R2 set scale to 1V/%, other scale factors possible. For A 0V . FIGURE 13. PERCENTAGE DEVIATION Which simplifies to: V MIX V OUT = ChB + ------------- ( ChA – ChB ) 5 VX+ HA-2556 VOUT A X + ∑ A-B W = 10 B + A When VMIX is 0V the equation becomes VOUT = Ch B and Ch A is removed, conversely when VMIX is 5V the equation becomes VOUT = Ch A eliminating Ch B. For VMIX values 0V ≤ VMIX ≤ 5V the output is a blend of Ch A and Ch B. 5K 1 REF NC NC NC Ch A Ch B VY+ VY-15V 2 3 4 5 6 7 8 50Ω + + - VX+ 1/5V VY+ + Y Z VZ + + - - B A VZ - 16 15 14 13 12 11 Σ NC NC NC VX + VY- 5K - VMIX (0V to 5V) FIGURE 14. DIFFERENCE DIVIDED BY SUM S (For A + B ≥ 0V) - +- + 10 9 +15 V VZ VZ + VOUT Automatic Gain Control Figure 15 shows the HA-2556 configured in an Automatic Gain Control or AGC application. The HA-5127 low noise amplifier provides the gain control signal to the X input. This control signal sets the peak output voltage of the multiplier to match the preset reference level. The feedback network around the HA-5127 provides a response time adjustment. High frequency changes in the peak are rejected as noise or the desired signal to be transmitted. These signals do not indicate a change in the average peak value and therefore no gain adjustment is needed. Lower frequency changes in the peak value are given a gain of -1 for feedback to the control input. At DC the circuit is an integrator automatically compensating for Offset and other constant error terms. FIGURE 11. VIDEO FADER Other Applications As shown above, a function may contain several different operators at the same time and use only one HA-2556. Some other possible multi-operator functions are shown in Figures 12, 13 and 14. 7 HA-2556 This multiplier has the advantage over other AGC circuits, in that the signal bandwidth is not affected by the control signal gain adjustment. HA-2556 1 REF NC NC NC VY+ 2 3 4 5 Y X Wave Shaping Circuits Wave shaping or curve fitting is another class of application for the analog multiplier. For example, where a nonlinear sensor requires corrective curve fitting to improve linearity the HA-2556 can provide nonintegral powers in the range 1 to 2 or nonintegral roots in the range 0.5 to 1.0 (refer to References). This effect is displayed in Figure 17. 1 X0.5 X0.7 16 NC 15 NC 14 NC 13 12 11 V+ Σ 0.8 OUTPUT (V) 6 V7 8 +Z 10 9 VOUT 0.6 0.4 X1.5 50Ω 10kΩ 1N914 10kΩ 5kΩ +15V 20kΩ 0.1µF 0.01µF + HA-5127 5.6V 0 0 0.2 0.4 0.6 INPUT (V) 0.1µF 0.2 X2 0.8 1 - FIGURE 17. EFFECT OF NONINTEGRAL POWERS / ROOTS A multiplier can’t do nonintegral roots “exactly”, but it can yield a close approximation. We can approximate nonintegral roots with equations of the form: 2 V o = ( 1 – α ) V IN + α V IN 1 V o = ( 1 – α ) V IN⁄ 2 + α V IN FIGURE 15. AUTOMATIC GAIN CONTROL HA-2556 16 NC REF NC 2 NC 3 NC 4 X 1 Figure 18 compares the function VOUT = VIN0.7 to the approximation VOUT = 0.5VIN0.5 + 0.5VIN. 1 15 NC 14 NC 13 VX + (VGAIN) 12 Y 0.8 X0.7 5 6 V7 8 Σ +- 10 Z OUTPUT (V) 11 V+ 0.6 0.5X0.5+ 0.5X 0.4 9 0.2 5kΩ X 500Ω VIN 0 0 0.2 0.4 0.6 0.8 1 VOUT + HFA0002 - INPUT (V) FIGURE 16. VOLTAGE CONTROLLED AMPLIFIER FIGURE 18. COMPARE APPROXIMATION TO NONINTEGRAL ROOT Voltage Controlled Amplifier A wide range of gain adjustment is available with the Voltage Controlled Amplifier configuration shown in Figure 16. Here the gain of the HFA0002 can be swept from 20V/V to a gain of almost 1000V/V with a DC voltage from 0V to 5V. This function can be easily built using an HA-2556 and a potentiometer for easy adjustment as shown in Figures 19 and 20. If a fixed nonintegral power is desired, the circuit shown in Figure 21 eliminates the need for the output buffer amp. These M circuits approximate the function VIN where M is the desired nonintegral power or root. 8 HA-2556 HA-2556 1 NC NC NC REF 2 3 4 5 6 V7 8 + Y Values for α to give a desired M root or power are as follows: 16 NC 15 NC 14 NC + X ROOTS - FIGURE 19 M 0.5 0.6 0.7 0.8 1-α VIN POWERS - FIGURE 20 M 1.0 1.2 1.4 1.6 1.8 2.0 α 1 α 0 13 - 12 11 V+ Σ +Z + 10 0.9 1.0 ≈0.25 ≈0.50 ≈0.70 ≈0.85 1 ≈0.75 ≈0.5 ≈0.3 ≈0.15 0 - 9 α Sine Function Generators Similar functions can be formulated to approximate a SINE function converter as shown in Figure 22. With a linearly changing (0V to 5V) input the output will follow 0 degrees to 90 degrees of a sine function (0V to 5V) output. This configuration is theoretically capable of ±2.1% maximum error to full scale. By adding a second HA-2556 to the circuit an improved fit may be achieved with a theoretical maximum error of ±0.5% as shown in Figure 23. Figure 23 has the added benefit that it will work for positive and negative input signals. This makes a convenient triangle (±5V input) to sine wave (±5V output) converter. 0.5 ≤ M ≤ 1.0 0V ≤ VIN ≤ 1V + - VOUT HA-5127 FIGURE 19. NONINTEGRAL ROOTS - ADJUSTABLE HA-2556 1 REF NC 2 NC 3 NC 4 5 6 V7 8 + Y 16 NC 15 NC 14 NC + X VIN 13 - 12 11 V+ Σ +Z + 10 1-α References [1] Pacifico Cofrancesco, “RF Mixers and Modulators made with a Monolithic Four-Quadrant Multiplier” Microwave Journal, December 1991 pg. 58 - 70. [2] Richard Goller, “IC Generates Nonintegral Roots” Electronic Design, December 3, 1992. - 9 α 1.0 ≤ M ≤ 2.0 0V ≤ VIN ≤ 1V + HA-5127 HA-2556 1 REF NC 1 REF NC NC NC 2 3 4 5 6 + Y - VOUT FIGURE 20. NONINTEGRAL POWERS - ADJUSTABLE HA-2556 16 NC 15 NC 14 NC + X 16 NC 15 NC 14 NC + + Y X 2 3 4 5 6 NC VIN VIN NC R2 470 R6 470 13 13 12 11 V+ - 12 11 V+ Σ Σ +Z + 10 +Z R1 VOUT V- 7 8 R1 262 R5 1410 + 10 - 9 VOUT V- 7 8 R3 9 R2 R3 , 644 R4, 1K 1.2 ≤ M ≤ 2.0 0V ≤ VIN ≤ 1V R4 FIGURE 22. SINE-FUNCTION GENERATOR FIGURE 21. NONINTEGRAL POWERS - FIXED 2  R3   R2  1  R3 -V OUT = --  ------ + 1 V IN +  ------ + 1  --------------------  V IN 5  R4 R4     R 1 + R 2 Setting:  1  R3 -1 – α = --  ------ + 1 5  R4   R3   R2  α =  ------ + 1  --------------------  R4    R 1 + R 2 9 HA-2556 ( 1 – 0.1284V IN ) π V IN V OUT = V IN -------------------------------------------------- ≈ 5sin  -- ⋅ --------- 2 5  ( 0.6082 – 0.05V ) IN 23.1K X+ 71.5K VOUT for; 0V ≤ VIN ≤ 5V where: R4 ; 0.6082 = -------------------R3 + R4 Max Theoretical Error = 2.1%FS VIN XX+ XVOUT 10K VOUT 5.71K Z+ Z10K R2 5 ( 0.1284 ) = -------------------R1 + R2 HA-2556 Y+ Y- R6 5 ( 0.05 ) = -------------------R5 + R6 π V IN V OUT = ------------------------------------------------------------------ ≈ 5sin  -- ⋅ --------- 2 5  3.18167 + 0.0177919V2 IN 3 5V IN – 0.05494V IN HA-2556 Y+ YZ+ Z- for; -5V ≤ VIN ≤ 5V Max Theoretical Error = 0.5%FS FIGURE 23. BIPOLAR SINE-FUNCTION GENERATOR Typical Performance Curves 1 1.5 Y = -4 1 0.5 ERROR (%FS) ERROR (%FS) Y=0 0 Y=1 Y=3 -0.5 Y=4 Y=5 -1 -6 -4 -2 0 X INPUT (V) 2 4 6 0.5 Y = -2 Y = -1 0 Y=0 Y = -5 Y = -3 -0.5 Y=2 -1 -1.5 -6 -4 -2 0 X INPUT (V) 2 4 6 FIGURE 24. X CHANNEL MULTIPLIER ERROR FIGURE 25. X CHANNEL MULTIPLIER ERROR 1.5 X = -3 X = -2 1 X = -4 ERROR (%FS) ERROR (%FS) 0.5 1 0.5 X=0 0 X=5 -0.5 X=1 X=2 -1 X=4 X=3 X = -1 X=0 0 X = -5 -0.5 -1 -6 -4 -2 0 Y INPUT (V) 2 4 6 -1.5 -6 -4 -2 0 Y INPUT (V) 2 4 6 FIGURE 26. Y CHANNEL MULTIPLIER ERROR FIGURE 27. Y CHANNEL MULTIPLIER ERROR 10 HA-2556 Typical Performance Curves 8 (Continued) 200 4 OUTPUT (mV) OUTPUT (V) 100 0 0 -4 VX = ±4V PULSE VY = 5VDC -8 0ns 500ns 2V/DIV.; 100ns/DIV. 1µs -100 VY = ±100mV PULSE VX = 5VDC 0ns 250ns 50mV/DIV.; 50ns/DIV. 500ns -200 FIGURE 28. LARGE SIGNAL RESPONSE FIGURE 29. SMALL SIGNAL RESPONSE 4 3 2 GAIN (dB) Y CHANNEL = 10VP-P X CHANNEL = 5VDC 4 3 2 GAIN (dB) 1 0 -1 -2 -3 -3dB AT 32.5MHz -4 10K Y CHANNEL = 4VP-P X CHANNEL = 5VDC 1 0 -1 -2 -3 -4 10K 100K 1M FREQUENCY (Hz) 10M 100K 1M FREQUENCY (Hz) 10M FIGURE 30. Y CHANNEL FULL POWER BANDWIDTH FIGURE 31. Y CHANNEL FULL POWER BANDWIDTH 4 3 2 GAIN (dB) X CHANNEL = 10VP-P Y CHANNEL = 5VDC 4 3 2 GAIN (dB) 1 0 -1 -2 -3 -4 X CHANNEL = 4VP-P Y CHANNEL = 5VDC 1 0 -1 -2 -3 -4 10K 100K 1M FREQUENCY (Hz) 10M 10K 100K 1M FREQUENCY (Hz) 10M FIGURE 32. X CHANNEL FULL POWER BANDWIDTH FIGURE 33. X CHANNEL FULL POWER BANDWIDTH 11 HA-2556 Typical Performance Curves (Continued) 0 VX = 5VDC -6 GAIN (dB) GAIN (dB) VX = 2VDC 0 VY = 5VDC -6 VY = 2VDC -12 -12 -18 -18 VY = 0.5VDC -24 10K VX = 0.5VDC 100K 1M FREQUENCY (Hz) VY = 200mVP-P 10M 100M -24 10K 100K 1M FREQUENCY (Hz) VX = 200mVP-P 10M 100M FIGURE 34. Y CHANNEL BANDWIDTH vs X CHANNEL 0 -10 -20 -30 CMRR (dB) CMRR (dB) -40 -50 -60 -70 -80 5MHz -38.8dB VY +, VY - = 200mVRMS VX = 5VDC FIGURE 35. X CHANNEL BANDWIDTH vs Y CHANNEL 0 -10 -20 -30 -40 -50 -60 -70 -80 5MHz -26.2dB VX +, VX - = 200mVRMS VY = 5VDC 10K 100K 1M FREQUENCY (Hz) 10M 100M 10K 100K 1M FREQUENCY (Hz) 10M 100M FIGURE 36. Y CHANNEL CMRR vs FREQUENCY FIGURE 37. X CHANNEL CMRR vs FREQUENCY 0 -10 -20 FEEDTHROUGH (dB) -30 -40 -50 -60 -70 -80 -52.6dB AT 5MHz VX = 200mVP-P VY = NULLED FEEDTHROUGH (dB) 0 -10 -20 -30 -40 -50 -60 -70 -80 -49dB AT 5MHz VY = 200mVP-P VX = NULLED 10K 100K 1M FREQUENCY (Hz) 10M 100M 10K 100K 1M FREQUENCY (Hz) 10M 100M FIGURE 38. FEEDTHROUGH vs FREQUENCY FIGURE 39. FEEDTHROUGH vs FREQUENCY 12 HA-2556 Typical Performance Curves 8 7 OFFSET VOLTAGE (mV) BIAS CURRENT (uA) 6 5 4 3 2 1 |VIOY| 0 -100 -50 0 50 100 150 TEMPERATURE (oC) |VIOX| |VIOZ| (Continued) 14 13 12 11 10 9 8 7 6 5 4 -100 -50 0 50 100 150 TEMPERATURE (oC) FIGURE 40. OFFSET VOLTAGE vs TEMPERATURE FIGURE 41. INPUT BIAS CURRENT (VX, VY, VZ) vs TEMPERATURE 6 2 1.5 1 0.5 0 -0.5 -1 -100 SCALE FACTOR ERROR (%) INPUT VOLTAGE RANGE (V) 5 X INPUT Y INPUT 4 3 2 1 -50 0 50 100 150 4 6 8 10 12 14 16 TEMPERATURE (oC) SUPPLY VOLTAGE (±V) FIGURE 42. SCALE FACTOR ERROR vs TEMPERATURE FIGURE 43. INPUT VOLTAGE RANGE vs SUPPLY VOLTAGE 15 X INPUT 10 SUPPLY CURRENT (mA) Y INPUT 5 CMR (V) 0 -5 X & Y INPUT -10 -15 4 6 8 10 12 14 16 SUPPLY VOLTAGE (±V) 25 20 ICC IEE 15 10 5 0 0 5 10 SUPPLY VOLTAGE (±V) 15 20 FIGURE 44. INPUT COMMON MODE RANGE vs SUPPLY VOLTAGE FIGURE 45. SUPPLY CURRENT vs SUPPLY VOLTAGE 13 HA-2556 Typical Performance Curves 5.0 MAX OUTPUT VOLTAGE (V) (Continued) 4.8 4.6 4.4 4.2 100 300 500 RLOAD (Ω) 700 900 1100 FIGURE 46. OUTPUT VOLTAGE vs RLOAD Die Characteristics DIE DIMENSIONS: 71 mils x 100 mils x 19 mils METALLIZATION: Type: Al, 1% Cu Thickness: 16kÅ ±2kÅ PASSIVATION: Type: Nitride (Si3N4) over Silox (SiO2, 5% Phos) Silox Thickness: 12kÅ ±2kÅ Nitride Thickness: 3.5kÅ ±2kÅ TRANSISTOR COUNT: 84 SUBSTRATE POTENTIAL: V- Metallization Mask Layout VREF GND (2) (1) HA-2556 VXIOA (16) VXIOB (15) VYIOB (3) VYIOA (4) VX+ (13) VY+ (5) VX(12) VY(6) V+ (11) (8) (7) V- VOUT (9) (10) VZ+ VZ- 14 HA-2556 All Intersil semiconductor products are manufactured, assembled and tested under ISO9000 quality systems certification. Intersil semiconductor products are sold by description only. Intersil Corporation reserves the right to make changes in circuit design and/or specifications at any time without notice. Accordingly, the reader is cautioned to verify that data sheets are current before placing orders. Information furnished by Intersil is believed to be accurate and reliable. However, no responsibility is assumed by Intersil or its subsidiaries for its use; nor for any infringements of patents or other rights of third parties which may result from its use. No license is granted by implication or otherwise under any patent or patent rights of Intersil or its subsidiaries. For information regarding Intersil Corporation and its products, see web site www.intersil.com Sales Office Headquarters NORTH AMERICA Intersil Corporation P. O. Box 883, Mail Stop 53-204 Melbourne, FL 32902 TEL: (321) 724-7000 FAX: (321) 724-7240 EUROPE Intersil SA Mercure Center 100, Rue de la Fusee 1130 Brussels, Belgium TEL: (32) 2.724.2111 FAX: (32) 2.724.22.05 ASIA Intersil (Taiwan) Ltd. 7F-6, No. 101 Fu Hsing North Road Taipei, Taiwan Republic of China TEL: (886) 2 2716 9310 FAX: (886) 2 2715 3029 15