KKA1062

TECHNICAL DATA TELEPHONE SPEECH NETWORK WITH DIALER INT`ERFACE FEATURES - Low DC line voltage; operates down to 1.6V (excluding polarity guard) - Voltage regulator with adjustable static resistance - Provides a supply for external circuits - Symmetrical high-impedance inputs (64 kΩ) for dynamic, magnetic or piezo-electric microphones - Asymmetrical high-impedance input (32 kΩ) for electret microphones - DTMF signal input with confidence tone - Mute KKA1062/1062A PIN CONNECTION LN 1 16 15 SLPE AGC REG GA S1 2 GA S2 OR GA R MI CMI C+ ST A B 3 4 5 6 7 8 14 input for pulse or DTMF dialing - KKA1062: active HIGH (MUTE) - KKA1062A: active LOW (MUTE) KKA1062 or BKA1062A K T 1062A 13 12 VCC MUTE DTMF IR VEE 11 10 9 - Receiving amplifier for dynamic, magnetic or piezo-electric earpieces - Large gain setting range on microphone and earpiece amplifiers - Line loss compensation (line current dependent) for microphone and earpiece amplifiers - Gain control curve adaptable to exchange supply - DC line voltage adjustment facility DESCRIPTION The KKA1062 and KKA1062A are integrated circuits that perform all speech and line interface functions required in fully electronic telephone sets. They perform electronic switching between dialing and speech. The ICs operates at line voltage down to 1.6 V DC (with reduced performance) to facilitate the use of more telephone sets connected in parallel. All statements and values refer to all versions unless otherwise specified. The KKA1062 (KKA1062A) is packaged in a standard 16-pin plastic DIP and special plastic DIP with internal heatsink is also available. QUICK REFERENCE DATA Characteristic Line Voltage Operating Line Current Normal Operation with Reduced Performance Internal Supply Current Supply Voltage for Peripherals I CC VCC VCC = 2.8V Iline= 15mA Ip= 1.2mA Ip= 0mA 2.2 2.2 Symbol VLN I line 11 1 0.9 2.7 3.4 Test Condition Iline = 15mA Min 3.55 Typ 4.0 2.0 140 11 1.35 Max 4.25 Unit V Vdc mA mA mA V Voltage Gain microphone amplifier receiving amplifier Line loss compensation Gain Control Exchange Supply Voltage Exchange Feeding bridge Resistance GV 44 20 ∆GV Vexch Rexch 36 0.4 52 31 dB dB 5.8 60 1 dB V kΩ KKA1062/1062A BLOCK DIAGRAM VCC 13 10 - LN 1 5 IR GAR BT1062A KKA1062A + 4 QR MIC+ MIC- 7 6 + 2 GAS1 + DTMF (1) 11 + 3 GAS2 dB - MUTE 12 SUPPLY AND REFERENCE CONTROL CURRENT LOW VOLTAGE CIRCUIT CURRENT REFERENCE 9 VEE 14 R EG 15 AGC 8 STAB 16 SLPE (1) Pin 12 is active HIGH (MUTE) for KKA1062. Fig.1 Block diagram for KKA1062A KKA1062/1062A FUNCTIONAL DESCRIPTION Supplies VCC, LN, SLPE, REG and STAB Power for the IC and its peripheral circuits is usually obtained from the telephone line. The supply voltage is delivered from the line via a dropping resistor and regulated by the IC. The supply voltage VCC may also be used to supply external circuits e.g. dialing and control circuits. Decoupling of the supply voltage is performed by a capacitor between VCC and VEE . The internal voltage regulator is decoupled by a capacitor between REG and VEE. The DC current flowing into the set is determined by the exchange supply voltage Vexch , the feeding bridge resistance Rexch and the DC resistance of the telephone line Rline . The circuit has internal current stabilizer operating at a level determined by a 3.6 kΩ resistor connected between STAB and VEE (see Fig.6). When the line current (Iline) is more than 0.5mA greater than the sum of the IC supply current (ICC) and the current drawn by the peripheral circuitry connected to VCC (Ip) the excess current is shunted to VEE via LN. The regulated voltage on the line terminal (VLN) can be calculated as: VLN = Vref + ISLPE x R9 VLN = Vref + {(Iline - ICC - 0.5 x 10-3A) - Ip} x R9 Vref is an internally generated temperature compensated reference voltage of 3.7V and R9 is an external resistor connected between SLPE and VEE. In normal use the value of R9 would be 20?. Changing the value of R9 will also affect microphone gain, DTMF gain, gain control characteristics, sidetone level, maximum output swing on LN and the DC characteristics (especially at the lower voltages). At line currents below 9mA the internal reference voltage is automatically adjusted to a lower value (typically 1.6V at 1mA). This means that more sets can be operated in parallel with DC line voltage (excluding the polarity guard) down to an absolute minimum voltage of 1.6V. At line currents below 9mA the circuit has limited sending and receiving levels. The internal reference voltage can be adjusted by means of an external resistor (RVA). This resistor when connected between LN and REG will decrease the internal reference voltage and when connected between REG and SLPE will increase the internal reference voltage. Microphone inputs MIC+ and MIC- and gain pins GAS1 and GAS2 The circuit has symmetrical microphone inputs. Its input impedance is 64 kΩ (2 x 32kΩ) and its voltage gain is typically 52 dB (when R7 = 68k?; see Fig.6). Dynamic, magnetic, piezo-electric or electret (with built-in FET source followers) can be used. The gain of the microphone amplifier can be adjusted between 44 dB and 52 dB to suit the sensitivity of the transducer in use. The gain is proportional to the value of R7 which is connected between GAS1 and GAS2. Stability is ensured by two external capacitors, C6 connected between GAS1 and SLPE and C8 connected between GAS1 and VEE. The value of C6 is 100pF but this may be increased to obtain a first-order low-pass filter. The value of C8 is 10 times the value of C6. The cut-off frequency corresponds to the time constant R7 x C6. Input MUTE (KKA1062A) When MUTE is LOW or open-circuit, the DTMF input is enable and the microphone and receiving amplifier inputs are inhibited. The reverse is true when MUTE is HIGH. MUTE switching causes only negligible clicking on the line and earpiece output. If the number of parallel sets in use causes a drop in line current to below 6 mA the DTMF amplifier becomes active independent to the DC level applied to the MUTE input. Fig.2 Equivalent impedance circuit Dual-tone multi-frequency input DTMF When the DTMF input is enable dialing tones may be sent on to the line. The voltage gain from DTMF to LN is typically 25.5 dB (when R7=68kΩ) and varies with R7 in the same way as the microphone gain. The signalling tones can be heard in the earpiece at a low level (confidence tone). Receiving amplifier IR, QR and GAR The receiving amplifier has one input (IR) and a non-inverting output (QR). The IR to QR gain is typically 31dB (when R4 = 100kΩ). It can be adjusted between 20 and 31dB to match the sensitivity of the transducer in use. The gain is set with the value of R4 which is connected between GAR and QR. The overall receive gain, between LN and QR, is calculated by subtracting the anti-sidetone network attenuation (32dB) from the amplifier gain. Two external capacitors, C4 and C7, ensure stability. C4 is normally 100pF and C7 is 10 times the value of C4. The value of C4 may be increased to obtain a firstorder low-pass filter. The cut-off frequency will depend on the time constant R4 x C4. Under normal conditions, when ISLPE >>ICC + 0.5mA + Ip, the static behaviour of the circuit is that of a 3.7V regulator diode with an internal resistance equal to that of R9. In the audio frequency range the dynamic impedance is largely determined by R1. Fig.2 show the equivalent impedance of the circuit. The output voltage of the receiving amplifier is specified for continuous-wave drive. The maximum output voltage will be higher under speech conditions where the peak to RMS ratio is higher. Automatic gain control input AGC KKA1062/1062A Automatic line loss compensation is achieved by connecting a resistor (R6) between AGC and VEE. The automatic gain control varies the gain of the microphone amplifier and the receiving amplifier in accordance with the DC line current. The control range is 5.8 dB which corresponds to a line length of 5 km for a 0.5mm diameter twisted-pair copper cable with a DC resistance of 176 ?/km and average attenuation of Z bal Z bal + R 8 Z line = Z line + R 1 (2) If fixed values are chosen for R1, R2, R3 and R9, then condition (1) will always be fulfilled when To obtain optimum sidetone suppression, condition (2) has to be fulfilled which results in: R8 1.2dB/km. Resistor R6 should be chosen in accordance with the exchange supply voltage and its feeding bridge resistance. The ratio of start and stop currents of the AGC curve is independent of the value of R6. If no automatic line-loss compensation is required the AGC pin may be left opencircuit. The amplifiers, in this condition, will give their maximum specified gain. Zbal = R1 x Zline = k x Zline R8 Where k is scale factor; k = R1 The scale factor k, dependent on the value of R8, is chosen to meet the following criteria: - compatibility with a standard capacitor from the E6 or E12 range for Zbal - |Zbal//R8|R9 to avoid influencing the transmit gain. In practise Zline varies considerably with the line type and length. The value chosen for Zbal should therefore be for an average line thus giving optimum setting for short or long lines. Sidetone suppression The anti-sidetone network, R1//Zline, R2, R3, R8, R9 and Zbal suppresses the transmitted signal in the earpiece. Maximum compensation is obtained when the following conditions are fulfilled: R9 x R2 = R1 x R 3 + ⎛ R 8 x Zbal ⎞ ⎜ ⎟ ⎝ R 8 + Zbal ⎠ (1) ABSOLUTE MAXIMUM RATING Characteristic Symbol Test Condition Min Typ Max Unit Positive Continuous Line Voltage Repetitive Line Voltage During Switch-on or Line Interruption Repetitive Peak Line Voltage for a 1ms Pulse per 5s Line Current Input Voltage on all other Pins Total Power Standard DIP Dissipation DIP with heatsink Operating Ambient Temperature Storage Temperature Junction Temperature VLN VLN(R) VLN(RM) Iline VI Ptot TA Tstg Tj R9 = 20Ω; R10 = 13Ω; see Fig.6 R9 = 20Ω; note 1 -0.7 R9 = 20Ω; note 2 -25 -40 12 13.2 28 140 VCC+0.7 0.58 0.67 +75 +125 +125 V V V mA V W o o C C o C Notes 1. Mostly dependent on the maximum required TA and on the voltage between LN and SLPE. 2. Calculated for the maximum ambient temperature specified and a maximum junction temperature of 125oC. (Thermal Resistance RJA = 85oC/W for standard DIP and RJA = 75oC/W for special DIP with heatsink). 150 I LN (mA ) 130 150 I LN (mA ) 130 110 (1) 90 (2) 110 (1) (2) (3) 90 (1) TA = 45oC; Ptot = 0.94 W (2) TA = 55oC; Ptot = 0.82 W (3) TA = 65oC; Ptot = 0.71 W (4) TA = 75oC; Ptot = 0.58 W 70 (3) (4) 50 30 2 4 6 8 10 12 V LN - V SL PE (V ) (1) TA = 45 C; Ptot = 1.07 W (2) TA = 55oC; Ptot = 0.93 W (3) TA = 65oC; Ptot = 0.80 W (4) TA = 75oC; Ptot = 0.67 W o 70 (4) 50 30 2 4 6 8 10 12 VLN - VSL PE (V) Fig.3a Safe operating area (Standard DIP) Fig.3b Safe operating area (DIP with HS) KKA1062/1062A ELECTRICAL CHARACTERISTICS Iline = 11mA to mA; VEE = 0V; f = 800Hz; TA = 25oC; unless otherwise specified. Characteristic Symbol Test Condition Min Typ Max Unit Voltage Drop over Circuit between LN and VEE VLN Variation with Temperature Voltage Drop over Circuit Between LN and VEE with External Resistor RVA Supply Current Supply Voltage available for Peripheral Circuitry |VLN/T VLN ICC VCC MIC inputs open-circuit Iline = 1mA Iline = 4mA Iline = 15mA Iline = 100mA Iline = 140mA Iline = 15mA Iline = 15mA RVA(LN to REG) = 68k Ω RVA(REG to SLPE) = 39kΩ VCC = 2.8V Iline = 15mA; Ip = 1.2mA Ip = 0mA 3.55 4.9 1.6 1.9 4.0 5.7 -0.3 3.5 4.5 0.9 V 4.25 6.5 7.5 mV/oC V 1.35 mA V 2.2 2.7 3.4 Microphone inputs MIC- and MIC+ (pins 6 and 7) Input Impedance Differential Single-ended Common mode rejection ratio Voltage Gain MIC+ or MIC- to LN Gain Variation with Frequency referenced to 800Hz Gain Variation with Temperature referenced to 25 o C DTMF Input (Pin 11) |Zi | between MIC- and MIC+ MIC- or MIC+ to VEE CMRR Gv ∆Gvf ∆GvT Iline = 15mA; R7 = 68k Ω f = 300 and 3400 Hz without R6; Iline = 50mA; TA = -25 and +75 oC 50.5 64 32 82 52.0 0.2 0.2 53.5 kΩ kΩ dB dB dB dB Input Impedance Voltage Gain from DTMF to LN Gain Variation with Frequency referenced to 800Hz Gain Variation with Temperature referenced to 25 o C |Zi | Gv ∆Gvf ∆GvT Iline = 15mA; R7 = 68kΩ f = 300 and 3400 Hz Iline = 50mA; TA = -25 and +75 oC 24.3 20.7 25.5 0.2 0.2 27.0 kΩ dB dB dB Gain adjustment inputs GAS1 and GAS2 (Pins2 and 3) Transmitting Amplifier Gain variation by adjustment of R7 between GAS1 and GAS2 Sending amplifier output LN (Pin1) ∆Gv -8 0 dB Output Voltage (RMS value) VLN(rms) THD = 10 % Iline = 4mA Iline = 15mA 1.7 0.8 2.3 V V Receiving amplifier input IR (Pin 10) Input Impedance Receiving amplifier output QR (Pin 4) |Zi | Iline = 15mA; RL = 300Ω; (from pin 9 to 21 kΩ Output Impedance Voltage Gain from IR to QR Gain Variation with Frequency referenced to 800Hz Gain Variation with Temperature referenced to 25o C Output Voltage (RMS value) |Zo | 4 Iline = 15mA; RL = 300Ω; (from pin 9 to pin 4) f = 300 and 3400 Hz without R6; Iline = 50mA; TA = -25 and +75oC THD = 2%; sine wave drive: 29.5 31 0.2 0.2 32.5 Ω Gv ∆Gvf ∆GvT dB dB dB Vo(rms) KKA1062/1062A R4 = 100 KΩ; Iline = 15 mA; Ip = 0 mA RL = 150 Ω RL = 450 Ω Output Voltage (RMS value) Vo(rms) Iline = 15mA; RL = 300Ω; (from pin 9 to pin 4) 0.22 0.3 0.33 0.48 15 V V mV Gain adjustment input GAR (Pin 5) Receiving Amplifier Gain Variation by adjustment of R4 between GAR and QR Mute input (Pin 12) ∆Gv Iline = 15mA; RL = 300Ω; (from pin 9 to pin 4) -11 0 dB HIGH Level Input Voltage LOW Level Input Voltage Input Current Reduction of Gain VIH VIIL IMUTE Iline = 15mA Iline = 15mA 1.5 8 VCC 0.3 15 V V uA MIC+ or MIC- to LN TEA1062 TEA1062A Voltage Gain from DTMF to QR TEA1062 TEA1062A Automatic Gain Control Input AGC (Pin 15) ∆Gv dB MUTE = HIGH MUTE = LOW R4 = 100kΩ; RL = 300Ω MUTE = HIGH MUTE = LOW 70 70 dB -17 -17 Gv Controlling the Gain from IR to QR and the Gain from MIC+, MIC- to LN Gain Control Range Highest Line Current for Maximum Gain Lowest Line Current for Minimum Gain ∆Gv R6 = 110kΩ (between AGC and VEE) Iline = 70mA Iline = 15mA Iline = 70mA 20 5.8 23 61 65 dB mA mA IlineH IlineL The supply possibilities can be increased by setting the voltage drop over the circuit VLN to a higher value be resistor RVA connected between REG and SLPE. VCC > 2.2V; Iline = 15mA at VLN = 4V; R1 = 620Ω; R9 = 20Ω (1) Ip = 2.1mA. Curve (1) is valid when the receiving or when MUTE = HIGH(KKA1062), MUTE = LOW(KKA1062A). (2) Ip = 1.7mA. Curve (2) is valid when MUTE = LOW(KKA1062), MUTE = HIGH(KKA1062A) and the receiving amplifier is driven; Vo(rms) = 150mV, RL = 150Ω. Fig.4 Typical current Ip available from VCC for peripheral circuitry. KKA1062/1062A Fig. 5 Variation of gain as a function of the line current with R6 as a parameter TABLE 1 Values of resistor R6 for optimum line-loss compensation at various values of exchange supply voltage (Vexch) and exchange bridge resistance (Rexch ); R9 = 20 . 400 Rexch (Ω) 600 Rexch (Ω) R6 (kΩ) 800 Rexch (Ω) 1000 Rexch (Ω) Vexch (V) 36 48 60 100 140 - 78.7 110 - 93.1 120 82 102 PINNING Pin Symbol Description 1 2 3 4 5 6 7 8 9 10 11 12 13 14 15 16 LN GAS1 GAS2 QR GAR MICMIC+ STAB VEE IR DTMF MUTE VCC REG AGC SLPE Positive Line Terminal Gain Adjustment; Transmitting Amplifier Gain Adjustment; Transmitting Amplifier Non-inverting Output; Receiving Amplifier Gain Adjustment; Receiving Amplifier Inverting Microphone Input Non-inverting Microphone Input Current Stabilizer Negative Line Terminal Receiving Amplifier Input Dual-tone Multi-Frequency Input Mute Input (see note 1) Positive Supply Decoupling Voltage Regulator Decoupling Automatic Gain Control Input Slope (DC resistance) Adjustment Note 1. Pin 12 is active HIGH (MUTE) for KKA1062 R1 620Ω 1 13 VCC + C5 10 IR 100 nF + 4 QR DTMF 11 C4 100pF 5 GAR (1) R10 13Ω LN C1 100 µF BZX79 C12 R2 130kΩ BAS11 (2x) C2 APPLICATION INFORMATION BZW14 (2x) elephone ne R4 R3 3.92kΩ 12 MUTE C7 1 nF 7 MI C+ KKA1062A BT1062A f r om dial and cont r ol cir cuit s - 6 MI CSLPE 16 C6 R7 100 pF RVA (R16- 14) C8 1 nF + R6 2 3 14 15 GAS1 GAS2 REG AGC STAB 8 VEE 9 R8 390Ω Zbal R9 20Ω R5 3.6 kΩ C3 4.7 µF Fig. 6 Typical application of KKA1062A, with piezo-electric earpiece and DTMF dialling he diode br idge, t he Zener and R10 l imit the cur r ent int o, and t he volt age acr oss, t he cir cuit dur ing line tr ansients. dif f er ent pr ot ect ion ar r angement is r equir ed f or pulse dialling or register r ecall. he DC line volt age can be set t o a higher value by the r esistor RVA (REG t o SLPE). KKA1062/1062A KK ) Pin 12 is act ive HI GH (MUTE) f or BT10. A1062 KKA1062/1062A N S UFFIX PLAS TIC DIP (MS - 0 0 1 BB) A Dimens ion, mm 16 9 B Symbol A MIN 18.67 6.1 MAX 19.69 7.11 5.33 1 8 B C F L D F 0.36 1.14 2.54 7.62 0° 2.92 7.62 0.2 0.38 0.56 1.78 C -T- SEATING PLAN E G H H J N G D 0.25 (0.010) M T K M J K L M N 10° 3.81 8.26 0.36 NOTES : 1. Dimen s io n s “A ”, “B” d o n o t in clu d e mo ld flas h o r p ro tru s io n s . Maximu m mo ld flas h o r p ro tru s io n s 0.25 mm (0.010) p er s id e. D S UFFIX S OIC (MS - 0 1 2 AC) Dimens ion, mm A 16 9 Symbol A MIN 9.8 3.8 1.35 0.33 0.4 1.27 5.72 0° 0.1 0.19 5.8 0.25 MAX 10 4 1.75 0.51 1.27 H B P B C 1 G 8 C R x 45 D F G -TD 0.25 (0.010) M T C M K SEAT ING PLAN E J F M H J K M P R 8° 0.25 0.25 6.2 0.5 NOTES : 1. Dimen s io ns A an d B d o n o t in clud e mo ld flas h o r p rotru s ion . 2. M aximu m mo ld flas h o r p ro tru s io n 0.15 mm (0.006) p er s id e fo r A ; fo r B ‑ 0.25 mm (0.010) p er s id e.