LT1801IMS8

LT1801/LT1802 Dual/Quad 80MHz, 25V/µs Low Power Rail-to-Rail Input and Output Precision Op Amps DESCRIPTION FEATURES n n n n n n n n n n n n n n n n n The LT ®1801/LT1802 are dual/quad, low power, high speed rail-to-rail input and output operational amplifiers with excellent DC performance. The LT1801/LT1802 feature reduced supply current, lower input offset voltage, lower input bias current and higher DC gain than other devices with comparable bandwidth. Gain Bandwidth Product: 80MHz Input Common Mode Range Includes Both Rails Output Swings Rail-to-Rail Low Voltage Operation: Single or Split Supplies 2.3V to 12.6V Low Quiescent Current: 2mA/Amplifier Max Input Offset Voltage: 350μV Max Input Bias Current: 250nA Max 3mm × 3mm × 0.8mm DFN Package Large Output Current: 50mA Typ Low Voltage Noise: 8.5nV/√Hz Typ Slew Rate: 25V/μs Typ Common Mode Rejection: 105dB Typ Power Supply Rejection: 97dB Typ Open-Loop Gain: 85V/mV Typ Operating Temperature Range: – 40°C to 85°C LT1801 is Available in 8-Lead SO, MS8 and DFN Packages LT1802 is Available in 14-Lead SO Package Typically, the LT1801/LT1802 have an input offset voltage of less than 100μV, an input bias current of less than 50nA and an open-loop gain of 85 thousand. The LT1801/LT1802 have an input range that includes both supply rails and an output that swings within 20mV of either supply rail to maximize the signal dynamic range in low supply applications. The LT1801/LT1802 maintain their performance for supplies from 2.3V to 12.6V and are specified at 3V, 5V and ±5V supplies. The inputs can be driven beyond the supplies without damage or phase reversal of the output. The LT1801 is available in the MS8, SO-8 and the 3mm × 3mm × 0.8mm dual fine pitch leadless package (DFN) with the standard dual op amp pinout. The LT1802 features the standard quad op amp configuration and is available in the 14-pin plastic SO package. The LT1801/LT1802 can be used as plug-in replacements for many op amps to improve input/output range and performance. APPLICATIONS n n n n n Low Voltage, High Frequency Signal Processing Driving A/D Converters Rail-to-Rail Buffer Amplifiers Active Filters Video Line Driver For a single version of these amplifiers, see the LT1800 data sheet. L, LT, LTC and LTM are registered trademarks of Linear Technology Corporation. All other trademarks are the property of their respective owners. 1MHz Filter Frequency Response TYPICAL APPLICATION 0 3V, 1MHz, 4th Order Butterworth Filter 909Ω 909Ω 2.67k VIN 220pF GAIN (dB) –20 47pF 1.1k – 3V 1.1k 2.21k – 470pF 1/2 LT1801 1/2 LT1801 + 22pF –60 –80 + VS/2 –40 VOUT –100 –120 18012 TA01 1k 10k 100k 1M FREQUENCY (Hz) 10M 100M 18012 TA02 18012fc 1 LT1801/LT1802 ABSOLUTE MAXIMUM RATINGS (Note 1) Total Supply Voltage (VS – to VS+) ......................... 12.6V Input Current (Note 2) ......................................... ± 10mA Output Short-Circuit Duration (Note 3) ........... Indefinite Operating Temperature Range (Note 4) ..–40°C to 85°C Specified Temperature Range (Note 5) ....–40°C to 85°C Junction Temperature .......................................... 150°C Storage Temperature Range .................. –65°C to 150°C Maximum Junction Temperature (DD Package) .... 125°C Storage Temperature (DD Package) ....... –65°C to 125°C Lead Temperature MSOP, SOIC (Soldering, 10 sec) ............................................ 300°C PIN CONFIGURATION TOP VIEW 8 V+ OUT A 1 TOP VIEW 7 OUT B –IN A 2 A +IN A 3 OUT A –IN A +IN A V– 6 –IN B B V– 4 5 +IN B 1 2 3 4 8 7 6 5 V+ OUT B –IN B +IN B MS8 PACKAGE 8-LEAD PLASTIC MSOP DD PACKAGE 8-LEAD (3mm × 3mm) PLASTIC DFN TJMAX = 125°C, θJA = 160°C/W, (Note 10) EXPOSED PAD INTERNALLY CONNECTED TO V–. (PCB CONNECTION OPTIONAL) TJMAX = 150°C, θJA = 250°C/W, (Note 10) TOP VIEW 14 OUT D OUT A 1 TOP VIEW OUT A 1 8 V+ –IN A 2 7 OUT B 6 –IN B +IN A 3 V– 4 – + – + 13 –IN D –IN A 2 5 +IN A 3 A D V+ 4 +IN B 5 +IN B 12 +IN D 11 V– B C 10 +IN C –IN B 6 9 –IN C OUT B 7 8 OUT C S8 PACKAGE 8-LEAD PLASTIC SO S PACKAGE 14-LEAD PLASTIC SO TJMAX = 150°C, θJA = 190°C/W, (Note 10) TJMAX = 150°C, θJA = 160°C/W, (Note 10) ORDER INFORMATION LEAD FREE FINISH TAPE AND REEL PART MARKING* PACKAGE DESCRIPTION OPERATING TEMPERATURE RANGE LT1801CDD#PBF LT1801CDD#TRPBF LAAM 8-Lead (3mm × 3mm) Plastic DFN –40°C to 85°C LT1801IDD#PBF LT1801IDD#TRPBF LAAM 8-Lead (3mm × 3mm) Plastic DFN –40°C to 85°C LT1801CMS8#PBF LT1801CMS8#TRPBF LTYR 8-Lead Plastic MSOP –40°C to 85°C LT1801IMS8#PBF LT1801IMS8#TRPBF LTYS 8-Lead Plastic MSOP –40°C to 85°C LT1801CS8#PBF LT1801CS8#TRPBF 1801 8-Lead Plastic SO –40°C to 85°C LT1801IS8#PBF LT1801IS8#TRPBF 1801I 8-Lead Plastic SO –40°C to 85°C LT1802CS#PBF LT1802CS#TRPBF LT1802CS 14-Lead Plastic SO –40°C to 85°C LT1802IS#PBF LT1802IS#TRPBF LT1802IS 14-Lead Plastic SO –40°C to 85°C Consult LTC Marketing for parts specified with wider operating temperature ranges. *The temperature grade is identified by a label on the shipping container. For more information on lead free part marking, go to: http://www.linear.com/leadfree/ For more information on tape and reel specifications, go to: http://www.linear.com/tapeandreel/ 18012fc 2 LT1801/LT1802 ELECTRICAL CHARACTERISTICS TA = 25°C, VS = 5V, 0V; VS = 3V, 0V; VCM = VOUT = half supply, unless otherwise noted. SYMBOL PARAMETER CONDITIONS VOS Input Offset Voltage VCM = 0V VCM = 0V (MS8) VCM = 0V (DD) VCM = VS ΔVOS Input Offset Shift VCM = 0V to VS – 1.5V 20 185 μV Input Offset Voltage Match (Channel-to-Channel) (Note 9) VCM = 0V VCM = 0V (MS8) VCM = 0V (DD) 100 150 280 650 900 1200 μV μV μV Input Bias Current VCM = 1V VCM = VS 25 500 250 1500 nA nA Input Bias Current Match (Channel-to-Channel) (Note 9) VCM = 1V VCM = VS 25 25 350 500 nA nA Input Offset Current VCM = 1V VCM = VS 25 25 200 200 nA nA Input Noise Voltage 0.1Hz to 10Hz 1.4 μVP-P en Input Noise Voltage Density f = 10kHz 8.5 nV/√Hz in Input Noise Current Density f = 10kHz 1 pA/√Hz CIN Input Capacitance 2 pF AVOL Large-Signal Voltage Gain VS = 5V, VO = 0.5V to 4.5V, RL = 1k at VS/2 VS = 5V, VO = 1V to 4V, RL = 100Ω at VS/2 VS = 3V, VO = 0.5V to 2.5V, RL = 1k at VS/2 35 3.5 30 85 8 85 V/mV V/mV V/mV CMRR Common Mode Rejection Ratio VS = 5V, VCM = 0V to 3.5V VS = 3V, VCM = 0V to 1.5V 85 78 105 97 dB dB CMRR Match (Channel-to-Channel) (Note 9) VS = 5V, VCM = 0V to 3.5V VS = 3V, VCM = 0V to 1.5V 79 72 105 97 dB dB Input Common Mode Range 0 IB IOS PSRR MIN TYP MAX UNITS 75 140 175 0.5 350 500 800 3 μV μV μV mV VS V VS = 2.5V to 10V, VCM = 0V 78 97 dB PSRR Match (Channel-to-Channel) (Note 9) VS = 2.5V to 10V, VCM = 0V 72 97 dB Power Supply Rejection Ratio Minimum Supply Voltage (Note 6) 2.3 2.5 V VOL Output Voltage Swing Low (Note 7) No Load ISINK = 5mA ISINK = 20mA 16 85 225 60 200 500 mV mV mV VOH Output Voltage Swing High (Note 7) No Load ISOURCE = 5mA ISOURCE = 20mA 18 120 450 60 250 800 mV mV mV ISC Short-Circuit Current VS = 5V VS = 3V IS Supply Current per Amplifier GBW Gain Bandwidth Product Frequency = 2MHz SR Slew Rate VS = 5V, AV = – 1, RL = 1k, VO = 1V to 4V FPBW Full Power Bandwidth VS = 5V, AV = 1, VO = 4VP-P HD Harmonic Distortion tS 20 20 45 40 1.6 mA mA 2 mA 40 80 MHz 12.5 25 V/μs 2 MHz VS = 5V, AV = 1, RL = 1k, VO = 2VP-P, fC = 500kHz –75 dBc Settling Time 0.01%, VS = 5V, VSTEP = 2V, AV = 1, RL = 1k 250 ns ΔG Differential Gain (NTSC) VS = 5V, AV = 2, RL = 150Ω 0.35 % Δθ Differential Phase (NTSC) VS = 5V, AV = 2, RL = 150Ω 0.4 Deg 18012fc 3 LT1801/LT1802 ELECTRICAL CHARACTERISTICS The l denotes the specifications which apply over the temperature range of 0°C < TA < 70°C. VS = 5V, 0V; VS = 3V, 0V; VCM = VOUT = half supply, unless otherwise noted. SYMBOL PARAMETER CONDITIONS MIN TYP MAX UNITS 125 140 290 0.6 500 650 950 3.5 μV μV μV mV VOS Input Offset Voltage VCM = 0V VCM = 0V (MS8) VCM = 0V (DD) VCM = VS l l l l ΔVOS Input Offset Shift VCM = 0V to VS – 1.5V l 30 275 μV Input Offset Voltage Match (Channel-to-Channel) (Note 9) VCM = 0V VCM = 0V (MS8) VCM = 0V (DD) l l l 200 200 275 850 1250 1500 μV μV μV l 1.5 5 VOS TC Input Offset Voltage Drift (Note 8) IB Input Bias Current VCM = 1V VCM = VS – 0.2V l l 50 550 300 2000 nA nA Input Bias Current Match (Channel-to-Channel) (Note 9) VCM = 1V VCM = VS – 0.2V l l 25 25 400 600 nA nA IOS Input Offset Current VCM = 1V VCM = VS – 0.2V l l 25 25 300 300 nA nA AVOL Large-Signal Voltage Gain VS = 5V, VO = 0.5V to 4.5V, RL = 1k at VS/2 VS = 5V, VO = 1V to 4V, RL = 100Ω at VS/2 VS = 3V, VO = 0.5V to 2.5V, RL = 1k at VS/2 l l l 25 2.5 20 75 6 75 V/mV V/mV V/mV CMRR Common Mode Rejection Ratio VS = 5V, VCM = 0V to 3.5V VS = 3V, VCM = 0V to 1.5V l l 82 74 101 93 dB dB CMRR Match (Channel-to-Channel) (Note 9) VS = 5V, VCM = 0V to 3.5V VS = 3V, VCM = 0V to 1.5V l l 76 68 101 93 dB dB Input Common Mode Range l 0 VS = 2.5V to 10V, VCM = 0V l 74 PSRR Match (Channel-to-Channel) (Note 9) VS = 2.5V to 10V, VCM = 0V l 68 Minimum Supply Voltage (Note 6) l 2.3 2.5 V PSRR Power Supply Rejection Ratio VS 91 μV/°C V dB 91 dB VOL Output Voltage Swing Low (Note 7) No Load ISINK = 5mA ISINK = 20mA l l l 18 100 300 80 225 600 mV mV mV VOH Output Voltage Swing High (Note 7) No Load ISOURCE = 5mA ISOURCE = 20mA l l l 25 150 600 80 300 950 mV mV mV ISC Short-Circuit Current VS = 5V VS = 3V l l IS Supply Current per Amplifier GBW Gain Bandwidth Product Frequency = 2MHz SR Slew Rate VS = 5V, AV = – 1, RL = 1k, VO = 1V to 4V 20 15 40 30 l 35 75 MHz l 11 22 V/μs l 2 mA mA 2.8 mA 18012fc 4 LT1801/LT1802 ELECTRICAL CHARACTERISTICS The l denotes the specifications which apply over the temperature range of – 40°C < TA < 85°C. VS = 5V, 0V; VS = 3V, 0V; VCM = VOUT = half supply, unless otherwise noted. (Note 5) SYMBOL PARAMETER TYP MAX UNITS VOS Input Offset Voltage CONDITIONS VCM = 0V VCM = 0V (MS8) VCM = 0V (DD) VCM = VS l l l l MIN 175 200 320 0.75 700 850 1150 4 μV μV μV mV ΔVOS Input Offset Shift VCM = 0V to VS – 1.5V l 30 300 μV Input Offset Voltage Match (Channel-to-Channel) (Note 9) VCM = 0V VCM = 0V (MS8) VCM = 0V (DD) l l l 200 280 320 1250 1600 1800 μV μV μV VOS TC Input Offset Voltage Drift (Note 8) l 1.5 5 IB Input Bias Current VCM = VS – 0.2V l l 50 600 400 2250 nA nA Input Bias Current Match (Channel-to-Channel) (Note 9) VCM = 1V VCM = VS – 0.2V l l 25 25 450 700 nA nA IOS Input Offset Current VCM = 1V VCM = VS – 0.2V l l 25 25 350 350 nA nA AVOL Large-Signal Voltage Gain VS = 5V, VO = 0.5V to 4.5V, RL = 1k at VS/2 VS = 5V, VO = 1.5V to 3.5V, RL = 100Ω at VS/2 VS = 3V, VO = 0.5V to 2.5V, RL = 1k at VS/2 l l l 20 2 17.5 65 6 65 V/mV V/mV V/mV CMRR Common Mode Rejection Ratio VS = 5V, VCM = 0V to 3.5V VS = 3V, VCM = 0V to 1.5V l l 81 73 101 93 dB dB CMRR Match (Channel-to-Channel) (Note 9) VS = 5V, VCM = 0V to 3.5V VS = 3V, VCM = 0V to 1.5V l l 75 67 101 93 dB dB Input Common Mode Range l 0 VS = 2.5V to 10V, VCM = 0V l 73 90 dB PSRR Match (Channel-to-Channel) (Note 9) VS = 2.5V to 10V, VCM = 0V l 67 90 dB PSRR Power Supply Rejection Ratio Minimum Supply Voltage (Note 6) VS μV/°C V VCM = VO = 0.5V l 2.3 2.5 V 15 105 170 90 250 400 mV mV mV 25 150 300 90 350 700 mV mV mV VOL Output Voltage Swing Low (Note 7) No Load ISINK = 5mA ISINK = 10mA l l l VOH Output Voltage Swing High (Note 7) No Load ISOURCE = 5mA ISOURCE = 10mA l l l ISC Short-Circuit Current VS = 5V VS = 3V l l IS Supply Current per Amplifier GBW Gain Bandwidth Product Frequency = 2MHz l 25 70 MHz SR Slew Rate VS = 5V, AV = – 1, RL = 1k, VO = 1V to 4V l 9 18 V/μs 12.5 12.5 l 30 30 2.1 mA mA 3 mA 18012fc 5 LT1801/LT1802 ELECTRICAL CHARACTERISTICS SYMBOL PARAMETER VOS Input Offset Voltage ΔVOS Input Offset Shift Input Offset Voltage Match (Channel-to-Channel) (Note 9) IB Input Bias Current Input Bias Current Match (Channel-to-Channel) (Note 9) IOS Input Offset Current TA = 25°C, VS = ± 5V, VCM = 0V, VOUT = 0V, unless otherwise noted. CONDITIONS MIN VCM = VS – VCM = VS – (MS8) VCM = VS – (DD) VCM = VS+ VCM = VS – to VS+ – 1.5V VCM = VS – VCM = VS – (MS8) VCM = VS – (DD) VCM = VS – + 1V VCM = VS+ VCM = VS – + 1V VCM = VS+ VCM = VS – + 1V VCM = VS+ TYP MAX UNITS 150 180 260 0.7 600 750 1050 3.5 μV μV μV mV 30 475 μV 150 275 325 1000 1300 1600 μV μV μV 25 400 250 1500 nA nA 20 20 350 500 nA nA 20 20 250 250 nA nA Input Noise Voltage 0.1Hz to 10Hz 1.4 μV/ P-P en Input Noise Voltage Density f = 10kHz 8.5 nV/√Hz in Input Noise Current Density f = 10kHz 1 pA/√Hz CIN Input Capacitance f = 100kHz 2 pF AVOL Large-Signal Voltage Gain VO = –4V to 4V, RL = 1k VO = –2V to 2V, RL = 100Ω 25 2.5 70 7 V/mV V/mV CMRR Common Mode Rejection Ratio VCM = VS – to 3.5V 85 109 dB – to 3.5V 79 109 CMRR Match (Channel-to-Channel) (Note 9) VCM = VS Input Common Mode Range PSRR Power Supply Rejection Ratio PSRR Match (Channel-to-Channel) (Note 9) VS VS+ = 2.5V to 10V, VS – = 0V VS+ = 2.5V to 10V, VS – = 0V – dB VS + V 78 97 dB 72 97 dB VOL Output Voltage Swing Low (Note 7) No Load ISINK = 5mA ISINK = 20mA 15 90 225 70 200 500 mV mV mV VOH Output Voltage Swing High (Note 7) No Load ISOURCE = 5mA ISOURCE = 20mA 20 130 450 80 260 850 mV mV mV ISC Short-Circuit Current IS Supply Current per Amplifier GBW Gain Bandwidth Product Frequency = 2MHz 70 MHz FPBW Full Power Bandwidth VO = 8VP-P 0.9 MHz SR Slew Rate AV = – 1, RL = 1k, VO = ±4V, Measured at VO = ±2V 20 V/μs HD Harmonic Distortion AV = 1, RL = 1k, VO = 2VP-P, fC = 500kHz –75 dBc tS Settling Time 0.01%, VSTEP = 5V, AV = 1V, RL = 1k 300 ns ΔG Differential Gain (NTSC) AV = 2, RL = 150Ω 0.35 % Δθ Differential Phase (NTSC) AV = 2, RL = 150Ω 0.2 deg 25 50 1.8 mA 3 mA 18012fc 6 LT1801/LT1802 ELECTRICAL CHARACTERISTICS The l denotes the specifications which apply over the temperature range of 0°C < TA < 70°C. VS = ± 5V, VCM = 0V, VOUT = 0V, unless otherwise noted. SYMBOL PARAMETER TYP MAX UNITS VOS Input Offset Voltage VCM = VS – VCM = VS – (MS8) VCM = VS – (DD) VCM = VS+ l l l l 200 220 290 0.75 800 1000 1300 4 μV μV μV mV ΔVOS Input Offset Shift VCM = VS – to VS+ – 1.5V l 45 675 μV Input Offset Voltage Match (Channel-to-Channel) (Note 9) VCM = VS – VCM = VS – (MS8) VCM = VS – (DD) l l l 240 300 340 1500 1700 1950 μV μV μV VOS TC IB CONDITIONS l 1.5 5 VCM = VS – + 1V VCM = VS+ – 0.2V VCM = VS – + 1V VCM = VS+ – 0.2V VCM = VS – + 1V VCM = VS+ – 0.2V l l 30 450 300 2000 nA nA l l 25 25 400 700 nA nA l l 25 25 300 300 nA nA Input Offset Voltage Drift (Note 8) Input Bias Current Input Bias Current Match (Channel-to-Channel) (Note 9) MIN μV/°C IOS Input Offset Current AVOL Large-Signal Voltage Gain VO = –4V to 4V, RL = 1k VO = –2V to 2V, RL = 100Ω l l 15 2 55 5 V/mV V/mV CMRR Common Mode Rejection Ratio VCM = VS – to 3.5V l 82 105 dB – to 3.5V l 76 105 l VS – VS+ = 2.5V to 10V, VS – = 0V VS+ = 2.5V to 10V, VS – = 0V l 74 91 dB l 68 93 dB CMRR Match (Channel-to-Channel) (Note 9) VCM = VS Input Common Mode Range PSRR Power Supply Rejection Ratio PSRR Match (Channel-to-Channel) (Note 9) dB VS + V VOL Output Voltage Swing Low (Note 7) No Load ISINK = 5mA ISINK = 20mA l l l 17 105 250 80 250 575 mV mV mV VOH Output Voltage Swing High (Note 7) No Load ISOURCE = 5mA ISOURCE = 20mA l l l 25 150 600 90 310 975 mV mV mV ISC Short-Circuit Current l IS Supply Current per Amplifier l 2.4 4 mA GBW Gain Bandwidth Product Frequency = 2MHz l 70 MHz SR Slew Rate AV = – 1, RL = 1k, VO = ±4V, Measured at VO = ±2V l 20 V/μs 22.5 45 mA The l denotes the specifications which apply over the temperature range of – 40°C < TA < 85°C. VS = ±5V, VCM = 0V, VOUT = 0V, unless otherwise noted. (Note 5) SYMBOL PARAMETER CONDITIONS TYP MAX UNITS VOS Input Offset Voltage VCM = VS – VCM = VS – (MS8) VCM = VS – (DD) VCM = VS+ l l l l MIN 350 350 350 0.75 1000 1200 1500 5 μV μV μV mV ΔVOS Input Offset Shift VCM = VS – to VS+ – 1.5V l 50 750 μV Input Offset Voltage Match (Channel-to-Channel) (Note 9) VCM = VS – VCM = VS – (MS8) VCM = VS – (DD) l l l 280 380 410 1700 1900 2100 μV μV μV 18012fc 7 LT1801/LT1802 ELECTRICAL CHARACTERISTICS The l denotes the specifications which apply over the temperature range of – 40°C < TA < 85°C. VS = ±5V, VCM = 0V, VOUT = 0V, unless otherwise noted. (Note 5) SYMBOL PARAMETER VOS TC IB CONDITIONS TYP MAX UNITS l MIN 1.5 5 μV/°C VCM = VS – + 1V VCM = VS+ – 0.2V VCM = VS – + 1V VCM = VS+ – 0.2V VCM = VS – + 1V VCM = VS+ – 0.2V l l 50 450 400 2250 nA nA l l 25 25 450 700 nA nA l l 25 25 350 350 nA nA Input Offset Voltage Drift (Note 8) Input Bias Current Input Bias Current Match (Channel-to-Channel) (Note 9) IOS Input Offset Current AVOL Large-Signal Voltage Gain VO = –4V to 4V, RL = 1k VO = –1V to 1V, RL = 100Ω l l CMRR Common Mode Rejection Ratio VCM = VS – to 3.5V l 81 104 dB CMRR Match (Channel-to-Channel) (Note 9) VCM = VS – to 3.5V Input Common Mode Range l 75 104 dB l VS – VS+ = 2.5V to 10V, VS – = 0V VS+ = 2.5V to 10V, VS – = 0V l 73 90 dB l 67 90 dB 20 110 180 100 275 400 mV mV mV 30 150 300 110 350 700 mV mV mV PSRR Power Supply Rejection Ratio PSRR Match (Channel-to-Channel) (Note 9) 12.5 2 55 5 V/mV V/mV VS + V VOL Output Voltage Swing Low (Note 7) No Load ISINK = 5mA ISINK = 10mA l l l VOH Output Voltage Swing High (Note 7) No Load ISOURCE = 5mA ISOURCE = 10mA l l l ISC Short-Circuit Current l IS Supply Current per Amplifier l 2.6 GBW Gain Bandwidth Product Frequency = 2MHz l 65 MHz SR Slew Rate AV = – 1, RL = 1k, VO = ±4V, Measured at VO = ±2V l 15 V/μs Note 1: Stresses beyond those listed under Absolute Maximum Ratings may cause permanent damage to the device. Exposure to any Absolute Maximum Rating condition for extended periods may affect device reliability and lifetime. Note 2: The inputs are protected by back-to-back diodes. If the differential input voltage exceeds 1.4V, the input current should be limited to less than 10mA. It is not 100% tested. Note 3: A heat sink may be required to keep the junction temperature below the absolute maximum rating when the output is shorted indefinitely. Note 4: The LT1801C/LT1801I and LT1802C/LT1802I are guaranteed functional over the temperature range of – 40°C to 85°C. Note 5: The LT1801C/LT1802C are guaranteed to meet specified performance from 0°C to 70°C. The LT1801C/LT1802C are designed, characterized and expected to meet specified performance from –40°C to 85°C but are not tested or QA sampled at these temperatures. The LT1801I/LT1802I are guaranteed to meet specified performance from –40°C to 85°C. 12.5 30 mA 4.5 mA Note 6: Minimum supply voltage is guaranteed by power supply rejection ratio test. Note 7: Output voltage swings are measured between the output and power supply rails. Note 8: This parameter is not 100% tested. Note 9: Matching parameters are the difference between amplifiers A and D and between B and C on the LT1802; between the two amplifiers on the LT1801. Note 10: Thermal resistance (θJA) varies with the amount of PC board metal connected to the package. The specified values are for short traces connected to the leads. If desired, the thermal resistance can be substantially reduced by connecting Pin 4 of the SO-8 and MS8, Pin 11 of the SO-14 or the underside metal of the DD package to a larger metal area (VS– trace). 18012fc 8 LT1801/LT1802 TYPICAL PERFORMANCE CHARACTERISTICS VOS Distribution, VCM = 0V (PNP Stage) VS = 5V, 0V VCM = 0V 25 20 15 10 35 30 25 20 15 10 5 –150 –50 50 150 INPUT OFFSET VOLTAGE (μV) 0 –2000 250 TA = 125°C 3 TA = 25°C 2 TA = –55°C 1 0 –1200 –400 400 1200 INPUT OFFSET VOLTAGE (μV) 18012 G01 1.0 0.8 INPUT BIAS CURRENT (μA) 300 200 TA = 25°C 100 0 –100 –200 TA = 125°C –300 –400 1 3 4 2 INPUT COMMON MODE VOLTAGE (V) 5 0.6 0.6 0.4 0.2 0 –0.2 –0.4 0.2 0 –1.0 0 2 3 4 5 1 INPUT COMMON MODE VOLTAGE (V) –40 –20 0 20 40 TEMPERATURE (°C) 60 80 18012 G06 Output Saturation Voltage vs Load Current (Output High) 10 TA = 125°C TA = 25°C 1 10 0.1 LOAD CURRENT (mA) 6 PNP ACTIVE VS = 5V, 0V VCM = 1V 18012 G05 0.1 0.001 0.01 0.3 –0.1 –60 –1 NPN ACTIVE VS = 5V, 0V VCM = 5V 0.4 –0.8 VS = 5V, 0V TA = –55°C 0.5 0.1 –0.6 1 0.01 3 4 5 6 7 8 9 10 11 12 TOTAL SUPPLY VOLTAGE (V) 0.7 Output Saturation Voltage vs Load Current (Output Low) 10 2 0.8 18012 G04 OUTPUT SATURATION VOLTAGE (V) 0 1 Input Bias Current vs Temperature VS = 5V, 0V TA = 25°C TA = 125°C TA = –55°C OUTPUT SATURATION VOLTAGE (V) 400 Input Bias Current vs Common Mode Voltage VS = 5V, 0V TYPICAL PART TA = –55°C 0 18012 G03 INPUT BIAS (μA) 500 2000 18012 G02 Offset Voltage vs Input Common Mode Voltage OFFSET VOLTAGE (μV) PER AMPLIFIER 5 0 –250 –500 Supply Current vs Supply Voltage 4 VS = 5V, 0V VCM = 5V 40 PERCENT OF UNITS (%) 30 PERCENT OF UNITS (%) 45 SUPPLY CURRENT (mA) 35 VOS Distribution, VCM = 5V (NPN Stage) 100 18012 G07 VS = 5V, 0V 1 0.1 TA = 125°C 0.01 TA = –55°C 0.001 0.01 TA = 25°C 1 10 0.1 LOAD CURRENT (mA) 100 18012 G08 18012fc 9 LT1801/LT1802 TYPICAL PERFORMANCE CHARACTERISTICS Output Short-Circuit Current vs Power Supply Voltage OUTPUT SHORT-CIRCUIT CURRENT (mA) TA = –55°C 0.4 0.2 TA = 25°C 0 –0.2 TA = 125°C –0.4 –0.6 0 1.5 2 2.5 3 3.5 4 4.5 TOTAL SUPPLY VOLTAGE (V) 5 70 60 50 40 30 20 10 0 –10 –20 –30 –40 –50 –60 –70 TA = 25°C TA = 125°C TA = –55°C SINKING TA = –55°C SOURCING TA = 125°C 2 4 2.5 4.5 3.5 3 POWER SUPPLY VOLTAGE (±V) Open-Loop Gain CHANGE IN OFFSET VOLTAGE (μV) CHANGE IN OFFSET VOLTAGE (μV) 1200 800 RL = 1k 0 –400 RL = 100Ω –1200 5 0.5 1 1.5 2 2.5 3 3.5 4 OUTPUT VOLTAGE (V) 4.5 –1200 2.0 1200 800 400 RL = 1k 0 –400 –800 RL = 100Ω –2000 5 –5 –4 –3 –2 –1 0 1 2 3 OUTPUT VOLTAGE (V) VS = ±5V 4 NOISE VOLTAGE (nV/√Hz) 90 VS = ±2.5V 70 VS = ±1.5V 1.0 TYPICAL PART 80 100 120 60 TIME AFTER POWER-UP (SECONDS) 20 40 TA = –55°C 0.5 0 –0.5 TA = 25°C TA = 125°C –1.0 –1.5 –2.0 15 30 –60 –45 –30 –15 0 OUTPUT CURRENT (mA) 5 45 60 18012 G14 VS = 5V, 0V 40 140 18012 G15 NPN ACTIVE VCM = 4.25V 30 20 10 50 0 VS = ±5V 50 100 40 3 Input Noise Voltage vs Frequency 120 60 2.5 1.5 60 80 1.5 2 1 OUTPUT VOLTAGE (V) 18012 G13 Warm-Up Drift vs Time 110 0.5 18012 G11 VS = ±5V RL TO GND 1600 18012 G12 OFFSET VOLTAGE (μV) RL = 100Ω –800 0 –1600 0 –400 –2000 –1200 –1600 –2000 RL = 1k 0 Offset Voltage vs Output Current 2000 VS = 5V, 0V RL TO GND –800 800 400 Open-Loop Gain 1600 400 1200 18012 G10 18012 G09 2000 VS = 3V, 0V RL TO GND 1600 –1600 TA = 25°C 1.5 5.5 Open-Loop Gain 2000 CHANGE IN OFFSET VOLTAGE (mV) CHANGE IN OFFSET VOLTAGE (mV) 0.6 CHANGE IN OFFSET VOLTAGE (μV) Minimum Supply Voltage PNP ACTIVE VCM = 2.5V 0 0.01 0.1 1 10 FREQUENCY (kHz) 100 18012 G16 18012fc 10 LT1801/LT1802 TYPICAL PERFORMANCE CHARACTERISTICS Input Current Noise vs Frequency 3.0 2000 VS = 5V, 0V PNP ACTIVE VCM = 2.5V 1.5 1.0 GAIN BANDWIDTH (MHz) INPUT NOISE VOLTAGE (nV) 2.0 1000 0 –1000 NPN ACTIVE VCM = 4.25V 0 0.01 1 10 FREQUENCY (kHz) 100 60 PHASE MARGIN 50 40 1 2 3 4 5 6 7 TIME (SECONDS) 8 9 50 40 30 AV = –1 RF = RG = 1k RL = 1k 25 VS = ±2.5V VS = ±5V 20 10 85 105 125 70 100 60 80 PHASE 50 60 40 40 30 20 GAIN 20 0 10 –20 0 –40 –20 10 –55 –35 –15 5 25 45 65 85 105 125 TEMPERATURE (°C) –30 0.01 –60 VS = ±2.5V VS = ±5V 0.1 –80 1 10 FREQUENCY (MHz) Gain vs Frequency (AV = 1) –100 100 300 18012 G22 18012 G21 18012 G20 Gain vs Frequency (AV = 2) 12 18 6 12 RL = 1k 15 CL = 10pF AV = 2 3 VS = ±2.5V 0 VS = ±5V GAIN (dB) RL = 1k 9 CL = 10pF AV = 1 GAIN (dB) 10 –10 15 20 –3 9 Gain and Phase vs Frequency OPEN-LOOP GAIN (dB) 60 PHASE MARGIN VS = ±5V 2 3 4 5 6 7 8 TOTAL SUPPLY VOLTAGE (V) PHASE (DEG) 60 PHASE MARGIN (DEG) GBW PRODUCT VS = ±5V SLEW RATE (V/μs) 30 PHASE MARGIN VS = ±2.5V 1 18012 G19 Slew Rate vs Temperature 35 80 5 25 45 65 TEMPERATURE (°C) 0 10 18012 G18 GBW PRODUCT VS = ±2.5V 90 –55 –35 –15 60 20 0 100 50 70 –2000 0.1 Gain Bandwidth and Phase Margin vs Temperature 70 GAIN BANDWIDTH PRODUCT 80 30 18012 G17 GAIN BANDWIDTH (MHz) TA = 25°C PHASE MARGIN (DEG) NOISE CURRENT (pA/√Hz) 100 VS = 5V, 0V 90 2.5 0.5 Gain Bandwidth and Phase Margin vs Supply Voltage 0.1Hz to 10Hz Input Voltage 9 6 VS = ±2.5V 3 VS = ±5V –6 0 –9 –3 –12 0.1 10 1 FREQUENCY (MHz) 100 300 18012 G23 –6 0.1 10 1 FREQUENCY (MHz) 100 300 18012 G24 18012fc 11 LT1801/LT1802 TYPICAL PERFORMANCE CHARACTERISTICS Common Mode Rejection Ratio vs Frequency 120 VS = ±2.5V COMMON MODE REJECTION RATIO (dB) OUTPUT IMPEDANCE (Ω) 100 AV = 10 10 AV = 1 1 AV = 2 0.1 0.01 0.001 0.1 1 10 FREQUENCY (MHz) 100 100 80 60 40 20 0 0.01 500 90 VS = 5V, 0V 0.1 1 10 FREQUENCY (MHz) Series Output Resistor vs Capacitive Load 50 60 50 OVERSHOOT (%) OVERSHOOT (%) 35 30 ROS = 20Ω 25 20 30 20 10 ROS = RL = 50Ω ROS = 10Ω 25 10 ROS = 20Ω ROS = RL = 50Ω 0 100 1000 CAPACITIVE LOAD (pF) 10000 10 100 1000 CAPACITIVE LOAD (pF) RL = 150Ω, 2ND RL = 1k, 2ND RL = 150Ω, 3RD –70 –80 –90 –100 RL = 1k, 3RD VS = 5V, 0V AV = 1 VOUT = 2VP-P –60 RL = 150Ω, 2ND –70 RL = 1k, 2ND RL = 150Ω, 3RD –80 –90 RL = 1k, 3RD 0.1 1 FREQUENCY (MHz) 10 18012 G30 4.5 4.4 AV = 2 4.3 AV = –1 4.2 4.1 4.0 VS = 5V, 0V RL = 1k 3.9 0.1 1 FREQUENCY (MHz) 100 4.6 VS = 5V, 0V AV = 2 VOUT = 2VP-P –60 10 Maximum Undistorted Output Signal vs Frequency OUTPUT VOLTAGE SWING (VP-P) DISTORTION (dBc) 0.1 1 FREQUENCY (MHz) 18012 G29 Distortion vs Frequency –110 0.01 0.01 –110 0.01 10000 18012 G28 –50 0 –100 5 0 –40 20 10 –50 35 15 10 40 30 Distortion vs Frequency 40 15 5 50 –40 45 ROS = 10Ω 40 POSITIVE SUPPLY 18012 G27 VS = 5V, 0V AV = 2 55 45 NEGATIVE SUPPLY 60 Series Output Resistor vs Capacitive Load VS = 5V, 0V AV = 1 55 70 18012 G26 18012 G25 60 VS = 5V, 0V TA = 25°C 80 –10 0.001 100 DISTORTION (dBc) 600 Power Supply Rejection Ratio vs Frequency POWER SUPPLY REJECTION RATIO (dB) Output Impedance vs Frequency 10 18012 G31 1k 10k 100k 1M FREQUENCY (Hz) 10M 18012 G32 18012fc 12 LT1801/LT1802 TYPICAL PERFORMANCE CHARACTERISTICS 5V Small-Signal Response 5V Large-Signal Response 50mV/DIV 0V 1V/DIV 0V VS = 5V, 0V AV = 1 RL = 1k 100ns/DIV VS = 5V, 0V AV = 1 RL = 1k 18012 G33 2V/DIV 50mV/DIV 0V 0V 200ns/DIV 18012 G34 ±5V Small-Signal Response ± 5V Large-Signal Response VS = ±5V AV = 1 RL = 1k 50ns/DIV VS = ±5V AV = 1 RL = 1k 18012 G35 50ns/DIV 18012 G36 Output Overdriven Recovery VIN 1V/DIV 0V VOUT 2V/DIV VS = 5V, 0V AV = 2 RL = 1k 100ns/DIV 18012 G37 18012fc 13 LT1801/LT1802 APPLICATIONS INFORMATION Circuit Description A pair of complementary common emitter stages Q14/Q15 that enable the output to swing from rail to rail constructs the output stage. The capacitors C2 and C3 form the local feedback loops that lower the output impedance at high frequency. These devices are fabricated on Linear Technology’s proprietary high speed complementary bipolar process. The LT1801/LT1802 have an input and output signal range that covers from the negative power supply to the positive power supply. Figure 1 depicts a simplified schematic of the amplifier. The input stage is comprised of two differential amplifiers, a PNP stage Q1/Q2 and an NPN stage Q3/Q4 that are active over the different ranges of common mode input voltage. The PNP differential pair is active between the negative supply to approximately 1.2V below the positive supply. As the input voltage moves closer toward the positive supply, the transistor Q5 will steer the tail current I1 to the current mirror Q6/Q7, activating the NPN differential pair and the PNP pair becomes inactive for the rest of the input common mode range up to the positive supply. Also at the input stage, devices Q17 to Q19 act to cancel the bias current of the PNP input pair. When Q1-Q2 are active, the current in Q16 is controlled to be the same as the current in Q1-Q2, thus the base current of Q16 is nominally equal to the base current of the input devices. The base current of Q16 is then mirrored by devices Q17-Q19 to cancel the base current of the input devices Q1-Q2. Power Dissipation The LT1801 amplifier is offered in a small package, SO-8, which has a thermal resistance of 190°C/W, θJA. So there is a need to ensure that the die’s junction temperature should not exceed 150°C. Junction temperature TJ is calculated from the ambient temperature TA, power dissipation PD and thermal resistance θJA: TJ = TA + (PD • θJA) The power dissipation in the IC is the function of the supply voltage, output voltage and the load resistance. For a given supply voltage, the worst-case power dissipation PDMAX occurs at the maximum supply current and the V+ R3 V+ + R5 V– ESDD1 I2 R4 + D1 ESDD2 Q12 Q11 I1 Q13 +IN D6 D8 D5 D7 –IN D2 Q5 I3 CC D3 BUFFER AND OUTPUT BIAS Q10 V+ D4 Q9 Q16 Q17 Q18 OUT V– Q1 Q2 ESDD3 V– + VBIAS Q4 Q3 ESDD4 Q15 C2 Q8 C1 Q19 Q7 Q14 Q6 R1 V– R2 18012 F01 Figure 1. LT1801/LT1802 Simplified Schematic Diagram 18012fc 14 LT1801/LT1802 APPLICATIONS INFORMATION output voltage is at half of either supply voltage (or the maximum swing is less than 1/2 supply voltage). PDMAX is given by: PDMAX = (VS • ISMAX) + (VS/2)2 /RL Example: An LT1801 in an SO-8 package operating on ±5V supplies and driving a 50Ω load, the worst-case power dissipation is given by: PDMAX = (10 • 4.5mA) + (2.5)2 /50 = 0.045 + 0.125 = 0.17W If both amplifiers are loaded simultaneously, then the total power dissipation is 0.34W. The maximum ambient temperature that the part is allowed to operate is: TA = TJ – (PDMAX • 190°C/W) = 150°C – (0.34W • 190°C/W) = 85°C Input Offset Voltage The offset voltage will change depending upon which input stage is active. The PNP input stage is active from the negative supply rail to 1.2V from the positive supply rail, then the NPN input stage is activated for the remaining input range up to the positive supply rail during which the PNP stage remains inactive. The offset voltage is typically less than 75μV in the range that the PNP input stage is active. Input Bias Current The LT1801/LT1802 employ a patent-pending technique to trim the input bias current to less than 250nA for the input common mode voltage of 0.2V above negative supply rail to 1.2V of the positive rail. The low input offset voltage and low input bias current of the LT1801/LT1802 provide precision performance especially for high source impedance applications. Output The LT1801/LT1802 can deliver a large output current, so the short-circuit current limit is set around 50mA to prevent damage to the device. Attention must be paid to keep the junction temperature of the IC below the absolute maximum rating of 150°C (refer to the Power Dissipation section) when the output is continuously short circuited. The output of the amplifier has reverse-biased diodes connected to each supply. If the output is forced beyond either supply, unlimited current will flow through these diodes. If the current is transient and limited to several hundred mA and the total supply voltage is less than 12.6V, the absolute maximum rating, no damage will occur to the device. Overdrive Protection When the input voltage exceeds the power supplies, two pairs of crossing diodes D1 to D4 will prevent the output from reversing polarity. If the input voltage exceeds either power supply by 700mV, diode D1/D2 or D3/D4 will turn on to keep the output at the proper polarity. For the phase reversal protection to perform properly, the input current must be limited to less than 10mA. If the amplifier is severely overdriven, an external resistor should be used to limit the overdrive current. The LT1801/LT1802’s input stages are also protected against a large differential input voltage of 1.4V or higher by a pair of back-back diodes D5/D8 to prevent the emitter-base breakdown of the input transistors. The current in these diodes should be limited to less than 10mA when they are active. The worst-case differential input voltage usually occurs when the input is driven while the output is shorted to ground in a unity gain configuration. In addition, the amplifier is protected against ESD strikes up to 3kV on all pins by a pair of protection diodes on each pin that are connected to the power supplies as shown in Figure 1. 18012fc 15 LT1801/LT1802 APPLICATIONS INFORMATION Capacitive Load Feedback Components The LT1801/LT1802 are optimized for high bandwidth, low power and precision applications. They can drive a capacitive load of about 75pF in a unity-gain configuration, and more for higher gain. When driving a larger capacitive load, a resistor of 10Ω to 50Ω should be connected between the output and the capacitive load to avoid ringing or oscillation. The feedback should still be taken from the output so that the resistor will isolate the capacitive load to ensure stability. Graphs on capacitive loads indicate the transient response of the amplifier when driving capacitive load with a specified series resistor. When feedback resistors are used to set up gain, care must be taken to ensure that the pole formed by the feedback resistors and the total capacitance at the inverting input does not degrade stability. For instance, the LT1801/LT1802 in a noninverting gain of 2, setup with two 5k resistors and a capacitance of 5pF (part plus PC board) will probably oscillate. The pole is formed at 12.7MHz that will reduce phase margin by 57 degrees when the crossover frequency of the amplifier is around 20MHz. A capacitor of 5pF or higher connected across the feedback resistor will eliminate any ringing or oscillation. TYPICAL APPLICATIONS Single 3V Supply, 1MHz, 4th Order Butterworth Filter Fast 1A Current Sense Amplifier The circuit shown on the first page of this data sheet makes use of the low voltage operation and the wide bandwidth of the LT1801 to create a DC accurate 1MHz 4th order lowpass filter powered from a 3V supply. The amplifiers are configured in the inverting mode for the lowest distortion and the output can swing rail-to-rail for maximum dynamic range. Also on the first page of this data sheet, the graph displays the frequency response of the filter. Stopband attenuation is greater than 100dB at 50MHz. With a 2.25VP-P, 250kHz input signal, the filter has harmonic distortion products of less than – 85dBc. Worst case output offset voltage is less than 6mV. A simple, fast current sense amplifier in Figure 2 is suitable for quickly responding to out-of-range currents. The circuit amplifies the voltage across the 0.1Ω sense resistor by a gain of 20, resulting in a conversion gain of 2V/A. The –3dB bandwidth of the circuit is 4MHz, and the uncertainty due to VOS and IB is less than 4mA. The minimum output voltage is 60mV, corresponding to 30mA. The large-signal response of the circuit is shown in Figure 3. IL 0A TO 1A 52.3Ω 3V + VOUT 0V TO 2V 1/2 LT1801 – 0.1Ω 52.3Ω 500mV/DIV 1k 0V 18012 F02 VOUT = 2 • IL f–3dB = 4MHz UNCERTAINTY DUE TO VOS, IB < 4mA Figure 2. Fast 1A Current Sense VS = 3V 50ns/DIV 18012 F03 Figure 3. Current Sense Amplifier Large-Signal Response 18012fc 16 LT1801/LT1802 TYPICAL APPLICATIONS Single Supply 1A Laser Driver Amplifier Figure 4 shows the LT1801 used in a 1A laser driver application. One of the reasons the LT1801 is well suited to this control task is that its 2.3V operation ensures that it will be awaked during power-up and operated before the circuit can otherwise cause significant current to flow in the 2.1V threshold laser diode. Driving the noninverting input of the LT1801 to a voltage VIN will control the turning on of the high current NPN transistor, FMMT619 and the laser diode. A current equal to VIN/R1 flows through the laser diode. The LT1801 low offset voltage and low input bias current allows it to control the current that flows through the laser diode precisely. The overall circuit is a 1A per volt V-to-I converter. Frequency compensation components R2 and C1 are selected for fast but zeroovershoot time domain response to avoid overcurrent conditions in the laser. The time domain response of this circuit, measured at R1 and given a 500mV 230ns input pulse, is shown in Figure 5. While the circuit is capable of 1A operation, the laser diode and the transistor are thermally limited due to power dissipation, so they must be operated at low duty cycles. 5V VIN DO NOT FLOAT + R3 10Ω Q1 ZETEX FMMT619 1/2 LT1801 – C1 39pF IR LASER INFINEON SFH495 R2 330Ω R1 1Ω 18012 F04 Figure 4. Single Supply 1A Laser Driver Amplifier 100mA/DIV 50ns/DIV 18012 F05 Figure 5. 500mA Pulse Response 18012fc 17 LT1801/LT1802 PACKAGE DESCRIPTION DD Package 8-Lead Plastic DFN (3mm × 3mm) (Reference LTC DWG # 05-08-1698) R = 0.115 TYP 5 0.38 ± 0.10 8 0.675 ±0.05 3.5 ±0.05 1.65 ±0.05 2.15 ±0.05 (2 SIDES) 1.65 ± 0.10 (2 SIDES) 3.00 ±0.10 (4 SIDES) PIN 1 PACKAGE TOP MARK (NOTE 6) OUTLINE (DD) DFN 1203 0.25 ± 0.05 4 0.25 ± 0.05 0.75 ±0.05 0.200 REF 0.50 BSC 2.38 ±0.05 (2 SIDES) 1 0.50 BSC 2.38 ±0.10 (2 SIDES) 0.00 – 0.05 BOTTOM VIEW—EXPOSED PAD RECOMMENDED SOLDER PAD PITCH AND DIMENSIONS NOTE: 1. DRAWING TO BE MADE A JEDEC PACKAGE OUTLINE M0-229 VARIATION OF (WEED-1) 2. DRAWING NOT TO SCALE 3. ALL DIMENSIONS ARE IN MILLIMETERS 4. DIMENSIONS OF EXPOSED PAD ON BOTTOM OF PACKAGE DO NOT INCLUDE MOLD FLASH. MOLD FLASH, IF PRESENT, SHALL NOT EXCEED 0.15mm ON ANY SIDE 5. EXPOSED PAD SHALL BE SOLDER PLATED 6. SHADED AREA IS ONLY A REFERENCE FOR PIN 1 LOCATION ON TOP AND BOTTOM OF PACKAGE MS8 Package 8-Lead Plastic MSOP (Reference LTC DWG # 05-08-1660 Rev F) 0.889 ± 0.127 (.035 ± .005) 5.23 (.206) MIN 3.20 – 3.45 (.126 – .136) 3.00 ± 0.102 (.118 ± .004) (NOTE 3) 0.65 (.0256) BSC 0.42 ± 0.038 (.0165 ± .0015) TYP 8 7 6 5 0.52 (.0205) REF RECOMMENDED SOLDER PAD LAYOUT 0.254 (.010) 3.00 ± 0.102 (.118 ± .004) (NOTE 4) 4.90 ± 0.152 (.193 ± .006) DETAIL “A” 0° – 6° TYP GAUGE PLANE 1 0.53 ± 0.152 (.021 ± .006) DETAIL “A” 2 3 4 1.10 (.043) MAX 0.86 (.034) REF 0.18 (.007) SEATING PLANE 0.22 – 0.38 (.009 – .015) TYP 0.65 (.0256) BSC 0.1016 ± 0.0508 (.004 ± .002) MSOP (MS8) 0307 REV F NOTE: 1. DIMENSIONS IN MILLIMETER/(INCH) 2. DRAWING NOT TO SCALE 3. DIMENSION DOES NOT INCLUDE MOLD FLASH, PROTRUSIONS OR GATE BURRS. MOLD FLASH, PROTRUSIONS OR GATE BURRS SHALL NOT EXCEED 0.152mm (.006") PER SIDE 4. DIMENSION DOES NOT INCLUDE INTERLEAD FLASH OR PROTRUSIONS. INTERLEAD FLASH OR PROTRUSIONS SHALL NOT EXCEED 0.152mm (.006") PER SIDE 5. LEAD COPLANARITY (BOTTOM OF LEADS AFTER FORMING) SHALL BE 0.102mm (.004") MAX 18012fc 18 LT1801/LT1802 PACKAGE DESCRIPTION S8 Package 8-Lead Plastic Small Outline (Narrow .150 Inch) (Reference LTC DWG # 05-08-1610) .189 – .197 (4.801 – 5.004) NOTE 3 .045 ±.005 .050 BSC 7 8 .245 MIN 5 6 .160 ±.005 .150 – .157 (3.810 – 3.988) NOTE 3 .228 – .244 (5.791 – 6.197) .030 ±.005 TYP 1 RECOMMENDED SOLDER PAD LAYOUT .010 – .020 × 45° (0.254 – 0.508) 3 2 4 .053 – .069 (1.346 – 1.752) .008 – .010 (0.203 – 0.254) .004 – .010 (0.101 – 0.254) 0°– 8° TYP .016 – .050 (0.406 – 1.270) .050 (1.270) BSC .014 – .019 (0.355 – 0.483) TYP NOTE: 1. DIMENSIONS IN INCHES (MILLIMETERS) 2. DRAWING NOT TO SCALE 3. THESE DIMENSIONS DO NOT INCLUDE MOLD FLASH OR PROTRUSIONS. MOLD FLASH OR PROTRUSIONS SHALL NOT EXCEED .006" (0.15mm) SO8 0303 S Package 14-Lead Plastic Small Outline (Narrow .150 Inch) (Reference LTC DWG # 05-08-1610) .337 – .344 (8.560 – 8.738) NOTE 3 .045 ±.005 .050 BSC 14 N 12 11 10 9 8 N .245 MIN .160 ±.005 .150 – .157 (3.810 – 3.988) NOTE 3 .228 – .244 (5.791 – 6.197) 1 .030 ±.005 TYP 13 2 3 N/2 N/2 RECOMMENDED SOLDER PAD LAYOUT 1 .010 – .020 × 45° (0.254 – 0.508) .008 – .010 (0.203 – 0.254) 2 3 4 5 6 .053 – .069 (1.346 – 1.752) .004 – .010 (0.101 – 0.254) 0° – 8° TYP .016 – .050 (0.406 – 1.270) NOTE: 1. DIMENSIONS IN .014 – .019 (0.355 – 0.483) TYP 7 .050 (1.270) BSC INCHES (MILLIMETERS) 2. DRAWING NOT TO SCALE 3. THESE DIMENSIONS DO NOT INCLUDE MOLD FLASH OR PROTRUSIONS. MOLD FLASH OR PROTRUSIONS SHALL NOT EXCEED .006" (0.15mm) S14 0502 18012fc Information furnished by Linear Technology Corporation is believed to be accurate and reliable. However, no responsibility is assumed for its use. Linear Technology Corporation makes no representation that the interconnection of its circuits as described herein will not infringe on existing patent rights. 19 LT1801/LT1802 TYPICAL APPLICATION Low Power High Voltage Amplifier Certain materials used in optical applications have characteristics that change due to the presence and strength of a DC electric field. The voltage applied across these materials should be precisely controlled to maintain desired properties, sometimes as high as 100’s of volts. The materials are not conductive and represent a capacitive load. The circuit of Figure 6 shows the LT1801 used in an amplifier capable of a 250V output swing and providing precise DC output voltage. When no signal is present, the op 130V 5V 4.99k 10k 1k Q5 amp output sits at about mid-supply. Transistors Q1 and Q3 create bias voltages for Q2 and Q4, which are forced into a low quiescent current by degeneration resistors R4 and R5. When a transient signal arrives at VIN, the op amp output moves and causes the current in Q2 or Q4 to change depending on the signal polarity. The current, limited by the clipping of the LT1801 output and the 3kΩ of total emitter degeneration, is mirrored to the output devices to drive the capacitive load. The LT1801 output then returns to near mid-supply, providing the precise DC output voltage to the load. The attention to limit the current of the output devices minimizes power dissipation thus allowing for dense layout, and inherits better reliability. Figure 7 shows the time domain response of the amplifier providing a 200V output swing into a 100pF load. Q6 0.1μF 5V Q2 Q1 + R2 2k 5V R4 2k R6 2k R5 2k R7 2k VOUT 1/2 LT1801 – Q3 VIN 2V/DIV MATERIAL UNDER ELECTRIC FIELD 100pF Q4 VIN R1 2k C1 39pF C2 8pF 150V R3 200k 10k Q7 Q8 1k 4.99k –130V AV = VOUT/VIN = –100 ±130V SUPPLY IQ = 130μA OUTPUT SWING = ±128.8V OUTPUT OFFSET ≅ 20mV OUTPUT SHORT-CIRCUIT CURRENT ≅ 3mA 10% TO 90% RISE TIME ≅ 8μs, 200V OUTPUT STEP SMALL-SIGNAL BANDWIDTH ≅ 150kHz Q1, Q2, Q7, Q8: ON SEMI MPSA42 Q3, Q4, Q5, Q6: ON SEMI MPSA92 VOUT 50V/DIV 10μs/DIV 18012 F07 18012 F06 Figure 7. Large-Signal Time Domain Response of the Amplifier Figure 6. Low Power, High Voltage Amplifier RELATED PARTS PART NUMBER DESCRIPTION LT1399 COMMENTS Triple 300MHz Current Feedback Amplifier LT1498/LT1499 Dual/Quad 10MHz, 6V/μs Rail-to-Rail Input and Output 0.1dB Gain Flatness to 150MHz, Shutdown C-Load™ Op Amps High DC Accuracy, 475μV VOS(MAX), 4μV/°C Max Drift LT1630/LT1631 Dual/Quad 30MHz, 10V/μs Rail-to-Rail Input and Output Op Amps High DC Accuracy, 525μV VOS(MAX), 70mA Output Current, Max Supply Current 4.4mA per Amplifier LT1800 Single Version of LT1801/LT1802 80MHz, 25V/μs Low Power Rail-to-Rail Input/Output Precision Op Amp LT1806/LT1807 Single/Dual 325MHz, 140V/μs Rail-to-Rail Input and Output Op Amps High DC Accuracy, 550μV VOS(MAX), Low Noise 3.5nV/√Hz, Low Distortion –80dB at 5MHz, Power-Down (LT1806) LT1809/LT1810 350V/μs Slew Rate, Low Distortion –90dBc at 5MHz, Power-Down (LT1809) Single/Dual 180MHz Rail-to-Rail Input/Output Op Amps C-Load is a trademark of Linear Technology Corporation 18012fc 20 Linear Technology Corporation LT 0309 REV C • PRINTED IN USA 1630 McCarthy Blvd., Milpitas, CA 95035-7417 (408) 432-1900 ● FAX: (408) 434-0507 ● www.linear.com © LINEAR TECHNOLOGY CORPORATION 2002