LT3470HDDB#TRMPBF

LT3470 Micropower Buck Regulator with Integrated Boost and Catch Diodes DESCRIPTION FEATURES Low Quiescent Current: 26µA at 12VIN to 3.3VOUT n Integrated Boost and Catch Diodes n Input Range: 4V to 40V n Low Output Ripple: 3V 5 50 0 –50 –25 125 BIAS Quiescent Current (Bias > 3V) vs Temperature 50 300 100 3470 G03 350 200 0 25 50 75 TEMPERATURE (°C) 3470 G02 Top and Bottom Switch Current Limits (VFB = 0V) vs Temperature 250 –25 0 25 50 75 100 125 150 TEMPERATURE (°C) 3470 G04 3470 G05 0 –50 –25 0 25 50 75 100 125 150 TEMPERATURE (°C) 3470 G06 Rev. E 4 For more information www.analog.com LT3470 TYPICAL PERFORMANCE CHARACTERISTICS FB Bias Current (VFB = 1V) vs Temperature SHDN Bias Current vs Temperature 9 VSHDN = 36V 8 FB Bias Current (VFB = 0V) vs Temperature 60 120 50 100 40 80 6 5 4 3 2 VSHDN = 2.5V FB CURRENT (µA) FB CURRENT (nA) SHDN CURRENT (µA) 7 30 20 60 40 20 10 1 0 –50 –25 0 0 –50 –25 25 50 75 100 125 150 TEMPERATURE (°C) 0 300 Catch Diode VF (IF = 100mA) vs Temperature 0.8 0.7 0.7 0.6 100 SCHOTTKY VF (V) 0.6 SCHOTTKY VF (V) SWITCH VCESAT (mV) 250 150 0.5 0.4 0.3 0.2 50 0 0 –50 –25 25 50 75 100 125 150 TEMPERATURE (°C) 0 CATCH BOOST SWITCH VCESAT (mV) 45 35 30 25 20 15 10 0 –50 –25 700 14 600 12 500 400 300 200 0 25 50 75 100 125 150 TEMPERATURE (°C) 25 50 75 100 125 150 TEMPERATURE (°C) 0 10 8 6 4 2 100 5 0 BOOST Pin Current Switch VCESAT 40 0.2 3470 G12 BOOST PIN CURRENT (mA) 50 0.3 3470 G11 Diode Leakage (VR = 36V) vs Temperature 55 0.4 0 –50 –25 25 50 75 100 125 150 TEMPERATURE (°C) 3470 G10 60 0.5 0.1 0.1 0 –50 –25 25 50 75 100 125 150 TEMPERATURE (°C) 3470 G09 Boost Diode VF (IF = 50mA) vs Temperature Switch VCESAT (ISW = 100mA) vs Temperature 200 0 3470 G08 3470 G07 SCHOTTKY DIODE LEAKAGE (µA) 0 –50 –25 25 50 75 100 125 150 TEMPERATURE (°C) 0 100 200 300 SWITCH CURRENT (mA) 400 3470 G14 3470 G13 0 0 100 200 300 SWITCH CURRENT (mA) 400 3470 G15 Rev. E For more information www.analog.com 5 LT3470 TYPICAL PERFORMANCE CHARACTERISTICS Boost Diode Forward Voltage Catch Diode Forward Voltage 1.0 900 0.8 700 SCHOTTKY VF (V) SCHOTTKY VF (V) 800 0.6 0.4 600 500 400 300 200 0.2 100 0 200 100 300 CATCH DIODE CURRENT (mA) 0 0 400 100 50 150 BOOST DIODE CURRENT (mA) 0 3470 G17 3470 G16 6.0 Minimum Input Voltage, VOUT = 3.3V TA = 25°C 200 8 Minimum Input Voltage, VOUT = 5V TA = 25°C VIN TO START VIN TO START 5.5 INPUT VOLTAGE (V) INPUT VOLTAGE (V) 7 5.0 4.5 4.0 VIN TO RUN 6 VIN TO RUN 5 3.5 3.0 0 50 100 150 LOAD CURRENT (mA) 200 4 0 3470 G18 100 150 50 LOAD CURRENT (mA) 200 3470 G19 Rev. E 6 For more information www.analog.com LT3470 PIN FUNCTIONS (ThinSOT/DD) SHDN (Pin 1/Pin 8): The SHDN pin is used to put the LT3470 in shutdown mode. Tie to ground to shut down the LT3470. Apply 2V or more for normal operation. If the shutdown feature is not used, tie this pin to the VIN pin. NC (Pin 2/Pin 7): This pin can be left floating or connected to VIN. VIN (Pin 3/Pin 6): The VIN pin supplies current to the LT3470’s internal regulator and to the internal power switch. This pin must be locally bypassed. GND (Pin 4/Pin 5): Tie the GND pin to a local ground plane below the LT3470 and the circuit components. Return the feedback divider to this pin. SW (Pin 5/Pin 4): The SW pin is the output of the internal power switch. Connect this pin to the inductor, catch diode and boost capacitor. BOOST (Pin 6/Pin 3): The BOOST pin is used to provide a drive voltage, which is higher than the input voltage, to the internal bipolar NPN power switch. BIAS (Pin 7/Pin 2): The BIAS pin connects to the internal boost Schottky diode and to the internal regulator. Tie to VOUT when VOUT > 2V or to VIN otherwise. When VBIAS > 3V the BIAS pin will supply current to the internal regulator. FB (Pin 8/Pin 1): The LT3470 regulates its feedback pin to 1.25V. Connect the feedback resistor divider tap to this pin. Set the output voltage according to VOUT = 1.25V (1 + R1/R2) or R1 = R2 (VOUT/1.25 – 1). Exposed Pad (DD, Pin 9): Ground. Must be soldered to PCB. BLOCK DIAGRAM VIN VIN BIAS C1 + – BOOST 500ns ONE SHOT R Q′ S Q C3 SW – NC SHDN VREF 1.25V gm GND FB R2 VOUT C2 + ENABLE Burst Mode DETECT L1 R1 3470 BD Rev. E For more information www.analog.com 7 LT3470 OPERATION The LT3470 uses a hysteretic control scheme in conjunction with Burst Mode operation to provide low output ripple and low quiescent current while using a tiny inductor and capacitors. Operation can best be understood by studying the Block Diagram. An error amplifier measures the output voltage through an external resistor divider tied to the FB pin. If the FB voltage is higher than VREF, the error amplifier will shut off all the high power circuitry, leaving the LT3470 in its micropower state. As the FB voltage falls, the error amplifier will enable the power section, causing the chip to begin switching, thus delivering charge to the output capacitor. If the load is light the part will alternate between micropower and switching states to keep the output in regulation (See Figure 1a). At higher loads the part will switch continuously while the error amp servos the top and bottom current limits to regulate the FB pin voltage to 1.25V (See Figure 1b). The switching action is controlled by an RS latch and two current comparators as follows: The switch turns on, and the current through it ramps up until the top current comparator trips and resets the latch causing the switch to turn off. While the switch is off, the inductor current ramps down through the catch diode. When both the bottom current comparator trips and the minimum off-time one-shot expires, the latch turns the switch back on thus completing a full cycle. The hysteretic action of this control scheme results in a switching frequency that depends on inductor value, input and output voltage. Since the switch only turns on when the catch diode current falls below threshold, the part will automatically switch slower to keep inductor current under control during start-up or short-circuit conditions. The switch driver operates from either the input or from the BOOST pin. An external capacitor and internal diode is used to generate a voltage at the BOOST pin that is higher than the input supply. This allows the driver to fully saturate the internal bipolar NPN power switch for efficient operation. If the SHDN pin is grounded, all internal circuits are turned off and VIN current reduces to the device leakage current, typically a few nA. 200mA LOAD NO LOAD VOUT 20mV/DIV VOUT 20mV/DIV IL 100mA/DIV IL 100mA/DIV 1µs/DIV 1ms/DIV 150mA LOAD 10mA LOAD VOUT 20mV/DIV VOUT 20mV/DIV IL 100mA/DIV IL 100mA/DIV 5µs/DIV 3470 F01a (1a) Burst Mode Operation 1µs/DIV 3470 F1b (1b) Continuous Operation Figure 1. Operating Waveforms of the LT3470 Converting 12V to 5V Using a 33µH Inductor and 10µF Output Capacitor Rev. E 8 For more information www.analog.com LT3470 APPLICATIONS INFORMATION Input Voltage Range The minimum input voltage required to generate a particular output voltage in an LT3470 application is limited by either its 4V undervoltage lockout or by its maximum duty cycle. The duty cycle is the fraction of time that the internal switch is on and is determined by the input and output voltages: DC = VOUT + VD VIN – VSW + VD where VD is the forward voltage drop of the catch diode (~0.6V) and VSW is the voltage drop of the internal switch at maximum load (~0.4V). Given DCMAX = 0.90, this leads to a minimum input voltage of: This analysis assumes the part has started up such that the capacitor tied between the BOOST and SW pins is charged to more than 2V. For proper start-up, the minimum input voltage is limited by the boost circuit as detailed in the section BOOST Pin Considerations. The maximum input voltage is limited by the absolute maximum VIN rating of 40V, provided an inductor of sufficient value is used. Inductor Selection The switching action of the LT3470 during continuous operation produces a square wave at the SW pin that results in a triangle wave of current in the inductor. The hysteretic mode control regulates the top and bottom current limits (see Electrical Characteristics) such that the average inductor current equals the load current. For safe operation, it must be noted that the LT3470 cannot turn the switch on for less than ~150ns. If the inductor is small and the input voltage is high, the current through the switch may exceed safe operating limit before the LT3470 is able to turn off. To prevent this from happening, the following equation provides a minimum inductor value: VIN(MAX) • t ON-TIME(MIN) f= ( 1– DC ) ( VD + VOUT ) L • ∆IL where f is the switching frequency, ∆IL is the ripple current in the inductor (~150mA), VD is the forward voltage drop of the catch diode, and VOUT is the desired output voltage. If the application circuit is intended to operate at high duty cycles (VIN close to VOUT), it is important to look at the calculated value of the switch off-time: ⎛V + VD ⎞ + VSW – VD VIN(MIN) = ⎜ OUT ⎝ DCMAX ⎟⎠ L MIN = where VIN(MAX) is the maximum input voltage for the application, tON-TIME(MIN) is ~150ns and IMAX is the maximum allowable increase in switch current during a minimum switch on-time (150mA). While this equation provides a safe inductor value, the resulting application circuit may switch at too high a frequency to yield good efficiency. It is advised that switching frequency be below 1.2MHz during normal operation: t OFF-TIME = 1– DC f The calculated tOFF-TIME should be more than LT3470’s minimum tOFF-TIME (See Electrical Characteristics), so the application circuit is capable of delivering full rated output current. If the full output current of 200mA is not required, the calculated tOFF-TIME can be made less than minimum tOFF-TIME possibly allowing the use of a smaller inductor. See Table 1 for an inductor value selection guide. Table 1. Recommended Inductors for Loads up to 200mA VOUT VIN UP TO 16V VIN UP TO 40V 2.5V 10µH 33µH 3.3V 10µH 33µH 5V 15µH 33µH 12V 33µH 47µH Choose an inductor that is intended for power applications. Table 2 lists several manufacturers and inductor series. For robust output short-circuit protection at high VIN (up to 40V) use at least a 33µH inductor with a minimum 450mA saturation current. If short-circuit performance is not required, inductors with ISAT of 300mA or more may I MAX Rev. E For more information www.analog.com 9 LT3470 APPLICATIONS INFORMATION Table 2. Inductor Vendors VENDOR URL PART SERIES INDUCTANCE RANGE (µH) SIZE (mm) Coilcraft www.coilcraft.com DO1605 ME3220 DO3314 10 to 47 10 to 47 10 to 47 1.8 × 5.4 × 4.2 2.0 × 3.2 × 2.5 1.4 × 3.3 × 3.3 Sumida www.sumida.com CR32 CDRH3D16/HP CDRH3D28 CDRH2D18/HP 10 to 47 10 to 33 10 to 47 10 to 15 3.0 × 3.8 × 4.1 1.8 × 4.0 × 4.0 3.0 × 4.0 × 4.0 2.0 × 3.2 × 3.2 Toko www.tokoam.com DB320C D52LC 10 to 27 10 to 47 2.0 × 3.8 × 3.8 2.0 × 5.0 × 5.0 Wurth Elektronik www.we-online.com WE-PD2 Typ S WE-TPC Typ S 10 to 47 10 to 22 3.2 × 4.0 × 4.5 1.6 × 3.8 × 3.8 Coiltronics www.cooperet.com SD10 10 to 47 1.0 × 5.0 × 5.0 Murata www.murata.com LQH43C LQH32C 10 to 47 10 to 15 2.6 × 3.2 × 4.5 1.6 × 2.5 × 3.2 be used. It is important to note that inductor saturation current is reduced at high temperatures—see inductor vendors for more information. Input Capacitor Step-down regulators draw current from the input supply in pulses with very fast rise and fall times. The input capacitor is required to reduce the resulting voltage ripple at the VIN pin of the LT3470 and to force this switching current into a tight local loop, minimizing EMI. The input capacitor must have low impedance at the switching frequency to do this effectively. A 1µF to 2.2µF ceramic capacitor satisfies these requirements. If the input source impedance is high, a larger value capacitor may be required to keep input ripple low. In this case, an electrolytic of 10µF or more in parallel with a 1µF ceramic is a good combination. Be aware that the input capacitor is subject to large surge currents if the LT3470 circuit is connected to a low impedance supply, and that some electrolytic capacitors (in particular tantalum) must be specified for such use. Output Capacitor and Output Ripple The output capacitor filters the inductor’s ripple current and stores energy to satisfy the load current when the LT3470 is quiescent. In order to keep output voltage ripple low, the impedance of the capacitor must be low at the LT3470’s switching frequency. The capacitor’s equivalent series resistance (ESR) determines this impedance. Choose one with low ESR intended for use in switching regulators. The contribution to ripple voltage due to the ESR is approximately ILIM • ESR. ESR should be less than ~150mΩ. The value of the output capacitor must be large enough to accept the energy stored in the inductor without a large change in output voltage. Setting this voltage step equal to 1% of the output voltage, the output capacitor must be: ⎛ C OUT > 50 • L • ⎜ ⎝ ILIM ⎞ VOUT ⎟⎠ 2 where ILIM is the top current limit with VFB = 0V (see Electrical Characteristics). For example, an LT3470 producing 3.3V with L = 33µH requires 22µF. The calculated value can be relaxed if small circuit size is more important than low output ripple. Sanyo’s POSCAP series in B-case and provides very good performance in a small package for the LT3470. Similar performance in traditional tantalum capacitors requires a larger package (C-case). With a high quality capacitor filtering the ripple current from the inductor, the output voltage ripple is determined by the delay in the LT3470’s feedback comparator. This ripple can be reduced further by adding a small (typically 22pF) phase lead capacitor between the output and the feedback pin. Rev. E 10 For more information www.analog.com LT3470 APPLICATIONS INFORMATION Ceramic Capacitors BOOST and BIAS Pin Considerations Ceramic capacitors are small, robust and have very low ESR. However, ceramic capacitors can cause problems when used with the LT3470. Not all ceramic capacitors are suitable. X5R and X7R types are stable over temperature and applied voltage and give dependable service. Other types, including Y5V and Z5U have very large temperature and voltage coefficients of capacitance. In an application circuit they may have only a small fraction of their nominal capacitance resulting in much higher output voltage ripple than expected. Capacitor C3 and the internal boost Schottky diode (see Block Diagram) are used to generate a boost voltage that is higher than the input voltage. In most cases a 0.22µF capacitor will work well. Figure 2 shows two ways to arrange the boost circuit. The BOOST pin must be more than 2.5V above the SW pin for best efficiency. For outputs of 3.3V and above, the standard circuit (Figure 2a) is best. For outputs between 2.5V and 3V, use a 0.47µF. For lower output voltages the boost diode can be tied to the input Ceramic capacitors are piezoelectric. The LT3470’s switching frequency depends on the load current, and at light loads the LT3470 can excite the ceramic capacitor at audio frequencies, generating audible noise. Since the LT3470 operates at a lower current limit during Burst Mode operation, the noise is typically very quiet to a casual ear. If this audible noise is unacceptable, use a high performance electrolytic capacitor at the output. The input capacitor can be a parallel combination of a 2.2µF ceramic capacitor and a low cost electrolytic capacitor. A final precaution regarding ceramic capacitors concerns the maximum input voltage rating of the LT3470. A ceramic input capacitor combined with trace or cable inductance forms a high quality (under damped) tank circuit. If the LT3470 circuit is plugged into a live supply, the input voltage can ring to twice its nominal value, possibly exceeding the LT3470’s rating. This situation is easily avoided; see the Hot-Plugging Safely section. VIN VIN BOOST C3 0.22µF LT3470 VOUT SW BIAS GND VBOOST – VSW ≅ VOUT MAX VBOOST ≅ VIN + VOUT (2a) VIN VIN BOOST C3 0.22µF LT3470 BIAS SW VOUT GND 3470 F02 VBOOST – VSW ≅ VIN MAX VBOOST ≅ 2VIN (2b) Figure 2. Two Circuits for Generating the Boost Voltage Table 3. Capacitor Vendors VENDOR PHONE URL PART SERIES COMMENTS Panasonic (714) 373-7366 www.panasonic.com Ceramic, Polymer, Tantalum EEF Series Kemet (864) 963-6300 www.kemet.com Ceramic, Tantalum T494, T495 Sanyo (408) 749-9714 www.sanyovideo.com Ceramic, Polymer, Tantalum POSCAP Murata (404) 436-1300 www.murata.com Ceramic www.avxcorp.com Ceramic, Tantalum www.taiyo-yuden.com Ceramic AVX Taiyo Yuden (864) 963-6300 TPS Series Rev. E For more information www.analog.com 11 LT3470 APPLICATIONS INFORMATION (Figure 2b). The circuit in Figure 2a is more efficient because the BOOST pin current and BIAS pin quiescent current comes from a lower voltage source. You must also be sure that the maximum voltage ratings of the BOOST and BIAS pins are not exceeded. The minimum operating voltage of an LT3470 application is limited by the undervoltage lockout (4V) and by the maximum duty cycle as outlined in a previous section. For proper start-up, the minimum input voltage is also limited by the boost circuit. If the input voltage is ramped slowly, or the LT3470 is turned on with its SHDN pin when the output is already in regulation, then the boost capacitor may not be fully charged. The plots in Figure 3 show minimum Minimum Input Voltage, VOUT = 3.3V 6.0 TA = 25°C VIN TO START INPUT VOLTAGE (V) 5.5 5.0 4.5 4.0 VIN TO RUN 3.5 3.0 0 50 100 150 LOAD CURRENT (mA) 200 3470 G18 Minimum Input Voltage, VOUT = 5V 8 Shorted Input Protection If the inductor is chosen so that it won’t saturate excessively at the top switch current limit maximum of 450mA, an LT3470 buck regulator will tolerate a shorted output even if VIN = 40V. There is another situation to consider in systems where the output will be held high when the input to the LT3470 is absent. This may occur in battery charging applications or in battery backup systems where a battery or some other supply is diode OR-ed with the LT3470’s output. If the VIN pin is allowed to float and the SHDN pin is held high (either by a logic signal or because it is tied to VIN), then the LT3470’s internal circuitry will pull its quiescent current through its SW pin. This is fine if your system can tolerate a few mA in this state. If you ground the SHDN pin, the SW pin current will drop to essentially zero. However, if the VIN pin is grounded while the output is held high, then parasitic diodes inside the LT3470 can pull large currents from the output through the SW pin and the VIN pin. Figure 4 shows a circuit that will run only when the input voltage is present and that protects against a shorted or reversed input. TA = 25°C D1 VIN TO START VIN 7 INPUT VOLTAGE (V) VIN to start and to run. At light loads, the inductor current becomes discontinuous and the effective duty cycle can be very high. This reduces the minimum input voltage to approximately 300mV above VOUT. At higher load currents, the inductor current is continuous and the duty cycle is limited by the maximum duty cycle of the LT3470, requiring a higher input voltage to maintain regulation. VIN 100k 6 SHDN VOUT SW BIAS VIN TO RUN 1M 5 4 BOOST LT3470 SOT-23 GND FB BACKUP 3470 F04 0 100 150 50 LOAD CURRENT (mA) 200 3470 G19 Figure 3. The Minimum Input Voltage Depends on Output Voltage, Load Current and Boost Circuit Figure 4. Diode D1 Prevents a Shorted Input from Discharging a Backup Battery Tied to the Output; It Also Protects the Circuit from a Reversed Input. The LT3470 Runs Only When the Input Is Present Hot-Plugging Safely Rev. E 12 For more information www.analog.com LT3470 APPLICATIONS INFORMATION PCB Layout For proper operation and minimum EMI, care must be taken during printed circuit board layout. Note that large, switched currents flow in the power switch, the internal catch diode and the input capacitor. The loop formed by these components should be as small as possible. Furthermore, the system ground should be tied to the regulator ground in only one place; this prevents the switched current from injecting noise into the system ground. These components, along with the inductor and output capacitor, should be placed on the same side of the circuit board, and their connections should be made on that layer. Place a local, unbroken ground plane below these components, and tie this ground plane to system ground at one location, ideally at the ground terminal of the output capacitor C2. Additionally, the SW and BOOST nodes should be kept as small as possible. Unshielded inductors can induce noise in the feedback path resulting in instability and increased output ripple. To avoid this problem, use vias to route the VOUT trace under the ground plane to the feedback divider (as shown in Figure 5). Finally, keep the FB node as small as possible so that the ground pin and ground traces will shield it from the SW and BOOST nodes. Figure 5 shows component placement with trace, ground plane and via locations. Include vias near the GND pin, or pad, of the LT3470 to help remove heat from the LT3470 to the ground plane. SHDN VIN SHDN VIN C1 GND GND C2 VIAS TO FEEDBACK DIVIDER VIAS TO LOCAL GROUND PLANE OUTLINE OF LOCAL GROUND PLANE VOUT VOUT 3470 F05 (5a) (5b) Figure 5. A Good PCB Layout Ensures Proper, Low EMI Operation Rev. E For more information www.analog.com 13 LT3470 APPLICATIONS INFORMATION Hot-Plugging Safely The small size, robustness and low impedance of ceramic capacitors make them an attractive option for the input bypass capacitor of LT3470. However, these capacitors can cause problems if the LT3470 is plugged into a live supply (see Linear Technology Application Note 88 for a complete discussion). The low loss ceramic capacitor combined with stray inductance in series with the power source forms an under damped tank circuit, and the voltage at the VIN pin of the LT3470 can ring to twice the nominal input voltage, possibly exceeding the LT3470’s rating and damaging the part. If the input supply is poorly controlled or the user will be plugging the LT3470 into an energized supply, the input network should be designed to prevent this overshoot. Figure 6 shows the waveforms that result when an LT3470 circuit is connected to a 24V supply through six feet of 24-gauge twisted pair. The first plot is the response with a 2.2µF ceramic capacitor at the input. The input voltage rings as high as 35V and the input current peaks at 20A. One method of damping the tank circuit is to add another capacitor with a series resistor to the circuit. In Figure 6b an aluminum electrolytic capacitor has been added. This capacitor’s high equivalent series resistance damps the circuit and eliminates the voltage overshoot. The extra capacitor improves low frequency ripple filtering and can slightly improve the efficiency of the circuit, though it is likely to be the largest component in the circuit. An alternative solution is shown in Figure 6c. A 1Ω resistor is added in series with the input to eliminate the voltage overshoot (it also reduces the peak input current). A 0.1µF capacitor improves high frequency filtering. This solution is smaller and less expensive than the electrolytic capacitor. For high input voltages its impact on efficiency is minor, reducing efficiency less than one half percent for a 5V output at full load operating from 24V. High Temperature Considerations The die junction temperature of the LT3470 must be lower than the maximum rating of 125°C (150°C for the H-grade). This is generally not a concern unless the ambient temperature is above 85°C. For higher temperatures, care should be taken in the layout of the circuit to ensure good heat sinking of the LT3470. The maximum load current should be derated as the ambient temperature approaches the maximum junction rating. The die temperature is calculated by multiplying the LT3470 power dissipation by the thermal resistance from junction to ambient. Power dissipation within the LT3470 can be estimated by calculating the total power loss from an efficiency measurement. Thermal resistance depends on the layout of the circuit board and choice of package. The DD package with the exposed pad has a thermal resistance of approximately 80°C/W while the ThinSOT is approximately 150°C/W. Finally, be aware that at high ambient temperatures the internal Schottky diode will have significant leakage current (see Typical Performance Characteristics) increasing the quiescent current of the LT3470 converter. Rev. E 14 For more information www.analog.com LT3470 APPLICATIONS INFORMATION CLOSING SWITCH SIMULATES HOT PLUG IIN VIN + LOW IMPEDANCE ENERGIZED 24V SUPPLY LT3470 VIN 10V/DIV 2.2µF IIN 10A/DIV STRAY INDUCTANCE DUE TO 6 FEET (2 METERS) OF TWISTED PAIR 10µs/DIV (6a) 10µF 35V AI.EI. LT3470 + 2.2µF (6b) 1Ω 0.1µF LT3470 2.2µF 3470 F06 (6c) Figure 6. A Well Chosen Input Network Prevents Input Voltage Overshoot and Ensures Reliable Operation When the LT3470 Is Connected to a Live Supply Rev. E For more information www.analog.com 15 LT3470 TYPICAL APPLICATIONS 3.3V Step-Down Converter VIN 5.5V TO 40V VIN BOOST LT3470 OFF ON SHDN 5V Step-Down Converter VIN R1 324k 22pF FB GND OFF ON SHDN C3 0.22µF, 6.3V L1 33µH 22pF C1 1µF FB GND C1: TDK C3216JB1H105M C2: CE JMK316 BJ226ML-T L1: TOKO A914BYW-330M=P3 1.8V Step-Down Converter 2.5V Step-Down Converter VIN 4.7V TO 40V BOOST LT3470 SHDN VIN 4V TO 23V C3 0.47µF, 6.3V L1 33µH VIN GND FB OFF ON SHDN C1 1µF C2 22µF R2 200k C3 0.22µF, 25V L1 22µH SW BIAS R1 200k 22pF BOOST LT3470 VOUT 2.5V 200mA SW BIAS C1 1µF C2 22µF 3470 TA04 C1: TDK C3216JB1H105M C2: CE JMK316 BJ226ML-T L1: TOKO A993AS-270M=P3 OFF ON R1 604k R2 200k 3470 TA03 VIN VOUT 5V 200mA SW BIAS C2 22µF R2 200k BOOST LT3470 VOUT 3.3V 200mA SW BIAS C1 1µF VIN 7V TO 40V C3 0.22µF, 6.3V L1 33µH 22pF GND FB 3470 TA07 R1 147k R2 332k VOUT 1.8V 200mA C2 22µF 3470 TA05 C1: TDK C3216JB1H105M C2: TDK C2012JB0J226M L1: MURATA LQH32CN150K53 C1: TDK C3216JB1H105M C2: TDK C2012JB0J226M L1: SUMIDA CDRH3D28 12V Step-Down Converter VIN 15V TO 34V VIN BOOST LT3470 OFF ON SHDN C3 0.22µF, 16V L1 33µH BIAS C1 1µF VOUT 12V 200mA SW 22pF GND FB R1 866k R2 100k C2 10µF 3470 TA06 C1: TDK C3216JB1H105M C2: TDK C3216JB1C106M L1: MURATA LQH32CN150K53 Rev. E 16 For more information www.analog.com LT3470 PACKAGE DESCRIPTION TS8 Package 8-Lead Plastic TSOT-23 (Reference LTC DWG # 05-08-1637 Rev A) 0.40 MAX 2.90 BSC (NOTE 4) 0.65 REF 1.22 REF 1.4 MIN 3.85 MAX 2.62 REF 2.80 BSC 1.50 – 1.75 (NOTE 4) PIN ONE ID RECOMMENDED SOLDER PAD LAYOUT PER IPC CALCULATOR 0.22 – 0.36 8 PLCS (NOTE 3) 0.65 BSC 0.80 – 0.90 0.20 BSC 0.01 – 0.10 1.00 MAX DATUM ‘A’ 0.30 – 0.50 REF 0.09 – 0.20 (NOTE 3) 1.95 BSC TS8 TSOT-23 0710 REV A NOTE: 1. DIMENSIONS ARE IN MILLIMETERS 2. DRAWING NOT TO SCALE 3. DIMENSIONS ARE INCLUSIVE OF PLATING 4. DIMENSIONS ARE EXCLUSIVE OF MOLD FLASH AND METAL BURR 5. MOLD FLASH SHALL NOT EXCEED 0.254mm 6. JEDEC PACKAGE REFERENCE IS MO-193 Rev. E For more information www.analog.com 17 LT3470 PACKAGE DESCRIPTION DDB Package 8-Lead Plastic DFN (3mm × 2mm) (Reference LTC DWG # 05-08-1702 Rev B) 0.61 ±0.05 (2 SIDES) 3.00 ±0.10 (2 SIDES) 0.70 ±0.05 2.55 ±0.05 1.15 ±0.05 PACKAGE OUTLINE 0.25 ± 0.05 0.50 BSC 2.20 ±0.05 (2 SIDES) PIN 1 BAR TOP MARK (SEE NOTE 6) 0.200 REF R = 0.115 TYP 5 R = 0.05 TYP 0.40 ± 0.10 8 2.00 ±0.10 (2 SIDES) 0.56 ± 0.05 (2 SIDES) 0.75 ±0.05 0 – 0.05 RECOMMENDED SOLDER PAD PITCH AND DIMENSIONS 4 0.25 ± 0.05 1 PIN 1 R = 0.20 OR 0.25 × 45° CHAMFER (DDB8) DFN 0905 REV B 0.50 BSC 2.15 ±0.05 (2 SIDES) BOTTOM VIEW—EXPOSED PAD NOTE: 1. DRAWING CONFORMS TO VERSION (WECD-1) IN JEDEC PACKAGE OUTLINE M0-229 2. DRAWING NOT TO SCALE 3. ALL DIMENSIONS ARE IN MILLIMETERS 4. DIMENSIONS OF EXPOSED PAD ON BOTTOM OF PACKAGE DO NOT INCLUDE MOLD FLASH. MOLD FLASH, IF PRESENT, SHALL NOT EXCEED 0.15mm ON ANY SIDE 5. EXPOSED PAD SHALL BE SOLDER PLATED 6. SHADED AREA IS ONLY A REFERENCE FOR PIN 1 LOCATION ON THE TOP AND BOTTOM OF PACKAGE Rev. E 18 For more information www.analog.com LT3470 REVISION HISTORY (Revision history begins at Rev D) REV DATE DESCRIPTION D 09/11 Corrected lead-based tape and reel part numbers in the Order Information section. PAGE NUMBER 2 E 04/20 Added AEC-Q100 Qualified. 1 Added #W options for automotive under Order Information. 3 Updated Inductor vendors table. 10 Rev. E Information furnished by Analog Devices is believed to be accurate and reliable. However, no responsibility is assumed by Analog Devices for its use, nor for any infringements of patents or other rights of third parties that may result from its use. Specifications subject to change without notice. No license For is granted implication or otherwise under any patent or patent rights of Analog Devices. more by information www.analog.com 19 LT3470 RELATED PARTS PART NUMBER DESCRIPTION COMMENTS LT1616 25V, 500mA (IOUT), 1.4MHz, High Efficiency Step-Down DC/DC Converter VIN = 3.6V to 25V, VOUT = 1.25V, IQ = 1.9mA, ISD < 1µA, ThinSOT Package LT1676 60V, 440mA (IOUT), 100kHz, High Efficiency Step-Down DC/DC Converter VIN = 7.4V to 60V, VOUT = 1.24V, IQ = 3.2mA, ISD = 2.5µA, S8 Package LT1765 25V, 2.75A (IOUT), 1.25MHz, High Efficiency Step-Down DC/DC Converter VIN = 3V to 25V, VOUT = 1.2V, IQ = 1mA, ISD = 15µA, S8, TSSOP16E Packages LT1766 60V, 1.2A (IOUT), 200kHz, High Efficiency Step-Down DC/DC Converter VIN = 5.5V to 60V, VOUT = 1.2V, IQ = 2.5mA, ISD = 25µA, TSSOP16/E Package LT1767 25V, 1.2A (IOUT), 1.25MHz, High Efficiency Step-Down DC/DC Converter VIN = 3V to 25V; VOUT = 1.2V, IQ = 1mA, ISD = 6µA, MS8/E Packages LT1776 40V, 550mA (IOUT), 200kHz, High Efficiency Step-Down DC/DC Converter VIN = 7.4V to 40V; VOUT = 1.24V, IQ = 3.2mA, ISD = 30µA, N8, S8 Packages LTC®1877 600mA (IOUT), 550kHz, Synchronous Step-Down DC/DC Converter VIN = 2.7V to 10V; VOUT = 0.8V, IQ = 10µA, ISD ≤ 1µA, MS8 Package LTC1879 1.2A (IOUT), 550kHz, Synchronous Step-Down DC/DC Converter VIN = 2.7V to 10V; VOUT = 0.8V, IQ = 15µA, ISD ≤ 1µA, TSSOP16 Package LT1933 36V, 600mA, 500kHz, High Efficiency Step-Down DC/DC Converter VIN = 3.6V to 36V; VOUT = 1.25V, IQ = 2.5µA, ISD ≤ 1µA, ??? Package LT1934 34V, 250mA (IOUT), Micropower, Step-Down DC/DC Converter VIN = 3.2V to 34V; VOUT = 1.25V, IQ = 12µA, ISD ≤ 1µA, ??? Package LT1956 60V, 1.2A (IOUT), 500kHz, High Efficiency Step-Down DC/DC Converter VIN = 5.5V to 60V, VOUT = 1.2V, IQ = 2.5mA, ISD = 25µA, TSSOP16/E Package LTC3405/LTC3405A 300mA (IOUT), 1.5MHz, Synchronous Step-Down DC/DC Converter VIN = 2.7V to 6V, VOUT = 0.8V, IQ = 20µA, ISD ≤ 1µA, ThinSOT Package LTC3406/LTC3406B 600mA (IOUT), 1.5MHz, Synchronous Step-Down DC/DC Converter VIN = 2.5V to 5.5V, VOUT = 0.6V, IQ = 20µA, ISD ≤ 1µA, ThinSOT Package LTC3411 1.25A (IOUT), 4MHz, Synchronous Step-Down DC/DC Converter VIN = 2.5V to 5.5V, VOUT = 0.8V, IQ = 60µA, ISD ≤ 1µA, MS Package LTC3412 2.5A (IOUT), 4MHz, Synchronous Step-Down DC/DC Converter VIN = 2.5V to 5.5V, VOUT = 0.8V, IQ = 60µA, ISD ≤ 1µA, TSSOP16E Package LTC3430 60V, 2.75A (IOUT), 200kHz, High Efficiency Step-Down DC/DC Converter VIN = 5.5V to 60V, VOUT = 1.2V, IQ = 2.5mA, ISD = 30µA, TSSOP16E Package Rev. E 20 04/20 www.analog.com For more information www.analog.com  ANALOG DEVICES, INC. 2004–2020