LT3517
Full-Featured LED Driver
with 1.5A Switch Current
Features
Description
5000:1 True Color PWM™ Dimming Ratio
nn 1.5A, 45V Internal Switch
nn 100mV High Side Current Sense
nn Open LED Protection
nn Adjustable Frequency: 250kHz to 2.5MHz
nn Wide Input Voltage Range:
nn Operation from 3V to 30V
nn Transient Protection to 40V
nn Operates in Boost, Buck Mode and Buck-Boost Mode
nn Gate Driver for PMOS LED Disconnect
nn Constant-Current and Constant-Voltage Regulation
nn CTRL Pin Provides 10:1 Analog Dimming
nn Low Shutdown Current: 1.5V, VC = 0V
PWM = 0V
SHDN = 0V
6
4.5
0.1
10
1
mA
mA
µA
Switching Frequency
RT = 16.7k
RT = 4.03k
RT = 91.5k
1
2.5
250
1.15
2.7
270
MHz
MHz
kHz
l
0.85
2.25
220
RT Voltage
1
Soft-Start Pin Current
SS = 0.5V, Out of Pin
SYNC Pull-Down Current (Into the Pin)
VSYNC = 2V
6
9
12
60
SYNC Input Low
1.5
RT = 91.5k (250kHz)
SYNC = 300kHz Clock Signal, RT = 91.5k
RT = 16.7k (1MHz)
RT = 4.03k (2.5MHz)
l
Switch Current Limit
Switch VCESAT
ISW = 1A
Switch Leakage Current
VSW = 45V, PWM = 0V
CTRL Input Bias Current
Current Out of Pin, VCTRL = 0.1V
µA
µA
0.4
SYNC Input High
Maximum Duty Cycle
V
V
V
95
94
85
97
96
90
74
1.5
1.9
%
%
%
%
2.3
300
20
A
mV
2
µA
100
nA
Error Amplifier Transconductance
550
µS
VC Output Impedance
1000
kΩ
VC Idle Input Bias Current
PWM = 0V, VC = 1V
FB Pin Input Bias Current
Current Out of Pin, VFB = 0.5V
FB Pin Threshold
l
ISP , ISN Idle Input Bias Current
PWM = 0V, ISP = ISN = 24V
ISP , ISN Full-Scale Input Bias Current
ISP Tied to ISN, VISP = 24V, VCTRL = 2V
SHDN Voltage High
SHDN Voltage Low
–20
0.98
20
nA
20
100
nA
1.01
1.04
V
300
nA
20
l
V
–40°C ≤ TJ ≤ 125°C
125°C < TJ ≤ 150°C
60
PWM Input High Voltage
l
0.45
0.40
V
V
100
µA
1.2
V
–40°C ≤ TJ ≤ 125°C
125°C < TJ ≤ 150°C
PWM Pin Bias Current
µA
1.2
SHDN Pin Bias Current
PWM Input Low Voltage
0
60
0.45
0.40
V
V
120
µA
3517fh
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3
LT3517
The
l denotes the specifications which apply over the full operating
Electrical
Characteristics
temperature range, otherwise specifications are at TA = 25°C. (Note 2) VIN = 5V, SHDN = 5V, PWM = 5V unless otherwise noted.
PARAMETER
CONDITIONS
MIN
TGEN Input High Voltage
TYP
MAX
UNITS
1.5
V
TGEN Input Low Voltage
0.4
V
100
200
µA
2
2.04
V
0.03
%/V
TGEN Pin Bias Current
TGEN = 5V
VREF Pin Voltage
IREF = –100µA
VREF Pin Voltage Line Regulation
3V < VIN < 40V
Gate Turn-On Delay
CLOAD = 1nF Between ISP and TG
200
ns
Gate Turn-Off Delay
CLOAD = 1nF Between ISP and TG
200
ns
Top Gate Drive VGS (VISP – VTG)
VISP = 24V, TGEN = 5V
PWM = 0V
1.96
l
Note 1: Stresses beyond those listed under Absolute Maximum Ratings
may cause permanent damage to the device. Exposure to any Absolute
Maximum Rating condition for extended periods may affect device
reliability and lifetime.
Note 2: The LT3517E is guaranteed to meet performance specifications
from 0°C to 125°C operating junction temperature range. Specifications
over the –40°C to 125°C operating junction temperature range are
assured by design, characterization and correlation with statistical
process controls. The LT3517I is guaranteed over the full –40°C to 125°C
operating junction temperature range. The LT3517H is guaranteed over
the full –40°C to 150°C operating junction temperature range. Operating
lifetime is derated at junction temperatures greater than 125°C.
7
0
V
V
0.3
Note 3: Absolute maximum voltage at VIN, SHDN, PWM and TGEN pins
is 40V for nonrepetitive 1 second transients and 30V for continuous
operation.
Note 4: This IC includes overtemperature protection that is intended
to protect the device during momentary overload conditions. Junction
temperature will exceed the maximum operating junction temperature
when overtemperature protection is active. Continuous operation above
the specified maximum operating junction temperature may impair device
reliability.
Typical Performance Characteristics
Switch Current Limit
vs Duty Cycle
VISP – VISN Threshold vs VCTRL
80
60
40
20
0
0.2
0.4
0.6 0.8 1.0
VCTRL (V)
1.2
1.4
1.6
3518 G01
4
1.5
1.0
1000
0.5
0
TA = 25°C
OSCILLATOR FREQUENCY (kHz)
SWITCH CURRENT LIMIT (A)
VISP – VISN THRESHOLD (mV)
VIN = 5V
VISP = 24V
100 VC = 1V
TA = 25°C
0
Oscillator Frequency vs RT
10000
2.0
120
TA = 25°C
0
20
40
60
DUTY CYCLE (%)
80
100
3517 G02
100
1
10
RT (kΩ)
100
3518 G03
3517fh
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LT3517
Typical Performance Characteristics
Switch Current Limit
vs Temperature
2.5
VIN = 5V
103 VISP = 24V
VC = 1V
102 VCTRL = 2V
SWITCH CURRENT LIMIT (A)
VISP – VISN THRESHOLD (mV)
104
101
100
99
98
Oscillator Frequency
vs Temperature
2.5
VIN = 5V
OSCILLATOR FREQUENCY (MHz)
VISP – VISN Threshold
vs Temperature
2.0
1.5
1.0
0.5
97
96
–40 –20 0
0
–40 –20 0
20 40 60 80 100 120 140 160
TEMPERATURE (°C)
2.02
1.7
1.5
–40 –20 0
Quiescent Current vs VIN
8
TA = 25°C
7 VC = 0V
VIN = 5V
100
99
98
6
VIN CURRENT (mA)
101
2.00
5
4
3
1.99
97
2
1
96
95
0
10
30
20
VISP (V)
40
50
1.98
–40 –20 0
0
20
10
30
40
VIN (V)
3517 G08
3517 G09
PMOS Turn-On
FB Pin Threshold vs Temperature
PMOS Turn-Off
VIN = 5V
1.03
FB PIN THRESHOLD (V)
0
20 40 60 80 100 120 140 160
TEMPERATURE (°C)
3517 G07
1.04
20 40 60 80 100 120 140 160
TEMPERATURE (°C)
3517 G06
2.01
102
VREF (V)
VISP – VISN THRESHOLD (mV)
103
1.9
Reference Voltage
vs Temperature
VCTRL = 2V
VIN = 5V
TA = 25°C
VC = 1V
104
2.1
3518 G05
VISP – VISN Threshold vs VISP
105
2.3
20 40 60 80 100 120 140 160
TEMPERATURE (°C)
3517 G04
VIN = 5V
RT = 6.04k
5V
5V
PWM
PWM
1.02
0V
0V
1.01
40V
40V
1.00
30V
30V
0.99
0.98
–40 –20 0
TG
TG
20 40 60 80 100 120 140 160
TEMPERATURE (°C)
VISP = 40V
200ns/DIV
3517 G11
VISP = 40V
200ns/DIV
3517 G11
3517 G10
3517fh
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5
LT3517
Pin Functions
SW: Switch Pin. Minimize trace at this pin to reduce EMI.
SHDN: Shutdown Pin. Tie to 1.5V or higher to enable
device or 0.4V or less to disable device.
CTRL: LED Current Adjustment Pin. Sets voltage across
sense resistor between ISP and ISN. Connect directly to
VREF for full-scale threshold of 100mV, or use signal values
between GND and 1V to modulate LED current. Tie the CTRL
pin to the VREF pin if not used.
VREF: Reference Output Pin. This pin can supply up to
100µA.
VC: gm Error Amplifier Output Pin. Stabilize the loop with
an RC network or compensating C.
RT : Switching Frequency Adjustment Pin. Set switching
frequency using a resistor to GND (see Typical Performance
Characteristics for values). For SYNC function, choose
the resistor to program a frequency 20% slower than the
SYNC pulse frequency. Do not leave this pin open.
FB: Voltage Loop Feedback Pin. Works as overvoltage
protection for LED drivers. If FB is higher than 1V, the
main switch is turned off.
VIN: Input Supply Pin. Must be locally bypassed.
SYNC: Frequency Synchronization Pin. Tie an external
clock signal here. RT resistor should be chosen to program a switching frequency 20% slower than SYNC pulse
frequency. Synchronization (power switch turn-on) occurs
a fixed delay after the rising edge of SYNC. Tie the SYNC
pin to ground if this feature is not used.
SS: Soft-Start Pin. Place a soft-start capacitor here. Leave
the pin open if not in use.
PWM: Pulse Width Modulated Input Pin. Signal low turns
off channel, disables the main switch and makes the TG
pin high. Tie the PWM pin to VREF pin or SHDN pin if not
used. There is an equivalent 50k resistor from PWM pin
to ground internally.
6
TGEN: Top Gate Enable Input Pin. Tie to 1.5V or higher
to enable the PMOS driver function. Tie the TGEN pin to
ground if TG function is not used. There is an equivalent
40k resistor from TGEN pin to ground internally.
ISN: Current Sense (–) Pin. The inverting input to the
current sense amplifier.
ISP: Current Sense (+) Pin. The noninverting input to the
current sense amplifier. Also serves as positive rail for
TG pin driver.
TG: Top Gate Driver Output. An inverted PWM signal drives series PMOS device between VISP and
(VISP – 7V). An internal 7V clamp protects the PMOS gate.
Leave TG unconnected if not used.
GND: Exposed Pad (QFN Package). Solder paddle directly
to ground plane.
3517fh
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LT3517
Block Diagram
LED ARRAY
CIN
CFILT
RSENSE
PVIN
ISP
+
ISN
TG
–
SW
PWM
VISP
CURRENT
SENSE
AMPLIFIER
X10
TGEN
VISP – 7V
SHDN
–
+
+
CTRL
1V
MOSFET DRIVER
A1
ERROR
AMPLIFIER
+
–
A3
+
+
1.01V
A4
R
+
A2
FB
MAIN SWITCH
DRIVER
S
Q1
POWER
SWITCH
Q
PWM
COMPARATOR
–
+
VC
A8
SYNC
RAMP
GENERATOR
+
VIN
A5
2.5MHz TO 250kHz
OSCILLATOR
–
1V
GND
–
SS
100µA
VREF
VIN
SS
RT
9µA
1V
+
+
–
+
A6
A7
Q2
2V
FREQ
ADJUST
–
VIN
3517 F01
Figure 1. Buck Mode LED Driver
3517fh
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7
LT3517
Operation
The LT3517 is a constant frequency, current mode regulator with an internal power switch. Operation can be best
understood by referring to the Block Diagram in Figure 1. At
the start of each oscillator cycle, the SR latch is set, which
turns on the Q1 power switch. A voltage proportional to
the switch current is added to a stabilizing ramp and the
resulting sum is fed into the positive terminal of the PWM
comparator, A4. When this voltage exceeds the level at the
negative input of A4, the SR latch is reset, turning off the
power switch. The level at the negative input of A4 is set
by the error amplifier A3. A3 has two inputs, one from the
voltage feedback loop and the other one from the current
loop. Whichever feedback input is lower takes precedence,
and forces the converter into either constant-current or
constant-voltage mode. The LT3517 is designed to transition cleanly between these two modes of operation. The
current sense amplifier senses the voltage across RSENSE
and provides a pre-gain to amplifier A1. The output of A1
is simply an amplified version of the difference between
the voltage across RSENSE and the lower of VCTRL/10
or 100mV. In this manner, the error amplifier sets the
correct peak switch current level to regulate the current
through RSENSE. If the error amplifier’s output increases,
more current is delivered to the output; if it decreases,
less current is delivered. The current regulated in RSENSE
can be adjusted by changing the input voltage VCTRL.
The current sense amplifier provides rail-to-rail current
sense operation. The FB voltage loop is implemented by
the amplifier A2. When the voltage loop dominates, the
error amplifier and the amplifier A2 regulate the FB pin to
1.01V (constant-voltage mode).
Dimming of the LED array is accomplished by pulsing the
LED current using the PWM pin. When the PWM pin is
low, switching is disabled and the error amplifier is turned
off so that it does not drive the VC pin. Also, all internal
loads on the VC pin are disabled so that the charge state
of the VC pin will be saved on the external compensation
capacitor. This feature reduces transient recovery time.
When the PWM input again transitions high, the demand
current for the switch returns to the value just before
PWM last transitioned low. To further reduce transient
recovery time, an external PMOS is used to disconnect
the LED array current loop when PWM is low, stopping
CFILT from discharging.
Applications Information
Dimming Control
There are two methods to control the current source for
dimming using the LT3517. The first method uses the
PWM pin to modulate the current source between zero
and full current to achieve a precisely programmed average current. To make this method of current control more
accurate, the switch demand current is stored on the VC
node during the quiescent phase. This feature minimizes
recovery time when the PWM signal goes high. To further
improve the recovery time, a disconnect switch is used in
the LED current path to prevent the output capacitor from
discharging in the PWM signal low phase. The minimum
PWM on or off time will depend on the choice of operating
frequency through RT input pin or SYNC pin. When using the SYNC function, the SYNC and PWM signals must
have the aligned rising edges to achieve the optimized
high PWM dimming ratio. For best current accuracy, the
8
minimum PWM low or high time should be at least four
switching cycles (2µs for fSW = 2MHz). Maximum PWM
period is determined by the system and is unlikely to be
longer than 12ms. The maximum PWM dimming ratio
(PWMRATIO) can be calculated from the maximum PWM
period (tMAX) and the minimum PWM pulse width (tMIN)
as follows:
PWMRATIO =
tMAX
tMIN
(1)
Example:
tMAX = 10ms, tMIN = 2µs (fSW = 2MHz)
PWMRATIO = 10ms/2µs = 5000:1
The second method of dimming control uses the CTRL
pin to linearly adjust the current sense threshold during
3517fh
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LT3517
Applications Information
the PWM high state. When the CTRL pin voltage is less
than 1V, the LED current is:
ILED =
VCTRL
10 • RSENSE
(2)
For a buck or a buck-boost configuration, the output
voltage is typically level-shifted to a signal with respect
to GND, as illustrated in the Figure 4. The output can be
expressed as:
When VCTRL is higher than 1V, the LED current is clamped
to be:
100mV
ILED =
RSENSE
VOUT =
R1
• 1.01V + VBE(Q1)
R2
R1
(3)
+
RSENSE
VOUT
The LED current programming feature possibly increases
total dimming range by a factor of ten.
LT3517
LED
ARRAY
–
Q2
FB
R2
The CTRL pin should not be left open (tie to VREF if not
used). The CTRL pin can also be used in conjunction with
a PTC thermistor to provide overtemperature protection
for the LED load.
3517 F04
Figure 4
Inductor Selection
2V
VREF
(5)
45.3k
The inductor used with the LT3517 should have a saturation current rating of 2A or greater. For buck mode LED
drivers, the inductor value should be chosen to give a
ripple current “ΔI” of ~30% to 40% of the LED current.
In the buck mode, the inductor value can be estimated
using the formula:
49.9k
CTRL
5k
PTC
3517 F02
Figure 2
L (µH) =
DBUCK • tSW (µs) • ( VIN – VLED )
ΔI
DBUCK =
VLED
VIN
Setting Output Voltage
For a boost application, the output voltage can be set by
selecting the values of R1 and R2 (see Figure 3) according
to the following equation:
⎛ R1 ⎞
VOUT = ⎜ + 1⎟ • 1.01V
⎝ R2 ⎠
(4)
VOUT
LT3517
R1
FB
R2
(6)
VLED is the voltage across the LED string, VIN is the input
voltage to the converter, and tSW is the switching period.
In the boost configuration, the inductor can be estimated
using the formula:
L (µH) =
DBOOST • tSW (µs) • VIN
ΔI
DBOOST =
VLED – VIN
VLED
(7)
3517 F03
Figure 3
3517fh
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9
LT3517
Applications Information
Table 1 provides some recommended inductor vendors.
Table 1. Inductor Manufacturers
VENDOR
PHONE
WEB
Sumida
(408) 321-9660
www.sumida.com
Toko
(408) 432-8281
www.toko.com
Cooper
(561) 998-4100
www.cooperet.com
Vishay
(402) 563-6866
www.vishay.com
Use only ceramic capacitors with X7R, X5R or better dielectric as they are best for temperature and DC bias stability
of the capacitor value. All ceramic capacitors exhibit loss
of capacitance value with increasing DC voltage bias, so it
may be necessary to choose a higher value capacitor to get
the required capacitance at the operation voltage. Always
check that the voltage rating of the capacitor is sufficient.
Table 2 shows some recommended capacitor vendors.
Input Capacitor Selection
Table 2. Ceramic Capacitor Manufacturers
For proper operation, it is necessary to place a bypass
capacitor to GND close to the VIN pin of the LT3517. A
1µF or greater capacitor with low ESR should be used. A
ceramic capacitor is usually the best choice.
VENDOR
PHONE
WEB
Taiyo Yuden
(408) 573-4150
www.t-yuden.com
AVX
(843) 448-9411
www.avxcorp.com
Murata
(770) 436-1300
www.murata.com
TDK
(847) 803-6100
www.tdk.com
In the buck mode configuration, the capacitor at the input
to the power converter has large pulsed currents due to
the current returned though the Schottky diode when the
switch is off. For best reliability, this capacitor should have
low ESR and ESL and have an adequate ripple current
rating. The RMS input current is:
IIN(RMS) = ILED • (1– D) • D
(8)
where D is the switch duty cycle. A 2.2µF ceramic type
capacitor is usually sufficient.
Output Capacitor Selection
The selection of output capacitor depends on the load
and converter configuration, i.e., step-up or step-down.
For LED applications, the equivalent resistance of the LED
is typically low, and the output filter capacitor should be
sized to attenuate the current ripple.
To achieve the same LED ripple current, the required filter
capacitor value is larger in the boost and buck-boost mode
applications than that in the buck mode applications. For
LED buck mode applications, a 1µF ceramic capacitor
is usually sufficient. For the LED boost and buck-boost
mode applications, a 2.2µF ceramic capacitor is usually
sufficient. Very high performance PWM dimming applications may require a larger capacitor value to support
the LED voltage during PWM transitions.
10
Loop Compensation
The LT3517 uses an internal transconductance error
amplifier whose VC output compensates the control loop.
The external inductor, output capacitor, and the compensation resistor and capacitor determine the loop stability.
The inductor and output capacitor are chosen based on
performance, size and cost. The compensation resistor
and capacitor at VC are selected to optimize control loop
stability. For typical LED applications, a 10nF compensation
capacitor at VC is adequate and a series resistor is not
required. A compensation resistor may be used to increase
the slew rate on the VC pin to maintain tighter regulation
of LED current during fast transients on VIN or CTRL.
Diode Selection
The Schottky diode conducts current during the interval
when the switch is turned off. Select a diode rated for
the maximum SW voltage. If using the PWM feature for
dimming, it is important to consider diode leakage, which
increases with the temperature, from the output during the
PWM low interval. Therefore, choose the Schottky diode
with sufficiently low leakage current. Table 3 has some
recommended component vendors.
3517fh
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LT3517
Applications Information
Table 3. Schottky Diodes
PART NUMBER
VR (V)
IAVE (A)
60
1
40
1
60
1.5
Diodes Inc.
DFLS160
Zetex
ZLLS1000TA
International Rectifier
10MQ060N
Board Layout
The high speed operation of the LT3517 demands careful
attention to board layout and component placement. The
Exposed Pad of the package is the only GND terminal of
the IC and is also important for thermal management of
the IC. It is crucial to achieve a good electrical and thermal
contact between the Exposed Pad and the ground plane of
the board. To reduce electromagnetic interference (EMI),
it is important to minimize the area of the SW node. Use
a GND plane under SW and minimize the length of traces
in the high frequency switching path between SW and
GND through the diode and the capacitors. Since there is
a small DC input bias current to the ISN and ISP inputs,
resistance in series with these inputs should be minimized
and matched, otherwise there will be an offset. Finally,
the bypass capacitor on the VIN supply to the LT3517
should be placed as close as possible to the VIN terminal
of the device.
Soft-Start
For many applications, it is necessary to minimize the
inrush current at start-up. The built-in soft-start circuit
significantly reduces the start-up current spike and
output voltage overshoot. A typical value for the soft-start
capacitor is 0.1µF.
Switching Frequency
There are two methods to set the switching frequency of
LT3517. Both methods require a resistor connected at RT
pin. Do not leave the RT pin open. Also, do not load this pin
with a capacitor. A resistor must always be connected for
proper operation. One way to set the frequency is simply
connecting an external resistor between the RT pin and
GND. See Table 4 below or see the Oscillator Frequency vs
RT graph in the Typical Performance Characteristics for
resistor values and corresponding switching frequencies.
Table 4. Switching Frequency vs RT
Switching Frequency (kHz)
RT ( kΩ )
250
90.9
500
39.2
1000
16.9
1500
9.53
2000
6.04
2500
4.02
The other way is to make the LT3517 synchronize with
an external clock via SYNC pin. For proper operation, a
resistor should be connected at the RT pin and be able
to generate a switching frequency 20% lower than the
external clock when external clock is absent.
In general, a lower switching frequency should be used
where either very high or very low switching duty cycle
operation is required, or high efficiency is desired. Selection
of a higher switching frequency will allow use of smaller
value external components and yield a smaller solution
size and profile.
Thermal Considerations
The LT3517 is rated to a maximum input voltage of 30V
for continuous operation, and 40V for nonrepetitive one
second transients. Careful attention must be paid to the
internal power dissipation of the LT3517 at higher input
voltages to ensure that the maximum junction temperature
is not exceeded. This junction limit is especially important
when operating at high ambient temperatures. The Exposed
Pad on the bottom of the package must be soldered to a
ground plane. This ground should then be connected to
an internal copper ground plane with thermal vias placed
directly under the package to spread out the heat dissipated
by the LT3517.
3517fh
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11
LT3517
Typical Applications
Buck Mode 1A LED Driver
RSENSE
100mΩ
PVIN
24V
VIN
3.3V
C2
2.2µF
C1
2.2µF
L1
15µH
1A
ISP
VIN
2000:1 PWM Dimming at 120Hz
C3
10µF
M1
PWM
5V/DIV
D1
ISN TG
SW
ILED
1A/DIV
IL
1A/DIV
SHDN
LT3517
VREF
CTRL
FB
PWM
PWM
SS
SYNC
RT
TGEN VREF VC GND
C4
0.1µF
1µs/DIV
RT
16.9k
1MHz
3517 TA02b
PVIN = 24V
fOSC = 1MHz
ILED = 1A
C5
0.1µF
3517 TA02a
C1: KEMET C0805C225K4RAC
C2: MURATA GRM31MR71E225KA93
C3: MURATA GRM32DR71E106KA12B
C4, C5: MURATA GRM21BR71H104KA01B
D1: DIODES DFLS160
L1: TOKO B992AS-150M
LEDS: LUXEON K2 (WHITE)
M1: ZETEX ZXMP6A13FTA
350mA, 5V to 12V Boost Converter with Accurate Input Current Limit
RSENSE
L1
100mΩ 6.8µH
VIN
5V
D1
C1
2.2µF
90
R1
549k
80
SW
FB
CTRL
PWM
SHDN
LT3517
C2
10µF
SYNC
TGEN
VREF
VC
R2
49.9k
RT
GND
R3
10k
C4
10nF
EFFICIENCY (%)
ISP TG ISN
VIN
SHDN
Efficiency
VOUT
12V
350mA
70
60
SS
C3
0.1µF
RT
6.04k
2MHz
50
3517 TA03a
50
100
150
200
250
ILOAD(mA)
300
350
3517 TA03b
C1: KEMET C0805C225K4RAC
C2: KEMET C1206C106K4RAC
C3: MURATA GRM21BR71H104KA01B
C4: MURATA GCM033R71A103KA03
D1: ZETEX ZLLS1000TA
L1: TOKO B992AS-6R8N
12
3517fh
For more information www.linear.com/LT3517
LT3517
Typical Applications
Buck-Boost Mode LED Driver
L1
6.8µH
VIN
8V TO 16V
SHDN VIN
D1
FB
R2
124k
PWM
300mA
PWM
TGEN
LT3517
ISP
RSENSE
330mΩ
VREF
C1
2.2µF
C5
0.22µF
R1
3.92M
SW
CTRL
ISN
TG
M1
C2
4.7µF
SYNC
VC
C4
0.1µF
RT SS
RT
6.04k
2MHz
GND
C3
0.1µF
3517 TA04a
C1: KEMET C0806C225K4RAC
C2: KEMET C1206C475K3RAC
C3, C4: MURATA GRM21BR71H104KA01B
C5: MURATA GRM21BR71H224KA01B
D1: DIODE DFLS160
L1: TOKO B992AS-6R8N
LEDS: LUXEON I (WHITE)
M1: ZETEX ZXMP6A13FTA
Efficiency
5000:1 PWM Dimming at 100Hz
90
VIN = 12V
CTRL = VREF
80
PWM
5V/DIV
70
EFFICIENCY (%)
ILED
200mA/DIV
IL
1A/DIV
60
50
40
500ns/DIV
VIN = 12V
fOSC = 2MHz
ILED = 300mA
3517 TA04b
30
20
0
20
40
60
80
PWM DUTY CYCLE (%)
100
3517 TA04c
3517fh
For more information www.linear.com/LT3517
13
LT3517
Typical Applications
Low Side Current Sensing Load Dump Protected Buck-Boost Mode LED Driver
L1
6.8µH
VIN
8V TO 16V
SHDN VIN
D1
C5
0.22µF
R1
3.92M
SW
FB
R2
124k
PWM
PWM
TGEN
LT3517
ISP
VREF
RSENSE
330mΩ
CTRL
C1
2.2µF
TG
VC
R3
10k
C4
33nF
C2
4.7µF
ISN
SYNC
RT SS
RT
6.04k
2MHz
GND
M1
300mA
C3
0.1µF
3517 TA05a
D1: DIODES DFLS160
L1: TOKO B992AS-6R8N
C1: KEMET C0806C225K4RAC
C2: KEMET C1206C475K3RAC
C3: MURATA GRM21BR71H104KA01B
C4: MURATA GRM219R71H333KAQ01B
C5: MURATA GRM21BR71H224KA01B
M1: ZETEX ZXMP6A13FTA
LEDs: LUXEON I (WHITE)
Efficiency
5000:1 PWM Dimming at 100Hz
90
VIN = 12V
CTRL = VREF
80
PWM
5V/DIV
70
EFFICIENCY (%)
ILED
200mA/DIV
IL
1A/DIV
60
50
40
500ns/DIV
3517 TA05b
30
VIN = 12V
fOSC = 2MHz
ILED = 300mA
20
Load Dump Response
0
20
40
60
80
PWM DUTY CYCLE (%)
100
3517 TA05c
VISP 10V/DIV
VIN 10V/DIV
VISP
15V TO 40V
VIN 15V TO 40V
VISP REF GND
ILED 200mA/DIV
VIN REF GND
IL 1A/DIV
5ms/DIV
3517 TA05d
VIN Raises From 15V to 40V in 5ms.
14
3517fh
For more information www.linear.com/LT3517
LT3517
Typical Applications
Boost 100mA LED Driver with LED Open Protection
L1
22µH
VIN
8V TO 16V
SHDN VIN
D1
SW
R1
1M
FB
R2
30.1k
ISP
PWM
PWM
RSENSE
1Ω
TGEN
VREF
LT3517
ISN
TG
CTRL
C1
2.2µF
M1
SYNC
VC
C4
0.1µF
RT
16.9k
1MHz
RT SS
C2
2.2µF
LED1
GND
LED2
100mA
C3
0.1µF
LED10
3517 TA06a
C1, C2: KEMET C1206C225K2RAC
C3, C4: MURATA GRM21BR71H104KA01B
D1: DIODES DFLS160
L1: COILCRAFT DS3316P-223
LEDS: CREE XLAMP 7090
M1: ZETEX ZXMP6A13FTA
Efficiency
3000:1 PWM Dimming at 100Hz
90
80
PWM
5V/DIV
EFFICIENCY (%)
70
ILED
100mA/DIV
IL
500mA/DIV
VIN = 12V
CTRL = VREF
60
50
40
1µs/DIV
VIN = 12V
fOSC = 1MHz
ILED = 100mA
3517 TA06b
30
20
0
20
40
60
80
PWM DUTY CYCLE (%)
100
3517 TA06c
3517fh
For more information www.linear.com/LT3517
15
LT3517
Typical Application
5.5V SEPIC Converter with Short-Circuit Protection
VIN
3V
C2
2.2µF
TG
ISP
LT3517
ISN
TGEN
RT
VREF
VC
GND
R3
10k
C4
10nF
R2
49.9k
SS
C3
0.1µF
80
R1
221k
SW
FB
SYNC
SHDN
C2
10µF
90
VOUT
5.5V
350mA
EFFICIENCY (%)
PWM
RSENSE
0.22Ω
D1
L2
4.3µH
VIN
CTRL
SHDN
Efficiency
C5
10µF
L1
4.3µH
RT
6.04k
2MHz
70
60
50
40
30
3517 TA07a
0
50
100
150 200
ILOAD (mA)
250
300
350
3517 TA07b
C1: KEMET C0805C225K4RAC
C2, C5: KEMET C1206C106K4RAC
C3: MURATA GRM21BR71H104KA01B
C4: MURATA GCM033R71A103KA03
D1: ZETEX ZLLS1000TA
L1, L2: TOKO B992AS-4R3N
16
3517fh
For more information www.linear.com/LT3517
LT3517
Package Description
Please refer to http://www.linear.com/product/LT3517#packaging for the most recent package drawings.
UF Package
16-Lead Plastic QFN (4mm × 4mm)
UF Package
(Reference LTC DWG # 05-08-1692 Rev Ø)
16-Lead Plastic QFN (4mm × 4mm)
(Reference LTC DWG # 05-08-1692 Rev Ø)
0.72 ±0.05
4.35 ±0.05
2.15 ±0.05
2.90 ±0.05 (4 SIDES)
PACKAGE OUTLINE
0.30 ±0.05
0.65 BSC
RECOMMENDED SOLDER PAD PITCH AND DIMENSIONS
BOTTOM VIEW—EXPOSED PAD
4.00 ±0.10
(4 SIDES)
0.75 ±0.05
R = 0.115
TYP
15
PIN 1 NOTCH R = 0.20 TYP
OR 0.35 × 45° CHAMFER
16
0.55 ±0.20
PIN 1
TOP MARK
(NOTE 6)
1
2.15 ±0.10
(4-SIDES)
2
(UF16) QFN 10-04
0.200 REF
0.00 – 0.05
0.30 ±0.05
0.65 BSC
NOTE:
1. DRAWING CONFORMS TO JEDEC PACKAGE OUTLINE MO-220 VARIATION (WGGC)
2. DRAWING NOT TO SCALE
3. ALL DIMENSIONS ARE IN MILLIMETERS
4. DIMENSIONS OF EXPOSED PAD ON BOTTOM OF PACKAGE DO NOT INCLUDE
MOLD FLASH. MOLD FLASH, IF PRESENT, SHALL NOT EXCEED 0.15mm ON ANY SIDE
5. EXPOSED PAD SHALL BE SOLDER PLATED
6. SHADED AREA IS ONLY A REFERENCE FOR PIN 1 LOCATION
ON THE TOP AND BOTTOM OF PACKAGE
3517fh
For more information www.linear.com/LT3517
17
LT3517
Package Description
Please refer to http://www.linear.com/product/LT3517#packaging for the most recent package drawings.
FE Package
16-Lead Plastic
TSSOP (4.4mm)
FE Package
(Reference
DWG #TSSOP
05-08-1663
Rev L)
16-LeadLTC
Plastic
(4.4mm)
Exposed
Pad Variation
BA Rev L)
(Reference
LTC DWG
# 05-08-1663
Exposed Pad Variation BA
4.90 – 5.10*
(.193 – .201)
2.74
(.108)
2.74
(.108)
16 1514 13 12 1110
6.60 ±0.10
4.50 ±0.10
9
2.74
(.108)
2.74 6.40
(.108) (.252)
BSC
SEE NOTE 4
0.45 ±0.05
1.05 ±0.10
0.65 BSC
1 2 3 4 5 6 7 8
RECOMMENDED SOLDER PAD LAYOUT
4.30 – 4.50*
(.169 – .177)
0.09 – 0.20
(.0035 – .0079)
0.25
REF
NOTE:
1. CONTROLLING DIMENSION: MILLIMETERS
MILLIMETERS
2. DIMENSIONS ARE IN
(INCHES)
18
0° – 8°
0.65
(.0256)
BSC
0.50 – 0.75
(.020 – .030)
3. DRAWING NOT TO SCALE
1.10
(.0433)
MAX
0.195 – 0.30
(.0077 – .0118)
TYP
0.05 – 0.15
(.002 – .006)
FE16 (BA) TSSOP REV L 0117
4. RECOMMENDED MINIMUM PCB METAL SIZE
FOR EXPOSED PAD ATTACHMENT
*DIMENSIONS DO NOT INCLUDE MOLD FLASH. MOLD FLASH
SHALL NOT EXCEED 0.150mm (.006") PER SIDE
3517fh
For more information www.linear.com/LT3517
LT3517
Revision History
(Revision history begins at Rev C)
REV
DATE
DESCRIPTION
C
4/10
Added H-grade to Order Information Section
PAGE NUMBER
2
D
7/10
Added conditions to ISP, ISN Idle Input Bias Current parameters
3
Changed VIN current sense to 9µA in Figure 1
7
E
01/11
Updated Electrical Characteristics
3
F
04/12
Subscript added to VC Pin Label
1
RT changed to RT in ABS Max Table, QFM Max Temp changed to 150°C
2
Added Operating in Note 2
4
Clarified Application Schematics
15, 16
Package Diagram Updated
18
G
04/13
Clarified Application schematic
15
H
03/17
Clarified TJ(MAX)
2
3517fh
Information furnished by Linear Technology Corporation is believed to be accurate and reliable.
However, no responsibility is assumed for its use. Linear Technology Corporation makes no representation that the interconnection
its circuits
as described
herein will not infringe on existing patent rights.
For of
more
information
www.linear.com/LT3517
19
LT3517
Related Parts
PART NUMBER
DESCRIPTION
COMMENTS
LT1618
Constant Current, 1.4MHz, 1.5A Boost Converter
VIN: 5V to 18V, VOUT(MAX) = 36V, Dimming = Analog/PWM, ISD < 1µA,
MSOP10 Package
LT3003
3-Channel LED Ballaster with PWM Dimming
VIN: 3V to 48V, Dimming = 3000:1 True Color PWM, ISD < 5µA,
MSOP10 Package
LT3474
36V, 1A (ILED), 2MHz, Step-Down LED Driver
VIN: 4V to 36V, VOUT(MAX) = 13.5V, Dimming = 400:1 True Color PWM,
ISD < 1µA, TSSOP16E Package
LT3475
Dual 1.5A (ILED), 36V 2MHz Step-Down LED Driver
VIN: 4V to 36V, VOUT(MAX) = 13.5V, Dimming = 3000:1 True Color PWM,
ISD < 1µA, TSSOP20E Package
LT3476
Quad-Output 1.5A, 36V, 2MHz High Current LED Driver
with 1000:1 Dimming
VIN: 2.8V to 16V, VOUT(MAX) = 36V, Dimming = 1000:1 True Color PWM,
ISD < 10µA, 5mm × 7mm QFN Package
LT3477
3A, 42V, 3MHz Boost, Buck-Boost, Buck LED Driver
VIN: 2.5V to 25V, VOUT(MAX) = 40V, Dimming = Analog/PWM, ISD < 1µA,
QFN, TSSOP20E Packages
LT3478/LT3478-1
4.5A, 42V, 2.5MHz High Current LED Driver with 3000:1
Dimming
VIN: 2.8V to 36V, VOUT(MAX) = 42V, Dimming = 3000:1 True Color PWM,
ISD < 3µA, TSSOP16E Packages
LT3479
3A, Full -Featured DC/DC Converter with Soft-Start and
Inrush Current Protection
VIN: 2.5V to 24V, VOUT(MAX) = 40V, IQ = 6.5mA, ISD < 1µA,
DFN and TSSOP Packages
LT3486
Dual 1.3A, 2MHz High Current LED Driver
VIN: 2.5V to 24V, VOUT(MAX) = 36V, Dimming = 1000:1 True Color PWM,
ISD < 1µA, 5mm × 3mm DFN, TSSOP16E
LT3496
Triple-Output LED Driver
VIN: 3V to 40V, VOUT(MAX) = 45V, Dimming = 3000:1 True Color PWM,
ISD < 10µA, 4mm × 5mm QFN Package
LT3518
Full-Featured LED Driver with 2.3A Switch Current
VIN: 3V to 40V, VOUT(MAX) = 45V, Dimming = 3000:1 True Color PWM,
ISD < 1µA, 4mm × 4mm QFN Package and TSSOP Package
LT3590
48V Buck Mode 50mA LED Driver
VIN: 4.5V to 55V, Drives Up to 10 LEDs, 200:1 Dimming,
ISO = 15mA, 2mm × 2mm DFN SC70
LT3595
16-Channel Buck LED Driver Mode
VIN: 4.5V to 45V, Drives Up to 160 LEDs, 5000:1 Dimming,
5mm × 9mm QFN
LTC®3783
High Current LED Controller
VIN: 3V to 36V, VOUT(MAX) = Ext FET, Dimming = 3000:1 True Color PWM,
ISD < 20µA, 5mm × 4mm QFN10, TSSOP16E Packages
20
3517fh
LT 0317 • PRINTED IN USA
For more information www.linear.com/LT3517
www.linear.com/LT3517
LINEAR TECHNOLOGY CORPORATION 2017
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