3517HFE

LT3517 Full-Featured LED Driver with 1.5A Switch Current FEATURES ■ ■ ■ ■ ■ ■ DESCRIPTION The LT®3517 is a current mode DC/DC converter with an internal 1.5A, 45V switch specifically designed to drive LEDs. The LT3517 operates as a LED driver in boost, buck mode and buck-boost mode. It combines a traditional voltage loop and a unique current loop to operate as a constant-current source or constant-voltage source. Programmable switching frequency allows optimization of the external components for efficiency or component size. The switching frequency of LT3517 can be synchronized to an external clock signal. The LED current is externally programmable with a 100mV sense resistor. The external PWM input provides up to 5000:1 LED dimming. The CTRL pin provides further 10:1 dimming ratio. The LT3517 is available in the tiny footprint 16-Lead QFN (4mm × 4mm) and the16-Pin TSSOP packages. The LT3517 provides a complete solution for both constant-voltage and constant-current applications. , LT, LTC and LTM are registered trademarks of Linear Technology Corporation. True Color PWM is a trademark of Linear Technology Corporation. Patent Pending. All other trademarks are the property of their respective owners. *Patents Pending. ■ ■ ■ ■ ■ ■ 5000:1 True Color PWMTM Dimming Ratio 1.5A, 45V Internal Switch 100mV High Side Current Sense Open LED Protection Adjustable Frequency: 250kHz to 2.5MHz Wide Input Voltage Range: Operation from 3V to 30V Transient Protection to 40V Operates in Boost, Buck Mode and Buck-Boost Mode Gate Driver for PMOS LED Disconnect* Constant-Current and Constant-Voltage Regulation CTRL Pin Provides 10:1 Analog Dimming Low Shutdown Current: 1.5V, VC = 0V PWM = 0V SHDN = 0V RT = 16.7k RT = 4.03k RT = 91.5k SS = 0.5V, Out of Pin VSYNC = 2V 1.5 RT = 91.5k (250kHz) SYNC = 300kHz Clock Signal, RT = 91.5k RT = 16.7k (1MHz) RT = 4.03k (2.5MHz) ISW = 1A VSW = 45V, PWM = 0V Current Out of Pin, VCTRL = 0.1V 20 550 1000 PWM = 0V, VC = 1V Current Out of Pin, VFB = 0.5V ● ● ● The ● denotes the specifications which apply over the full operating temperature range, otherwise specifications are at TA = 25°C. (Note 2) VIN = 5V, SHDN = 5V, PWM = 5V unless otherwise noted. CONDITIONS MIN 30 96 100 100 9 0.03 6 4.5 0.1 0.85 2.25 220 6 1.0 2.5 250 1 9 60 0.4 95 94 85 1.5 97 96 90 74 1.9 300 2 100 2.3 12 10 1 1.15 2.7 270 103 TYP MAX 3 UNITS V V mV mV mV %/V mA mA μA MHz MHz kHz V μA μA V V % % % % A mV μA nA μS kΩ 20 100 1.04 300 20 1.5 0.4 60 1.5 0.4 60 120 100 nA nA V nA μA V V μA V V μA Switching Frequency RT Voltage Soft-Start Pin Current SYNC Pull-Down Current (Into the Pin) SYNC Input Low SYNC Input High Maximum Duty Cycle ● Switch Current Limit Switch VCESAT Switch Leakage Current CTRL Input Bias Current Error Amplifier Transconductance VC Output Impedance VC Idle Input Bias Current FB Pin Input Bias Current FB Pin Threshold ISP , ISN Idle Input Bias Current ISP , ISN Full-Scale Input Bias Current SHDN Voltage High SHDN Voltage Low SHDN Pin Bias Current PWM Input High Voltage PWM Input Low Voltage PWM Pin Bias Current PWM = 0V ISP Tied to ISN, VISP = 24V, VCTRL = 2V –20 0.98 0 20 1.01 3517fa 3 LT3517 ELECTRICAL CHARACTERISTICS PARAMETER TGEN Input High Voltage TGEN Input Low Voltage TGEN Pin Bias Current VREF Pin Voltage VREF Pin Voltage Line Regulation Gate Turn-On Delay Gate Turn-Off Delay Top Gate Drive VGS (VISP – VTG) TGEN = 5V IREF = –100μA 3V < VIN < 40V CLOAD = 1nF Between ISP and TG CLOAD = 1nF Between ISP and TG VISP = 24V, TGEN = 5V PWM = 0V 200 200 7 0 0.3 ● The ● denotes the specifications which apply over the full operating temperature range, otherwise specifications are at TA = 25°C. (Note 2) VIN = 5V, SHDN = 5V, PWM = 5V unless otherwise noted. CONDITIONS MIN 1.5 0.4 100 1.96 2 200 2.04 0.03 TYP MAX UNITS V V μA V %/V ns ns V V Note 1: Stresses beyond those listed under Absolute Maximum Ratings may cause permanent damage to the device. Exposure to any Absolute Maximum Rating condition for extended periods may affect device reliability and lifetime. Note 2: The LT3517E is guaranteed to meet performance specifications from 0°C to 125°C junction temperature. Specifications over the –40°C to 125°C operating junction temperature range are assured by design, characterization and correlation with statistical process controls. The LT3517I is guaranteed over the full –40°C to 125°C operating junction temperature range. The LT3517H is guaranteed over the full –40ºC to 150ºC operating junction temperature range. Operating lifetime is derated at junction temperatures greater than 125ºC. Note 3: Absolute maximum voltage at VIN, SHDN, PWM and TGEN pins is 40V for nonrepetitive 1 second transients and 30V for continuous operation. Note 4: This IC includes overtemperature protection that is intended to protect the device during momentary overload conditions. Junction temperature will exceed the maximum operating junction temperature when overtemperature protection is active. Continuous operation above the specified maximum operating junction temperature may impair device reliability. TYPICAL PERFORMANCE CHARACTERISTICS VISP – VISN Threshold vs VCTRL 120 2.0 VIN = 5V VISP = 24V 100 VC = 1V TA = 25°C 80 60 40 20 0 0 0.2 0.4 0 0.6 0.8 1.0 VCTRL (V) 1.2 1.4 1.6 0 TA = 25°C 20 40 60 DUTY CYCLE (%) 80 100 3517 G02 Switch Current Limit vs Duty Cycle 10000 OSCILLATOR FREQUENCY (kHz) Oscillator Frequency vs RT TA = 25°C VISP – VISN THRESHOLD (mV) SWITCH CURRENT LIMIT (A) 1.5 1.0 1000 0.5 100 1 10 RT (kΩ) 100 3518 G03 3518 G01 3517fa 4 LT3517 TYPICAL PERFORMANCE CHARACTERISTICS VISP – VISN Threshold vs Temperature 104 VIN = 5V 103 VISP = 24V VC = 1V 102 VCTRL = 2V 101 100 99 98 97 96 –40 –20 0 20 40 60 80 100 120 140 160 TEMPERATURE (°C) 3517 G04 Switch Current Limit vs Temperature 2.5 VIN = 5V OSCILLATOR FREQUENCY (MHz) 2.5 Oscillator Frequency vs Temperature VIN = 5V RT = 6.04k VISP – VISN THRESHOLD (mV) SWITCH CURRENT LIMIT (A) 2.0 2.3 1.5 2.1 1.0 1.9 0.5 1.7 0 –40 –20 0 20 40 60 80 100 120 140 160 TEMPERATURE (°C) 3518 G05 1.5 –40 –20 0 20 40 60 80 100 120 140 160 TEMPERATURE (°C) 3517 G06 VISP – VISN Threshold vs VISP 105 104 VISP – VISN THRESHOLD (mV) 103 102 VREF (V) 101 100 99 98 97 96 95 0 10 30 20 VISP (V) 40 50 3517 G07 Reference Voltage vs Temperature 2.02 VIN = 5V 8 Quiescent Current vs VIN TA = 25°C 7 VC = 0V VIN CURRENT (mA) 6 5 4 3 2 1 VCTRL = 2V VIN = 5V TA = 25°C VC = 1V 2.01 2.00 1.99 1.98 –40 –20 0 20 40 60 80 100 120 140 160 TEMPERATURE (°C) 3517 G08 0 0 10 20 VIN (V) 30 40 3517 G09 FB Pin Threshold vs Temperature 1.04 1.03 FB PIN THRESHOLD (V) 1.02 1.01 40V 1.00 0.99 0.98 –40 –20 0 TG 30V VIN = 5V 5V PWM 0V PMOS Turn-On PMOS Turn-Off 5V PWM 0V 40V TG 30V 20 40 60 80 100 120 140 160 TEMPERATURE (°C) 3517 G10 VISP = 40V 200ns/DIV 3517 G11 VISP = 40V 200ns/DIV 3517 G11 3517fa 5 LT3517 PIN FUNCTIONS SW: Switch Pin. Minimize trace at this pin to reduce EMI. VIN: Input Supply Pin. Must be locally bypassed. SHDN: Shutdown Pin. Tie to 1.5V or higher to enable device or 0.4V or less to disable device. VREF: Reference Output Pin. This pin can supply up to 100μA. RT : Switching Frequency Adjustment Pin. Set switching frequency using a resistor to GND (see Typical Performance Characteristics for values). For SYNC function, choose the resistor to program a frequency 20% slower than the SYNC pulse frequency. Do not leave this pin open. SYNC: Frequency Synchronization Pin. Tie an external clock signal here. RT resistor should be chosen to program a switching frequency 20% slower than SYNC pulse frequency. Synchronization (power switch turn-on) occurs a fixed delay after the rising edge of SYNC. Tie the SYNC pin to ground if this feature is not used. SS: Soft-Start Pin. Place a soft-start capacitor here. Leave the pin open if not in use. PWM: Pulse Width Modulated Input Pin. Signal low turns off channel, disables the main switch and makes the TG pin high. Tie the PWM pin to VREF pin or SHDN pin if not used. There is an equivalent 50k resistor from PWM pin to ground internally. CTRL: LED Current Adjustment Pin. Sets voltage across sense resistor between ISP and ISN. Connect directly to VREF for full-scale threshold of 100mV, or use signal values between GND and 1V to modulate LED current. Tie the CTRL pin to the VREF pin if not used. VC: gm Error Amplifier Output Pin. Stabilize the loop with an RC network or compensating C. FB: Voltage Loop Feedback Pin. Works as overvoltage protection for LED drivers. If FB is higher than 1V, the main switch is turned off. TGEN: Top Gate Enable Input Pin. Tie to 1.5V or higher to enable the PMOS driver function. Tie the TGEN pin to ground if TG function is not used. There is an equivalent 40k resistor from TGEN pin to ground internally. ISN: Current Sense (–) Pin. The inverting input to the current sense amplifier. ISP: Current Sense (+) Pin. The noninverting input to the current sense amplifier. Also serves as positive rail for TG pin driver. TG: Top Gate Driver Output. An inverted PWM signal drives series PMOS device between VISP and (VISP – 7V). An internal 7V clamp protects the PMOS gate. Leave TG unconnected if not used. Ground: Exposed Pad. Solder paddle directly to ground plane. 3517fa 6 LT3517 BLOCK DIAGRAM CIN RSENSE PVIN LED ARRAY CFILT ISP ISN TG VISP CURRENT SENSE AMPLIFIER VISP – 7V MOSFET DRIVER TGEN PWM SW + X10 – SHDN CTRL 1V 1.01V FB VC SYNC 1V VIN SS RT + + – + – A1 + A3 ERROR AMPLIFIER + A4 R S Q MAIN SWITCH DRIVER Q1 POWER SWITCH + A2 – PWM COMPARATOR A8 SS + – GND RAMP GENERATOR VIN 2.5MHz TO 250kHz OSCILLATOR 100μA VREF + A5 – + + – 10μA 1V + A6 FREQ ADJUST VIN 3517 F01 Q2 2V A7 – Figure 1. Buck Mode LED Driver 3517fa 7 LT3517 OPERATION The LT3517 is a constant frequency, current mode regulator with an internal power switch. Operation can be best understood by referring to the Block Diagram in Figure 1. At the start of each oscillator cycle, the SR latch is set, which turns on the Q1 power switch. A voltage proportional to the switch current is added to a stabilizing ramp and the resulting sum is fed into the positive terminal of the PWM comparator, A4. When this voltage exceeds the level at the negative input of A4, the SR latch is reset, turning off the power switch. The level at the negative input of A4 is set by the error amplifier A3. A3 has two inputs, one from the voltage feedback loop and the other one from the current loop. Whichever feedback input is lower takes precedence, and forces the converter into either constant-current or constant-voltage mode. The LT3517 is designed to transition cleanly between these two modes of operation. The current sense amplifier senses the voltage across RSENSE and provides a pre-gain to amplifier A1. The output of A1 is simply an amplified version of the difference between the voltage across RSENSE and the lower of VCTRL/10 or 100mV. In this manner, the error amplifier sets the correct peak switch current level to regulate the current through RSENSE. If the error amplifier’s output increases, more current is delivered to the output; if it decreases, less current is delivered. The current regulated in RSENSE can be adjusted by changing the input voltage VCTRL. The current sense amplifier provides rail-to-rail current sense operation. The FB voltage loop is implemented by the amplifier A2. When the voltage loop dominates, the error amplifier and the amplifier A2 regulate the FB pin to 1.01V (constant-voltage mode). Dimming of the LED array is accomplished by pulsing the LED current using the PWM pin. When the PWM pin is low, switching is disabled and the error amplifier is turned off so that it does not drive the VC pin. Also, all internal loads on the VC pin are disabled so that the charge state of the VC pin will be saved on the external compensation capacitor. This feature reduces transient recovery time. When the PWM input again transitions high, the demand current for the switch returns to the value just before PWM last transitioned low. To further reduce transient recovery time, an external PMOS is used to disconnect the LED array current loop when PWM is low, stopping CFILT from discharging. APPLICATIONS INFORMATION Dimming Control There are two methods to control the current source for dimming using the LT3517. The first method uses the PWM pin to modulate the current source between zero and full current to achieve a precisely programmed average current. To make this method of current control more accurate, the switch demand current is stored on the VC node during the quiescent phase. This feature minimizes recovery time when the PWM signal goes high. To further improve the recovery time, a disconnect switch is used in the LED current path to prevent the output capacitor from discharging in the PWM signal low phase. The minimum PWM on or off time will depend on the choice of operating frequency through RT input pin or SYNC pin. When using the SYNC function, the SYNC and PWM signals must have the aligned rising edges to achieve the optimized high PWM dimming ratio. For best current accuracy, the minimum PWM low or high time should be at least four switching cycles (2μs for fSW = 2MHz). Maximum PWM period is determined by the system and is unlikely to be longer than 12ms. The maximum PWM dimming ratio (PWMRATIO) can be calculated from the maximum PWM period (tMAX) and the minimum PWM pulse width (tMIN) as follows: PWMRATIO = Example: tMAX = 10ms, tMIN = 2μs (fSW = 2MHz) PWMRATIO = 10ms/2μs = 5000:1 The second method of dimming control uses the CTRL pin to linearly adjust the current sense threshold during the PWM high state. When the CTRL pin voltage is less 3517fa tMAX tMIN (1) 8 LT3517 APPLICATIONS INFORMATION than 1V, the LED current is: ILED = VCTRL 10 • RSENSE (2) For a buck or a buck-boost configuration, the output voltage is typically level-shifted to a signal with respect to GND as illustrated in the Figure 4. The output can be expressed as: VOUT = R1 • 1.01V + VBE(Q2) R2 + R1 VOUT RSENSE LED ARRAY When VCTRL is higher than 1V, the LED current is clamped to be: ILED = 100mV RSENSE (3) (5) The LED current programming feature possibly increases total dimming range by a factor of ten. The CTRL pin should not be left open (tie to VREF if not used). The CTRL pin can also be used in conjunction with a PTC thermistor to provide overtemperature protection for the LED load. 2V 45.3k 49.9k CTRL LT3517 FB Q2 – R2 3517 F04 Figure 4 Inductor Selection The inductor used with the LT3517 should have a saturation current rating of 2A or greater. For buck mode LED drivers, the inductor value should be chosen to give a ripple current “ΔI” of ~30% to 40% of the LED current. In the buck mode, the inductor value can be estimated using the formula: L (µH) = DBUCK • t SW (µs) • (VIN – VLED) ΔI VLED VIN (6) VREF 5k PTC 3517 F02 Figure 2 Setting Output Voltage For a boost application, the output voltage can be set by selecting the values of R1 and R2 (see Figure 3) according to the following equation: ⎛ R1 ⎞ VOUT = ⎜ + 1⎟ • 1.01V ⎝ R2 ⎠ VOUT LT3517 FB R2 3517 F03 DBUCK = (4) VLED is the voltage across the LED string, VIN is the input voltage to the converter, and tSW is the switching period. In the boost configuration, the inductor can be estimated using the formula: L (µH) = DBOOST • t SW (µs) • VIN ΔI VLED – VIN VLED (7) R1 DBOOST = Figure 3 3517fa 9 LT3517 APPLICATIONS INFORMATION Table 1 provides some recommended inductor vendors. Table 1. Inductor Manufacturers VENDOR Sumida Toko Cooper Vishay PHONE (408) 321-9660 (408) 432-8281 (561) 998-4100 (402) 563-6866 WEB www.sumida.com www.toko.com www.cooperet.com www.vishay.com Input Capacitor Selection For proper operation, it is necessary to place a bypass capacitor to GND close to the VIN pin of the LT3517. A 1μF or greater capacitor with low ESR should be used. A ceramic capacitor is usually the best choice. In the buck mode configuration, the capacitor at the input to the power converter has large pulsed currents due to the current returned though the Schottky diode when the switch is off. For best reliability, this capacitor should have low ESR and ESL and have an adequate ripple current rating. The RMS input current is: IIN(RMS) = ILED • (1 – D) • D (8) To achieve the same LED ripple current, the required filter capacitor value is larger in the boost and buck-boost mode applications than that in the buck mode applications. For LED buck mode applications, a 1μF ceramic capacitor is usually sufficient. For the LED boost and buck-boost mode applications, a 2.2μF ceramic capacitor is usually sufficient. Very high performance PWM dimming applications may require a larger capacitor value to support the LED voltage during PWM transitions. Use only ceramic capacitors with X7R, X5R or better dielectric as they are best for temperature and DC bias stability of the capacitor value. All ceramic capacitors exhibit loss of capacitance value with increasing DC voltage bias, so it may be necessary to choose a higher value capacitor to get the required capacitance at the operation voltage. Always check that the voltage rating of the capacitor is sufficient. Table 2 shows some recommended capacitor vendors. Table 2. Ceramic Capacitor Manufacturers VENDOR Taiyo Yuden AVX Murata TDK PHONE (408) 573-4150 (843) 448-9411 (770) 436-1300 (847) 803-6100 WEB www.t-yuden.com www.avxcorp.com www.murata.com www.tdk.com where D is the switch duty cycle. A 2.2μF ceramic type capacitor is usually sufficient. Output Capacitor Selection The selection of output capacitor depends on the load and converter configuration, i.e., step-up or step-down. For LED applications, the equivalent resistance of the LED is typically low, and the output filter capacitor should be sized to attenuate the current ripple. Loop Compensation The LT3517 uses an internal transconductance error amplifier whose VC output compensates the control loop. The external inductor, output capacitor, and the compensation resistor and capacitor determine the loop stability. The inductor and output capacitor are chosen based on 3517fa 10 LT3517 APPLICATIONS INFORMATION performance, size and cost. The compensation resistor and capacitor at VC are selected to optimize control loop stability. For typical LED applications, a 10nF compensation capacitor at VC is adequate and a series resistor is not required. A compensation resistor may be used to increase the slew rate on the VC pin to maintain tighter regulation of LED current during fast transients on VIN or CTRL. Diode Selection The Schottky diode conducts current during the interval when the switch is turned off. Select a diode rated for the maximum SW voltage. If using the PWM feature for dimming, it is important to consider diode leakage, which increases with the temperature, from the output during the PWM low interval. Therefore, choose the Schottky diode with sufficiently low leakage current. Table 3 has some recommended component vendors. Table 3. Schottky Diodes PART NUMBER Diodes Inc. DFLS160 Zetex ZLLS1000TA International Rectifier 10MQ060N 60 1.5 40 1 60 1 VR (V) IAVE (A) Board Layout The high speed operation of the LT3517 demands careful attention to board layout and component placement. The Exposed Pad of the package is the only GND terminal of the IC and is also important for thermal management of the IC. It is crucial to achieve a good electrical and thermal contact between the Exposed Pad and the ground plane of the board. To reduce electromagnetic interference (EMI), it is important to minimize the area of the SW node. Use a GND plane under SW and minimize the length of traces in the high frequency switching path between SW and GND through the diode and the capacitors. Since there is a small DC input bias current to the ISN and ISP inputs, resistance in series with these inputs should be minimized and matched, otherwise there will be an offset. Finally, the bypass capacitor on the VIN supply to the LT3517 should be placed as close as possible to the VIN terminal of the device. Soft-Start For many applications, it is necessary to minimize the inrush current at start-up. The built-in soft-start circuit significantly reduces the start-up current spike and output voltage overshoot. A typical value for the soft-start capacitor is 0.1μF . 3517fa 11 LT3517 APPLICATIONS INFORMATION Switching Frequency There are two methods to set the switching frequency of LT3517. Both methods require a resistor connected at RT pin. Do not leave the RT pin open. Also, do not load this pin with a capacitor. A resistor must always be connected for proper operation. One way to set the frequency is simply connecting an external resistor between the RT pin and GND. See Table 4 below or see the Oscillator Frequency vs RT graph in the Typical Performance Characteristics for resistor values and corresponding switching frequencies. Table 4. Switching Frequency vs RT Switching Frequency (kHz) 250 500 1000 1500 2000 2500 RT ( kΩ ) 90.9 39.2 16.9 9.53 6.04 4.02 In general, a lower switching frequency should be used where either very high or very low switching duty cycle operation is required, or high efficiency is desired. Selection of a higher switching frequency will allow use of smaller value external components and yield a smaller solution size and profile. Thermal Considerations The LT3517 is rated to a maximum input voltage of 30V for continuous operation, and 40V for nonrepetitive one second transients. Careful attention must be paid to the internal power dissipation of the LT3517 at higher input voltages to ensure that the maximum junction temperature is not exceeded. This junction limit is especially important when operating at high ambient temperatures. The Exposed Pad on the bottom of the package must be soldered to a ground plane. This ground should then be connected to an internal copper ground plane with thermal vias placed directly under the package to spread out the heat dissipated by the LT3517. The other way is to make the LT3517 synchronize with an external clock via SYNC pin. For proper operation, a resistor should be connected at the RT pin and be able to generate a switching frequency 20% lower than the external clock when external clock is absent. 3517fa 12 LT3517 TYPICAL APPLICATIONS Buck Mode 1A LED Driver RSENSE 100mΩ C2 2.2μF ISP VIN C1 2.2μF VREF PWM SHDN LT3517 CTRL PWM FB SS IL 1A/DIV 1μs/DIV RT 16.9k 1MHz C5 0.1μF 3517 TA02a 3517 TA02b PVIN 24V M1 1A C3 10μF L1 15μH D1 SW ILED 1A/DIV PWM 5V/DIV 2000:1 PWM Dimming at 120Hz VIN 3.3V ISN TG RT SYNC TGEN VREF VC GND C4 0.1μF C1: KEMET C0805C225K4RAC C2: MURATA GRM31MR71E225KA93 C3: MURATA GRM32DR71E106KA12B C4, C5: MURATA GRM21BR71H104KA01B D1: DIODES DFLS160 L1: TOKO B992AS-150M LEDS: LUXEON K2 (WHITE) M1: ZETEX ZXMP6A13FTA PVIN = 24V fOSC = 1MHz ILED = 1A 350mA, 5V to 12V Boost Converter with Accurate Input Current Limit RSENSE L1 100mΩ 6.8μH D1 VIN 5V C1 2.2μF VOUT 12V 350mA R1 549k EFFICIENCY (%) Efficiency 90 ISP TG ISN VIN CTRL PWM SHDN SHDN TGEN VREF VC R3 10k C4 10nF C1: KEMET C0805C225K4RAC C2: KEMET C1206C106K4RAC C3: MURATA GRM21BR71H104KA01B C4: MURATA GCM033R71A103KA03 D1: ZETEX ZLLS1000TA L1: TOKO B992AS-6R8N GND LT3517 SW FB C2 10μF R2 49.9k 80 70 SYNC RT SS C3 0.1μF RT 6.04k 2MHz 3517 TA03a 60 50 50 100 150 200 250 ILOAD(mA) 300 350 3517 TA03b 3517fa 13 LT3517 TYPICAL APPLICATIONS Buck-Boost Mode LED Driver L1 6.8μH D1 R1 3.92M FB R2 124k PWM PWM TGEN C1 2.2μF VREF CTRL ISN TG M1 C2 4.7μF LT3517 ISP RSENSE 330mΩ 300mA C5 0.22μF VIN 8V TO 16V SHDN VIN SW SYNC VC RT 6.04k 2MHz C3 0.1μF RT SS GND C4 0.1μF 3517 TA04a C1: KEMET C0806C225K4RAC C2: KEMET C1206C475K3RAC C3, C4: MURATA GRM21BR71H104KA01B C5: MURATA GRM21BR71H224KA01B D1: DIODE DFLS160 L1: TOKO B992AS-6R8N LEDS: LUXEON I (WHITE) M1: ZETEX ZXMP6A13FTA 5000:1 PWM Dimming at 100Hz 90 PWM 5V/DIV EFFICIENCY (%) ILED 200mA/DIV 80 70 60 50 40 500ns/DIV VIN = 12V fOSC = 2MHz ILED = 300mA 3517 TA04b Efficiency VIN = 12V CTRL = VREF IL 1A/DIV 30 20 0 20 40 60 80 PWM DUTY CYCLE (%) 100 3517 TA04c 3517fa 14 LT3517 TYPICAL APPLICATIONS Low Side Current Sensing Load Dump Protected Buck-Boost Mode LED Driver L1 6.8μH D1 R1 3.92M FB R2 124k PWM PWM TGEN VREF C1 2.2μF CTRL ISN SYNC VC R3 10k C4 33nF RT 6.04k 2MHz C3 0.1μF 3517 TA05a VIN 8V TO 16V SHDN VIN SW C5 0.22μF LT3517 ISP RSENSE 330mΩ C2 4.7μF M1 300mA D1: DIODES DFLS160 L1: TOKO B992AS-6R8N C1: KEMET C0806C225K4RAC C2: KEMET C1206C475K3RAC C3: MURATA GRM21BR71H104KA01B C4: MURATA GRM219R71H333KAQ01B C5: MURATA GRM21BR71H224KA01B M1: ZETEX ZXMP6A13FTA LEDs: LUXEON I (WHITE) TG RT SS GND 5000:1 PWM Dimming at 100Hz 90 PWM 5V/DIV EFFICIENCY (%) ILED 200mA/DIV 80 70 60 50 40 500ns/DIV VIN = 12V fOSC = 2MHz ILED = 300mA 3517 TA05b Efficiency VIN = 12V CTRL = VREF IL 1A/DIV 30 20 0 20 40 60 80 PWM DUTY CYCLE (%) 100 3517 TA05c Load Dump Response VISP 10V/DIV VISP 15V TO 40V VIN 15V TO 40V VISP REF GND VIN REF GND ILED 200mA/DIV IL 1A/DIV 5ms/DIV VIN Raises From 15V to 40V in 5ms. 3517 TA05d VIN 10V/DIV 3517fa 15 LT3517 TYPICAL APPLICATIONS Boost 100mA LED Driver with LED Open Protection L1 22μH D1 VIN 8V TO 16V SHDN VIN PWM TGEN VREF C1 2.2μF CTRL SYNC VC RT 16.9k 1MHz C4 0.1μF PWM SW ISP RSENSE 1Ω LT3517 ISN TG FB R1 1M 100mA C3 0.1μF R2 30.1k M1 LED1 LED2 C1, C2: KEMET C1206C225K2RAC C3, C4: MURATA GRM21BR71H104KA01B D1: DIODES DFLS160 L1: COILCRAFT DS3316P-223 LEDS: CREE XLAMP 7090 M1: ZETEX ZXMP6A13FTA C2 2.2μF RT SS GND LED10 3517 TA06a 3000:1 PWM Dimming at 100Hz 90 PWM 5V/DIV ILED 100mA/DIV IL 500mA/DIV 1μs/DIV VIN = 12V fOSC = 1MHz ILED = 100mA 3517 TA06b Efficiency 80 70 EFFICIENCY (%) 60 50 40 30 20 0 20 40 60 80 PWM DUTY CYCLE (%) 100 3517 TA06c VIN = 12V CTRL = VREF 3517fa 16 LT3517 TYPICAL APPLICATION 5.5V SEPIC Converter with Short-Circuit Protection Efficiency VIN 3V C2 2.2μF VIN CTRL SYNC SHDN SHDN TGEN VREF VC R3 10k C4 10nF C1: KEMET C0805C225K4RAC C2, C5: KEMET C1206C106K4RAC C3: MURATA GRM21BR71H104KA01B C4: MURATA GCM033R71A103KA03 D1: ZETEX ZLLS1000TA L1, L2: TOKO B992AS-4R3N GND SS C3 0.1μF RT 6.04k 2MHz 3517 TA07a 3517 TA07b L1 4.3μH C5 10μF D1 RSENSE 0.22Ω VOUT 5.5V 350mA R1 221k EFFICIENCY (%) R2 49.9k 90 80 70 60 50 40 30 0 50 100 150 200 ILOAD (mA) 250 300 350 L2 4.3μH PWM SW FB TG LT3517 ISP ISN RT C2 10μF 3517fa 17 LT3517 PACKAGE DESCRIPTION UF Package 16-Lead Plastic QFN (4mm × 4mm) (Reference LTC DWG # 05-08-1692) 0.72 0.05 4.35 0.05 2.90 2.15 0.05 0.05 (4 SIDES) NOTE: 1. DRAWING CONFORMS TO JEDEC PACKAGE OUTLINE MO-220 VARIATION (W 2. DRAWING NOT TO SCALE 3. ALL DIMENSIONS ARE IN MILLIMETERS 4. DIMENSIONS OF EXPOSED PAD ON BOTTOM OF PACKAGE DO NOT INCLUDE MOLD FLASH. MOLD FLASH, IF PRESENT, SHALL NOT EXCEED 0.15mm ON A 5. EXPOSED PAD SHALL BE SOLDER PLATED 6. SHADED AREA IS ONLY A REFERENCE FOR PIN 1 LOCATION ON THE TOP AND BOTTOM OF PACKAGE PACKAGE OUTLINE 0.30 0.05 0.65 BSC RECOMMENDED SOLDER PAD PITCH AND DIMENSIONS BOTTOM VIEW—EXPOSED PAD 4.00 0.10 (4 SIDES) PIN 1 TOP MARK (NOTE 6) 0.75 0.05 R = 0.115 TYP PIN 1 NOTCH R = 0.20 TYP OR 0.35 45 CHAMFER 15 16 0.55 1 0.20 2.15 0.10 (4-SIDES) 2 (UF16) QFN 1004 0.200 REF 0.00 – 0.05 0.30 0.05 0.65 BSC 3517fa 18 LT3517 PACKAGE DESCRIPTION FE Package 16-Lead Plastic TSSOP (4.4mm) (Reference LTC DWG # 05-08-1663) Exposed Pad Variation BA 2.74 (.108) 4.90 – 5.10* (.193 – .201) 2.74 (.108) 16 1514 13 12 1110 9 6.60 0.10 4.50 0.10 SEE NOTE 4 2.74 (.108) 0.45 0.05 1.05 0.65 BSC 0.10 2.74 6.40 (.108) (.252) BSC RECOMMENDED SOLDER PAD LAYOUT 12345678 1.10 (.0433) MAX 0° – 8° 4.30 – 4.50* (.169 – .177) 0.25 REF 0.09 – 0.20 (.0035 – .0079) 0.50 – 0.75 (.020 – .030) 0.65 (.0256) BSC NOTE: 1. CONTROLLING DIMENSION: MILLIMETERS MILLIMETERS 2. DIMENSIONS ARE IN (INCHES) 3. DRAWING NOT TO SCALE 0.195 – 0.30 (.0077 – .0118) TYP 0.05 – 0.15 (.002 – .006) FE16 (BA) TSSOP 0204 4. RECOMMENDED MINIMUM PCB METAL SIZE FOR EXPOSED PAD ATTACHMENT *DIMENSIONS DO NOT INCLUDE MOLD FLASH. MOLD FLASH SHALL NOT EXCEED 0.150mm (.006") PER SIDE 3517fa Information furnished by Linear Technology Corporation is believed to be accurate and reliable. However, no responsibility is assumed for its use. Linear Technology Corporation makes no representation that the interconnection of its circuits as described herein will not infringe on existing patent rights. 19 LT3517 RELATED PARTS PART NUMBER LT1618 LT3003 LT3474 LT3475 LT3476 LT3477 LT3478/LT3478-1 LT3479 LT3486 LT3496 LT3518 LT3590 LT3595 LTC®3783 DESCRIPTION Constant Current, 1.4MHz, 1.5A Boost Converter 3-Channel LED Ballaster with PWM Dimming 36V, 1A (ILED), 2MHz, Step-Down LED Driver Dual 1.5A (ILED), 36V 2MHz Step-Down LED Driver Quad Output 1.5A, 36V, 2MHz High Current LED Driver with 1,000:1 Dimming 3A, 42V, 3MHz Boost, Buck-Boost, Buck LED Driver 4.5A, 42V, 2.5MHz High Current LED Driver with 3,000:1 Dimming 3A, Full Featured DC/DC Converter with Soft-Start and Inrush Current Protection Dual 1.3A, 2MHz High Current LED Driver Triple Output LED Driver Full-Featured LED Driver with 2.3A Switch Current 48V Buck Mode 50mA LED Driver 16 Channel Buck LED Driver Mode High Current LED Controller COMMENTS VIN: 5V to 18V, VOUT(MAX) = 36V, Dimming = Analog/PWM, ISD < 1μA, MSOP10 Package VIN: 3V to 48V, Dimming = 3,000:1 True Color PWM, ISD < 5μA, MSOP10 Package VIN: 4V to 36V, VOUT(MAX) = 13.5V, Dimming = 400:1 True Color PWM, ISD < 1μA, TSSOP16E Package VIN: 4V to 36V, VOUT(MAX) = 13.5V, Dimming = 3,000:1 True Color PWM, ISD < 1μA, TSSOP20E Package VIN: 2.8V to 16V, VOUT(MAX) = 36V, Dimming = 1,000:1 True Color PWM, ISD < 10μA, 5mm × 7mm QFN Package VIN: 2.5V to 25V, VOUT(MAX) = 40V, Dimming = Analog/PWM, ISD < 1μA, QFN, TSSOP20E Packages VIN: 2.8V to 36V, VOUT(MAX) = 42V, Dimming = 3,000:1 True Color PWM, ISD < 3μA, TSSOP16E Packages VIN: 2.5V to 24V, VOUT(MAX) = 40V, IQ = 6.5mA, ISD < 1μA, DFN and TSSOP Packages VIN: 2.5V to 24V, VOUT(MAX) = 36V, Dimming = 1,000:1 True Color PWM, ISD < 1μA, 5mm × 3mm DFN, TSSOP16E VIN: 3V to 40V, VOUT(MAX) = 45V, Dimming = 3,000:1 True Color PWM, ISD < 10μA, 4mm × 5mm QFN Package VIN: 3V to 40V, VOUT(MAX) = 45V, Dimming = 3,000:1 True Color PWM, ISD < 10μA, 4mm × 4mm QFN Package VIN: 4.5V to 55V, Drives Up to 10 LEDs, 200:1 Dimming, ISO = 15mA, 2mm × 2mm DFN SC70 VIN: 4.5V to 45V, Drives Up to 160 LEDs, 5,000:1 Dimming, 5mm × 9mm QFN VIN: 3V to 36V, VOUT(MAX) = Ext FET, Dimming = 3,000:1 True Color PWM, ISD < 20μA, 5mm × 4mm QFN10, TSSOP16E Packages 3517fa 20 Linear Technology Corporation (408) 432-1900 ● FAX: (408) 434-0507 ● LT 0308 REV A • PRINTED IN USA 1630 McCarthy Blvd., Milpitas, CA 95035-7417 www.linear.com © LINEAR TECHNOLOGY CORPORATION 2007