LTC3406AIS5-PBF

FEATURES ■ ■ ■ LTC3406A 1.5MHz, 600mA Synchronous Step-Down Regulator in ThinSOT DESCRIPTION The LTC®3406A is a high efficiency monolithic synchronous buck regulator using a constant frequency, current mode architecture. Supply current during operation is only 20μA, dropping to ≤1μA in shutdown. The 2.5V to 5.5V input voltage range makes the LTC3406A ideally suited for single Li-Ion battery-powered applications. 100% duty cycle provides low dropout operation, extending battery runtime portable systems. Automatic Burst Mode operation increases efficiency at light loads, further extending battery runtime. Switching frequency is internally set at 1.5MHz, allowing the use of small surface mount inductors and capacitors. The internal synchronous switch increases efficiency and eliminates the need for an external Schottky diode. Low output voltages are easily supported with the 0.6V feedback reference voltage. The LTC3406A is available in a low profile (1mm) ThinSOT package. , LT LTC and LTM are registered trademarks of Linear Technology Corporation. , ThinSOT is a registered trademark of Linear Technology Corporation. All other trademarks are the property of their respective owners. Protected by U.S. Patents including 5481178, 6580258. ■ ■ ■ ■ ■ ■ ■ ■ ■ ■ ■ High Efficiency: Up to 96% Very Low Quiescent Current: Only 20µA Low Output Ripple Voltage During Burst Mode® Operation 600mA Output Current 2.5V to 5.5V Input Voltage Range 1.5MHz Constant Frequency Operation No Schottky Diode Required Low Dropout Operation: 100% Duty Cycle ±2% 0.6V Reference Shutdown Mode Draw ≤1µA Supply Current Internal Soft-Start Limits Inrush Current Current Mode Operation for Excellent Line and Load Transient Response Overtemperature Protected Low Profile (1mm) ThinSOTTM Package APPLICATIONS ■ ■ ■ ■ ■ ■ Cellular Telephones Wireless and DSL Modems Digital Still Cameras Media Players Portable Instruments Point of Load Regulation TYPICAL APPLICATION Efficiency vs Load Current 100 2.2μH VIN 4.7μF CER VIN SW 22pF 10μF CER 619k 309k 3406A TA01 VOUT 1.8V 600mA EFFICIENCY (%) 90 80 70 60 50 40 30 20 10 VIN = 2.7V VIN = 3.6V VIN = 4.2V 1000 3406A TA01b LTC3406A RUN GND VFB VOUT = 1.8V 0 0.1 10 100 1 OUTPUT CURRENT (mA) 3406afa 1 LTC3406A ABSOLUTE MAXIMUM RATINGS (Note 1) PIN CONFIGURATION TOP VIEW RUN 1 GND 2 SW 3 4 VIN 5 VFB Input Supply Voltage ....................................– 0.3V to 6V RUN, VFB Voltages .......................................–0.3V to VIN SW Voltage (DC) ........................... – 0.3V to (VIN + 0.3V) P-Channel Switch Source Current (DC) (Note 7)................................................................800mA N-Channel Switch Sink Current (DC) (Note 7) .....800mA Peak SW Sink and Source Current (Note 7) .............1.3A Operating Temperature Range (Note 2) LTC3406AE ..............................................– 40°C to 85°C LTC3406AI .............................................– 40°C to 125°C Junction Temperature (Notes 3, 6)........................ 125°C Storage Temperature Range...................– 65°C to 150°C Lead Temperature (Soldering, 10 sec) .................. 300°C S5 PACKAGE 5-LEAD PLASTIC TSOT-23 TJMAX = 125°C, θJA = 250°C/W, θJC = 90°C/W ORDER INFORMATION LEAD FREE FINISH LTC3406AES5#PBF LTC3406AIS5#PBF TAPE AND REEL LTC3406AES5#TRPBF LTC3406AIS5#TRPBF PART MARKING* LTCWJ LTCWJ PACKAGE DESCRIPTION 5-Lead Plastic TSOT-23 5-Lead Plastic TSOT-23 TEMPERATURE RANGE –40°C to 85°C –40°C to 125°C Consult LTC Marketing for parts specified with wider operating temperature ranges. *Temperature grades are identified by a label on the shipping container. Consult LTC Marketing for information on non-standard lead based finish parts. For more information on lead free part marking, go to: http://www.linear.com/leadfree/ For more information on tape and reel specifications, go to: http://www.linear.com/tapeandreel/ ELECTRICAL CHARACTERISTICS SYMBOL IVFB VFB ∆VFB IPK VLOADREG VIN IS PARAMETER Feedback Current Regulated Feedback Voltage Reference Voltage Line Regulation Peak Inductor Current Output Voltage Load Regulation Input Voltage Range Input DC Bias Current Active Mode Sleep Mode Shutdown Oscillator Frequency RDS(ON) of P-Channel FET The ● denotes the specifications which apply over the full operating temperature range, otherwise specifications are at TA = 25°C. VIN = 3.6V unless otherwise specified. CONDITIONS ● MIN ● ● ● ● TYP 0.6 0.6 0.04 0.04 MAX ±30 0.6120 0.615 0.4 0.6 1.25 UNITS nA V V %/V %/V A % (Note 4) LTC3406AE (Note 4) LTC3406AI VIN = 2.5V to 5.5V (Note 4) LTC3406AE VIN = 2.5V to 5.5V (Note 4) LTC3406AI VIN = 3V, VFB = 0.5V Duty Cycle < 35% 0.5880 0.585 0.75 1 0.5 ● 2.5 200 16 0.1 5.5 300 30 1 1.8 0.35 V μA μA μA MHz Ω 3406afa (Note 5) VFB = 0V VFB = 0.63V VRUN = 0V, VIN = 5.5V VFB = 0.6V ISW = 100mA ● fOSC RPFET 1.2 1.5 0.23 2 LTC3406A ELECTRICAL CHARACTERISTICS SYMBOL RNFET ILSW tSOFT-START VRUN IRUN PARAMETER RDS(ON) of N-Channel FET SW Leakage Soft-Start Time RUN Threshold RUN Leakage Current The ● denotes the specifications which apply over the full operating temperature range, otherwise specifications are at TA = 25°C. VIN = 3.6V unless otherwise specified. CONDITIONS ISW = –100mA VRUN = 0V, VSW = 0V or 5V, VIN = 5V VFB from 10% to 90% Full-Scale ● ● MIN TYP 0.21 ±0.01 MAX 0.35 ±1 1.2 1.5 ±1 UNITS Ω μA ms V μA 0.6 0.3 0.9 1 ±0.01 Note 1: Stresses beyond those listed under Absolute Maximum Ratings may cause permanent damage to the device. Exposure to any Absolute Maximum Rating condition for extended periods may affect device reliability and lifetime. Note 2: The LTC3406AE is guaranteed to meet performance specifications from 0°C to 85°C. Specifications over the –40°C to 85°C operating temperature range are assured by design, characterization and correlation with statistical process controls. The LTC3406AI is guaranteed to meet the specified performance over the full –40°C to 125°C operating temperature range. Note 3: TJ is calculated from the ambient temperature TA and power dissipation PD according to the following formula: LTC3406A: TJ = TA + (PD)(250°C/W) Note 4: The LTC3406A is tested in a proprietary test mode that connects VFB to the output of the error amplifier. Note 5: Dynamic supply current is higher due to the gate charge being delivered at the switching frequency. Note 6: This IC includes overtemperature protection that is intended to protect the device during momentary overload conditions. Junction temperature will exceed 125°C when overtemperature protection is active. Continuous operation above the specified maximum operating junction temperature may impair device reliability. Note 7: Limited by long term current density considerations. TYPICAL PERFORMANCE CHARACTERISTICS (From Front Page Figure Except for the Resistive Divider Resistor Values) Efficiency vs Input Voltage 100 90 80 EFFICIENCY (%) EFFICIENCY (%) 70 60 50 40 30 20 10 0 2 VOUT = 1.8V 3 IL = 10mA IL = 100mA IL = 600mA 6 3406A G01 Efficiency vs Load Current 100 90 80 EFFICIENCY (%) 70 60 50 40 30 20 10 VIN = 2.7V VIN = 3.6V VIN = 4.2V 1000 3406A G02 Efficiency vs Load Current 100 90 80 70 60 50 40 30 20 10 VIN = 2.7V VIN = 3.6V VIN = 4.2V 1000 3406A G03 4 5 INPUT VOLTAGE (V) VOUT = 1.2V 0 0.1 1 10 100 OUTPUT CURRENT (mA) VOUT = 2.5V 0 0.1 1 10 100 OUTPUT CURRENT (mA) 3406afa 3 LTC3406A TYPICAL PERFORMANCE CHARACTERISTICS (From Front Page Figure Except for the Resistive Divider Resistor Values) Output vs Load Current 1.820 1.816 1.812 OUTPUT VOLTAGE (V) 1.808 1.804 1.800 1.796 1.792 1.788 1.784 1.780 0 400 200 OUTPUT CURRENT (mA) 600 3406A G04 Efficiency vs Input Voltage VIN = 2.7V VIN = 3.6V VIN = 4.2V EFFICIENCY (%) 100 90 80 70 60 50 40 30 20 10 0 2 VOUT = 2.5V 3 IL = 10mA IL = 100mA IL = 600mA 6 3406A G05 Reference Voltage vs Temperature 0.615 0.610 REFERENCE VOLTAGE (V) 0.605 0.600 0.595 0.590 0.585 –50 –25 VIN = 3.6V VOUT = 1.8V 4 5 INPUT VOLTAGE (V) 50 25 75 0 TEMPERATURE (°C) 100 125 3406A G06 Oscillator Frequency vs Temperature 1.60 OSCILLATOR FREQUENCY (MHz) 1.55 1.50 1.45 1.40 1.35 1.30 –50 –25 VIN = 3.6V OSCILLATOR FREQUENCY (MHz) 1.60 1.55 1.50 1.45 1.40 1.35 1.30 1.25 50 25 75 0 TEMPERATURE (°C) 100 125 Oscillator Frequency vs Input Voltage Burst Mode SW 2V/DIV VOUT 20mV/DIV AC COUPLED IL 200mA/DIV 1.20 2.0 2.5 3.0 3.5 4.0 4.5 5.0 INPUT VOLTAGE (V) 5.5 6.0 4μs/DIV VIN = 3.6V VOUT = 1.8V ILOAD = 10mA Burst Mode OPERATION 3406A G09 3406A G07 3406A G08 RDS(ON) vs Input Voltage 0.40 0.35 0.30 RDS(ON) (Ω) RDS(0N) (Ω) MAIN SWITCH 0.25 SYNCHRONOUS SWITCH 0.20 0.15 0.10 0 1 4 3 5 2 INPUT VOLTAGE (V) 6 7 0.40 0.35 0.30 0.25 0.20 0.15 0.10 0.05 RDS(ON) vs Temperature 10 9 VIN = 2.7V VIN = 3.6V DYNAMIC SUPPLY CURRENT (μA) 8 7 6 5 4 3 2 1 0 Dynamic Supply Current VOUT = 1.2V ILOAD = 0A VIN = 4.2V SYNCHRONOUS SWITCH MAIN SWITCH 0 75 50 25 TEMPERATURE (°C) 100 125 0 –50 –25 2.0 2.5 3.0 3.5 4.0 4.5 5.0 INPUT VOLTAGE (V) 5.5 6.0 3406A G10 3406A G11 3406A G12 3406afa 4 LTC3406A TYPICAL PERFORMANCE CHARACTERISTICS (From Front Page Figure Except for the Resistive Divider Resistor Values) Dynamic Supply Current vs Temperature 300 DYNAMIC SUPPLY CURRENT (μA) 250 200 150 100 50 0 –50 –25 VIN = 3.6V VOUT = 1.2V ILOAD = 0A SWITCH LEAKAGE (nA) 140 120 100 80 MAIN SWITCH 60 40 20 0 –50 –25 SYNCHRONOUS SWITCH SWITCH LEAKAGE (pA) Switch Leakage vs Temperature 1000 900 800 700 600 500 400 300 200 100 0 50 25 75 0 TEMPERATURE (°C) 100 125 Switch Leakage vs Input Voltage RUN = 0V MAIN SWITCH SYNCHRONOUS SWITCH 50 25 75 0 TEMPERATURE (°C) 100 125 0 1 3 4 2 INPUT VOLTAGE (V) 5 6 3406A G15 3406A G13 3406A G14 Start-Up from Shutdown Load Step VOUT 200mV/DIV Load Step RUN 2V/DIV VOUT 1V/DIV ILOAD 500mA/DIV VOUT 200mV/DIV IL 500mA/DIV ILOAD 500mA/DIV IL 500mA/DIV ILOAD 500mA/DIV 500μs/DIV VIN = 3.6V VOUT = 1.8V ILOAD = 600mA (3Ω RES) 3406A G16 VIN = 3.6V 20μs/DIV VOUT = 1.8V ILOAD = 0mA TO 600mA 3406A G17 VIN = 3.6V 20μs/DIV VOUT = 1.8V ILOAD = 50mA TO 600mA 3406A G18 Load Step Load Step Discontinuous Operation VOUT 200mV/DIV IL 500mA/DIV ILOAD 500mA/DIV VOUT 200mV/DIV IL 500mA/DIV ILOAD 500mA/DIV SW 2V/DIV VOUT 20mV/DIV AC COUPLED IL 200mA/DIV VIN = 3.6V 20μs/DIV VOUT = 1.8V ILOAD = 100mA TO 600mA 3406A G19 VIN = 3.6V 20μs/DIV VOUT = 1.8V ILOAD = 200mA TO 600mA 3406A G20 VIN = 3.6V VOUT = 1.8V ILOAD = 50mA 500ns/DIV 3406A G21 3406afa 5 LTC3406A PIN FUNCTIONS RUN (Pin 1): Run Control Input. Forcing this pin above 1.5V enables the part. Forcing this pin below 0.3V shuts down the device. In shutdown, all functions are disabled drawing 40%. However, the LTC3406A uses a patented scheme that counteracts this compensating ramp, which allows the maximum inductor peak current to remain unaffected throughout all duty cycles. 3406afa 7 LTC3406A APPLICATIONS INFORMATION The basic LTC3406A application circuit is shown on the front page. External component selection is driven by the load requirement and begins with the selection of L followed by CIN and COUT. Inductor Selection For most applications, the value of the inductor will fall in the range of 1μH to 4.7μH. Its value is chosen based on the desired ripple current. Large value inductors lower ripple current and small value inductors result in higher ripple currents. Higher VIN or VOUT also increases the ripple current as shown in Equation 1. A reasonable starting point for setting ripple current is ∆IL = 240mA (40% of 600mA). IL = V 1 VOUT 1 OUT VIN ( f )(L ) (1) Sumida CMD4D06 Panasonic ELT5KT Murata LQH32CN Table 1. Representative Surface Mount Inductors PART NUMBER Sumida CDRH3D16 VALUE (μH) 1.5 2.2 3.3 4.7 2.2 3.3 4.7 3.3 4.7 1.0 2.2 4.7 DCR (Ω MAX) 0.043 0.075 0.110 0.162 0.116 0.174 0.216 0.17 0.20 0.060 0.097 0.150 MAX DC CURRENT (A) 1.55 1.20 1.10 0.90 0.950 0.770 0.750 1.00 0.95 1.00 0.79 0.65 SIZE W × L × H (mm3) 3.8 × 3.8 × 1.8 3.5 × 4.3 × 0.8 4.5 × 5.4 × 1.2 2.5 × 3.2 × 2.0 The DC current rating of the inductor should be at least equal to the maximum load current plus half the ripple current to prevent core saturation. Thus, a 720mA rated inductor should be enough for most applications (600mA + 120mA). For better efficiency, choose a low DC-resistance inductor. The inductor value also has an effect on Burst Mode operation. The transition to low current operation begins when the inductor current peaks fall to approximately 100mA. Lower inductor values (higher ∆IL) will cause this to occur at lower load currents, which can cause a dip in efficiency in the upper range of low current operation. In Burst Mode operation, lower inductance values will cause the burst frequency to increase. Inductor Core Selection Different core materials and shapes will change the size/current and price/current relationship of an inductor. Toroid or shielded pot cores in ferrite or permalloy materials are small and don’t radiate much energy, but generally cost more than powdered iron core inductors with similar electrical characteristics. The choice of which style inductor to use often depends more on the price vs size requirements and any radiated field/EMI requirements than on what the LTC3406A requires to operate. Table 1 shows some typical surface mount inductors that work well in LTC3406A applications. CIN and COUT Selection In continuous mode, the source current of the top MOSFET is a square wave of duty cycle VOUT/VIN. To prevent large voltage transients, a low ESR input capacitor sized for the maximum RMS current must be used. The maximum RMS capacitor current is given by: CIN required IRMS IOMAX VOUT ( VIN VOUT ) VIN 1/2 This formula has a maximum at VIN = 2VOUT, where IRMS = IOUT/2. This simple worst-case condition is commonly used for design because even significant deviations do not offer much relief. Note that the capacitor manufacturer’s ripple current ratings are often based on 2000 hours of life. This makes it advisable to further derate the capacitor, or choose a capacitor rated at a higher temperature than required. Always consult the manufacturer if there is any question. 3406afa 8 LTC3406A APPLICATIONS INFORMATION The selection of COUT is driven by the required effective series resistance (ESR). Typically, once the ESR requirement for COUT has been met, the RMS current rating generally far exceeds the IRIPPLE(P-P) requirement. The output ripple ∆VOUT is determined by: VOUT IL ESR + 1 8fCOUT induce ringing at the input, VIN. At best, this ringing can couple to the output and be mistaken as loop instability. At worst, a sudden inrush of current through the long wires can potentially cause a voltage spike at VIN, large enough to damage the part. When choosing the input and output ceramic capacitors, choose the X5R or X7R dielectric formulations. These dielectrics have the best temperature and voltage characteristics of all the ceramics for a given value and size. Output Voltage Programming In the adjustable version, the output voltage is set by a resistive divider according to the following formula: VOUT = 0.6V 1+ R2 R1 (2) where f = operating frequency, COUT = output capacitance and ∆IL = ripple current in the inductor. For a fixed output voltage, the output ripple is highest at maximum input voltage since ∆IL increases with input voltage. Aluminum electrolytic and dry tantalum capacitors are both available in surface mount configurations. In the case of tantalum, it is critical that the capacitors are surge tested for use in switching power supplies. An excellent choice is the AVX TPS series of surface mount tantalum. These are specially constructed and tested for low ESR so they give the lowest ESR for a given volume. Other capacitor types include Sanyo POSCAP Kemet T510 and T495 series, and , Sprague 593D and 595D series. Consult the manufacturer for other specific recommendations. Using Ceramic Input and Output Capacitors Higher values, lower cost ceramic capacitors are now becoming available in smaller case sizes. Their high ripple current, high voltage rating and low ESR make them ideal for switching regulator applications. Because the LTC3406A’s control loop does not depend on the output capacitor’s ESR for stable operation, ceramic capacitors can be used freely to achieve very low output ripple and small circuit size. However, care must be taken when ceramic capacitors are used at the input and the output. When a ceramic capacitor is used at the input and the power is supplied by a wall adapter through long wires, a load step at the output can The external resistive divider is connected to the output, allowing remote voltage sensing as shown in Figure 1. 0.6V ≤ VOUT ≤ 5.5V R2 VFB LTC3406A GND 3406A F01 R1 Figure 1. Setting the LTC3406A Output Voltage Efficiency Considerations The efficiency of a switching regulator is equal to the output power divided by the input power times 100%. It is often useful to analyze individual losses to determine what is limiting the efficiency and which change would produce the most improvement. Efficiency can be expressed as: Efficiency = 100% – (L1 + L2 + L3 + ...) where L1, L2, etc. are the individual losses as a percentage of input power. 3406afa 9 LTC3406A APPLICATIONS INFORMATION Although all dissipative elements in the circuit produce losses, two main sources usually account for most of the losses in LTC3406A circuits: VIN quiescent current and I2R losses. The VIN quiescent current loss dominates the efficiency loss at very low load currents whereas the I2R loss dominates the efficiency loss at medium to high load currents. In a typical efficiency plot, the efficiency curve at very low load currents can be misleading since the actual power lost is of no consequence as illustrated in Figure 2. 1 VIN = 3.6V 2. I2R losses are calculated from the resistances of the internal switches, RSW, and external inductor RL. In continuous mode, the average output current flowing through inductor L is “chopped” between the main switch and the synchronous switch. Thus, the series resistance looking into the SW pin is a function of both top and bottom MOSFET RDS(ON) and the duty cycle (DC) as follows: RSW = (RDS(ON)TOP)(DC) + (RDS(ON)BOT)(1 – DC) The RDS(ON) for both the top and bottom MOSFETs can be obtained from the Typical Performance Characteristics curves. Thus, to obtain I2R losses, simply add RSW to RL and multiply the result by the square of the average output current. Other losses including CIN and COUT ESR dissipative losses and inductor core losses generally account for less than 2% total additional loss. 0.1 POWER LOSS (W) 0.01 0.001 VOUT = 1.2V VOUT = 1.8V VOUT = 2.5V 10 100 1 OUTPUT CURRENT (mA) 1000 3406A F02 0.0001 0.1 Thermal Considerations In most applications the LTC3406A does not dissipate much heat due to its high efficiency. But, in applications where the LTC3406A is running at high ambient temperature with low supply voltage and high duty cycles, such as in dropout, the heat dissipated may exceed the maximum junction temperature of the part. If the junction temperature reaches approximately 150°C, both power switches will be turned off and the SW node will become high impedance. To avoid the LTC3406A from exceeding the maximum junction temperature, the user will need to do some thermal analysis. The goal of the thermal analysis is to determine whether the power dissipated exceeds the maximum junction temperature of the part. The temperature rise is given by: TR = (PD)(θJA) where PD is the power dissipated by the regulator and θJA is the thermal resistance from the junction of the die to the ambient temperature. Figure 2. Power Lost vs Load Current 1. The VIN quiescent current is due to two components: the DC bias current as given in the electrical characteristics and the internal main switch and synchronous switch gate charge currents. The gate charge current results from switching the gate capacitance of the internal power MOSFET switches. Each time the gate is switched from high to low to high again, a packet of charge, dQ, moves from VIN to ground. The resulting dQ/dt is the current out of VIN that is typically larger than the DC bias current. In continuous mode, IGATECHG = f(QT + QB) where QT and QB are the gate charges of the internal top and bottom switches. Both the DC bias and gate charge losses are proportional to VIN and thus their effects will be more pronounced at higher supply voltages. 3406afa 10 LTC3406A APPLICATIONS INFORMATION The junction temperature, TJ, is given by: TJ = TA + TR where TA is the ambient temperature. As an example, consider the LTC3406A in dropout at an input voltage of 2.7V, a load current of 600mA and an ambient temperature of 70°C. From the typical performance graph of switch resistance, the RDS(ON) of the P-channel switch at 70°C is approximately 0.27Ω. Therefore, power dissipated by the part is: PD = ILOAD2 • RDS(ON) = 97.2mW For the SOT-23 package, the θJA is 250°C/ W. Thus, the junction temperature of the regulator is: TJ = 70°C + (0.0972)(250) = 94.3°C which is below the maximum junction temperature of 125°C. Note that at higher supply voltages, the junction temperature is lower due to reduced switch resistance (RDS(ON)). Checking Transient Response The regulator loop response can be checked by looking at the load transient response. Switching regulators take several cycles to respond to a step in load current. When a load step occurs, VOUT immediately shifts by an amount equal to (∆ILOAD • ESR), where ESR is the effective series resistance of COUT. ∆ILOAD also begins to charge or discharge COUT, which generates a feedback error signal. The regulator loop then acts to return VOUT to its steady-state value. During this recovery time VOUT can be monitored for overshoot or ringing that would indicate a stability problem. For a detailed explanation of switching control loop theory, see Application Note 76. A second, more severe transient is caused by switching in loads with large (>1μF) supply bypass capacitors. The discharged bypass capacitors are effectively put in parallel with COUT, causing a rapid drop in VOUT. No regulator can deliver enough current to prevent this problem if the load switch resistance is low and it is driven quickly. The only solution is to limit the rise time of the switch drive so that the load rise time is limited to approximately (25 • CLOAD). Thus, a 10μF capacitor charging to 3.3V would require a 250μs rise time, limiting the charging current to about 130mA. PC Board Layout Checklist When laying out the printed circuit board, the following checklist should be used to ensure proper operation of the LTC3406A. These items are also illustrated graphically in Figures 3 and 4. Check the following in your layout: 1. The power traces, consisting of the GND trace, the SW trace, the VOUT trace and the VIN trace should be kept short, direct and wide. 2. Does the VFB pin connect directly to the feedback resistors? The resistive divider R1/R2 must be connected between the (+) plate of COUT and ground. 3. Does CIN connect to VIN as closely as possible? This capacitor provides the AC current to the internal power MOSFETs. 4. Keep the switching node, SW, away from the sensitive VFB node. 5. Keep the (–) plates of CIN and COUT, and the IC ground, as close as possible. 3406afa 11 LTC3406A APPLICATIONS INFORMATION 1 RUN VFB 5 R2 R1 LTC3406A 2 – VOUT COUT GND 4 CFWD + 3 L1 SW VIN CIN VIN BOLD LINES INDICATE HIGH CURRENT PATHS 3406A F03 Figure 3. LTC3406A Layout Diagram VIA TO VIN R1 VIN VIA TO VOUT PIN 1 VOUT L1 SW LTC3406A R2 CFWD COUT GND CIN 3406A F04 Figure 4. LTC3406A Suggested Layout Design Example As a design example, assume the LTC3406A is used in a single lithium-ion battery-powered cellular phone application. The VIN will be operating from a maximum of 4.2V down to about 2.7V. The load current requirement is a maximum of 0.6A but most of the time it will be in standby mode, requiring only 2mA. Efficiency at both low and high load currents is important. Output voltage is 2.5V. With this information we can calculate L using Equation (1), L= Substituting VOUT = 2.5V, VIN = 4.2V, ∆IL = 240mA and f = 1.5MHz in Equation (3) gives: L= 2.5V 2.5V 1 = 2.81μH 1.5MHz(240mA) 4.2V A 2.2μH inductor works well for this application. For best efficiency choose a 720mA or greater inductor with less than 0.2Ω series resistance. CIN will require an RMS current rating of at least 0.3A ≅ ILOAD(MAX)/2 at temperature and COUT will require an ESR of less than 0.25Ω. In most cases, a ceramic capacitor will satisfy this requirement. ( f)( 1 IL ) VOUT 1 VOUT VIN (3) 3406afa 12 LTC3406A APPLICATIONS INFORMATION For the feedback resistors, choose R1 = 316k. R2 can then be calculated from Equation (2) to be: R2 = VOUT 0.6 1 R1= 1000k (4) 4 CIN 4.7μF CER 1 † Figure 5 shows the complete circuit along with its efficiency curve. VIN 2.7V TO 4.2V VIN SW 3 2.2μH* 22pF LTC3406A RUN GND 2 VFB 5 1M 316k 3406A F05a VOUT 2.5V 600mA COUT** 10μF CER * MURATA LQH32CN2R2M33 ** TAIYO YUDEN JMK316BJ106ML † TAIYO YUDEN LMK212BJ475MG 100 90 80 EFFICIENCY (%) 70 60 50 40 30 20 10 0 0.1 VIN = 2.7V VIN = 3.6V VIN = 4.2V 1 10 100 OUTPUT CURRENT (mA) 1000 3406A F05b VOUT 100mV/DIV IL 500mA/DIV ILOAD 500mA/DIV 20μs/DIV VIN = 3.6V VOUT = 2.5V ILOAD = 300mA TO 600mA 3406A F05d Figure 5. 3406afa 13 LTC3406A TYPICAL APPLICATIONS Single Li-Ion 1.2V/600mA Regulator for High Efficiency and Small Footprint VIN CIN 4.7μF CER 1 † 4 VIN SW 3 2.2μH* 22pF LTC3406A RUN GND 2 VFB 5 301k 301k VOUT 1.2V 600mA COUT** 10μF CER * MURATA LQH32CN2R2M33 ** TAIYO YUDEN JMK316BJ106ML † TAIYO YUDEN JMK212BJ475MG 3406A TA02 Efficiency vs Load Current 100 90 80 EFFICIENCY (%) 70 60 50 40 30 20 10 0 0.1 VOUT = 1.2V VIN = 2.7V VIN = 3.6V VIN = 4.2V 1000 3406A TA03 Load Step VOUT 100mV/DIV IL 500mA/DIV ILOAD 500mA/DIV 1 10 100 OUTPUT CURRENT (mA) VIN = 3.6V 20μs/DIV VOUT = 1.2V ILOAD = 300mA TO 600mA 3406A TA05 3406afa 14 LTC3406A PACKAGE DESCRIPTION S5 Package 5-Lead Plastic TSOT-23 (Reference LTC DWG # 05-08-1635) 0.62 MAX 0.95 REF 2.90 BSC (NOTE 4) 1.22 REF 3.85 MAX 2.62 REF 1.4 MIN 2.80 BSC 1.50 – 1.75 (NOTE 4) PIN ONE RECOMMENDED SOLDER PAD LAYOUT PER IPC CALCULATOR 0.30 – 0.45 TYP 5 PLCS (NOTE 3) 0.95 BSC 0.80 – 0.90 0.20 BSC 1.00 MAX DATUM ‘A’ 0.01 – 0.10 0.30 – 0.50 REF 0.09 – 0.20 (NOTE 3) NOTE: 1. DIMENSIONS ARE IN MILLIMETERS 2. DRAWING NOT TO SCALE 3. DIMENSIONS ARE INCLUSIVE OF PLATING 4. DIMENSIONS ARE EXCLUSIVE OF MOLD FLASH AND METAL BURR 5. MOLD FLASH SHALL NOT EXCEED 0.254mm 6. JEDEC PACKAGE REFERENCE IS MO-193 1.90 BSC S5 TSOT-23 0302 REV B 3406afa Information furnished by Linear Technology Corporation is believed to be accurate and reliable. However, no responsibility is assumed for its use. Linear Technology Corporation makes no representation that the interconnection of its circuits as described herein will not infringe on existing patent rights. 15 LTC3406A RELATED PARTS PART NUMBER LTC3406/LTC3406B LTC3407/LTC3407-2 LTC3410/LTC3410B LTC3411 LTC3412 LTC3440 LTC3530 LTC3531/LTC3531-3/ LTC3531-3.3 LTC3532 LTC3542 LTC3544/LTC3544B LTC3547/LTC3547B LTC3548/LTC3548-1/ LTC3548-2 LTC3560 LTC3561 DESCRIPTION 600mA (IOUT), 1.5MHz, Synchronous Step-Down DC/DC Converters Dual 600mA/800mA (IOUT), 1.5MHz/2.25MHz, Synchronous Step-Down DC/DC Converters 300mA (IOUT), 2.25MHz, Synchronous Step-Down DC/DC Converters 1.25A (IOUT), 4MHz, Synchronous Step-Down DC/DC Converter 2.5A (IOUT), 4MHz, Synchronous Step-Down DC/DC Converter 600mA (IOUT), 2MHz, Synchronous Buck-Boost DC/DC Converter 600mA (IOUT), 2MHz, Synchronous Buck-Boost DC/DC Converter 200mA (IOUT), 1.5MHz, Synchronous Buck-Boost DC/DC Converters 500mA (IOUT), 2MHz, Synchronous Buck-Boost DC/DC Converter 500mA (IOUT), 2.25MHz, Synchronous Step-Down DC/DC Converter Quad 300mA + 2 × 200mA + 100mA, 2.25MHz, Synchronous Step-Down DC/DC Converters Dual 300mA, 2.25MHz, Synchronous Step-Down DC/DC Converters Dual 400mA/800mA (IOUT), 2.25MHz, Synchronous Step-Down DC/DC Converters 800mA (IOUT), 2.25MHz, Synchronous Step-Down DC/DC Converter 1.25A (IOUT), 4MHz, Synchronous Step-Down DC/DC Converter COMMENTS 96% Efficiency, VIN: 2.5V to 5.5V, VOUT(MIN) = 0.6V, IQ = 20μA, ISD