LTC4214-1

LTC4214-1/LTC4214-2 Negative Low Voltage Hot Swap Controllers FEATURES s s s DESCRIPTIO s s s s s s s Allows Safe Board Insertion and Removal from a Live Backplane Controls Supplies from 0V to –16V Adjustable Analog Current Limit With Circuit Breaker Timer Fast Response Time Limits Peak Fault Current Adjustable Soft-Start Current Limit Adjustable Timer with Drain Voltage Accelerated Response Adjustable Undervoltage/Overvoltage Protection LTC4214-1: Latch Off After Fault LTC4214-2: Automatic Retry After Fault Available in the 10-Pin MSOP Package The LTC®4214 negative voltage Hot SwapTM controller allows a board to be safely inserted and removed from a live backplane. Output current is controlled by three stages of current limiting: a timed circuit breaker, active current limiting and a fast feedforward path that limits peak current under worst-case catastrophic fault conditions. Adjustable undervoltage and overvoltage detectors disconnect the load whenever the input supply exceeds the desired operating range. The LTC4214 controls negative supplies ranging from near zero to –16V. A multifunction timer delays initial start-up and controls the circuit breaker’s response time. This response time is accelerated by sensing excessive MOSFET drain voltage, keeping the MOSFET within its safe operating area (SOA). An adjustable soft-start circuit controls MOSFET inrush current at start-up. A power good status output can enable a power module at start-up or disable it if the circuit breaker trips. The LTC4214-1 latches off after a circuit breaker fault times out. The LTC4214-2 provides automatic retry after a fault. The LTC4214 is available in the 10-pin MSOP package. , LTC and LT are registered trademarks of Linear Technology Corporation. Hot Swap is a trademark of Linear Technology Corporation. APPLICATIO S s s s s s s s s Hot Board Insertion Electronic Circuit Breaker Negative Power Supply Control Central Office Switching High Availability Servers Disk Arrays Optical Networking/Switching ECL TYPICAL APPLICATIO 3.3V – 5.2V/5A ECL Supply Hot Swap Controller EN 2k GND 10Ω SMAJ7A 100nF GND (SHORT PIN) 34k 1% 32.4k 1% 5.6nF 1nF PUSH RESET 1 VIN LTC4214-1 2 PWRGD 9, 8 7 UV/OV DRAIN 10 6 TIMER GATE 3 4 SS SENSE VEE 3.3nF 5 10nF 4214 TA01 BSS138 GND 470Ω CLOAD 100µF 0.1µF 75k + –5.2V ECL SENSE 20mV/DIV VOUT 5V/DIV IRF7413 22Ω 10Ω 0.01Ω –5.2V U Start-Up Behavior GATE 5V/DIV PWRGD 5V/DIV 4214 TA02 U U 421412f 1 LTC4214-1/LTC4214-2 ABSOLUTE AXI U RATI GS PACKAGE/ORDER I FOR ATIO ORDER PART NUMBER TOP VIEW VIN PWRGD SS SENSE VEE 1 2 3 4 5 10 9 8 7 6 TIMER UV OV DRAIN GATE All Voltages Referred to VEE (Note 1) VIN ............................................................ – 0.3V to 17V Input/Output Pins (Except SENSE and DRAIN) Voltage ..........– 0.3V to 17V SENSE Pin Voltage ................................... – 0.6V to 17V Current Out of SENSE Pin (20µs Pulse) ........... – 200mA DRAIN Pin Minimum Voltage .............................. – 0.3V Current into DRAIN Pin (100µs Pulse) ................... 5mA Maximum Junction Temperature .......................... 125°C Operating Temperature Range LTC4214-1C/LTC4214-2C ....................... 0°C to 70°C LTC4214-1I/LTC4214-2I ................... – 40°C to 85°C Storage Temperature Range ................. – 65°C to 150°C Lead Temperature (Soldering, 10 sec).................. 300°C LTC4214-1CMS LTC4214-2CMS LTC4214-1IMS LTC4214-2IMS MS PART MARKING LTABH LTABK LTABJ LTABL MS PACKAGE 10-LEAD PLASTIC MSOP TJMAX = 125°C, θJA = 160°C/W Consult LTC Marketing for parts specified with wider operating temperature ranges. The q denotes the specifications which apply over the full operating temperature range, otherwise specifications are at TA = 25°C. VIN = 12V, UV = OV = 2.5V unless otherwise noted. (Note 2) SYMBOL VIN IIN VLKO VLKH VCB VACL VFCL VSS RSS ISS VOS PARAMETER Supply Voltage VIN Supply Current VIN Undervoltage Lockout VIN Undervoltage Lockout Hysteresis Circuit Breaker Current Limit Voltage Analog Current Limit Voltage Fast Current Limit Voltage SS Voltage SS Output Impedance SS Pin Current Analog Current Limit Offset Voltage UV = OV = 2.5V, VSENSE = VEE, VSS = 0V (Sourcing) UV = OV = 0V, VSENSE = VEE, VSS = 1V (Sinking) VCB = (VSENSE – VEE) VACL = (VSENSE – VEE), SS = Open VFCL = (VSENSE – VEE) After End of SS Timing Cycle q q q ELECTRICAL CHARACTERISTICS CONDITIONS q MIN 6 q q TYP 0.8 5.1 0.3 MAX 16 2 5.6 56 80 300 UNITS V mA V V mV mV mV V kΩ µA mA mV V/V UV = OV = 2.5V Coming Out of UVLO (Rising VIN) 44 60 150 50 70 200 1.6 73 –22 14 10 0.05 VACL+VOS Ratio (VACL + VOS) to SS Voltage VSS IGATE GATE Pin Output Current VSENSE = VEE, VGATE = 0V (Sourcing) VSENSE – VEE = 0.15V, VGATE = 3V (Sinking) VSENSE – VEE = 0.3V, VGATE = 1V (Sinking) VGATE – VEE VGATEH = VIN – VGATE for PWRGD Status (Before Gate Ramp-Up) UV Rising OV Rising q q q q q –30 –50 17 190 11 2.8 0.5 –70 VGATE VGATEH VGATEL VUVHI VUVHST VOVHI VOVHST External MOSFET Gate Drive Gate High Threshold Gate Low Threshold UV Pin Threshold UV Pin Hysteresis OV Pin Threshold OV Pin Hysteresis q 10 12 2.137 0.22 2.85 0.12 2.25 0.25 3 0.15 2.363 0.28 3.15 0.18 421412f 2 U µA mA mA V V V V V V V W U U WW W LTC4214-1/LTC4214-2 The q denotes the specifications which apply over the full operating temperature range, otherwise specifications are at TA = 25°C. VIN = 12V, UV = OV = 2.5V unless otherwise noted. (Note 2) SYMBOL ISENSE IINP VTMRH VTMRL ITMR PARAMETER SENSE Pin Input Current UV, OV Pin Input Current TIMER Pin Voltage High Threshold TIMER Pin Voltage Low Threshold TIMER Pin Current Timer On (Initial Cycle/Latchoff/ Shutdown Cooling, Sourcing), VTMR = 2.2V Timer Off (Initial Cycle, Sinking), VTMR = 2.2V Timer On (Circuit Breaker, Sourcing, IDRN = 0µA), VTMR = 2.2V Timer On (Circuit Breaker, Sourcing, IDRN = 20µA), VTMR = 2.2V Timer Off (Circuit Breaker/ Shutdown Cooling, Sinking), VTMR = 2.2V ∆ITMRACC [(ITMR at IDRN = 20µA) – (ITMR at IDRN = 0µA)] ∆IDRN 20µA VDRNL IDRNL VDRNCL VPGL IPGH tSS tPLLUG tPHLOG DRAIN Pin Voltage Low Threshold DRAIN Leakage Current DRAIN Pin Clamp Voltage PWRGD Output Low Voltage PWRGD Pull-Up Current SS Default Ramp Period UV Low to Gate Low OV High to Gate Low Timer On (Circuit Breaker with IDRN = 20µA) For PWRGD Status VDRAIN = 2.5V IDRN = 20µA IPG = 1.6mA IPG = 5mA VPWRGD = 0V (Sourcing) SS Pin Floating, VSS Ramps from 0.2V to 1.4V q q q q ELECTRICAL CHARACTERISTICS CONDITIONS VSENSE = 50mV UV = OV = 2.5V q q MIN TYP – 15 ± 0.1 3 1.7 –5 28 –40 –200 5 8 MAX –30 ±1 UNITS µA µA V V µA mA µA µA µA µA/µA 1.109 3.5 1.232 ± 0.1 4.2 0.2 1.355 ±1 5 0.4 1.1 –70 V µA V V V µA µs µs µs –30 –50 130 0.4 0.4 Note 1: Absolute Maximum Ratings are those values beyond which the life of a device may be impaired. Note 2: All currents into device pins are positive; all currents out of device pins are negative. All voltages are referenced to VEE unless otherwise specified. TYPICAL PERFOR A CE CHARACTERISTICS otherwise specified. IIN vs Temperature 1200 1100 1000 IIN (mA) VIN = 12V 900 VLKO (V) 0 2 4 6 8 10 12 14 16 18 20 VIN (V) 4214 G02 IIN (µA) 800 700 600 500 400 –55 –35 –15 5 25 45 65 85 105 125 4214 G01 TEMPERATURE (°C) UW All voltages are referenced to VEE Unless Undervoltage Lockout VLKO vs Temperature IIN vs VIN 1.6 1.4 1.2 1.0 0.8 0.6 0.4 0.2 0 TA = –40°C TA = 25°C TA = 85°C TA = 125°C 6 5.8 5.6 5.4 5.2 5 4.8 4.6 4.4 4.2 4 –55 –35 –15 5 25 45 65 85 105 125 TEMPERATURE (°C) 4214 G03 421412f 3 LTC4214-1/LTC4214-2 TYPICAL PERFOR A CE CHARACTERISTICS otherwise specified. Undervoltage Lockout Hysteresis VLKH vs Temperature 0.7 0.6 0.5 56 54 52 VACL (mV) VCB (mV) VLKH (V) 0.4 0.3 0.2 0.1 0 –55 –35 –15 5 25 45 65 85 105 125 TEMPERATURE (°C) 4214 G04 Fast Current Limit Voltage VFCL vs Temperature 300 275 250 VIN = 12V 1.80 1.75 1.70 VFCL (mV) RSS (kΩ) VSS (V) 225 200 175 150 –55 –35 –15 5 25 45 65 85 105 125 TEMPERATURE (°C) 4214 G07 ISS (Sinking) vs Temperature 25 VIN = 12V UV = OV = VSENSE = VEE VSS = 1V 11.0 10.8 10.6 10.4 VOS (mV) 20 (VACL + VOS)/VSS (V/V) ISS (mA) 15 10 5 0 –55 –35 –15 5 25 45 65 85 105 125 TEMPERATURE (°C) 4214 G10 4 UW All voltages are referenced to VEE Unless Analog Current Limit Voltage VACL vs Temperature 80 78 76 74 72 70 68 66 64 62 VIN = 12V Circuit Breaker Current Limit Voltage VCB vs Temperature VIN = 12V 50 48 46 44 –55 –35 –15 5 25 45 65 85 105 125 TEMPERATURE (°C) 4214 G05 60 –55 –35 –15 5 25 45 65 85 105 125 TEMPERATURE (°C) 4214 G06 VSS vs Temperature VIN = 12V 85 83 81 79 77 75 73 71 69 RSS vs Temperature VIN = 12V 1.65 1.60 1.55 1.50 1.45 1.40 –55 –35 –15 67 5 25 45 65 85 105 125 TEMPERATURE (°C) 4214 G08 65 –55 –35 –15 5 25 45 65 85 105 125 TEMPERATURE (°C) 4214 G09 VOS vs Temperature VIN = 12V 0.060 0.058 0.056 0.054 0.052 0.050 0.048 0.046 0.044 0.042 5 25 45 65 85 105 125 TEMPERATURE (°C) 4214 G11 (VACL + VOS)/VSS vs Temperature VIN = 12V 10.2 10.0 9.8 9.6 9.4 9.2 9.0 –55 –35 –15 0.040 –55 –35 –15 5 25 45 65 85 105 125 TEMPERATURE (°C) 4214 G12 421412f LTC4214-1/LTC4214-2 TYPICAL PERFOR A CE CHARACTERISTICS otherwise specified. IGATE (Sourcing) vs Temperature 60 58 56 54 IGATE (µA) 52 50 48 46 44 42 40 –55 –35 –15 5 25 45 65 85 105 125 TEMPERATURE (°C) 4214 G13 VIN = 12V UV/OV = 2.5V TIMER = 0V VSENSE = VEE VGATE = 0V IGATE (mA) 15 10 5 0 –55 –35 –15 IGATE (mA) VGATE vs Temperature 12.0 11.8 11.6 11.4 VIN = 12V UV/OV = 2.5V TIMER = 0V VSENSE = VEE 3.6 3.4 3.2 VGATE (V) 11.2 11.0 10.8 10.6 10.4 10.2 10.0 –55 –35 –15 5 25 45 65 85 105 125 TEMPERATURE (°C) 4214 G16 VGATEH (V) VGATEL (V) VUVHI vs Temperature 2.40 2.35 2.30 VUVHST (V) VIN = 12V VUVHI (V) 2.25 2.20 2.15 2.10 –55 –35 –15 0.25 0.24 0.23 0.22 –55 –35 –15 VOVHI (V) 5 25 45 65 85 105 125 TEMPERATURE (°C) 4214 G19 UW All voltages are referenced to VEE Unless IGATE (FCL, Sinking) vs Temperature 400 350 300 250 200 150 100 50 VIN = 12V UV/OV = 2.5V TIMER = 0V VSENSE – VEE = 0.3V VGATE = 1V IGATE (ACL, Sinking) vs Temperature 30 25 20 VIN = 12V UV/OV = 2.5V TIMER = 0V VSENSE – VEE = 0.15V VGATE = 3V 5 25 45 65 85 105 125 TEMPERATURE (°C) 4214 G14 0 –55 –35 –15 5 25 45 65 85 105 125 4214 G15 TEMPERATURE (°C) VGATEH vs Temperature VIN = 12V UV/OV = 2.5V VGATEH = VIN – VGATE 0.8 0.7 0.6 0.5 0.4 0.3 0.2 0.1 5 25 45 65 85 105 125 4214 G17 VGATEL vs Temperature VIN = 12V UV/OV = 2.5V TIMER = 0V GATE THRESHOLD BEFORE RAMP-UP 3.0 2.8 2.6 2.4 2.2 2.0 –55 –35 –15 0 –55 –35 –15 5 25 45 65 85 105 125 4214 G18 TEMPERATURE (°C) TEMPERATURE (°C) VUVHST vs Temperature 0.28 0.27 0.26 VIN = 12V 3.15 3.10 3.05 3.00 2.95 2.90 VOVHI vs Temperature VIN = 12V 5 25 45 65 85 105 125 TEMPERATURE (°C) 4214 G20 2.85 –55 –35 –15 5 25 45 65 85 105 125 TEMPERATURE (°C) 4214 G21 421412f 5 LTC4214-1/LTC4214-2 TYPICAL PERFOR A CE CHARACTERISTICS otherwise specified. VOVHST vs Temperature 0.18 0.17 0.16 0.15 0.14 0.13 0.12 –55 –35 –15 ISENSE (µA) VIN = 12V –ISENSE (mA) VOVHST (V) 5 25 45 65 85 105 125 TEMPERATURE (°C) 4214 G22 TIMER Threshold vs Temperature 4.0 3.5 VIN = 12V TIMER THRESHOLD (V) 3.0 2.5 2.0 1.5 1.0 0.5 –55 –35 –15 5.0 4.5 4.0 3.5 3.0 –55 –35 –15 5 25 45 65 85 105 125 4214 G26 ITMR (mA) VTMRH ITMR (µA) VTMRL 5 25 45 65 85 105 125 TEMPERATURE (°C) 4214 G25 ITMR (Circuit Breaker, Sourcing) vs Temperature 60 55 50 ITMR (µA) VIN = 12V TIMER = 2.2V IDRN = 0µA ITMR (µA) 40 35 30 25 20 –55 –35 –15 5 25 45 65 85 105 125 4214 G28 200 195 190 185 180 –55 –35 –15 5 25 45 65 85 105 125 4214 G29 ITMR (µA) 45 TEMPERATURE (°C) 6 UW All voltages are referenced to VEE Unless ISENSE vs Temperature 0 –5 –10 –15 –20 –25 –30 –55 –35 –15 VIN = 12V UV/OV = 2.5V TIMER = 0V GATE = HIGH VSENSE – VEE = 50mV ISENSE vs (VSENSE – VEE) 0.01 0.10 1 10 VIN = 12V UV/OV = 2.5V TIMER = 0V GATE = HIGH TA = 25°C 1.5 2.0 100 5 25 45 65 85 105 125 TEMPERATURE (°C) 4214 G23 1000 0.5 0 1.0 –1.5 –1.0 –0.5 (VSENSE – VEE) (V) 4214 G24 ITMR (Initial Cycle, Sourcing) vs Temperature 7.0 6.5 6.0 5.5 VIN = 12V TIMER = 2.2V 50 45 40 35 30 25 20 15 ITMR (Initial Cycle, Sinking) vs Temperature VIN = 12V TIMER = 2.2V 10 –55 –35 –15 5 25 45 65 85 105 125 4214 G27 TEMPERATURE (°C) TEMPERATURE (°C) ITMR (Circuit Breaker, IDRN = 20µA, Sourcing) vs Temperature 220 215 210 205 VIN = 12V TIMER = 2.2V IDRN = 20µA 7.0 6.5 6.0 5.5 5.0 4.5 4.0 3.5 ITMR (Cooling Cycle, Sinking) vs Temperature VIN = 12V TIMER = 2.2V 3.0 –55 –35 –15 5 25 45 65 85 105 125 4214 G30 TEMPERATURE (°C) TEMPERATURE (°C) 421412f LTC4214-1/LTC4214-2 TYPICAL PERFOR A CE CHARACTERISTICS otherwise specified. ITMR (Circuit Breaker, Sourcing) vs IDRN 10 VIN = 12V TIMER = 2.2V TA = 25°C (∆ITMRACC/∆IDRN (µA/µA) 1 ITMR (mA) IDRN (mA) 0.1 0.01 0.001 0.01 0.1 IDRN (mA) VDRNL vs Temperature 1.40 1.35 1.30 VIN = 12V FOR PWRGD STATUS VDRNCL (V) VDRNL (V) 4.2 4.0 3.8 3.6 1.25 1.20 1.15 VPGL (V) 1.10 –55 –35 –15 5 25 45 65 85 105 125 TEMPERATURE (°C) 4214 G34 IPGH (Sourcing) vs Temperature 70 65 60 VIN = 12V VPWRGD = 0V DELAY (µs) IPGH (µA) 55 tSS (µs) 50 45 40 35 30 –55 –35 –15 5 25 45 65 85 105 125 4214 G37 TEMPERATURE (°C) UW 1 All voltages are referenced to VEE Unless ∆ITMRACC/∆IDRN vs Temperature 9.0 8.8 8.6 8.4 8.2 8.0 7.8 7.6 7.4 7.2 10 IDRN vs VDRAIN 100 10 1 0.1 0.01 0.001 0.0001 0.00001 TA = –40°C TA = 25°C TA = 85°C TA = 125°C 0 2 4 6 8 10 12 14 16 VDRAIN (V) 4214 G33 VIN = 12V TIMER ON (CIRCUIT BREAKING, IDRN = 20µA) VIN = 12V 7.0 –55 –35 –15 5 25 45 65 85 105 125 TEMPERATURE (°C) 4214 G32 4214 G31 VDRNCL vs Temperature 5.0 4.8 4.6 4.4 VIN = 12V IDRN = 20µA VPGL vs Temperature 2.5 VIN = 12V 2.0 IPG = 10mA 1.5 IPG = 5mA 1.0 0.5 IPG = 1.6mA 3.4 3.2 –55 –35 –15 5 25 45 65 85 105 125 TEMPERATURE (°C) 4214 G35 0 –55 –35 –15 5 25 45 65 85 105 125 TEMPERATURE (°C) 4214 G36 tSS vs Temperature 160 150 140 130 120 110 100 –55 –35 –15 VIN = 12V SS PIN FLOATING, VSS RAMPS FROM 0.2V TO 1.4V 0.8 0.7 0.6 0.5 0.4 0.3 0.2 0.1 tPLLUG and tPHLOG vs Temperature VIN = 12V tPLLUG tPHLOG 5 25 45 65 85 105 125 TEMPERATURE (°C) 4214 G38 0 –55 –35 –15 5 25 45 65 85 105 125 4214 G39 TEMPERATURE (°C) 421412f 7 LTC4214-1/LTC4214-2 PI FU CTIO S VIN (Pin 1): Positive Supply Input. Connect this pin to the positive side of the supply via a resistor. An internal undervoltage lockout (UVLO) circuit holds GATE low until the VIN pin is greater than VLKO (5.1V), overriding UV and OV. If UV is high, OV is low and VIN comes out of UVLO, TIMER starts an initial timing cycle before initiating a GATE ramp-up. If VIN drops below approximately 4.8V, GATE pulls low immediately. PWRGD (Pin 2): Power Good Status Output. At start-up, PWRGD latches low if DRAIN is below 1.232V and GATE is within 2.8V of VIN. PWRGD status is reset by UV, VIN (UVLO) or a circuit breaker fault timeout. This pin is internally pulled high by a 50µA current source. SS (Pin 3): Soft-Start Pin. This pin is used to ramp inrush current during start up, thereby effecting control over di/ dt. A 20x attenuated version of the SS pin voltage is presented to the current limit amplifier. This attenuated voltage limits the MOSFET’s drain current through the sense resistor during the soft-start current limiting. At the beginning of a start-up cycle, the SS capacitor (CSS) is ramped by a 22µA current source. The GATE pin is held low until SS exceeds 20 • VOS = 0.2V. SS is internally shunted by a 73k resistor (RSS) which limits the SS pin voltage to 1.6V. This corresponds to an analog current limit SENSE voltage of 70mV. If the SS capacitor is omitted, the SS pin ramps from 0V to 1.6V in about 220µs. The SS pin is pulled low under any of the following conditions: in UVLO, in an undervoltage condition, in an overvoltage condition, during the initial timing cycle or when the circuit breaker fault times out. SENSE (Pin 4): Circuit Breaker/Current Limit Sense Pin. Load current is monitored by a sense resistor RS connected between SENSE and VEE, and controlled in three steps. If SENSE exceeds VCB (50mV), the circuit breaker comparator activates a (40µA + 8 • IDRN) TIMER pull-up current. If SENSE exceeds VACL (70mV), the analog current limit amplifier pulls GATE down to regulate the MOSFET current at VACL/RS. In the event of a catastrophic shortcircuit, SENSE may overshoot 70mV. If SENSE reaches VFCL (200mV), the fast current limit comparator pulls GATE low with a strong pull-down. To disable the circuit breaker and current limit functions, connect SENSE to VEE. VEE (Pin 5): Negative Supply Voltage Input. Connect this pin to the negative side of the power supply. GATE (Pin 6): N-Channel MOSFET Gate Drive Output. This pin is pulled high by a 50µA current source. GATE is pulled low by invalid conditions at VIN (UVLO), UV, OV, or a circuit breaker fault timeout. GATE is actively servoed to control the fault current as measured at SENSE. A compensation capacitor at GATE stabilizes this loop. A comparator monitors GATE to ensure that it is low before allowing an initial timing cycle, GATE ramp-up after an overvoltage event or restart after a current limit fault. During GATE start-up, a second comparator detects if GATE is within 2.8V of VIN before PWRGD is set. DRAIN (Pin 7): Drain Sense Input. DRAIN measures the drain-source voltage of the external N-channel MOSFET switch for two purposes: first, a comparator detects when VDS < 1.232V and together with the GATE high comparator, controls the status of the PWRGD output. Second, if VDS is greater than the DRAIN clamp of approximately 4.2V (VDRNCL), the current through resistor RD is multiplied by 8 and added to the TIMER’s 40µA pull-up current during a circuit breaker fault cycle. This reduces the fault time and MOSFET heating under conditions of high dissipation. OV (Pin 8): Overvoltage Input. The active high threshold at the OV pin is set at 3V with respect to VEE and exhibits 0.15V hysteresis. If OV > 3V, GATE pulls low. When OV returns below 2.85V, GATE start-up begins without an initial timing cycle. If an overvoltage condition occurs in the middle of an initial timing cycle, the initial timing cycle is restarted after the overvoltage condition goes away. An overvoltage condition does not reset the PWRGD flag. The internal UVLO at VIN always overrides OV. A 1nF to 10nF capacitor at OV prevents transients and switching noise from affecting the OV thresholds and prevents glitches at the GATE pin. 8 U U U 421412f LTC4214-1/LTC4214-2 PI FU CTIO S UV (Pin 9): Undervoltage Input. The active high threshold at the UV pin is set at 2.25V with respect to VEE and exhibits 0.25V hysteresis. If UV < 2V, PWRGD pulls high, both GATE and TIMER pull low. If UV rises above 2.25V, this initiates an initial timing cycle followed by GATE start-up. The internal UVLO at VIN always overrides UV. A low at UV resets an internal fault latch. A 1nF to 10nF capacitor at UV prevents transients and switching noise from affecting the UV thresholds and prevents glitches at the GATE pin. TIMER (Pin 10): Timer Input. TIMER is used to generate an initial timing delay at start-up and to delay shutdown in the event of an output overload (circuit breaker fault). TIMER starts an initial timing cycle when the following conditions are met: UV is high, OV is low, VIN clears UVLO, TIMER pin is low, GATE is lower than VGATEL, SS < 0.2V, and VSENSE – VEE < VCB. A pull-up current of 5µA then charges CT, generating a time delay. If CT charges to VTMRH (3V), the timing cycle terminates, TIMER quickly pulls low and GATE is activated. If SENSE exceeds 50mV while GATE is high, a circuit breaker cycle begins with a 40µA pull-up current charging CT. If DRAIN is approximately 4.2V during this cycle, the timer pull-up has an additional current of 8 • IDRN. If SENSE drops below 50mV before TIMER reaches 3V, a 5µA pulldown current slowly discharges the CT. In the event that CT eventually integrates up to the VTMRH threshold, the circuit breaker trips, GATE quickly pulls low and PWRGD pulls high. The LTC4214-1 TIMER pin latches high with a 5µA pull-up source. This latched fault is cleared by either pulling TIMER low with an external device or by pulling UV below 2V. The LTC4214-2 starts a shutdown cooling cycle following an overcurrent fault. This cycle consists of 4 discharging ramps and 3 charging ramps. The charging and discharging currents are 5µA and TIMER ramps between its 1.7V and 3V thresholds. At the completion of a shutdown cooling cycle, the LTC4214-2 attempts a startup cycle. U U U 421412f 9 LTC4214-1/LTC4214-2 BLOCK DIAGRA VIN 1 3V – + OV 8 UV 9 – 2.25V VIN VEE + – LOGIC 40µA 5µA VIN 3V – + TIMER 10 – VEE 5µA VIN 22µA VEE 1.7V FCL + SS 3 69.35k RSS 3.65k VEE VEE CB VOS = 10mV + ACL –+ + – 50mV +– VEE 5 VEE 10 + + – – + – + – W 7 DRAIN VIN 1.232V 8× 1× VIN 1× VEE 2 PWRGD VIN 50µA VEE 6 GATE 2.8V 1× 50µA 3V –+ VIN 0.5V 200mV +– VEE VEE 4 SENSE 4214 BD 421412f LTC4214-1/LTC4214-2 OPERATIO Hot Circuit Insertion When circuit boards are inserted into a live backplane, the supply bypass capacitors can draw huge transient currents from the power bus as they charge. The flow of current damages the connector pins and glitches the power bus, causing other boards in the system to reset. The LTC4214 is designed to turn on a circuit board supply in a controlled manner, allowing insertion or removal without glitches or connector damage. Initial Start-Up The LTC4214 resides on a removable circuit board and controls the path between the connector and the load with an external MOSFET switch (see Figure 1). Both inrush control and short-circuit protection are provided by the MOSFET. A detailed schematic is shown in Figure 2. – 12V and GND receive power through the longest connector pins and are the first to connect when the board is inserted. The GATE pin holds the MOSFET off during this time. UV/OV determines whether or not the MOSFET should be turned on based upon internal high accuracy thresholds and an external divider. UV/OV does double duty by also monitoring whether or not the connector is seated. The top of the divider detects GND by way of a short connector pin that is the last to mate during the insertion sequence. Interlock Conditions A start-up sequence commences once these “interlock” conditions are met. 1. The input voltage VIN exceeds 5.1V (UVLO). 2. The voltage at UV > 2.25V. LONG GND LTC4214 LONG –12V BACKPLANE 4214 F01 Figure 1. Basic LTC4214 Hot Swap Topology U 3. The voltage at OV < 2.85V. 4. The (SENSE – VEE) voltage is < 50mV (VCB). 5. The voltage at SS is < 0.2V (20 • VOS). 6. The voltage on the TIMER capacitor (CT) is < 1.7V (VTMRL). 7. The voltage at GATE is < 0.5V (VGATEL). The first three conditions are continuously monitored and the latter four are checked prior to initial timing or GATE ramp-up. Upon exiting an OV condition, the TIMER pin voltage requirement is inhibited. Details are described in the Applications Information, Timing Waveforms section. TIMER begins the start-up sequence by sourcing 5µA into CT. If VIN, UV or OV falls out of range, the start-up cycle stops and TIMER discharges CT to less than 1.7V, then waits until the aforementioned conditions are once again met. If CT successfully charges to 3V, TIMER pulls low and both SS and GATE pins are released. GATE sources 50µA (IGATE), charging the MOSFET gate and associated capacitance. The SS voltage ramp limits VSENSE to control the inrush current. PWRGD pulls active low when GATE is within 2.8V of VIN and DRAIN is lower than VDRNL. Two modes of operation are possible during the time the MOSFET is first turning on, depending on the values of external components, MOSFET characteristics and nominal design current. One possibility is that the MOSFET will LONG GND RX 10Ω CX 100nF SHORT R1 121k 1% C1 1nF Z1 RIN 470Ω R3 10k CLOAD 100µF TYP GND + CIN 0.1µF VIN OV 9 2 UV PWRGD LTC4214-1 10 TIMER 3 7 SS DRAIN VEE SENSE 4 GATE 6 5 8 1 EN R4 10k PLUG-IN BOARD R2 32.4k 1% Z1: SMAJ15A CSS 22nF CT 47nF + CLOAD LOAD –12V LONG CC 10nF RS 0.025Ω RD RC 10Ω 475k VOUT Q1 IRF7413 4214 F02 Figure 2. –12V, 2A Hot Swap Controller 421412f 11 LTC4214-1/LTC4214-2 OPERATIO turn on gradually so that the inrush into the load capacitance remains a low value. The output will simply ramp to –12V and the LTC4214 will fully enhance the MOSFET. A second possibility is that the load current exceeds the soft-start current limit threshold of [VSS(t)/20 – VOS]/RS. In this case the LTC4214 will ramp the output by sourcing soft-start limited current into the load capacitance. If the soft-start voltage is below 1.2V, the circuit breaker TIMER is held low. Above 1.2V, TIMER ramps up. It is important to set the timer delay so that, regardless of which start-up mode is used, the TIMER ramp is less than one circuit breaker delay time. If this condition is not met, the LTC4214-1 may shut down after one circuit breaker delay time whereas the LTC4214-2 may continue to autoretry. Board Removal If the board is withdrawn from the card cage, the UV/OV divider is the first to lose connection. This shuts off the MOSFET and commutates the flow of current in the connector. When the power pins subsequently separate, there is no arcing. Current Control Three levels of protection handle short-circuit and overload conditions. Load current is monitored by SENSE and resistor RS. There are three distinct thresholds at SENSE: 50mV for a timed circuit breaker function; 70mV for an analog current limit loop; and 200mV for a fast, feedforward comparator which limits peak current in the event of a catastrophic short-circuit. If, owing to an output overload, the voltage drop across RS exceeds 50mV, TIMER sources 40µA into CT. CT eventually charges to a 3V threshold and the LTC4214 shuts off. If the overload goes away before CT reaches 3V and SENSE measures less than 50mV, CT slowly discharges (5µA). In this way the LTC4214’s circuit breaker function responds to low duty cycle overloads and accounts for fast heating and slow cooling characteristics of the MOSFET. 12 U Higher overloads are handled by an analog current limit loop. If the drop across RS reaches 70mV, the current limiting loop servos the MOSFET gate and maintains a constant output current of 70mV/RS. In current limit mode, VOUT typically rises and this increases MOSFET heating. If VOUT > VDRNCL (4.2V), connecting an external resistor, RD, between VOUT and DRAIN allows the fault timing cycle to be shortened by accelerating the charging of the TIMER capacitor. The TIMER pull-up current is increased by 8 • IDRN. Note that because SENSE > 50mV, TIMER charges CT during this time and the LTC4214 will eventually shut down. Low impedance failures on the load side of the LTC4214 can produce high current slew rates. Under these conditions, overshoot is inevitable. A fast SENSE comparator with a threshold of 200mV detects overshoot and pulls GATE low much harder and hence much faster than the weaker current limit loop. The 70mV/RS current limit loop then takes over and servos the current as previously described. As before, TIMER runs and shuts down the LTC4214 when CT reaches 3V. If CT reaches 3V, the LTC4214-1 latches off with a 5µA pull-up current source whereas the LTC4214-2 starts a shutdown cooling cycle. The LTC4214-1 circuit breaker latch is reset by either pulling UV momentarily low or dropping the input voltage VIN below the internal UVLO threshold of 4.8V or pulling TIMER momentarily low with a switch. The LTC4214-2 retries after its shutdown cooling cycle. Although short-circuits are the most obvious fault type, several operating conditions may invoke overcurrent protection. Noise spikes from the backplane or load, transient currents caused by faults on adjacent circuit boards sharing the same power bus or the insertion of non-hotswappable products could cause higher than anticipated input current and temporary detection of an overcurrent condition. The action of TIMER and CT rejects these events allowing the LTC4214 to “ride out” temporary overloads and disturbances that could trip a simple current comparator and, in some cases, blow a fuse. 421412f LTC4214-1/LTC4214-2 APPLICATIO S I FOR ATIO SUPPLY VOLTAGE The LTC4214 requires a (VIN – VEE) voltage of 6V to 16V to function. This can be derived from GND and –12V of a –12V system or the 3.3V and –5.2V of a –5.2V system. The positive supply is connected to VIN via an RC network so that the LTC4214 can have a usable VIN during load short or other transient events when (VIN – VEE) glitches below 6V. INTERNAL UNDERVOLTAGE LOCKOUT (UVLO) A hysteretic comparator, UVLO, monitors VIN f or undervoltage. The thresholds are defined by VLKO and its hysteresis, VLKH. When VIN rises above 5.1V (VLKO) the chip is enabled; below 4.8V (VLKO – VLKH) it is disabled and GATE is pulled low. The UVLO function at VIN should not be confused with the UV/OV pins. These are completely separate functions. UV/OV COMPARATORS An UV hysteretic comparator detects undervoltage conditions at the UV pin, with the following thresholds: UV low-to-high (VUVHI) = 2.25V UV high-to-low (VUVHI – VUVHST) = 2V GND RX 10Ω CX 100nF GND (SHORT PIN) Z1 RIN 470Ω R4 100k GND R1 124k 1% R2 3.65k 1% R3 32.4k 1% C2 1nF CT 47nF –12V Z1: SMAJ15A Figure 3. – 12V/2A Application with Wider Input Operating Range 421412f U An OV hysteretic comparator detects overvoltage conditions at the OV pin, with the following thresholds: OV low-to-high (VOVHI) = 3V OV high-to-low (VOVHI – V0VHST) = 2.85V In Figure 2, a divider (R1-R2) is used to scale the supply voltage of 12V ±10%. Using R1 = 121k and R2 = 32.4k gives a typical operating range of 10.7V to 13.5V. The under and overvoltage shutdown thresholds are then 9.5V to 14.2V. 1% divider resistors are recommended to preserve threshold accuracy. The R1-R2 divider values shown in Figure 2 set a standing current of slightly more than 75µA and define an impedance at UV/OV of 25kΩ. In most applications, 25kΩ impedance coupled with 250mV UV hysteresis makes the LTC4214 insensitive to noise. If more noise immunity is desired, add a 1nF to 10nF filter capacitor from UV/OV to VEE. Separate UV and OV pins can be used for a wider operating range such as 10V to 14V as shown in Figure 3. Other combinations are possible with different resistor arrangements. + Q2 NDS0605 EN RPULLDN 10k VOUT Q1 IRF7413 RC 10Ω CC 10nF RS 0.025Ω CL 100µF 1 VIN LTC4214-1 9 8 10 3 UV OV TIMER SS VEE CSS 22nF 5 PWRGD DRAIN GATE SENSE 2 7 6 4 RD 475k CIN 0.1µF 4214 F03 W U U 13 LTC4214-1/LTC4214-2 APPLICATIO S I FOR ATIO UV/OV OPERATION A low input to the UV comparator will reset the LTC4214 and pull the GATE and TIMER pins low. A low-to-high UV transition will initiate an initial timing sequence if the other interlock conditions are met. A high-to-low transition in the UV comparator immediately shuts down the LTC4214, pulls the MOSFET gate low and resets the latched PWRGD high. Overvoltage conditions detected by the OV comparator will also pull GATE low, thereby shutting down the load. However, it will not reset the circuit breaker TIMER, PWRGD flag or shutdown cooling timer. Returning the supply voltage to an acceptable range restarts the GATE pin if all the interlock conditions except TIMER are met. Only during the initial timing cycle does an OV condition reset the TIMER. DRAIN Connecting an external resistor, RD, to the dual function DRAIN pin allows VOUT sensing without it being damaged by large voltage transients. Below 3V, negligible pin leakage allows a DRAIN low comparator to detect VOUT less than 1.232V (VDRNL). This condition, together with the GATE low comparator, sets the PWRGD flag. If VOUT > VDRNCL (4.2V), the DRAIN pin is clamped at about 4.2V and the current flowing in RD is given by: IDRN ≈ VOUT − VDRNCL RD This current is scaled up 8 times during a circuit breaker fault and is added to the nominal 40µA TIMER current. This accelerates the fault TIMER pull-up when the MOSFET’s drain-source voltage exceeds 4.2V and effectively shortens the MOSFET heating duration. TIMER The operation of the TIMER pin is somewhat complex as it handles several key functions. A capacitor CT is used at TIMER to provide timing for the LTC4214. Four different charging and discharging modes are available at TIMER: 14 U 1) A 5µA slow charge; initial timing and shutdown cooling delay. 2) A (40µA + 8 • IDRN) fast charge; circuit breaker delay. 3) A 5µA slow discharge; circuit breaker "cool off" and shutdown cooling. 4) Low impedance switch; resets the TIMER capacitor after an initial timing delay, in UVLO, in UV and in OV during initial timing. For initial start-up, the 5µA pull-up is used. The low impedance switch is turned off and the 5µA current source is enabled when the interlock conditions are met. CT charges to 3V in a time period given by: W U U t= 3 V • CT 5µA (2) When CT reaches 3V (VTMRH), the low impedance switch turns on and discharges CT. A GATE start-up cycle begins and both SS and GATE are released. CIRCUIT BREAKER TIMER OPERATION If the SENSE pin detects more than a 50mV drop across RS, the TIMER pin charges CT with (40µA + 8 • IDRN). If CT charges to 3V, the GATE pin pulls low and the LTC4214-1 latches off while the LTC4214-2 starts a shutdown cooling cycle. The LTC4214-1 remains latched off until the UV pin is momentarily pulsed low or TIMER is momentarily discharged low by an external switch or VIN dips below UVLO and is then restored. The circuit breaker timeout period is given by: (1) t= 3 V • CT 40µA + 8 • IDRN (3) If VOUT < 3V, an internal PMOS device isolates any DRAIN pin leakage current, making IDRN = 0µA in Equation (3). If VOUT > 4.2V (VDRNCL) during the circuit breaker fault period, the charging of CT accelerates by 8 • IDRN of Equation (1). Intermittent overloads may exceed the 50mV threshold at SENSE, but, if their duration is sufficiently short, TIMER will not reach 3V and the LTC4214 will not shut the external 421412f LTC4214-1/LTC4214-2 APPLICATIO S I FOR ATIO MOSFET off. To handle this situation, the TIMER discharges CT slowly with a 5µA pull-down whenever the SENSE voltage is less than 50mV. Therefore, any intermittent overload with VOUT < 3V and an aggregate duty cycle of 12.5% or more will eventually trip the circuit breaker and shut down the LTC4214. Figure 4 shows the circuit breaker response time in seconds normalized to 1µF for IDRN = 0µA. The asymmetric charging and discharging of CT is a fair gauge of MOSFET heating. The normalized circuit response time is estimated by t 3 = CT (µF) (40 + 8 • IDRN ) • D − 5 [ ] 100 NORMALIZED RESPONSE TIME (s/µF) IDRN = 0µA 10 t 1 CT(µF) = 3 [(40 + 8 • IDRN) • D – 5] 0.1 0.01 0 10 20 30 40 50 60 70 80 90 100 FAULT DUTY CYCLE (%) 4214 F04 Figure 4. Circuit-Breaker Response Time SHUTDOWN COOLING CYCLE For the LTC4214-1 (latchoff version), TIMER latches high with a 5µA pull-up after the circuit breaker fault TIMER reaches 3V. For the LTC4214-2 (automatic retry version), a shutdown cooling cycle begins if TIMER reaches the 3V threshold. TIMER starts with a 5µA pull-down until it reaches the 1.7V threshold. Then, the 5µA pull-up turns back on until TIMER reaches the 3V threshold. Four 5µA U pull-down cycles and three 5µA pull-up cycles occur between the 1.7V and 3V thresholds, creating a time interval given by: W U U tSHUTDOWN = 7 • 1.3V • CT 5µA (5) At the 1.7V threshold of the last pull-down cycle, a GATE ramp-up is attempted. SOFT-START (4) Soft-start limits the inrush current profile during GATE start-up. Unduly long soft-start intervals can exceed the MOSFET’s SOA rating if powering up into an active load. If SS floats, an internal current source ramps SS from 0V to 1.6V in about 220µs. Connecting an external capacitor CSS from SS to ground modifies the ramp to approximate an RC response of:  t    − R •C  VSS (t) ≈ VSS •  1 − e  SS SS         (6) An internal resistor divider (69.35k/3.65k) scales VSS(t) down by 20 times to give the analog current limit threshold: VACL (t) = VSS (t) − VOS 20 (7) This allows the inrush current to be limited to VACL(t)/RS. The offset voltage, VOS (10mV), ensures CSS is sufficiently discharged and the ACL amplifier is in current limit before GATE start-up. SS is pulled low under any of the following conditions: in UVLO, in an undervoltage condition, in an overvoltage condition, during the initial timing cycle or when the circuit breaker fault times out. 421412f 15 LTC4214-1/LTC4214-2 APPLICATIO S I FOR ATIO GATE GATE is pulled low to VEE under any of the following conditions: in UVLO, in an undervoltage condition, in an overvoltage condition, during the initial timing cycle or when the circuit breaker fault times out. When GATE turns on, a 50µA current source charges the MOSFET gate and any associated external capacitance. The gate drive is limited to no more than VIN. Gate-drain capacitance (CGD) feedthrough at the first abrupt application of power can cause a gate-source voltage sufficient to turn on the MOSFET. A unique circuit pulls GATE low with practically no usable voltage at VIN and eliminates current spikes at insertion. A large external gate-source capacitor is thus unnecessary for the purpose of compensating CGD. Instead, a smaller value (≥ 5nF) capacitor CC is adequate. CC also provides compensation for the analog current limit loop. GATE has two comparators: the GATE low comparator looks for < 0.5V threshold prior to initial timing or a GATE start-up cycle; the GATE high comparator looks for < 2.8V relative to VIN and, together with the DRAIN low comparator, sets PWRGD status during GATE start-up. SENSE The SENSE pin is monitored by the circuit breaker (CB) comparator, the analog current limit (ACL) amplifier and the fast current limit (FCL) comparator. Each of these three measures the potential of SENSE relative to VEE. When SENSE exceeds 50mV, the CB comparator activates the 40µA TIMER pull-up. At 70mV, the ACL amplifier servos the MOSFET current and, at 200mV, the FCL comparator abruptly pulls GATE low in an attempt to bring the MOSFET current under control. If any of these conditions persists long enough for TIMER to charge CT to 3V (see Equation 3), the LTC4214 shuts down and pulls GATE low. If the SENSE pin encounters a voltage greater than 70mV, the ACL amplifier will servo GATE downwards in an attempt to control the MOSFET current. Since GATE 16 U overdrives the MOSFET in normal operation, the ACL amplifier needs time to discharge GATE to the threshold of the MOSFET. For a mild overload the ACL amplifier can control the MOSFET current, but in the event of a severe overload the current may overshoot. At SENSE = 200mV the FCL comparator takes over, quickly discharging the GATE pin to near VEE potential. FCL then releases and the ACL amplifier takes over. All the while TIMER is running. The effect of FCL is to add a nonlinear response to the control loop in favor of reducing MOSFET current. Owing to inductive effects in the system, FCL typically overcorrects the current limit loop and GATE undershoots. A zero in the loop (resistor RC in series with the gate capacitor) helps the ACL amplifier to recover. SHORT-CIRCUIT OPERATION Circuit behavior arising from a load side low impedance short is shown in Figure 5 for the LTC4214. Initially, the current overshoots the fast current limit level of VSENSE = 200mV (Trace 2) as the GATE pin works to bring VGS under control (Trace 3). The overshoot glitches the backplane in the negative direction and when the current is reduced to 70mV/RS, the backplane responds by glitching in the positive direction. SUPPLY RING OWING TO CURRENT OVERSHOOT GND WITH RESPECT TO –12V 0.1ms 10V SENSE 0.1ms 200mV GATE 0.1ms 10V TIMER 0.1ms 2V SUPPLY RING OWING TO MOSFET TURN-OFF TRACE 1 ONSET OF OUTPUT SHORT CIRCUIT TRACE 2 FAST CURRENT LIMIT ANALOG CURRENT LIMIT TRACE 3 TRACE 4 CTIMER RAMP LATCH OFF 4214 F05 W U U Figure 5. Output Short-Circuit Behavior of LTC4214 421412f LTC4214-1/LTC4214-2 APPLICATIO S I FOR ATIO TIMER commences charging CT (Trace 4) while the analog current limit loop maintains the fault current at 70mV/RS, which in this case is 3.5A (Trace 2). Note that the backplane voltage (Trace 1) sags under load. Timer pull-up is accelerated by VOUT. When CT reaches 3V, GATE turns off, PWRGD pulls high, the load current drops to zero and the backplane rings in the positive direction. The transient associated with the GATE turn off can be controlled with a snubber to reduce ringing and transient voltage suppressor to clip off large spikes. The choice of RC for the snubber is usually done experimentally. The value of the snubber capacitor is usually chosen between 10 to 100 times the MOSFET COSS. The value of the snubber resistor is typically between 3Ω to 100Ω. In many cases, a simple short-circuit test can be performed to determine the component values needed. A low impedance short on one card may influence the behavior of others sharing the same backplane. The initial glitch and backplane sag as seen in Figure 5 Trace 1, can rob charge from output capacitors on adjacent cards. When the faulty card shuts down, current flows in to refresh the capacitors. If LTC4214s are used by the other cards, they respond by limiting the inrush current to a value of 70mV/RS. If CT is sized correctly, the capacitors will recharge long before CT times out. POWER GOOD, PWRGD PWRGD latches low if GATE charges up to within 2.8V of VIN and DRAIN pulls below VDRNL during start-up. PWRGD is reset in UVLO, in a UV condition or if CT charges up to 3V. An overvoltage condition has no effect on PWRGD status. A 50µA current pulls this pin high during reset. Various ways of using the PWRGD pin for interfacing with a Power Module load are shown in the Typical Application as well as Figures 2, 3, 18 and 19. MOSFET SELECTION The external MOSFET switch must have adequate safe operating area (SOA) to handle short-circuit conditions U until TIMER times out. These considerations take precedence over DC current ratings. A MOSFET with adequate SOA for a given application can always handle the required current, but the opposite may not be true. Consult the manufacturer’s MOSFET data sheet for safe operating area and effective transient thermal impedance curves. MOSFET selection is a 3-step process by assuming the absense of a soft-start capacitor. First, RS is calculated and then the time required to charge the load capacitance is determined. This timing, along with the maximum shortcircuit current and maximum input voltage defines an operating point that is checked against the MOSFET’s SOA curve. To begin a design, first specify the required load current and Ioad capacitance, IL and CL. The circuit breaker current trip point (VCB/RS) should be set to accommodate the maximum load current. Note that maximum input current to a DC/DC converter is expected at VSUPPLY(MIN). RS is given by: RS = VCB(MIN) IL(MAX) W U U (8) where VCB(MIN) = 44mV represents the guaranteed minimum circuit breaker threshold. During the initial charging process, the LTC4214 may operate the MOSFET in current limit, forcing (VACL) between 60mV to 80mV across RS. The minimum inrush current is given by: IINRUSH(MIN)= 60mV RS (9) Maximum short-circuit current limit is calculated using the maximum VSENSE. This gives I SHORTCIRCUIT(MAX)= 80mV RS (10) The TIMER capacitor CT must be selected based on the slowest expected charging rate; otherwise TIMER might time out before the load capacitor is fully charged. A value 421412f 17 LTC4214-1/LTC4214-2 APPLICATIO S I FOR ATIO for CT is calculated based on the maximum time it takes the load capacitor to charge. That time is given by: tCL(CHARGE) = C • V C L• V SUPPLY(MAX) = I IINRUSH(MIN) The maximum current flowing in the DRAIN pin is given by: IDRN(MAX) = V SUPPLY(MAX)− V DRNCL RD (12) Approximating a linear charging rate as IDRN drops from IDRN(MAX) to zero, the IDRN component in Equation (3) can be approximated with 0.5 • IDRN(MAX). Rearranging equation, TIMER capacitor CT is given by: CT = tCL(CHARGE) • 40µA + 4 • IDRN(MAX) 3V ( ) Returning to Equation (3), the TIMER period is calculated and used in conjunction with V SUPPLY(MAX) a nd ISHORTCIRCUIT(MAX) to check the SOA curves of a prospective MOSFET. As a numerical design example, consider a 10W load, which requires 1.1A input current at – 10.8V. If VSUPPLY(MAX) = 13.2V and CL = 100µF, RD = 475k, Equation (8) gives RS = 40mΩ; Equation (13) gives CT = 34nF. To account for errors in RS, CT, TIMER current (40µA), TIMER threshold (3V), RD, DRAIN current multiplier and DRAIN voltage clamp (VDRNCL), the calculated value should be multiplied by 1.5, giving the nearest standard value of CT = 56nF. If a short-circuit occurs, a current of up to 80mV/ 40mΩ = 2A will flow in the MOSFET for 0.9ms as dictated by CT = 56nF in Equation (3). The MOSFET must be selected based on this criterion. The IRF7413 can handle 20V and 2A for 9ms and is safe to use in this application. Computing the maximum soft-start capacitor value during soft-start to a load short is complicated by the nonlinear MOSFET’s SOA characteristics and the RSSCSS response. An overly conservative but simple approach begins with 18 U the maximum circuit breaker current, given by: (11) W U U 56mV (14) RS From the SOA curves of a prospective MOSFET, determine the time allowed, tSOA(MAX). CSS is given by: I CB(MAX)= tSOA(MAX) (15) 1.61 • RSS In the above example, 56mV/40mΩ gives 1.4A. tSOA(MAX) for the IRF7413 is 8ms for 1.4A at 30V. From Equation (15), CSS = 68nF. Actual board evaluation showed that CSS = 33nF was appropriate. The ratio (RSS • CSS) to tCL(CHARGE) is a good gauge as a large ratio may result in the time-out period expiring. This gauge is determined empirically with board level evaluation. CSS = SUMMARY OF DESIGN FLOW To summarize the design flow, consider the application shown in Figure 2. It was designed for 12W for a –10V to –14V supply. Calculate the maximum load current: 12W/10V = 1.2A; allowing for 75% converter efficiency, IIN(MAX) = 1.6A. Calculate RS: from Equation (8) RS = 25mΩ. Calculate I SHORTCIRCUIT(MAX) : from Equation (10) ISHORTCIRCUIT(MAX) = 3.2A. Select a MOSFET that can handle 3.2A at 14V: IRF7413. Calculate CT: from Equation (13) CT = 24nF. Select CT = 47nF, which gives the circuit breaker time-out period tMAX = 0.7ms. Consult MOSFET SOA curves: the IRF7413 can handle 3.2A at 20V for 3.5ms, so it is safe to use in this application. Calculate CSS: using Equations (14) and (15) select CSS = 22nF. FREQUENCY COMPENSATION The LTC4214 typical frequency compensation network for the analog current limit loop is a series RC (10Ω) and CC connected to VEE. Figure 6 depicts the relationship be421412f (13) LTC4214-1/LTC4214-2 APPLICATIO S I FOR ATIO 25 COMPENSATION CAPACITANCE, CC (nF) Si4864DY • 20 Si4876DY 15 IRF7413 Si4410DY • 10 • • 5 IRF7803 0 0 • Si4412ADY • TO SENSE TO VEE 1000 2000 3000 4000 5000 6000 7000 MOSFET, CISS (pF) 4214 F06 Figure 6. Recommended Compensation Capacitor CC vs MOSFET CISS tween the compensation capacitor CC and the MOSFET’s CISS. The line in Figure 6 is used to select a starting value for CC based upon the MOSFET’s CISS specification. Optimized values for CC are shown for several popular MOSFETs. Differences in the optimized value of CC versus the starting value are small. Nevertheless, compensation values should be verified by board level short-circuit testing. As seen in Figure 5 previously, at the onset of a shortcircuit event, the input supply voltage can ring dramatically owing to series inductance. If this voltage avalanches the MOSFET, current continues to flow through the MOSFET to the output. The analog current limit loop cannot control this current flow and therefore the loop undershoots. This effect cannot be eliminated by frequency compensation. A zener diode is required to clamp the input supply voltage and prevent MOSFET avalanche. SENSE RESISTOR CONSIDERATIONS For proper circuit breaker operation, Kelvin-sense PCB connections between the sense resistor and the LTC4214’s VEE and SENSE pins are strongly recommended. The drawing in Figure 7 illustrates the correct way of making connections between the LTC4214 and the sense resistor. PCB layout should be balanced and symmetrical to minimize wiring errors. In addition, the PCB layout for the sense resistor should include good thermal management techniques for optimal sense resistor power dissipation. U CURRENT FLOW FROM LOAD CURRENT FLOW TO –12V BACKPLANE SENSE RESISTOR TRACK WIDTH W: 0.03" PER AMP ON 1 OZ COPPER W 4214 F07 W U U Figure 7. Making PCB Connections to the Sense Resistor TIMING WAVEFORMS System Power-Up Figure 8 details the timing waveforms for a typical powerup sequence in the case where a board is already installed in the backplane and system power is applied abruptly. At time point 1, the supply ramps up, together with UV/OV, VIN, VOUT, DRAIN and PWRGD. At time point 2, VIN exceeds VLKO and the internal logic checks for UV > VUVHI, OV < VOVHI, GATE < VGATEL, SENSE < VCB, SS < 20 • VOS and TIMER < VTMRL. If all conditions are met, an initial timing cycle starts and the TIMER capacitor is charged by a 5µA current source pull-up. At time point 3, TIMER reaches the VTMRH threshold and the initial timing cycle terminates. The TIMER capacitor is quickly discharged. At time point 4, the VTMRL threshold is reached and the conditions of GATE < V GATEL , SENSE < V CB a nd SS < 20 • VOS must be satisfied before a GATE ramp-up cycle begins. SS ramps up as dictated by RSS • CSS (as in Equation 6); GATE is held low by the analog current limit (ACL) amplifier until SS crosses 20 • VOS. Upon releasing GATE, 50µA sources into the external MOSFET gate and compensation network. When the GATE voltage reaches the MOSFET’s threshold, current begins flowing into the load capacitor at time point 5. At time point 6, load current reaches the SS control level and the analog current limit loop activates. Between time points 6 and 8, the GATE voltage is servoed, the SENSE voltage is regulated at VACL(t) (Equation 7) and soft-start limits the slew rate of 421412f 19 LTC4214-1/LTC4214-2 APPLICATIO S I FOR ATIO VIN CLEARS VLKO, CHECK UV > VUVHI, OV < VOVHI, GATE < VGATEL, SENSE < VCB, SS < 20 • VOS AND TIMER < VTMRL TIMER CLEARS VTMRL, CHECK GATE < VGATEL, SENSE < VCB AND SS < 20 • VOS 1 GND – (–12V) 2 3 4 56 7 8 9 10 11 UV/OV VIN VLKO VTMRH 40µA + 8 • IDRN VTMRL 50µA TIMER 5µA GATE VGATEL 20 • (VACL + VOS) 20 • (VCB + VOS) 20 • VOS SS SENSE VOUT VDRNCL DRAIN VDRNL PWRGD INITIAL TIMING GATE START-UP Figure 8. System Power-Up Timing (All Waveforms are Referenced to VEE) the load current. If the SENSE voltage (VSENSE – VEE) reaches the VCB threshold at time point 7, the circuit breaker TIMER activates. The TIMER capacitor, CT, is charged by a (40µA + 8 • IDRN) current pull-up. As the load capacitor nears full charge, load current begins to decline. At time point 8, the load current falls and the SENSE voltage drops below VACL(t). The analog current limit loop shuts off and the GATE pin ramps further. At time point 9, the SENSE voltage drops below VCB, the fault TIMER cycle ends, followed by a 5µA discharge cycle (cool off). The duration between time points 7 and 9 must be shorter than one circuit breaker delay to avoid a fault time out during 20 U 5µA 5µA 50µA VIN – VGATEH VACL VCB 4214 F08 W U U GATE ramp-up. When GATE ramps past the VGATEH threshold at time point 10, PWRGD pulls low. At time point 11, GATE reaches its maximum voltage as determined by VIN. Live Insertion with Short Pin Control of UV/OV In the example shown in Figure 9, power is delivered through long connector pins whereas the UV/OV divider makes contact through a short pin. This ensures the power connections are firmly established before the LTC4214 is activated. At time point 1, the power pins make contact and VIN ramps through VLKO. At time point 2, the UV/OV divider 421412f LTC4214-1/LTC4214-2 APPLICATIO S I FOR ATIO U TIMER CLEARS VTMRL, CHECK GATE < VGATEL, SENSE < VCB AND SS < 20 • VOS 1 GND – (–12V) 2 3 4 56 7 8 9 1011 VTMRH TIMER 5µA VTMRL GATE VGATEL SS 20 • (VACL + VOS) 20 • (VCB + VOS) 20 • VOS VACL SENSE VCB 50µA 50µA 40µA + 8 • IDRN 5µA 5µA VIN – VGATEH VDRNCL DRAIN VDRNL GATE START-UP 4214 F09 UV CLEARS VUVHI, CHECK OV < VOVHI, GATE < VGATEL, SENSE < VCB, SS < 20 • VOS AND TIMER < VTMRL UV/OV VUVHI VIN VLKO VOUT PWRGD INITIAL TIMING Figure 9. Power-Up Timing with a Short Pin (All Waveforms are Referenced to VEE) makes contact and its voltage exceeds VUVHI. In addition, the internal logic checks for OV < VOVHI, GATE < VGATEL, SENSE < VCB, SS < 20 • VOS and TIMER < VTMRL. If all conditions are met, an initial timing cycle starts and the TIMER capacitor is charged by a 5µA current source pullup. At time point 3, TIMER reaches the VTMRH threshold and the initial timing cycle terminates. The TIMER capacitor is quickly discharged. At time point 4, the V TMRL threshold is reached and the conditions of GATE < VGATEL, SENSE < VCB and SS < 20 • VOS must be satisfied before a GATE start-up cycle begins. SS ramps up as dictated by RSS • CSS; GATE is held low by the analog current limit W U U amplifier until SS crosses 20 • VOS. Upon releasing GATE, 50µA sources into the external MOSFET gate and compensation network. When the GATE voltage reaches the MOSFET’s threshold, current begins flowing into the load capacitor at time point 5. At time point 6, load current reaches the SS control level and the analog current limit loop activates. Between time points 6 and 8, the GATE voltage is servoed, the SENSE voltage is regulated at VACL(t) and soft-start limits the slew rate of the load current. If the SENSE voltage (VSENSE – VEE) reaches the VCB threshold at time point 7, the circuit breaker TIMER activates. The TIMER capacitor, CT, is charged by a 421412f 21 LTC4214-1/LTC4214-2 APPLICATIO S I FOR ATIO (40µA + 8 • IDRN) current pull-up. As the load capacitor nears full charge, load current begins to decline. At point 8, the load current falls and the SENSE voltage drops below VACL(t). The analog current limit loop shuts off and the GATE pin ramps further. At time point 9, the SENSE voltage drops below VCB and the fault TIMER cycle ends, followed by a 5µA discharge cycle (cool off). When GATE ramps past VGATEH threshold at time point 10, PWRGD pulls low. At time point 11, GATE reaches its maximum voltage as determined by VIN. UV DROPS BELOW VUVHI – VUVHST. GATE, SS AND TIMER ARE PULLED DOWN, PWRGD RELEASES UV CLEARS VUVHI, CHECK OV CONDITION, GATE < VGATEL, SENSE < VCB, SS < 20 • VOS AND TIMER < VTMRL TIMER CLEARS VTMRL, CHECK GATE < VGATEL, SENSE < VCB AND SS < 20 • VOS 1 VUVHI – VUVHST 2 VUVHI VTMRH TIMER 5µA VTMRL 50µA GATE VGATEL 20 • (VACL + VOS) 20 • (VCB + VOS) 20 • VOS VACL SENSE VCB VDRNCL DRAIN VDRNL 50µA 40µA + 8 • IDRN 3 4 56 7 8 9 10 11 UV SS PWRGD INITIAL TIMING GATE START-UP Figure 10. Undervoltage Timing (All Waveforms are Referenced to VEE) 22 U Undervoltage Timing In Figure 10 when the UV pin drops below VUVHI – VUVHST (time point 1), the LTC4214 shuts down with TIMER, SS and GATE all pulling low. If current has been flowing, the SENSE pin voltage decreases to zero as GATE collapses. When UV recovers and clears VUVHI (time point 2), an initial timer cycle begins followed by a start-up cycle. 5µA 5µA VIN – VGATEH 4214 F10 W U U 421412f LTC4214-1/LTC4214-2 APPLICATIO S I FOR ATIO VIN Undervoltage Lockout Timing The VIN undervoltage lockout comparator, UVLO, has a similar timing behavior as the UV pin timing except it looks for VIN < (VLKO – VLKH) to shut down and VIN > VLKO to start. In an undervoltage lockout condition, both UV and OV comparators are held off. When VIN exits undervoltage lockout, the UV and OV comparators are enabled. UV/OV CLEARS VUVHI, CHECK OV CONDITION, GATE < VGATEL, SENSE < VCB, SS < 20 • VOS AND TIMER < VTMRL UV/OV OVERSHOOTS VOVHI AND TIMER ABORTS INITIAL TIMING CYCLE UV/OV DROPS BELOW VOVHI – VOVHST AND TIMER RESTARTS INITIAL TIMING CYCLE TIMER CLEARS VTMRL, CHECK GATE < VGATEL, SENSE < VCB AND SS < 20 • VOS 1 VOVHI UV/OV VUVHI VTMRH TIMER 5µA VTMRL 50µA GATE VGATEL SS 20 • (VACL + VOS) 20 • (VCB + VOS) 20 • VOS VACL SENSE VCB VDRNCL DRAIN VDRNL 50µA 40µA + 8 • IDRN 2 3 VOVHI – VOVHST 4 5 67 8 10 12 9 11 PWRGD INITIAL TIMING GATE START-UP Figure 11. Undervoltage Timing with an Overvoltage Glitch (All Waveforms are Referenced to VEE) U Undervoltage Timing with Overvoltage Glitch In Figure 11, both UV and OV pins are connected together. When UV clears VUVHI (time point 1), an initial timing cycle starts. If the system bus voltage overshoots VOVHI as shown at time point 2, TIMER discharges. At time point 3, the supply voltage recovers and drops below the VOVHI – VOVHST threshold. The initial timing cycle restarts, followed by a GATE start-up cycle. 5µA 5µA VIN – VGATEH 4214 F11 W U U 421412f 23 LTC4214-1/LTC4214-2 APPLICATIO S I FOR ATIO Overvoltage Timing During normal operation, if the OV pin exceeds VOVHI as shown at time point 1 of Figure 12, the TIMER and PWRGD status are unaffected. Nevertheless, SS and GATE pull down and the load is disconnected. At time point 2, OV OV OVERSHOOTS VOVHI. GATE AND SS ARE PULLED DOWN, PWRGD AND TIMER ARE UNAFFECTED OV DROPS BELOW VOVHI – VOVHST, CHECK GATE < VGATEL, SENSE < VCB AND SS < 20 • VOS 1 VOVHI VTMRH TIMER 40µA + 8 • IDRN 50µA GATE VGATEL 50µA 2 34 5 67 8 9 OV VOVHI – VOVHST SS 20 • (VCB + VOS) 20 • VOS VACL VCB GATE START-UP SENSE Figure 12. Overvoltage Timing (All Waveforms are Referenced to VEE) 24 U recovers and drops below the VOVHI – VOVHST threshold. A GATE start-up cycle begins. If the overvoltage glitch is long enough to deplete the load capacitor, a full start-up cycle as shown between time points 4 through 7 may occur. 5µA 5µA VIN – VGATEH 20 • (VACL + VOS) 4214 F12 W U U 421412f LTC4214-1/LTC4214-2 APPLICATIO S I FOR ATIO Circuit Breaker Timing In Figure 13a, the TIMER capacitor charges at 40µA if the SENSE pin exceeds VCB but VDRN is less than 4.2V. If the SENSE pin drops below VCB before TIMER reaches the VTMRH threshold, TIMER is discharged by 5µA. In Figure 13b, when TIMER exceeds VTMRH, GATE pulls down 1 VTMRH TIMER 2 VTMRH 5µA 40µA + 8 • IDRN TIMER GATE SS VACL SENSE VCB VOUT DRAIN PWRGD CB FAULT (13a) Momentary Circuit-Breaker Fault (13b) Circuit-Breaker Time Out Figure 13. Circuit-Breaker Timing Behavior (All Waveforms are Referenced to VEE) U immediately and the LTC4214 shuts down. In Figure 13c, multiple momentary faults cause the TIMER capacitor to integrate and reach VTMRH. GATE pull down follows and the LTC4214 shuts down. During shutdown, the LTC4214-1 latches TIMER high with a 5µA pull-up current source; the LTC4214-2 activates a shutdown cooling cycle. CB TIMES OUT 1 2 VTMRH 40µA + 8 • IDRN TIMER 1 2 5µA 3 CB TIMES OUT 4 40µA + 8 • IDRN 40µA + 8 • IDRN GATE GATE SS VACL SENSE VCB SENSE SS VACL VCB VOUT VDRNCL DRAIN DRAIN VOUT VDRNCL PWRGD CB FAULT PWRGD 4214 F13 W U U CB FAULT CB FAULT (13c) Multiple Circuit-Breaker Fault 421412f 25 LTC4214-1/LTC4214-2 APPLICATIO S I FOR ATIO Resetting a Fault Latch (LTC4214-1) The latched circuit breaker fault of LTC4214-1 benefits from long cooling time. It is reset by pulling the UV pin below VUVHI – VUVHST with a switch. Reset is also accomplished by pulling the VIN pin momentarily below (VLKO – VLKH). A third reset method involves pulling the TIMER pin below VTMRL as shown in Figure 14. An initial timing cycle is skipped if TIMER is used for reset. An initial timing cycle is generated if reset by the UV pin or the VIN pin. SWITCH RESETS LATCHED TIMER SWITCH RELEASES SS 1 2 34 5 67 8 9 5µA 5µA TIMER VTMRH 40µA + 8 • IDRN VTMRL 50µA 50µA GATE VGATEL SS 20 • (VACL + VOS) 20 • (VCB + VOS) 20 • VOS VACL SENSE DRAIN PWRGD GATE START-UP MOMENTARY DPST SWITCH RESET 4214 F14 Figure 14. Pushbutton Reset of LTC4214-1’s Latched Fault (All Waveforms are Referenced to VEE) 26 U The duration of the TIMER reset pulse should be smaller than the time taken to reach 0.2V at SS pin. With a single pole mechanical pushbutton switch, this may not be feasible. A double pole, single throw pushbutton switch removes this restriction by connecting the second switch to the SS pin. With this method, both the SS and TIMER pins are released at the same time. 5µA VIN – VGATEH VCB VDRNCL VDRNL 421412f W U U LTC4214-1/LTC4214-2 APPLICATIO S I FOR ATIO Shutdown Cooling Cycle (LTC4214-2) Figure 15 shows the timer behavior of the LTC4214-2. At time point 2, TIMER exceeds VTMRH, GATE pulls down immediately and the LTC4214 shuts down. TIMER starts a shutdown cooling cycle by discharging TIMER with 5µA to the VTMRL threshold. TIMER then charges with 5µA to the VTMRH threshold. There are four 5µA discharge phases CIRCUIT BREAKER TIMES OUT 1 40µA + 8 • IDRN TIMER 5µA 2 5µA VTMRL 50µA GATE 50µA VGATEL 20 • (VACL + VOS) 20 • (VCB + VOS) 20 • VOS VACL SENSE VCB VIN – VGATEH 5µA 5µA 5µA 5µA SS VOUT VDRNCL DRAIN VDRNL PWRGD SHUTDOWN COOLING GATE START-UP 4214 F15 CB Figure 15. Shutdown Cooling Timing Behavior of LTC4214-2 (All Waveforms are Referenced to VEE) U and three 5µA charge phases in this shutdown cooling cycle spanning time points 2 and 3. At time point 3, the LTC4214 automatic retry occurs with a start-up cycle. Good thermal management techniques are highly recommended; power and thermal dissipation must be carefully evaluated when implementing the automatic retry scheme. RETRY 3 45 6 78 9 10 5µA VTMRH 40µA + 8 • IDRN 5µA 5µA 421412f W U U 27 LTC4214-1/LTC4214-2 APPLICATIO S I FOR ATIO Analog Current Limit and Fast Current Limit In Figure 16a, when SENSE exceeds VACL, GATE is regulated by the analog current limit amplifier loop. When SENSE drops below VACL, GATE is allowed to pull up. In Figure 16b, when a severe fault occurs, SENSE exceeds VFCL and GATE immediately pulls down until the analog current amplifier can establish control. If the severe fault 12 34 VTMRH 5µA 5µA 40µA + 8 • IDRN TIMER GATE SS VACL SENSE VCB VOUT DRAIN PWRGD (16a) Analog Current Limit Fault Figure 16. Current Limit Behavior (All Waveforms are Referenced to VEE) 28 U causes VOUT to exceed VDRNCL, the DRAIN pin is clamped at VDRNCL. IDRN flows into the DRAIN pin and is multiplied by 8. This extra current is added to the TIMER pull-up current of 40µA. This accelerated TIMER current of [40µA+8 • IDRN] produces a shorter circuit breaker fault delay. Careful selection of CT, RD and MOSFET can help prevent SOA damage in a low impedance fault condition. CB TIMES OUT 1 VTMRH 40µA + 8 • IDRN TIMER 2 GATE SS SENSE VFCL VACL VCB VOUT VDRNCL DRAIN PWRGD 4214 F16 W U U (16b) Fast Current Limit Fault 421412f LTC4214-1/LTC4214-2 APPLICATIO S I FOR ATIO Soft-Start If the SS pin is not connected, this pin defaults to a linear voltage ramp, from 0V to 1.6V in about 220µs at GATE start-up, as shown in Figure 17a. If a soft-start capacitor, CSS, is connected to this SS pin, the soft-start response is modified from a linear ramp to an RC response (Equation 6), as shown in Figure 17b. This feature allows load current to slowly ramp-up at GATE start-up. Soft-start is initiated at time point 3 by a TIMER transition from VTMRH to VTMRL (time points 1 to 2) or by the OV pin falling below the VOVHI – VOVHST threshold after an OV condition. When the SS pin is below 0.2V, the analog current limit amplifier holds GATE low. Above 0.2V, GATE is released and 50µA ramps up the compensation network and GATE capacitance at time point 4. Meanwhile, the SS pin voltage continues to ramp up. When GATE reaches the MOSFET’s threshold, the MOSFET begins to conduct. Due to the MOSFET’s high gm, the MOSFET current quickly reaches END OF INTIAL TIMING CYCLE 12 34 567 VTMRH TIMER VTMRL 50µA GATE 50µA 20 • (VACL + VOS) SS 20 • (VCB + VOS) 20 • VOS VACL SENSE VCB VDRNCL DRAIN VDRNL DRAIN SENSE SS 20 • VOS VACL VCB VDRNCL VDRNL VGS(th) VIN – VGATEH 7a 40µA + 8 • IDRN 89 10 11 TIMER 5µA PWRGD (17a) Without External CSS Figure 17. Soft-Start Timing (All Waveforms are Referenced to VEE) U the soft-start control value of VACL(t) (Equation 7). At time point 6, the GATE voltage is controlled by the current limit amplifier. The soft-start control voltage reaches the circuit breaker voltage, VCB, at time point 7 and the circuit breaker TIMER activates. As the load capacitor nears full charge, load current begins to decline below VACL(t). The current limit loop shuts off and GATE releases at time point 8. At time point 9, the SENSE voltage falls below VCB and TIMER deactivates. Large values of CSS can cause premature circuit breaker time out as VACL(t) may exceed the VCB potential during the circuit breaker delay. The load capacitor is unable to achieve full charge in one GATE start-up cycle. A more serious side effect of large CSS values is SOA duration may be exceeded during soft-start into a low impedance load. A soft-start voltage below VCB will not activate the circuit breaker TIMER. END OF INTIAL TIMING CYCLE 12 3 4 5 6 VTMRH VTMRL 50µA GATE VGS(th) 50µA 20 • (VACL + VOS) 20 • (VCB + VOS) VIN – VGATEH 7 89 10 11 40µA + 8 • IDRN 5µA PWRGD 4214 F17 W U U (17b) With External CSS 421412f 29 LTC4214-1/LTC4214-2 APPLICATIO S I FOR ATIO Power Limit Circuit Breaker Figure 18 shows the LTC4214-1 in a power limit circuit breaking application. The SENSE pin is modulated by the board supply voltage, VSUPPLY. The zener voltage, VZ is set to be the same as the low supply operating voltage, VSUPPLY(MIN) = 10V. If the goal is to have the high supply operating voltage, VSUPPLY(MAX) = 14V give the same power at VSUPPLY(MIN), then resistors R4 and R6 are selected using the ratio: R6 VCB = R4 VSUPPLY(MAX) If R6 is 20Ω, R4 is 5.6k. The peak circuit breaker power limit is: POWERMAX (VSUPPLY(MIN) + VSUPPLY(MAX) )2 = 4 • VSUPPLY(MIN) • VSUPPLY(MAX) • POWERSUPPLY(MIN) = 1.029 • POWERSUPPLY(MIN) VLOGIC RPULLUP EN GND RX 10Ω CX 100nF GND (SHORT PIN) Z1 RIN 470Ω CIN 0.1µF 1 R1 124k 1% R2 3.65k 1% R3 32.4k 1% C1 1nF –12V Z1: SMAJ15A CT 47nF VIN LTC4214-1 9 8 10 3 UV OV TIMER SS VEE CSS 22nF 5 PWRGD DRAIN GATE SENSE 2 7 6 4 R6 20Ω RC 10Ω CC 10nF D1 BZX84C10 R5 10k VOUT R4 5.6k D2 1N4148 Q2 2N2222 GND Figure 18. Power Limit Circuit Breaking Application 30 U when VSUPPLY = 0.5 • (VSUPPLY(MIN) + VSUPPLY(MAX)) = 12V. The peak power at the fault current limit occurs at the supply overvoltage threshold. The fault current limited power is: POWERFAULT = VSUPPLY  R6  •  VACL – (VSUPPLY – VZ ) •   RS R4  (18) (16) (17) + CL 100µF RD 475k Q1 IRF7413 RS 0.025Ω 4214 F18 W U U 421412f LTC4214-1/LTC4214-2 PACKAGE DESCRIPTIO U MS Package 10-Lead Plastic MSOP (Reference LTC DWG # 05-08-1661) 0.889 ± 0.127 (.035 ± .005) 3.20 – 3.45 (.126 – .136) 3.00 ± 0.102 (.118 ± .004) (NOTE 3) 10 9 8 7 6 0.497 ± 0.076 (.0196 ± .003) REF DETAIL “A” 0° – 6° TYP 12345 0.53 ± 0.152 (.021 ± .006) DETAIL “A” 0.18 (.007) SEATING PLANE 0.17 – 0.27 (.007 – .011) TYP 0.127 ± 0.076 (.005 ± .003) MSOP (MS) 0603 5.23 (.206) MIN 0.50 0.305 ± 0.038 (.0197) (.0120 ± .0015) BSC TYP RECOMMENDED SOLDER PAD LAYOUT 0.254 (.010) GAUGE PLANE 4.90 ± 0.152 (.193 ± .006) 3.00 ± 0.102 (.118 ± .004) (NOTE 4) 1.10 (.043) MAX 0.86 (.034) REF NOTE: 1. DIMENSIONS IN MILLIMETER/(INCH) 2. DRAWING NOT TO SCALE 3. DIMENSION DOES NOT INCLUDE MOLD FLASH, PROTRUSIONS OR GATE BURRS. MOLD FLASH, PROTRUSIONS OR GATE BURRS SHALL NOT EXCEED 0.152mm (.006") PER SIDE 4. DIMENSION DOES NOT INCLUDE INTERLEAD FLASH OR PROTRUSIONS. INTERLEAD FLASH OR PROTRUSIONS SHALL NOT EXCEED 0.152mm (.006") PER SIDE 5. LEAD COPLANARITY (BOTTOM OF LEADS AFTER FORMING) SHALL BE 0.102mm (.004") MAX 0.50 (.0197) BSC 421412f Information furnished by Linear Technology Corporation is believed to be accurate and reliable. However, no responsibility is assumed for its use. Linear Technology Corporation makes no representation that the interconnection of its circuits as described herein will not infringe on existing patent rights. 31 LTC4214-1/LTC4214-2 TYPICAL APPLICATIO GND RX 10Ω CX 100nF GND (SHORT PIN) R1 121k 1% Z1 RIN 470Ω CIN 0.1µF * 2 7 CONTROLLER VEE RD 475k Q1 IRF7413 RC 10Ω CC 10nF RS 0.025Ω VOUT R3 5.1k 1 VIN LTC4214-1 8 9 R2 32.4k 1% C1 1nF –12V *M0C207 Z1:SMAJ15A OV UV PWRGD DRAIN 10 6 TIMER GATE 3 4 CT SS SENSE 47nF VEE CSS 22nF 5 Figure 19. – 12V/2A Hot Swap Controller RELATED PARTS PART NUMBER LTC1421 LTC1642 LTC1644 LTC4210 LTC4211 LT4220 LTC4230 DESCRIPTION Two Channels, Hot Swap Controller Fault Protected Hot Swap Controller PCI Hot Swap Controller Hot Swap Controller in SOT-23 Single Hot Swap with Multifunction Current Control Dual Hot Swap Controller for Positive/Negative Supplies Triple Hot Swap Controller with Multifunction Current Control COMMENTS Operates from 3V to 12V and Supports –12V 3V to 16.5V, Overvoltage Protection up to 33V 3.3V, 5V and ±12V; 1V Precharge; PCI Reset Logic Active Current Limiting, 2.7V to 16.5V Operates from 2.5V to 16.5V Operates from ±2.7V to ±16.5V Operates from 1.7V to 16.5V 32 Linear Technology Corporation 1630 McCarthy Blvd., Milpitas, CA 95035-7417 (408) 432-1900 q FAX: (408) 434-0507 q U GND + CL 100µF EN Start-Up Behavior GATE 5V/DIV SENSE 50mV/DIV VOUT 10V/DIV 4214 F19 PWRGD 10V/DIV 4214 TA03 421412f LT/TP 0204 1K PRINTED IN USA www.linear.com © LINEAR TECHNOLOGY CORPORATION 2002