LTC6256CTS8-TRPBF

FeAtures n n n n n n n n n n n n n LTC6255/LTC6256/LTC6257 6.5MHz, 65µA Power Efficient Rail-to-Rail I/O Op Amps Description The LTC®6255/LTC6256/LTC6257 are single/dual/quad operational amplifiers with low noise, low power, low supply voltage, rail-to-rail input/output. They are unity gain stable with capacitive load up to 100nF . They feature 6.5MHz gain-bandwidth product, 1.8V/µs slew rate while consuming only 65µA of supply current per amplifier operating on supply voltages ranging from 1.8V to 5.25V. The combination of low supply current, low supply voltage, high gain bandwidth product and low noise makes the LTC6255 family unique among rail-to-rail input/output op amps with similar supply currents. These operational amplifiers are ideal for low power and low noise applications. For applications that require power-down, LTC6255 and LTC6256 in S6 and MS10 packages offer shutdown pins which reduces the current consumption to 7µA maximum. The LTC6255 family can be used as plug-in replacements for many commercially available op amps to reduce power or to improve input/output range and performance. L, LT, LTC, LTM, Linear Technology and the Linear logo are registered trademarks and Over-The-Top is a trademark of Linear Technology Corporation. All other trademarks are the property of their respective owners. Gain Bandwidth Product: 6.5MHz –3dB Bandwidth (AV = +1): 4.5MHz Low Quiescent Current: 65µA Stable for Capacitive Load Up to 100nF Offset Voltage: 350µV Maximum Rail-to-Rail Input and Output Supply Voltage Range: 1.8V to 5.25V Input Bias Current: 35nA Maximum CMRR/PSRR: 100dB/100dB Shutdown Current: 7µA Maximum Operating Temperature Range: –40°C to 125°C Single in 6-Lead TSOT-23 Package Dual in 8-Lead MS8, MS10, TS0T-23, 2mm × 2mm Thin DFN Packages n Quad in MS16 Package ApplicAtions n n n n Micropower Active Filters Portable Instrumentation Battery or Solar Powered Systems Automotive Electronics typicAl ApplicAtion Low Power, Low Distortion ADC Driver 0 3.3V 3.3V –10 –20 324 1% 470pF NPO 6.34k, 1% CS SDO SCK OVDD MAGNITUDE (dB) VDD AIN VREF –30 –40 –50 –60 –70 –80 10k 1% 625567 TA01a LTC6255 Driving LTC2361 ADC VIN = –1dBFS, 5kHz fS = 125kSps SNR = 72.5dB SFDR = 89dB tACQ = 5µs tCONV = 3µs – 22pF + LTC6255 VIN 5mV TO 2V LTC2361 GND –90 –100 –110 ISUPPLY = 540µA TOTAL AT 125kSps 0 10 20 30 40 FREQUENCY (kHz) 50 60 625567 TA01b 625567f  LTC6255/LTC6256/LTC6257 Absolute MAxiMuM rAtings (Note 1) Supply Voltage: V+ – V– ...........................................5.5V Input Voltage .................................. V– – 0.2 to V+ + 0.2 . Input Current: +IN, –IN, SHDN (Note 2) ............... ±10mA Output Current: OUT ........................................... ±20mA Output Short-Circuit Duration (Note 3) ............ Indefinite Operating Temperature Range (Note 4) ................................................. –40°C to 125°C . Specified Temperature Range (Note 5) ................................................. –40°C to 125°C . Storage Temperature Range .................. –65°C to 150°C Junction Temperature ........................................... 150°C Lead Temperature (Soldering, 10 sec) S6, TS8, MS8, MS only ........................................ 300°C . pin conFigurAtion TOP VIEW OUTA –INA +INA V – 1 3 4 + – 8 9 V– 7 6 5 + – V+ OUTB –INB +INB OUT 1 +IN 3 V– 2 TOP VIEW 6 V+ + – 2 5 SHDN 4 –IN KC PACKAGE 8-LEAD (2mm 2mm) PLASTIC UTDFN TJMAX = 125°C, θJA = 89°C/W (NOTE 6) EXPOSED PAD (PIN 9) IS V–, MUST BE SOLDERED TO PCB TOP VIEW OUTA –INA +INA V– 1 2 3 4 8 7 6 5 V+ OUTB –INB +INB S6 PACKAGE 6-LEAD PLASTIC TSOT-23 TJMAX = 150°C, θJA = 192°C/W (NOTE 6) TOP VIEW + – + – TS8 PACKAGE 8-LEAD PLASTIC TSOT-23 TJMAX = 150°C, θJA = 195°C/W (NOTE 6) MS8 PACKAGE 8-LEAD PLASTIC MSOP TJMAX = 150°C, θJA = 163°C/W (NOTE 6) TOP VIEW TOP VIEW + – MS PACKAGE 10-LEAD PLASTIC MSOP TJMAX = 150°C, θJA = 160°C/W (NOTE 6)  + – OUTA –INA +INA V– SHDNA 1 2 3 4 5 10 9 8 7 6 + – MS PACKAGE 16-LEAD PLASTIC MSOP TJMAX = 150°C, θJA = 125°C/W (NOTE 6) + – V+ OUTB –INB +INB SHDNB OUTA –INA +INA V+ +INB –INB OUTB NC 1 2 3 4 5 6 7 8 + – OUTA –INA +INA V– 1 2 3 4 8 7 6 5 V+ OUTB –INB +INB + – + – + – 16 15 14 13 12 11 10 9 OUTD –IND +IND V– +INC –INC OUTC NC 625567f LTC6255/LTC6256/LTC6257 orDer inForMAtion LEAD FREE FINISH LTC6255IS6#TRMPBF TAPE AND REEL LTC6255IS6#TRPBF PART MARKING* PACKAGE DESCRIPTION LTFFT LTFFT LTFFT LTFFW LTFFW LTFFW DXYT DXYT LTDXW LTDXX LTDXX 6257 6257 6257 6-Lead Plastic TSOT-23 6-Lead Plastic TSOT-23 6-Lead Plastic TSOT-23 8-Lead Plastic TSOT-23 8-Lead Plastic TSOT-23 8-Lead Plastic TSOT-23 SPECIFIED TEMPERATURE RANGE (Notes 4,5) 0°C to 70°C –40°C to 85°C –40°C to 125°C 0°C to 70°C –40°C to 85°C –40°C to 125°C LTC6255CS6#TRMPBF LTC6255CS6#TRPBF LTC6255HS6#TRMPBF LTC6255HS6#TRPBF LTC6256CTS8#TRMPBF LTC6256CTS8#TRPBF LTC6256ITS8#TRMPBF LTC6256ITS8#TRPBF LTC6256HTS8#TRMPBF LTC6256HTS8#TRPBF LTC6256CKC#TRMPBF LTC6256CKC#TRPBF LTC6256IKC#TRMPBF LTC6256CMS8#PBF LTC6256IMS8#PBF LTC6256CMS#PBF LTC6256IMS#PBF LTC6257CMS#PBF LTC6257IMS#PBF LTC6257HMS#PBF LTC6256IKC#TRPBF LTC6256IMS8#TRPBF LTC6256CMS#TRPBF LTC6256IMS#TRPBF LTC6257CMS#TRPBF LTC6257IMS#TRPBF LTC6257HMS#TRPBF 8-Lead (2mm × 2mm) Plastic UTDFN 0°C to 70°C 8-Lead (2mm × 2mm) Plastic UTDFN –40°C to 85°C 8-Lead Plastic MSOP 8-Lead Plastic MSOP 10-Lead Plastic MSOP 10-Lead Plastic MSOP 16-Lead Plastic MSOP 16-Lead Plastic MSOP 16-Lead Plastic MSOP 0°C to 70°C –40°C to 85°C 0°C to 70°C –40°C to 85°C 0°C to 70°C –40°C to 85°C –40°C to 125°C LTC6256CMS8#TRPBF LTDXW Consult LTC Marketing for parts specified with wider operating temperature ranges. *The temperature grade is identified by a label on the shipping container. Consult LTC Marketing for information on non-standard lead based finish parts. For more information on lead free part marking, go to: http://www.linear.com/leadfree/ For more information on tape and reel specifications, go to: http://www.linear.com/tapeandreel/ 5V electricAl chArActeristics SYMBOL PARAMETER VOS Input Offset Voltage The l denotes the specifications which apply over the full operating temperature range, otherwise specifications are at TA = 25°C. VSUPPLY = 5V, VCM = VOUT = VSUPPLY/2, CL = 10pF SHDN is unconnected. , V CONDITIONS VCM = V– + 2.5V (PNP Region) l MIN –350 –700 –350 –700 –35 –60 –35 –60 –15 –30 –15 –30 TYP 100 100 1.5 –5 5 2 2 20 2.5 380 850 1 10 0.4 0.3 MAX 350 700 350 700 35 60 35 60 15 30 15 30 UNITS µV µV µV µV µV/°C nA nA nA nA nA nA nA nA nV/√Hz µVP-P fA/√Hz fA/√Hz MΩ MΩ pF pF 625567f VCM = V+ – 0.3V (NPN Region) l VOS TC IB Input Offset Voltage Drift Input Bias Current (Note 7) VCM = V– + 2.5V, V+ – 0.3V VCM = V– + 2.5V l l VCM = V+ – 0.3V l IOS Input Offset Current VCM = V– + 2.5V l VCM = V+ – 0.3V l en in RIN CIN Input Voltage Noise Density Input Noise Voltage Input Current Noise Density Input Resistance Input Capacitance f = 1kHz f = 0.1Hz to 10Hz f = 1kHz, VCM = 0V to 4V (PNP Input) f = 1kHz, VCM = 4V to 5V (NPN Input) Differential Common Mode Differential Common Mode  LTC6255/LTC6256/LTC6257 5V electricAl chArActeristics SYMBOL PARAMETER CMRR IVR PSRR AV Common Mode Rejection Ratio Input Voltage Range Power Supply Rejection Ratio Large Signal Gain VCM = 0.4V, VS Ranges From 1.8V to 5V l The l denotes the specifications which apply over the full operating temperature range, otherwise specifications are at TA = 25°C. VSUPPLY = 5V, VCM = VOUT = VSUPPLY/2, CL = 10pF SHDN is unconnected. , V CONDITIONS VCM = 0.3V to 3.5V l l MIN 80 76 –0.1 85 81 50 28 25 8 TYP 100 MAX UNITS dB dB 5.1 100 200 50 6 25 35 30 40 75 95 55 60 80 90 150 170 V dB dB V/mV V/mV V/mV V/mV mV mV mV mV mV mV mV mV mV mV mV mV mA mA VO = 0.5V to 4.5V, RLOAD = 100k l VO = 0.5V to 4.5V, RLOAD = 10k l VOL Output Swing Low (Input Overdrive 30mV). Measured from V– No Load l ISINK = 100µA l 10 30 l ISINK = 1mA VOH Output Swing High (Input Overdrive 30mV). Measured from V+ No Load l 24 30 l ISOURCE = 100µA ISOURCE = 1mA l 75 17 8 57 42 35 65 6 l ISC IS Output Short-Circuit Current l Supply Current per Amplifier l 73 88 7 12 µA µA µA µA nA nA Supply Current in Shutdown ISHDN VIL VIH tON tOFF BW GBW tS SR FPBW THD+N ILEAK Shutdown Pin Current SHDN Input Low Voltage SHDN Input High Voltage Turn-On Time Turn-Off Time –3dB Closed Loop Bandwidth Gain-Bandwidth Product Settling Time, 0.5V to 4.5V, Unity Gain Slew Rate Full Power Bandwidth (Note 8) Total Harmonic Distortion and Noise Output Leakage Current in Shutdown AV = 1 f = 200kHz l VSHDN = 0.6V VSHDN = 1.5V Disable Enable l –1400 –1000 l –900 –500 l l 0.6 1.5 5 3 4.5 2.5 2 6.5 4 6 V V µs µs MHz MHz MHz µs µs V/µs V/µs kHz % dB 0.1% 0.01% AV = –1, VOUT = 0.5V to 4.5V, CLOAD = 10pF , RF = RG = 10kΩ 4VP-P f = 500Hz, AV = 2, RL = 4kΩ, VOUTP-P = 1V VIN = 2.25V to 2.75V VSHDN = 0V, VOUT = 0V VSHDN = 0V, VOUT = 5V l l l 1.0 0.75 1.8 140 0.0022 93 –400 –400 400 400 nA nA 625567f  LTC6255/LTC6256/LTC6257 The l denotes the specifications which apply over the full operating temperature range, otherwise specifications are at TA = 25°C. VSUPPLY = 1.8V, VCM = VOUT = 0.4V, CL = 10pF SHDN is , V unconnected. SYMBOL PARAMETER VOS Input Offset Voltage CONDITIONS VCM = V– + 0.3V l 1.8V electricAl chArActeristics MIN –350 –700 –350 –700 –35 –60 –35 –60 –15 –30 –15 –30 TYP 100 100 1.5 –8 5 2 2 21 2.5 580 870 1 10 0.4 0.3 MAX 350 700 350 700 35 60 35 60 15 30 15 30 UNITS µV µV µV µV µV/°C nA nA nA nA nA nA nA nA nV/√Hz µVP-P fA/√Hz fA/√Hz MΩ MΩ pF pF dB dB VCM = V+ – 0.3V l VOS TC IB Input Offset Voltage Drift Input Bias Current (Note 7) VCM = V– + 0.3V, V+ – 0.3V VCM = V– + 0.3V l l VCM = V+ – 0.3V l IOS Input Offset Current VCM = V– + 0.3V l VCM = V+ – 0.3V l en in RIN CIN CMRR IVR PSRR AV Input Voltage Noise Density Input Noise Voltage Input Current Noise Density Input Resistance Input Capacitance Common Mode Rejection Ratio Input Voltage Range Power Supply Rejection Ratio Large Signal Gain f = 1kHz, VCM = 0.4V f = 0.1Hz to 10Hz f = 1kHz, VCM = 0V to 0.8V (PNP Input) f = 1kHz, VCM = 1V to 1.8V (NPN Input) Differential Common Mode Differential Common Mode VCM = 0.2V to 1.6V l l 74 67 –0.1 85 81 30 17 15 5 90 1.9 100 110 50 6 35 40 40 45 75 90 V dB dB V/mV V/mV V/mV V/mV mV mV mV mV mV mV VCM = 0.4V, VS Ranges From 1.8V to 5V l VO = 0.5V to 1.3V, RLOAD = 100k l VO = 0.5V to 1.3V, RLOAD = 10k l VOL Output Swing Low (Input Overdrive 30mV), Measured from V– No Load l ISINK = 100µA l 10 30 l ISINK = 1mA 625567f  LTC6255/LTC6256/LTC6257 The l denotes the specifications which apply over the full operating temperature range, otherwise specifications are at TA = 25°C. VSUPPLY = 1.8V, VCM = VOUT = 0.4V, CL = 10pF SHDN is , V unconnected. SYMBOL PARAMETER VOH Output Swing High (Input Overdrive 30mV), Measured from V+ CONDITIONS No Load l 1.8V electricAl chArActeristics MIN TYP 24 30 MAX 55 60 65 75 135 150 UNITS mV mV mV mV mV mV mA mA ISOURCE = 100µA l ISOURCE = 1mA l 75 12.5 3.5 53 35 17 60 1.4 l ISC IS Output Short-Circuit Current l Supply Current per Amplifier l 68 83 2.0 3.0 µA µA µA µA nA nA Supply Current in Shutdown ISHDN VIL VIH tON tOFF BW GBW TS SR FPBW THD+N Shutdown Pin Current SHDN Input Low Voltage SHDN Input High Voltage Turn-On Time Turn-Off Time –3dB Closed Loop Bandwidth Gain-Bandwidth Product Settling Time, 0.3V to 1.5V, Unity Gain Slew Rate Full Power Bandwidth (Note 8) Total Harmonic Distortion and Noise AV = 1 f = 200kHz l VSHDN = 0.5V VSHDN = 1.3V Disable Enable l l l l –480 –350 –160 –40 0.5 1.3 5 3 4 2.4 1.8 6 4 6 V V µs µs MHz MHz MHz µs µs V/µs V/µs kHz % dB 0.1% 0.01% AV = –1, VOUT = 0.3V to 1.5V, CLOAD = 10pF l 0.9 0.75 1.5 400 0.006 84 1.2VP-P f = 500Hz, AV = 2, RL = 4kΩ, VOUTP-P = 1V VIN = 0.25V to 0.75V Note 1: Stresses beyond those listed under Absolute Maximum Ratings may cause permanent damage to the device. Exposure to any Absolute Maximum Rating condition for extended periods may affect device reliability and lifetime. Note 2: The inputs are protected by back-to-back diodes as well as ESD protection diodes to each power supply. If the differential input voltage exceeds 3.6V or the input extends more than 500mV beyond the power supply, the input current should be limited to less than 10mA. Note 3: A heat sink may be required to keep the junction temperature below the absolute maximum rating when the output is shorted indefinitely. Note 4: The LTC6255C/LTC6256C/LTC6257C and LTC6255I/LTC6256I/ LTC6257I are guaranteed functional over the temperature range of –40°C to 85°C. The LTC6255H/LTC6256H/LTC6257H are guaranteed functional over the temperature range of –40°C to 125°C. Note 5: The LTC6255C/LTC6256C/LTC6257C are guaranteed to meet the specified performance from 0°C to 70°C. The LTC6255C/LTC6256C/ LTC6257C are designed, characterized and expected to meet specified performance from –40°C to 85°C but are not tested or QA sampled at these temperatures. The LTC6255I/LTC6256I/LTC6257I are guaranteed to meet specified performance from –40°C to 85°C. The LTC6255H/ LTC6256H/LTC6257H are guaranteed to meet specified performance from –40°C to 125°C. Note 6: Thermal resistance varies with the amount of PC board metal connected to the package. The specified values are for short traces connected to the leads. Note 7: The input bias current is the average of the currents through the positive and negative input pins. Note 8: Full power bandwidth is calculated from the slew rate FPBW = SR/π • VP-P. 625567f  LTC6255/LTC6256/LTC6257 typicAl perForMAnce chArActeristics 250 Input VOS Histogram VS = ±2.5V VCM = 0V 140 120 NUMBER OF UNITS 100 Input VOS Histogram VS = ±2.5V VCM = 2.2V 200 NUMBER OF UNITS 100 60 40 20 50 0 –1000 –500 0 VOS (µV) 500 1000 625567 G01 0 –1000 –600 –200 200 VOS (µV) 600 1000 625567 G02 VOS (µV) 150 80 300 VS = ±2.5V 250 VCM = 0V 200 150 100 50 0 –50 –100 –150 –200 –250 –300 –350 –400 –40 –25 –10 5 20 35 50 65 80 95 110 125 TEMPERATURE (°C) 625567 G03 VOS vs Temperature 20 18 16 14 VOS (µV) 12 10 8 6 4 2 VOS TC (–40°C to 125°C) H-GRADE INDUSTRIAL COMMERCIAL VS = ±2.5V VCM = 0V VOS (µV) 500 400 300 200 VOS vs Supply Voltage (25°C) VCM = 0.4V VOS vs Common Mode Voltage 500 400 300 200 VOS (µV) 100 0 –100 –200 –300 –400 VS = 5V, 0V 100 0 –100 –200 –300 –400 0 –3.5 –2.5 –1.5 –0.5 0 0.5 DISTRIBUTION (µV/°C) 1.5 625567 G04 –500 1.8 2.3 2.8 3.3 3.8 4.3 SUPPLY VOLTAGE (V) 4.8 625567 G05 –500 0 1 2 VCM (V) 3 4 5 625567 G06 25 VOS vs IOUT Input Bias Current vs Common Mode Voltage 100 80 INPUT BIAS CURRENT (nA) 60 40 20 0 –20 –40 –60 –80 +IN –IN VS = 5V, 0V INPUT BIAS CURRENT (nA) 100 80 60 40 20 0 –20 –40 –60 –80 0 1 2 VCM (V) 3 4 5 625567 G08 Input Bias Current vs Common Mode Voltage VS = 1.8V, 0V VS = ±2.5V 20 VCM = 0V 15 10 VOS (mV) 5 0 –5 –10 –15 –20 –25 –5 –4 –3 –2 –1 0 1 IOUT (mA) 2 3 4 5 –55°C, 25°C 125°C +IN –IN –100 –100 0 625567 G07 0.2 0.4 0.6 0.8 1.0 1.2 1.4 1.6 1.8 VCM (V) 625567 G09 625567f  LTC6255/LTC6256/LTC6257 typicAl perForMAnce chArActeristics Input Bias Current vs Supply Voltage 25 20 INPUT BIAS CURRENT (nA) 15 10 5 0 –5 –10 –15 –20 –25 1.8 2.8 3.8 SUPPLY VOLTAGE (V) 4.8 625567 G10 Input Bias Current vs Temperature 50 40 INPUT BIAS CURRENT (nA) 30 20 10 0 –10 –20 –30 –40 –50 –40 10 60 TEMPERATURE (°C) 110 625567 G11 Supply Current vs Supply Voltage per Channel, –40°C, 25°C, 125°C 100 VCM = 0.4V 125°C 25°C –40°C 40 VCM = 0.4V VS = ±2.5V VCM = 2V SUPPLY CURRENT (µA) 80 60 +IN –IN VCM = –2V 20 0 0 1 2 3 SUPPLY VOLTAGE (V) 4 5 625567 G32 Supply Current vs Temperature 100 SATURATION VOLTAGE FROM TOP RAIL (V) VCM = 0.4V VS = 5V, 0V 0 –0.05 –0.10 –0.15 –0.20 –0.25 –0.30 –0.35 Output Saturation Voltage vs Load Current (Output High) SATURATION VOLTAGE FROM BOTTOM RAIL (V) 125°C, VS = 1.8V 85°C, VS = 1.8V 25°C, VS = 1.8V –40°C, VS = 1.8V 0.5 Output Saturation Voltage vs Load Current (Output Low) 125°C, VS = 1.8V 125°C, VS = 5V 85°C, VS = 1.8V 85°C, VS = 5V 25°C, VS = 1.8V 25°C, VS = 5V –40°C, VS = 1.8V –40°C, VS = 5V 80 SUPPLY CURRENT (µA) 0.4 60 VS = 1.8V, 0V 0.3 40 0.2 20 0 –40 125°C, VS = 5V 85°C, VS = 5V 25°C, VS = 5V –40°C, VS = 5V 0 1 2 3 LOAD CURRENT (mA) 4 5 625567 G14 0.1 –15 10 35 60 85 TEMPERATURE (°C) 110 625567 G13 0 0 1 2 3 LOAD CURRENT (mA) 4 5 625567 G15 Output Short-Circuit Current vs Supply Voltage (Sourcing) 100 MAXIMUM SOURCING CURRENT (mA) 90 80 70 60 50 40 30 20 10 0 1.8 2.3 2.8 3.3 3.8 4.3 SUPPLY VOLTAGE (V) 4.8 625567 G16 Output Short-Circuit Current vs Supply Voltage (Sinking) 100 MAXIMUM SINKING CURRENT (mA) 90 80 –40°C NOISE VOLTAGE (µV) 70 60 50 40 30 20 10 0 1.8 2.3 125°C 2.8 3.3 3.8 4.3 SUPPLY VOLTAGE (V) 4.8 625567 G17 0.1Hz to 10Hz Output Voltage Noise 5 VS = ±2.5V 4 VCM = 0V AV = 1 3 2 1 0 –1 –2 –3 –4 –5 0 2 4 6 TIME (s) 8 10 625567 G18 VCM = 0.4V VCM = 0.4V 125°C –40°C 25°C 25°C 625567f  LTC6255/LTC6256/LTC6257 typicAl perForMAnce chArActeristics INPUT REFERRED NOISE VOLTAGE DENSITY (nV/√Hz) 300 250 200 150 100 50 0 INPUT REFERRED NOISE VOLTAGE DENSITY (nV/√Hz) Noise Voltage Density vs Frequency VS = ±2.5V VCM = 0V Wide Band Noise Voltage Density vs Frequency INPUT REFERRED NOISE CURRENT (pA/√Hz) 80 VS = ±2.5V 70 VCM = 0V 60 50 40 30 20 10 0 0 2M 4M FREQUENCY (Hz) 6M 625567 G20 Input Noise Current vs Frequency 25 VS = ±2.5V VCM = 0V 20 15 10 5 1 10 100 1k FREQUENCY (Hz) 10k 100k 625567 G19 0 1 10 100 1k FREQUENCY (Hz) 10k 625567 G21 Total Harmonic Distortion and Noise 1 VS = ±0.9V VCM = 0V AV = 2 RG = RF = 10k THD+N (%) 1 Total Harmonic Distortion and Noise VS = ±2.5V VCM = 0V AV = 2 RF = RG = 10k AMPLITUDE (dB) 80 70 60 50 40 30 20 10 0 –10 Gain and Phase vs Frequency VS = ±2.5V VCM = 0V –60 –70 –80 PHASE –90 –100 –110 MAGNITUDE –120 –130 –140 –150 100k 1M FREQUENCY (Hz) –160 10M 625567 G24 0.1 THD+N (%) 0.1 PHASE 0.01 1kHz 500Hz 0.01 1kHz 0.001 0.01 500Hz 0.1 VOUTP-P (V) 1 625567 G23 0.001 0.01 0.1 VOUTP-P (V) 1 10 625567 G22 –20 10k 625567f  LTC6255/LTC6256/LTC6257 typicAl perForMAnce chArActeristics Slew Rate vs Supply Voltage 2.5 150 Common Mode Rejection Ratio vs Frequency VS = ±2.5V VCM = 0V 150 Power Supply Rejection Ratio vs Frequency V+, VS = 1.8V, 0V V+, VS = 5V, 0V V–, VS = 1.8V, 0V V–, VS = 5V, 0V 2.0 SLEW RATE (V/µs) RISING CMMR (dB) 1.5 FALLING 100 PSSR (dB) 50 V – = 0V 0.5 S VSTEP = VS+ – 1V AV = 1 RF = RG = 10k 0 1.5 2.5 3.5 4.5 VS+, SUPPLY VOLTAGE (V) 50 0 1k 10k 100k 1M FREQUENCY (Hz) 10M 625567 G26 100 1.0 5.5 625567 G25 0 0.001 0.01 0.1 1 10 100 FREQUENCY (Hz) 1k 10k 625567 G27 Capacitive Load Handling Overshoot vs Capacitive Load 16 VS = ±2.5V 14 VCM = 0V AV = 1 V = ±2V 12 IN OVERSHOOT (%) VOLTAGE (V) 10 8 6 4 2 0 0.01 0.1 1 CLOAD (nF) 10 100 625567 G28 Large-Signal Response 2.5 2.0 1.5 1.0 0.5 0 –0.5 –10 –1.5 –2.0 –2.5 0 20 CLOAD = 10pF CLOAD = 100pF CLOAD = 1nF CLOAD = 10nF 40 60 TIME (ms) 80 100 625567 G29 Large-Signal Response 0.9 0.6 0.3 0 –0.3 –0.6 –0.9 CLOAD = 10pF CLOAD = 100pF CLOAD = 1nF CLOAD = 10nF 0 20 60 40 TIME (µs) 80 100 625567 G30 VS = ±2.5V AV = 1 RLOAD = 10k VOLTAGE (V) VS = ±0.9V AV = 1 RLOAD = 10k 625567f 0 LTC6255/LTC6256/LTC6257 typicAl perForMAnce chArActeristics Small-Signal Response 0.05 0.04 0.03 0.02 VOLTAGE (V) 0.01 0 –0.01 –0.02 –0.03 –0.04 –0.05 0 20 CLOAD = 10pF CLOAD = 100pF CLOAD = 1nF CLOAD = 10nF 40 60 TIME (µs) 80 100 625567 G31 Large-Signal Response 2.5 2.0 1.5 1.0 VOLTAGE (V) 0.5 0 –0.5 –1.0 –1.5 –2.0 –2.5 0 20 40 60 TIME (µs) 80 100 625567 G33 Small-Signal Response 0.05 0.04 VS = ±2.5V AV = 1 CLOAD = 100nF VS = ±0.9V AV = 1 RLOAD = 10k VOLTAGE (V) VS = ±2.5V AV = 1 CLOAD = 100nF 0.03 0.02 0.01 0 –0.01 –0.02 –0.03 –0.04 –0.05 0 200 400 600 TIME (µs) 800 1000 625567 G34 Output Impedance vs Frequency 1000 VS = ±2.5V VCM = 0V SUPPLY CURRENT (µA) 80 Supply Current vs SHDN Pin Voltage VS = 1.8V, 0V 70 VCM = 0.4V 60 50 40 30 20 10 90 125°C –40°C 25°C SUPPLY CURRENT (µA) Supply Current vs SHDN Pin Voltage VS = 5V, 0V 80 VCM = 0.4V 70 60 50 40 30 20 10 –40°C 25°C 125°C OUTPUT IMPEDANCE ( ) 100 AV = 10 10 1 AV = 1 0.1 0.01 0.01 0.1 1 10 100 FREQUENCY (Hz) 1k 10k 0 0 625567 G12 0.2 0.4 0.6 0.8 1.0 1.2 1.4 1.6 1.8 2.0 VSHDN (V) 625567 G35 0 0 0.2 0.4 0.6 0.8 1.0 VSHDN (V) 1.2 1.4 1.6 625567 G36 625567f  LTC6255/LTC6256/LTC6257 pin Functions –IN: Inverting Input of the Amplifier. Voltage range of this pin can go from V– – 0.1V to V+ + 0.1V. +IN: Non-Inverting Input of Amplifier. This pin has the same voltage range as –IN. V+: Positive Power Supply. Typically the voltage is from 1.8V to 5.25V. Split supplies are possible as long as the voltage between V+ and V– is between 1.8V and 5.25V. A bypass capacitor of 0.1µF as close to the part as possible should be used between power supply pins or between supply pins and ground. V–: Negative Power Supply. It is normally tied to ground. It can also be tied to a voltage other than ground as long as the voltage between V+ and V– is from 1.8V to 5.25V. If it is not connected to ground, bypass it with a capacitor of 0.1µF as close to the part as possible. SHDN: Active Low Shutdown. Shutdown threshold is 0.6V above negative rail. If left unconnected, the amplifier will be on. OUT: Amplifier Output. The voltage range extends to within millivolts of each supply rail. siMpliFieD scheMAtic V+ R6 5M R3 R4 R5 + V+ I2 +IN ESDD1 V– ESDD2 D6 D5 ESDD4 ESDD3 V+ D8 D7 Q4 Q3 Q5 Q15 + C2 I1 Q11 Q12 Q13 ESDD5 SHDN LOGIC –IN VBIAS Q1 Q2 Q10 Q9 Q8 CC + V– I3 OUT V – BUFFER AND OUTPUT BIAS ESDD6 Q16 Q17 Q18 Q19 Q7 Q6 R1 R2 C1 Q14 V– 625567 F01 Figure 1. LTC6255/LTC6256/LTC6257 Simplified Schematic 625567f  LTC6255/LTC6256/LTC6257 operAtion The LTC6255 family input signal range extends beyond the negative and positive power supplies. The output can even extend all the way to the negative supply with the proper external pull-down current source. Figure 1 depicts a Simplified Schematic of the amplifier. The input stage is comprised of two differential amplifiers, a PNP stage Q1/Q2 and NPN stage Q3/Q4 that are active over different ranges of common mode input voltage. The PNP stage is active between the negative power supply to approximately 1V below the positive supply. As the input voltage approaches the positive supply, transistor Q5 will steer the tail current I1 to the current mirror Q6/Q7, activating the NPN differential pair and the PNP pair becomes inactive for the remaining input common mode range. Also for the input stage, devices Q17, Q18 and Q19 act to cancel the bias current of the PNP input pair. When Q1/Q2 is active, the current in Q16 is controlled to be the same as the current Q1/Q2. Thus, the base current of Q16 is normally equal to the base current of the input devices of Q1/Q2. Similar circuitry (not shown) is used to cancel the base current of Q3/Q4. The buffer and output bias stage uses a special compensation technique to take full advantage of the process technology to drive high capacitive loads. The common emitter topology of Q14/Q15 enables the output to swing from rail to rail. ApplicAtions inForMAtion Low Supply Voltage and Low Power Consumption The LTC6255 family of operational amplifiers can operate with power supply voltages from 1.8V to 5.25V. Each amplifier draws only 65µA. The low supply voltage capability and low supply current are ideal for portable applications. High Capacitive Load Driving Capability and Wide Bandwidth The LTC6255 family is optimized for wide bandwidth low power applications. They have an extremely high gain-bandwidth to power ratio and are unity gain stable. When the load capacitance increases, the increased capacitance at the output pushed the non-dominant pole to lower frequency in the open loop frequency response, worsening the phase and gain margin. They are designed to directly drive up to 100nF capacitive load in unity gain configuration (see Typical Performance Characteristics, Capacitive Load Handling). Higher gain configurations tend to have better capacitive drive capability than lower gain configurations due to lower closed loop bandwidth and hence higher phase margin. Low Input Referred Noise The LTC6255 family provides a low input referred noise of 20nV/√Hz at 1kHz. The noise density will grow slowly with the frequency in wideband range. The average noise voltage density over 3MHz range is less than 24nV/√Hz. The LTC6255 family is ideal for low noise and low power signal processing applications. Low Input Offset Voltage The LTC6255 family has a low offset voltage of 350μV maximum which is essential for precision applications. The offset voltage is trimmed with a proprietary trim algorithm to ensure low offset voltage over the entire common mode voltage range. Low Input Bias Current The LTC6255 family uses a bias current cancellation circuit to compensate for the base current of the input transistors. When the input common mode voltage is within 200mV of either rail, the bias cancellation circuit are no longer active. For common mode voltages ranging from 0.2V above 625567f  LTC6255/LTC6256/LTC6257 ApplicAtions inForMAtion the negative supply to 0.2V below the positive supply, the low input bias current allows the amplifiers to be used in applications with high resistance sources. Ground Sensing and Rail to Rail Output The LTC6255 family has excellent output drive capability, delivering over 10mA of output drive current. The output stage is a rail-to-rail topology that is capable of swinging to within 30mV of either rail. If output swing to the negative rail is required, an external pull down resistor to a negative supply can be added. For 5V/0V op amp supplies, a pull down resistor of 2.1k to –2V will allow a ‘true zero’ output swing. In this case, the output can swing all the way to the bottom rail while maintaining 80dB of open loop gain. Since the inputs can go 100mV beyond either rail, the op amp can easily perform ‘true ground’ sensing. The maximum output current is a function of total supply voltage. As the supply voltage to the amplifier increases, the output current capability also increases. Attention must be paid to keep the junction temperature of the IC below 150°C when the output is in continuous short-circuit. The output of the amplifier has reverse-biased diodes connected to each supply. The output should not be forced more than 0.5V beyond either supply, otherwise current will flow through these diodes. Input Protection and Output Overdrive To prevent breakdown of the input transistors, the input stages are protected against a large differential input voltage by two pairs of back-to-back diodes, D5 to D8. If the differential input voltage exceeds 1.4V, the current in these diodes must be limited to less than 10mA. These amplifiers are not intended for open loop applications such as comparators. When the output stage is overdriven, internal limiting circuitry is activated to improve overdrive recovery. In some applications, this circuitry may draw as much as 1mA supply current. ESD The LTC6255 family has reverse-biased ESD protection diodes on all inputs and output as shown in Figure 1. Supply Voltage Ramping Fast ramping of the supply voltage can cause a current glitch in the internal ESD protection circuits. Depending on the supply inductance, this could result in a supply voltage transient that exceeds the maximum rating. A supply voltage ramp time of greater than 1ms is recommended. Feedback Components Care must be taken to ensure that the pole formed by the feedback resistors and the parasitic capacitance at the inverting input does not degrade stability. For example, in a gain of +2 configuration with gain and feedback resistors of 10k, a poorly designed circuit board layout with parasitic capacitance of 5pF (part +PC board) at the amplifier’s inverting input will cause the amplifier to oscillate due to a pole formed at 3.2MHz. An additional capacitor of 5pF across the feedback resistor as shown in Figure 2 will eliminate any ringing or oscillation. Shutdown The single and dual versions have SHDN pins that can shut down the amplifier to less than 7µA supply current. The SHDN pin voltage needs to be within 0.6V of V– for the amplifier to shut down. During shutdown, the output will be in high output resistance state, which is suitable for multiplexer applications. When left floating, the SHDN pin is internally pulled up to the positive supply and the amplifier remains enabled. 5pF 10k – 10k CPAR VIN LTC6255 + Figure 2. VOUT 625567 F02 625567f  LTC6255/LTC6256/LTC6257 typicAl ApplicAtions 200kHz 130µA Gain-of-100 Amplifier 0.9V VIN Frequency Response of 40dB Gain Amplifier 50 40 30 + 1/2 LTC6256 + 1/2 LTC6256 VOUT GAIN (dB) 20 10 0 –10 –20 – –0.9V – 90.9k 625567 F03a 10k 90.9k 10k –30 –40 –50 10 100 1k 10k 100k FREQUENCY (Hz) 1M 10M 625567 F03b Figure 3. Gain of 100 Amplifier (3dB Bandwidth of 200kHz on 130µA Supply Current) LTC6255 Very Low Power 2nd Order Lowpass Filter The LTC6256 circuit shown in Figure 4 is a 2nd order, 100kHz, Butterworth lowpass filter. The filter’s differential output maximizes the dynamic range in very low voltage operation. A general 2nd order lowpass circuit is shown in A, 1.8V, 140µA, 100kHz, Lowpass Filter (Single-Ended Input and Differential Output) 1.8V 2.49k VIN 2.49k 10k 1000pF 3 1.8V 100k 100k 10µF 100pF 8 1 6 0.1µF Figure 5 with the equations to calculate the RC components for cutoff frequencies up to 100kHz for a Butterworth or a Bessel approximation (a Bessel lowpass filter has very low transient response overshoot). In addition the equations for a 4th order lowpass filter are provided to calculate the RC components for two cascaded 2nd order sections. Frequency Response VOUT – 6 0 2.49k 2.49k GAIN (dB) + – 2 –6 –12 –18 –24 –30 –36 625567 F04a 1/2 LTC6256 – 1/2 LTC6256 7 5 + VOUT+ 4 –42 10k 100k FREQUENCY (Hz) 1M 625567 F04b Figure 4 625567f  LTC6255/LTC6256/LTC6257 typicAl ApplicAtions V+ 0.1µF R2 VIN R1 R3 C1 10µF C2 4 6 LTC6255 5 2 SHDN 1 VOUT Table 1. fO AND Q VALUES 2nd Order Lowpass Butterworth Bessel 4th Order Lowpass Butterworth Bessel fO = f–3dB fO = f–3dB fO = 1.419 • f–3dB fO = 1.591 • f–3dB Q = 0.541 Q = 1.307 Q = 0.522 Q = 0.806 fO = f–3dB fO = 1.274 • f–3dB Q = 0.707 Q = 0.577 100k 100k V+ Figure 5 RC Component Equations C2   1−  1− 4 Q 2 [Gain + 1]   C1 R2 = 4 π Q fO C2 R3 = 1 4 π 2 R2 C1 C2 fO2 R2 R1 Gain = R1= R2 Gain 2 C1 > 4 Q (Gain + 1) C2 Maximum f–3dB = 100kHz and Maximum Gain = 100kHz f–3dB  + 3 – 625567 F05 2µs Rise Time Analog 1A Pulsed LED Current Driver Figure 6 shows the LTC6255 applied as a fast, efficient analog LED current driver. High power LEDs are used in applications ranging from brake lights to video projectors. Most LED applications pulse the LEDs for the best efficiency, and many applications take advantage of control of both pulse width and analog current amplitude. In order to extend the circuit’s input range to accommodate 5V output DACs, the input voltage is initially divided by 50 through the R1:R2 divider. The reduced step is applied to the LTC6255 non inverting input, and LTC6255 output rises until MOSFETs Q1 through Q3 begin to turn on, increasing the current in their drains and therefore the LED. The amount of current is sensed on R3, and fed back to the LTC6255 inverting input through R5. The loop is compensated by R5 and C1, with R4 distancing the gate capacitance from the op amp output for the best time domain response. 10% to 90% rise time was measured at 2µs on a 10mA to 1A pulse. Starting at 0 current there is an additional delay of 2.7µs. It may seem strange to use a micropower op amp in a high current LED application, but it can be justified by the low duty cycles encountered in LED drive applications. A one 625567f LTC6255/LTC6256/LTC6257 typicAl ApplicAtions amp LED is quite bright even when driven at 1% or even 0.1% duty cycles and these constitute 10mA and 1mA average current levels respectively, in which case the supply current of the op amp becomes noticeable. The LTC6255 combines 6.5MHz of gain-bandwidth product and 1.8V/μs slew rate on a supply current budget of only 65µA. When VIN is at 0V, the op amp supply current is nominally 65µA, but the 450µV maximum input offset may appear across R3 inducing a 4.5mA current in the LED. Some applications want a guaranteed zero LED current at VIN = 0, and 2µs Rise Time Analog 1A Pulsed LED Current Driver R1 9.76k R2 200 5V SHDN ILED = VIN • 200mA/V ILED R4 51 Q1 Q2 Q3 Q1 TO Q3 MOSFETs 3 2N7000 5V LED OSRAM LRW5SM this is the purpose of RUP. RUP forces 5µA reverse current through R5 creating a negative 1.2mV output offset at R3. This guarantees a zero LED current, but note that the op amp supply current rises from 65µA to a still respectable 650µA in this case due to internal protection circuitry for the output stage. For reduced current, the LTC6255 can be shut down, but the output becomes high impedance and may leak high which will turn on the MOSFETs and LED hard. Adding pull-down resistor RSD ensures that the LTC6255 output goes low when shutting down. VIN VIN 10mA TO 1A 5V RUP 1M** *RSD GUARANTEES LED OFF WHEN OP AMP SHDN. OTHERWISE OPTIONAL. *RUP FORCES LED COMPLETELY OFF WHEN VIN = 0. OTHERWISE OPTIONAL. STANDBY SUPPLY CURRENT WITH VIN = 0: 65µA RUP OPEN 650µA RUP INSTALLED 10% TO 90% RISE TIME: 10mA TO 1A, 2µs 0mA TO 1A, ADD 2.7µs DELAY Figure 6: LTC6255 Applied as a LED Current Driver with 2µs Rise Time – + LTC6255 C1 220pF RSD 100k* R5 240 0mA TO 1A (EXTRA DELAY) 625567 F07 R3 0.1 100mW 625567 F06 Figure 7: Time Domain Response Showing 2µs Rise Time. Top Waveform Is VIN. Middle Waveform Is the 10mA to 1A Step Measured at R3, then the 0mA to 1A Step Showing Extra 2.7µs Delay When Recovering From 0mA 625567f  LTC6255/LTC6256/LTC6257 pAckAge Description (Reference LTC DWG # 05-08-1749 Rev Ø) 1.37 ±0.05 0.70 ±0.05 2.55 ±0.05 0.64 ±0.05 1.15 ±0.05 2.00 ±0.10 R = 0.115 TYP 5 R = 0.05 TYP KC Package 8-Lead Plastic UTDFN (2mm × 2mm) 1.37 ± 0.10 8 0.40 ± 0.10 PIN 1 NOTCH R = 0.20 OR 0.25 45° CHAMFER (KC8) UTDFN 0107 REVØ 2.00 ±0.10 PACKAGE OUTLINE 0.25 ± 0.05 0.45 BSC 1.35 REF PIN 1 BAR TOP MARK (SEE NOTE 6) 0.64 ± 0.10 4 0.125 REF 0.55 ±0.05 0.00 – 0.05 0.23 ± 0.05 0.45 BSC 1.35 REF 1 RECOMMENDED SOLDER PAD PITCH AND DIMENSIONS APPLY SOLDER MASK TO AREAS THAT ARE NOT SOLDERED BOTTOM VIEW—EXPOSED PAD NOTE: 1. DRAWING IS NOT A JEDEC PACKAGE OUTLINE 2. DRAWING NOT TO SCALE 3. ALL DIMENSIONS ARE IN MILLIMETERS 4. DIMENSIONS OF EXPOSED PAD ON BOTTOM OF PACKAGE DO NOT INCLUDE MOLD FLASH. MOLD FLASH, IF PRESENT, SHALL NOT EXCEED 0.15mm ON ANY SIDE 5. EXPOSED PAD SHALL BE SOLDER PLATED 6. SHADED AREA IS ONLY A REFERENCE FOR PIN 1 LOCATION ON THE TOP AND BOTTOM OF PACKAGE 625567f  LTC6255/LTC6256/LTC6257 pAckAge Description (Reference LTC DWG # 05-08-1636) 0.62 MAX 0.95 REF 2.90 BSC (NOTE 4) S6 Package 6-Lead Plastic TSOT-23 1.22 REF 3.85 MAX 2.62 REF 1.4 MIN 2.80 BSC 1.50 – 1.75 (NOTE 4) PIN ONE ID RECOMMENDED SOLDER PAD LAYOUT PER IPC CALCULATOR 0.95 BSC 0.80 – 0.90 0.30 – 0.45 6 PLCS (NOTE 3) 0.20 BSC DATUM ‘A’ 1.00 MAX 0.01 – 0.10 0.30 – 0.50 REF NOTE: 1. DIMENSIONS ARE IN MILLIMETERS 2. DRAWING NOT TO SCALE 3. DIMENSIONS ARE INCLUSIVE OF PLATING 4. DIMENSIONS ARE EXCLUSIVE OF MOLD FLASH AND METAL BURR 5. MOLD FLASH SHALL NOT EXCEED 0.254mm 6. JEDEC PACKAGE REFERENCE IS MO-193 0.09 – 0.20 (NOTE 3) 1.90 BSC S6 TSOT-23 0302 REV B 625567f  LTC6255/LTC6256/LTC6257 pAckAge Description (Reference LTC DWG # 05-08-1637) 0.52 MAX 0.65 REF 2.90 BSC (NOTE 4) TS8 Package 8-Lead Plastic TSOT-23 1.22 REF 3.85 MAX 2.62 REF 1.4 MIN 2.80 BSC 1.50 – 1.75 (NOTE 4) PIN ONE ID RECOMMENDED SOLDER PAD LAYOUT PER IPC CALCULATOR 0.65 BSC 0.80 – 0.90 0.22 – 0.36 8 PLCS (NOTE 3) 0.20 BSC DATUM ‘A’ 1.00 MAX 0.01 – 0.10 0.30 – 0.50 REF NOTE: 1. DIMENSIONS ARE IN MILLIMETERS 2. DRAWING NOT TO SCALE 3. DIMENSIONS ARE INCLUSIVE OF PLATING 4. DIMENSIONS ARE EXCLUSIVE OF MOLD FLASH AND METAL BURR 5. MOLD FLASH SHALL NOT EXCEED 0.254mm 6. JEDEC PACKAGE REFERENCE IS MO-193 0.09 – 0.20 (NOTE 3) 1.95 BSC TS8 TSOT-23 0802 625567f 0 LTC6255/LTC6256/LTC6257 pAckAge Description (Reference LTC DWG # 05-08-1660 Rev F) 3.00 0.102 (.118 .004) (NOTE 3) 0.52 (.0205) REF MS8 Package 8-Lead Plastic MSOP 0.889 (.035 0.127 .005) 8 7 65 5.23 (.206) MIN 3.20 – 3.45 (.126 – .136) GAUGE PLANE 0.254 (.010) DETAIL “A” 0 – 6 TYP 4.90 0.152 (.193 .006) 3.00 0.102 (.118 .004) (NOTE 4) 0.42 0.038 (.0165 .0015) TYP 0.65 (.0256) BSC DETAIL “A” 0.53 0.152 (.021 .006) 0.18 (.007) SEATING PLANE 1 1.10 (.043) MAX 23 4 0.86 (.034) REF RECOMMENDED SOLDER PAD LAYOUT 0.22 – 0.38 (.009 – .015) TYP NOTE: 1. DIMENSIONS IN MILLIMETER/(INCH) 2. DRAWING NOT TO SCALE 3. DIMENSION DOES NOT INCLUDE MOLD FLASH, PROTRUSIONS OR GATE BURRS. MOLD FLASH, PROTRUSIONS OR GATE BURRS SHALL NOT EXCEED 0.152mm (.006") PER SIDE 4. DIMENSION DOES NOT INCLUDE INTERLEAD FLASH OR PROTRUSIONS. INTERLEAD FLASH OR PROTRUSIONS SHALL NOT EXCEED 0.152mm (.006") PER SIDE 5. LEAD COPLANARITY (BOTTOM OF LEADS AFTER FORMING) SHALL BE 0.102mm (.004") MAX 0.65 (.0256) BSC 0.1016 (.004 0.0508 .002) MSOP (MS8) 0307 REV F 625567f  LTC6255/LTC6256/LTC6257 pAckAge Description (Reference LTC DWG # 05-08-1661 Rev E) 0.889 ± 0.127 (.035 ± .005) MS Package 10-Lead Plastic MSOP 5.23 (.206) MIN 3.20 – 3.45 (.126 – .136) 3.00 ± 0.102 (.118 ± .004) (NOTE 3) 0.50 0.305 ± 0.038 (.0197) (.0120 ± .0015) BSC TYP RECOMMENDED SOLDER PAD LAYOUT 10 9 8 7 6 0.497 ± 0.076 (.0196 ± .003) REF 0.254 (.010) GAUGE PLANE DETAIL “A” 0° – 6° TYP 4.90 ± 0.152 (.193 ± .006) 3.00 ± 0.102 (.118 ± .004) (NOTE 4) 12345 0.53 ± 0.152 (.021 ± .006) DETAIL “A” 0.18 (.007) SEATING PLANE 1.10 (.043) MAX 0.86 (.034) REF 0.50 (.0197) NOTE: BSC 1. DIMENSIONS IN MILLIMETER/(INCH) 2. DRAWING NOT TO SCALE 3. DIMENSION DOES NOT INCLUDE MOLD FLASH, PROTRUSIONS OR GATE BURRS. MOLD FLASH, PROTRUSIONS OR GATE BURRS SHALL NOT EXCEED 0.152mm (.006") PER SIDE 4. DIMENSION DOES NOT INCLUDE INTERLEAD FLASH OR PROTRUSIONS. INTERLEAD FLASH OR PROTRUSIONS SHALL NOT EXCEED 0.152mm (.006") PER SIDE 5. LEAD COPLANARITY (BOTTOM OF LEADS AFTER FORMING) SHALL BE 0.102mm (.004") MAX 0.17 – 0.27 (.007 – .011) TYP 0.1016 ± 0.0508 (.004 ± .002) MSOP (MS) 0307 REV E 625567f  LTC6255/LTC6256/LTC6257 pAckAge Description (Reference LTC DWG # 05-08-1669 Rev Ø) 0.889 (.035 0.127 .005) MS Package 16-Lead Plastic MSOP 5.23 (.206) MIN 3.20 – 3.45 (.126 – .136) 0.305 0.038 (.0120 .0015) TYP 0.50 (.0197) BSC 4.039 0.102 (.159 .004) (NOTE 3) 16151413121110 9 RECOMMENDED SOLDER PAD LAYOUT DETAIL “A” 0 – 6 TYP 0.280 0.076 (.011 .003) REF 0.254 (.010) GAUGE PLANE 4.90 0.152 (.193 .006) 3.00 0.102 (.118 .004) (NOTE 4) 0.53 0.152 (.021 .006) DETAIL “A” 0.18 (.007) SEATING PLANE 1.10 (.043) MAX 12345678 0.86 (.034) REF NOTE: 1. DIMENSIONS IN MILLIMETER/(INCH) 2. DRAWING NOT TO SCALE 3. DIMENSION DOES NOT INCLUDE MOLD FLASH, PROTRUSIONS OR GATE BURRS. MOLD FLASH, PROTRUSIONS OR GATE BURRS SHALL NOT EXCEED 0.152mm (.006") PER SIDE 4. DIMENSION DOES NOT INCLUDE INTERLEAD FLASH OR PROTRUSIONS. INTERLEAD FLASH OR PROTRUSIONS SHALL NOT EXCEED 0.152mm (.006") PER SIDE 5. LEAD COPLANARITY (BOTTOM OF LEADS AFTER FORMING) SHALL BE 0.102mm (.004") MAX 0.17 – 0.27 (.007 – .011) TYP 0.50 (.0197) BSC 0.1016 (.004 0.0508 .002) MSOP (MS16) 1107 REV Ø 625567f Information furnished by Linear Technology Corporation is believed to be accurate and reliable. However, no responsibility is assumed for its use. Linear Technology Corporation makes no representation that the interconnection of its circuits as described herein will not infringe on existing patent rights.  LTC6255/LTC6256/LTC6257 typicAl ApplicAtion 2µs Rise Time Analog 1A Pulsed LED Current Driver. LTC6255 Applied as a LED Current Driver with 2µs Rise Time R1 9.76k R2 200 5V SHDN ILED = VIN • 200mA/V ILED R4 51 Q1 Q2 Q3 Q1 TO Q3 MOSFETs 3 2N7000 5V LED OSRAM LRW5SM Time Domain Response Showing 2µs Rise Time. Top Waveform Is VIN. Middle Waveform Is the 10mA to 1A Step Measured at R3, then the 0mA to 1A Step Showing Extra 2.7µs Delay When Recovering From 0mA VIN VIN 5V RUP 1M** *RSD GUARANTEES LED OFF WHEN OP AMP SHDN. OTHERWISE OPTIONAL. *RUP FORCES LED COMPLETELY OFF WHEN VIN = 0. OTHERWISE OPTIONAL. STANDBY SUPPLY CURRENT WITH VIN = 0: 65µA RUP OPEN 650µA RUP INSTALLED 10% TO 90% RISE TIME: 10mA TO 1A, 2µs 0mA TO 1A, ADD 2.7µs DELAY relAteD pArts PART NUMBER DESCRIPTION COMMENTS 180MHz GBW, 1mA, 500μV VOS, RR In/Out, 2.5V to 5.25V, 90V/µs Slew Rate 10MHz GBW, 1.7mA, 475μV VOS, RR In/Out, 2.2V to ±15V, 10nF CLOAD 3.6MHz GBW, 330μA, 70μV VOS, RR In/Out, 2.7V to 5.5V, 100dB CMRR 3MHz GBW, 800μA, 3μV VOS, V– to V+ – 1V In, RR Out, 2.7V to 6V, 130dB CMRR/PSRR 2.5MHz GBW, 1mA, 5μV VOS, V– to V+ – 2.3V In, RR Out, 4.75V to 16V, 120dB CMRR, 125dB PSRR 1.5MHz GBW, 110μA, 750μV VOS, RR In/Out, 2.5V to 5.5V 1.25MHz GBW, 300μA, 800μV VOS, RR In/Out, 2.5V to 18V 1.1MHz GBW, 250μA, 350μV VOS, RR In/Out, 2.7V to 44V, 110dB CMRR 500kHz GBW, 150μA, 3μV VOS, V– to V+ – 0.5V In, RR Out, 2.7V to 6V 330kHz GBW, 135μA, 35μV VOS, V– + 1.0V to V+ – 1.2V In, RR Out, 2.7V to 36V LTC6246/LTC6247/ 180MHz, 1µA, Power Efficient Rail-to-Rail Op Amps LTC6248 LT1498/LT1499 LTC6081/LT6082 10MHz, 6V/µs, Dual/Quad,Rail-to-Rail Input and Output, Precision C-Load Op Amps Precision Dual/Quad CMOS Rail-to-Rail Input/Output Amplifiers LTC2050/LTC2051/ Zero-Drift Operational Amplifiers in SOT-23 LTC2052 LTC1050/LTC1051/ Precision Zero-Drift, Operational Amplifierwith Internal LTC1052 Capacitors LTC6084/LTC6085 LT1783 LT1637/LT1638/ LT1639 LT2054/LT2055 LT6010/LT6011/ LT6012 LT1782 LT1636 LT1490A/LT1491A LT2178/LT2179 LT6000/LT6001/ LT6002 Dual/Quad 1.5MHz, Rail-to-Rail, CMOS Amplifiers 1.25MHz, Over-The-Top Micropower, Rail-to-Rail Input and Output Op Amp in SOT-23 ®  Linear Technology Corporation (408) 432-1900 ● FAX: (408) 434-0507 ● www.linear.com 1630 McCarthy Blvd., Milpitas, CA 95035-7417 – + LTC6255 C1 220pF RSD 100k* R5 240 10mA TO 1A R3 0.1 100mW 625567 TA02a 0mA TO 1A (EXTRA DELAY) 625567 TA02b 1.1MHz, 0.4V/μs Over-The-Top Micropower, Rail-to-Rail Input and Output Op Amps Single/Dual Micropower Zero-Drift Operational Amplifiers 135μA, 14nV/√Hz, Rail-to-Rail Output Precision Op Amp with Shutdown Micropower, Over-The-Top, SOT-23, Rail-to-Rail Input and 200kHz GBW, 55μA, 800μV VOS, RR In/Out, 2.5V to 18V Output Op Amp Over-The-Top, Micropower Rail-to-Rail, Input and Output 200kHz GBW, 50μA, 225μV VOS, RR In/Out, 2.7V to 44V, –40°C to 125°C Op Amp Dual/Quad Over-The-Top, Micropower Rail-to-Rail Input and Output Op Amps 17μA Max, Dual and Quad, Single Supply, Precision Op Amps Single, Dual and Quad, 1.8V, 13μA Precision Rail-to-Rail Op Amps 200kHz GBW, 50μA, 500μV VOS, RR In/Out, 2V to 44V 85kHz GBW, 17μA, 70μV VOS, RR In/Out, 5V to 44V 50kHz GBW, 16μA , 600μV VOS(MAX), RR In/Out, 1.8V to 18V 625567f LT 0610 • PRINTED IN USA  LINEAR TECHNOLOGY CORPORATION 2010