MP2317
26V, 1A, 600kHz, High-Efficiency,
Synchronous, Step-Down Converter
The Future of Analog IC Technology
DESCRIPTION
FEATURES
The MP2317 is a high-efficiency, synchronous,
rectified, step-down, switch-mode converter
with built-in internal power MOSFETs. It offers a
very compact solution that achieves 1A of
continuous output current with excellent load
and line regulation over a wide input supply
range.
The MP2317’s switching edge is optimized for
low EMI. SW anti-ringing is employed to
address high-frequency radiation EMI issues.
Full protection features include over-current
protection (OCP) and thermal shutdown.
The MP2317 requires a minimum number of
readily
available,
standard,
external
components and is available in a space-saving,
6-pin, TSOT23 package.
Wide 7.5V to 26V Operating Input Range
1A Load Current
100mΩ/50mΩ Low RDS(ON) Internal Power
MOSFETs
Internal Power-Save Mode for Light Load
600kHz Fixed Switching Frequency at CCM
Optimized for Low EMI
Internal Soft Start
Over-Current Protection (OCP) and Hiccup
Thermal Shutdown
Output Adjustable from 3.3V
Available in a TSOT23-6 Package
APPLICATIONS
Stand-By Power Supply
White Goods
Flat-Panel Television and Monitors
All MPS parts are lead-free, halogen-free, and adhere to the RoHS directive. For
MPS green status, please visit the MPS website under Quality Assurance. “MPS”
and “The Future of Analog IC Technology” are registered trademarks of
Monolithic Power Systems, Inc.
TYPICAL APPLICATION
Efficiency vs.
Output Current
100
VIN=12V, VOUT=5V
90
80
70
60
50
40
30
20
10
0
0.01
0.1
1
OUTPUT CURRENT (A)
MP2317 Rev. 1.0
3/24/2016
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1
MP2317 – 26V, 1A, SYNCHRONOUS, STEP-DOWN CONVERTER
ORDERING INFORMATION
Part Number*
MP2317GJ
Package
TSOT23-6
Top Marking
See Below
* For Tape & Reel, add suffix –Z (e.g. MP2317GJ–Z)
TOP MARKING
AQR: Product code of MP2317GJ
Y: Year code
PACKAGE REFERENCE
TOP VIEW
IN
1
6
FB
SW
2
5
VCC
GND
3
4
BST
TSOT23-6
MP2317 Rev. 1.0
3/24/2016
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2
MP2317 – 26V, 1A, SYNCHRONOUS, STEP-DOWN CONVERTER
ABSOLUTE MAXIMUM RATINGS (1)
Thermal Resistance
VIN .................................................-0.3V to +28V
VSW ..... -0.6V (-5V < 10ns) to +28V (30V < 10ns)
VBST ...................................................... VSW + 6V
All other pins ...................................-0.3V to +6V
(2)
Continuous power dissipation (TA = +25°C)
................................................................. 1.25W
Junction temperature ................................150°C
Lead temperature .....................................260°C
Storage temperature .................. -65°C to 150°C
TSOT23-6………………..…..100…..55......°C/W
Recommended Operating Conditions
(3)
Supply voltage (VIN) ......................... 7.5V to 26V
Output voltage (VOUT) ............. 3.3V to VIN x DMAX
Operating junction temp (TJ). ... -40°C to +125°C
MP2317 Rev. 1.0
3/24/2016
(4)
θJA
θJC
NOTES:
1) Exceeding these ratings may damage the device.
2) The maximum allowable power dissipation is a function of the
maximum junction temperature TJ (MAX), the junction-toambient thermal resistance θJA, and the ambient temperature
TA. The maximum allowable continuous power dissipation at
any ambient temperature is calculated by PD (MAX) = (TJ
(MAX)-TA)/θJA. Exceeding the maximum allowable power
dissipation produces an excessive die temperature, causing
the regulator to go into thermal shutdown. Internal thermal
shutdown circuitry protects the device from permanent
damage.
3) The device is not guaranteed to function outside of its
operating conditions.
4) Measured on JESD51-7, 4-layer PCB.
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3
MP2317 – 26V, 1A, SYNCHRONOUS, STEP-DOWN CONVERTER
ELECTRICAL CHARACTERISTICS
(5)
VIN = 12V, TJ = -40°C to 125°C , unless otherwise noted. Typical value is based on the average
value when TJ = 25°C.
Parameter
Supply current (quiescent)
HS switch-on resistance
LS switch-on resistance
Switch leakage
Current limit
Oscillator frequency
Foldback frequency
Maximum duty cycle
Minimum on time(6)
Feedback voltage
Feedback current
VIN under-voltage lockout
threshold rising
VIN under-voltage lockout
threshold hysteresis
VCC regulator
VCC load regulation
Soft-start period
Symbol
Iq
HSRDS-ON
LSRDS-ON
SWLKG
ILIMIT
fSW
fFB
DMAX
TON MIN
VFB
IFB
Thermal hysteresis
(6)
Duty cycle = 40%, TJ = 25°C
VFB = 750mV
VFB = 200mV
VFB = 750mV
Min
1.4
500
775
VFB = 820mV
5.2
INUVVth
Typ
150
100
50
2.2
600
0.2
93
90
791
10
6.3
Max
807
50
Units
μA
mΩ
mΩ
μA
A
kHz
fSW
%
ns
mV
nA
7.5
V
1
3
700
INUVHYS
500
mV
VCC
4
1.5
V
%
ICC = 5mA
TSS
Thermal shutdown(6)
Condition
VFB = 1V
VBST-SW = 4V
VCC = 4V
10% to 90%
TSD
TSD
HYS
0.8
1.5
2.2
ms
150
°C
20
°C
NOTES:
5) Not tested in production and guaranteed by over-temperature correlation.
6) Guaranteed by design and characterization test.
MP2317 Rev. 1.0
3/24/2016
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4
MP2317 – 26V, 1A, SYNCHRONOUS, STEP-DOWN CONVERTER
TYPICAL PERFORMANCE CHARACTERISTICS
VIN = 12V, VOUT = 5V, L = 10μH, TA = 25°C, unless otherwise noted.
160
810
650
155
800
630
150
790
610
145
780
590
770
140
570
760
135
550
750
130
0
5
10
15
20
25
30
2.35
2.3
2.25
2.2
2.15
2.1
2.05
0.1
0.2
0.3
0.4
0.5
0.6
0.7
14
530
-40 -20 0
20 40 60 80 100 120
100
100
90
90
80
80
70
70
60
60
50
50
40
40
30
30
20
20
10
10
0
0.01
0.1
1
20 40 60 80 100 120
0
0.01
0.1
1
0.12
0.10
0.10
12
0.08
0.05
10
0.06
8
0.04
0
6
0.02
0
4
-0.05
-0.02
2
0
0
740
-40 -20 0
-0.04
0.2
MP2317 Rev. 1.0
3/24/2016
0.4
0.6
0.8
1
1.2
-0.10
0
0.2
0.4
0.6
0.8
1.0
1.2
-0.06
0
5
10
15
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20
25
30
5
MP2317 – 26V, 1A, SYNCHRONOUS, STEP-DOWN CONVERTER
TYPICAL PERFORMANCE CHARACTERISTICS (continued)
VIN = 12V, VOUT = 5V, L = 10μH, TA = 25°C, unless otherwise noted.
Bode Plot
GAIN MARGIN[B/A] (dB)
60
40
Phase Margin
20
0
Gain Margin
-20
-40
-60
1000
10000
100000
200
160
120
80
40
0
-40
-80
-120
-160
-200
PHASE[B-A] (DEG)
IOUT=1A
1000000
FREQUENCY (Hz)
MP2317 Rev. 1.0
3/24/2016
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MP2317 – 26V, 1A, SYNCHRONOUS, STEP-DOWN CONVERTER
TYPICAL PERFORMANCE CHARACTERISTICS (continued)
VIN = 12V, VOUT = 5V, L = 10μH, TA = 25°C, unless otherwise noted.
Start-Up through
Input Voltage
Start-Up through
Input Voltage
Shutdown through
Input Voltage
IOUT=0A
IOUT=1A
IOUT=0A
VOUT
2V/div.
VOUT
2V/div.
VIN
10V/div.
VOUT
2V/div.
VIN
10V/div.
VSW
10V/div.
VIN
10V/div.
VSW
10V/div.
VSW
10V/div.
IINDUCTOR
2A/div.
IINDUCTOR
1A/div.
IINDUCTOR
500mA/div.
Shutdown through
Input Voltage
Input/Output Ripple
Input/Output Ripple
IOUT=0A
IOUT=1A
IOUT=1A
VOUT/AC
10mV/div.
VOUT/AC
10mV/div.
VIN/AC
50mV/div.
VOUT
2V/div.
VIN/AC
100mV/div.
VIN
10V/div.
VSW
10V/div.
IINDUCTOR
1A/div.
VSW
5V/div.
VSW
10V/div.
IINDUCTOR
200mA/div.
IINDUCTOR
1A/div.
OCP Entry
OCP Recovery
Load Transient Response
IOUT=0A
IOUT=0A
IOUT=0.5A to 1A
VOUT
5V/div.
VOUT
5V/div.
VIN
10V/div.
VIN
10V/div.
VSW
10V/div.
VSW
10V/div.
IINDUCTOR
5A/div.
IINDUCTOR
5A/div.
MP2317 Rev. 1.0
3/24/2016
VOUT/AC
50mV/div.
IOUT
500mA/div.
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MP2317 – 26V, 1A, SYNCHRONOUS, STEP-DOWN CONVERTER
PIN FUNCTIONS
Package
Pin #
Name
1
IN
2
SW
3
GND
4
BST
5
VCC
6
FB
MP2317 Rev. 1.0
3/24/2016
Description
Supply voltage. The MP2317 operates from a +7.5V to +26V input rail. C1 is needed to
decouple the input rail. Connect using wide PCB traces.
Switch output. Connect using wide PCB traces.
System ground. GND is the reference ground of the regulated output voltage. GND
requires special consideration during PCB layout. Connect GND with copper traces and
vias.
Bootstrap. Connect a capacitor between SW and BST to form a floating supply across the
high-side switch driver.
Internal LDO output. Decouple VCC with a 0.1μF - 0.22μF capacitor. VCC can be biased
by an external 5V output voltage through a diode.
Feedback. An external resistor divider from the output to GND tapped to FB sets the
output voltage. To prevent a current-limit runaway during a short-circuit fault condition, the
frequency foldback comparator lowers the oscillator frequency when the FB voltage is
below 396mV.
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8
MP2317 – 26V, 1A, SYNCHRONOUS, STEP-DOWN CONVERTER
BLOCK DIAGRAM
Figure 1: Functional Block Diagram
MP2317 Rev. 1.0
3/24/2016
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9
MP2317 – 26V, 1A, SYNCHRONOUS, STEP-DOWN CONVERTER
OPERATION
The MP2317 is a high-frequency, synchronous,
rectified, step-down, switch-mode converter
with built-in, internal power MOSFETs. It offers
a very compact solution that achieves 1A of
continuous output current with excellent load
and line regulation over a wide input supply
range.
The MP2317 operates in a fixed-frequency,
peak-current-control mode to regulate the
output voltage. A pulse width modulation
(PWM) cycle is initiated by the internal clock.
The integrated high-side power MOSFET (HSFET) turns on and remains on until its current
reaches the value set by the COMP voltage
(VCOMP). When the power switch is off, it
remains off until the next clock cycle begins. If
the current in the power MOSFET does not
reach the current value set by COMP within
93% of one PWM period, the power MOSFET is
forced off.
Internal VCC Regulator
Most of the internal circuitries are powered by
the internal VCC regulator. This regulator takes
the VIN input and operates in the full VIN range.
When VIN is greater than its UVLO rising
threshold, the output of the regulator is in full
regulation. When VIN is lower than its UVLO
falling threshold, the internal VCC regulator
shuts off. A 0.1µF ceramic capacitor is required
for decoupling.
Error Amplifier (EA)
The error amplifier compares the FB voltage
with the internal 0.791V reference (REF) and
outputs a COMP voltage, which is used to
control the power MOSFET current. The
optimized internal compensation network
minimizes the external component counts and
simplifies the control loop design.
AAM Operation
The MP2317 uses advanced asynchronous
modulation (AAM) power-save mode for light
loads. The AAM voltage is set at 0.4V internally.
Under heavy-load conditions, VCOMP is higher
than VAAM. When the clock goes high, the HSFET turns on and remains on until VILsense
reaches the value set by VCOMP. The internal
clock resets whenever VCOMP is higher than
VAAM.
MP2317 Rev. 1.0
3/24/2016
Under light-load conditions, the value of VCOMP
is low. When VCOMP is less than VAAM, and VFB is
less than VREF, VCOMP ramps up until it exceeds
VAAM. During this time, the internal clock is
blocked, and the MP2317 skips some pulses for
pulse frequency modulation (PFM) mode and
achieves light-load power save.
Figure 2: Simplified AAM Control Logic
Under-Voltage Lockout (UVLO)
Under-voltage lockout (UVLO) is implemented
to protect the chip from operating at an
insufficient supply voltage. The UVLO
comparator monitors the input voltage. When
the input voltage is higher than the UVLO rising
threshold, the MP2317 powers up and shuts off
when the input voltage is lower than the UVLO
falling threshold. It has non-latch protection.
Internal Soft Start (SS)
The soft start (SS) is implemented to prevent
the converter output voltage from overshooting
during start-up. When the chip starts up, the
internal circuitry generates a soft-start voltage
that ramps up from 0V. The soft-start period
lasts until the voltage on the soft-start capacitor
exceeds the 0.791V reference voltage. At this
point, the reference voltage takes over. The
soft-start time is set to be around 1.5ms
internally from 10% to 90% of VOUT.
Over-Current Protection (OCP) and Hiccup
The MP2317 employs a cycle-by-cycle overcurrent limit when the inductor current peak
value exceeds the set current-limit threshold.
Meanwhile, the output voltage starts to drop
until FB is below the under-voltage (UV)
threshold, typically 50% below the reference.
Once UV is triggered, the MP2317 enters
hiccup mode to restart the part periodically.
This protection mode is especially useful when
the output is dead-shorted to ground. The
average short-circuit current is greatly reduced
to alleviate thermal issues and to protect the
regulator. The MP2317 exits hiccup mode once
the over-current condition is removed.
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10
MP2317 – 26V, 1A, SYNCHRONOUS, STEP-DOWN CONVERTER
Thermal Shutdown
Thermal shutdown prevents the chip from
operating at exceedingly high temperatures.
When the silicon die temperature is higher than
150°C, the entire chip shuts down. When the
temperature is below its lower threshold,
typically 130°C, the chip is enabled again.
Circuit Start-Up and Shutdown
If VIN is higher than its UVLO threshold, the chip
starts up. The reference block starts first,
generating a stable reference voltage and
current, and then the internal regulator is
enabled. The regulator provides a stable supply
for the remaining circuitries.
Floating Driver and Bootstrap Charging
The floating power MOSFET driver is powered
by an external bootstrap capacitor. This floating
driver has its own UVLO protection. This
UVLO’s rising threshold is 2.2V with a
hysteresis of 150mV. The bootstrap capacitor
voltage is regulated internally by VIN through
D1, C3, L1, and C2 (see Figure 3). If VIN - VSW
is more than 4V, U2 regulates M3 to maintain a
4V BST voltage across C3.
In the shutdown procedure, the signaling path is
first blocked to prevent any fault triggering.
VCOMP and the internal supply rail are then
pulled down. The floating driver is not subject to
this shutdown command.
C3
Figure 3: Internal Bootstrap Charging
MP2317 Rev. 1.0
3/24/2016
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MP2317 – 26V, 1A, SYNCHRONOUS, STEP-DOWN CONVERTER
APPLICATION INFORMATION
Setting the Output Voltage
The external resistor divider is used to set the
output voltage (see the Typical Application on
page 1). The feedback resistor (R1) also sets
the feedback loop bandwidth with the external
compensation capacitor. Calculate R2 with
Equation (1):
R1
R2
X7R dielectrics are highly recommended
because of their low ESR and small
temperature coefficients. For most applications,
a 22µF capacitor is sufficient.
Since the input capacitor (C1) absorbs the input
switching current, it requires an adequate ripple
current rating. The RMS current in the input
capacitor can be estimated with Equation (4):
(1)
V OUT 1
0.791V
Table 1 lists the recommended resistor values
for common output voltages.
IC1 ILOAD
IC1
25.5
10
5
80.6
15
10
Selecting the Inductor
A 1µH to 22µH inductor with a DC current rating
at least 25% percent higher than the maximum
load current is recommended for most
applications. For highest efficiency, the inductor
DC resistance should be less than 30mΩ. For
most designs, the inductance value can be
derived from Equation (2):
L1
VOUT (VIN VOUT )
VIN IL fOSC
(2)
VIN
Choose
the
inductor
current
to
be
approximately 30% of the maximum load
current. The maximum inductor peak current
can be calculated with Equation (3):
I L
2
(3)
Under light-load conditions below 100mA, a
larger inductance is recommended for improved
efficiency.
Selecting the Input Capacitor
The input current to the step-down converter is
discontinuous, and therefore requires a
capacitor to supply AC current to the step-down
converter while maintaining the DC input
voltage. For best performance, use low ESR
capacitors. Ceramic capacitors with X5R or
MP2317 Rev. 1.0
3/24/2016
(5)
The input capacitor can be electrolytic, tantalum,
or ceramic. When using electrolytic or tantalum
capacitors, a small, high-quality ceramic
capacitor (i.e.: 1μF) should be placed as close
to the IC as possible. When using ceramic
capacitors, ensure that they have enough
capacitance to provide a sufficient charge to
prevent excessive voltage ripple at the input.
The input voltage ripple caused by capacitance
can be estimated with Equation (6):
Where ∆IL is the inductor ripple current.
IL(MAX ) ILOAD
ILOAD
2
For simplification, choose an input capacitor
with an RMS current rating greater than half of
the maximum load current.
VOUT (V) R1 (kΩ) R2 (kΩ) Lo (µH)
80.6
(4)
The worst-case condition occurs at VIN = 2VOUT,
shown in Equation (5):
Table 1: Resistor Selection for Common Output
Voltages
3.3
VOUT VOUT
1
VIN VIN
ILOAD
V
V
OUT 1 OUT
fS C1 VIN
VIN
(6)
Selecting the Output Capacitor
The output capacitor (C2) is required to
maintain the DC output voltage. Ceramic,
tantalum, or low ESR electrolytic capacitors are
recommended. For best results, use low ESR
capacitors to keep the output voltage ripple low.
The output voltage ripple can be estimated with
Equation (7):
VOUT
(7)
VOUT VOUT
1
1
RESR
fS L1
VIN
8 fS C2
Where L1 is the inductor value and RESR is the
equivalent series resistance (ESR) value of the
output capacitor.
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12
MP2317 – 26V, 1A, SYNCHRONOUS, STEP-DOWN CONVERTER
For ceramic capacitors, the impedance at the
switching frequency is dominated by the
capacitance, which mainly causes the output
voltage ripple. For simplification, the output
voltage ripple can be estimated with Equation
(8):
∆VOUT
V
VOUT
1 OUT
VIN
8 fS L1 C2
2
(8)
In the case of tantalum or electrolytic capacitors,
the ESR dominates the impedance at the
switching frequency. For simplification, the
output ripple can be approximated with
Equation (9):
∆VOUT
VOUT
V
1 OUT
fS L1
VIN
RESR
External VCC Diode
When VOUT is 5V, an external optional diode
from VOUT to VCC may enhance the efficiency
of the regulator (see Figure 5).
1N4148
C4
0.1µF
Figure 5: Optional External Diode Added to
Enhance Efficiency
9)
The characteristics of the output capacitor also
affect the stability of the regulation system. The
MP2317 can be optimized for a wide range of
capacitance and ESR values.
External Bootstrap Diode
An optional, external diode may enhance the
efficiency of the regulator. The conditions of the
external diode are applied when the output
voltage is 5V.
In this case, it is recommended to connect an
external BST diode from VOUT to BST (see
Figure 4).
Figure 4: Optional External Bootstrap Diode
Added to Enhance Efficiency
MP2317 Rev. 1.0
3/24/2016
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13
MP2317 – 26V, 1A, SYNCHRONOUS, STEP-DOWN CONVERTER
(7)
PCB Layout Guidelines
Efficient PCB layout is critical for stable
operation. For best results, refer to Figure 6 and
follow the guidelines below.
Design Example
Table 2 is a design example following the
application guidelines for the specifications
below:
1. Keep the connection of the input ground
and GND as short and wide as possible.
Table 2: Design Example
12V
VIN
5V
VOUT
1A
IO
2. Connect the ground of the VCC capacitor to
the IC’s GND through multiple vias or wide
traces.
3. Keep the connection of the input capacitor
and IN as short and wide as possible.
4. Ensure that all feedback connections are
short and direct.
The detailed application schematics are shown
in Figure 7 and Figure 8. The typical
performance and circuit waveforms are shown
in the Typical Performance Characteristics
section. For more device applications, please
refer to the related evaluation board datasheets.
5. Place
the
feedback
resistors
and
compensation components as close to the
chip as possible.
6. Route SW away from sensitive analog
areas such as FB.
NOTE:
7)
The recommended layout is based on Figure 8: Typical
Application Circuit.
Top Layer
Bottom Layer
Figure 6: Recommended PCB Layout
MP2317 Rev. 1.0
3/24/2016
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14
MP2317 – 26V, 1A, SYNCHRONOUS, STEP-DOWN CONVERTER
TYPICAL APPLICATION CIRCUITS
7.5V-26V
1
C1A
10µF
C1
0.1µF
4
MP 2317
C3
0.1µF
L1
10µH
2
3.3 V/1A
C2
22µF
5
C4
0.1µF
C2A
22µF
C2B
NS
R1
80.6K
6
R3
24.9K
3
R2
25.5K
C5
22 pF
Figure 7: 3.3V/1A Output
7.5V-26V
1
C1A
10µF
C1
0.1µF
4
MP 2317
C3
0.1µF
L1
10µH
2
5V/1A
C2
22µF
5
C4
0.1µF
C2A
22µF
C2B
NS
R1
80.6K
6
R3
15K
3
R2
15K
C5
10 pF
Figure 8: 5V/1A Output
MP2317 Rev. 1.0
3/24/2016
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15
MP2317 – 26V, 1A, SYNCHRONOUS, STEP-DOWN CONVERTER
PACKAGE INFORMATION
TSOT23-6
See note 7
EXAMPLE
TOP MARK
PIN 1 ID
IAAAA
RECOMMENDED LAND PATTERN
TOP VIEW
SEATING PLANE
SEE DETAIL''A''
FRONT VIEW
SIDE VIEW
NOTE:
DETAIL "A"
1) ALL DIMENSIONS ARE IN MILLIMETERS
.
2) PACKAGE LENGTH DOES NOT INCLUDE MOLD FLASH
,
PROTRUSION OR GATE BURR.
3) PACKAGE WIDTH DOES NOT INCLUDE INTERLEAD FLASH
OR PROTRUSION.
4) LEAD COPLANARITY(BOTTOM OF LEADS AFTER FORMING)
SHALL BE 0.10 MILLIMETERS MAX.
5) DRAWING CONFORMS TO JEDEC MO-193, VARIATION AB.
6) DRAWING IS NOT TO SCALE.
7) PIN 1 IS LOWER LEFT PIN WHEN READING TOP MARK
FROM LEFT TO RIGHT, (SEE EXAMPLE TOP MARK)
NOTICE: The information in this document is subject to change without notice. Users should warrant and guarantee that third
party Intellectual Property rights are not infringed upon when integrating MPS products into any application. MPS will not
assume any legal responsibility for any said applications.
MP2317 Rev. 1.0
3/24/2016
www.MonolithicPower.com
MPS Proprietary Information. Patent Protected. Unauthorized Photocopy and Duplication Prohibited.
© 2016 MPS. All Rights Reserved.
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