MP4054
Non-isolated
Offline LED Controller with Active PFC
The Future of Analog IC Technology
DESCRIPTION
FEATURES
The MP4054 is a non-isolated, offline LED
lighting controller. In a tiny TSOT23-8 package,
it achieves high power factor (PF) and accurate
LED current for isolated, single-power-stage
lighting applications.
The MP4054 integrates power factor correction
(PFC) and valley switching mode to reduce
MOSFET switching losses.
To enhance system reliability and safety, the
MP4054 has multiple internally integrated
protection features, including over-voltage
protection (OVP), short-circuit protection (SCP),
over-current protection (OCP), brown-out
protection, over-temperature protection (OTP),
cycle-by-cycle current limit, VCC under-voltage
lockout (UVLO), and auto-restart function.
Unique Architecture for Superior Line
Regulation
Achieve 0.3V
ZCD Blanking Time
tLEB_ZCD
After turn-off,
VMULT_O ≤0.3V
After turn-off,
VMULT_O >0.3V
Over-Voltage Blanking Time
tLEB_OVP
After turn-off,
VMULT_O ≤0.3V
Over-Voltage Threshold
VZCD_OVP
1.6μs delay after turn-off
Minimum Off Time
tOFF_MIN
Starter
Start-Timer Period
tSTART
Gate Driver
Output-Clamp Voltage
VGATE_CLAMP VCC=28V
Minimum-Output Voltage
VGATE_MIN
VCC=VCCOFF + 50mV
Max. Source Current(6)
IGATE_SOURCE
Max. Sink Current(6)
IGATE_SINK
Thermal Shutdown
Thermal Shutdown Threshold(6)
TSD
Thermal Shutdown Recovery
THYS
Hysteresis(6)
Min
Typ
Max
Units
190
280
480
ns
2.36
2.46
2.56
V
0.270
562
0.295
595
0.318
628
V
mV
1.2
1.6
2.1
μs
0.6
0.8
1.1
μs
1.2
1.6
2.1
μs
0.6
0.8
1.1
μs
4.9
4
5.1
5.5
5.4
8
V
µs
190
13.0
6.7
14.5
µs
17.0
0.8
-1
V
V
A
A
150
°C
25
°C
Notes:
5) The multiplier output VMULT_O is given by: VCS=VMULT_O=K•VMULT• (VCOMP-1.5).
6) Guaranteed by characterization.
MP4054 Rev. 1.0
12/25/2014
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5
MP4054 – NON-ISOLATED OFFLINE LED CONTROLLER WITH ACTIVE PFC
TYPICAL PERFORMANCE CHARACTERISTICS
VIN = 90VAC to 264VAC, Low-side Buck-boost Converter, 30 LEDs in series, VOUT = 90V,
ILED=200mA, TA = 25°C, unless otherwise noted.
MP4054 Rev. 1.0
12/25/2014
www.MonolithicPower.com
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© 2014 MPS. All Rights Reserved.
6
MP4054 – NON-ISOLATED OFFLINE LED CONTROLLER WITH ACTIVE PFC
TYPICAL PERFORMANCE CHARACTERISTICS (continued)
VIN = 120VAC/60Hz, Low-side Buck-boost Converter, 30 LEDs in series, VOUT = 90V, ILED=200mA,
TA = 25°C, unless otherwise noted.
MP4054 Rev. 1.0
12/25/2014
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© 2014 MPS. All Rights Reserved.
7
MP4054 – NON-ISOLATED OFFLINE LED CONTROLLER WITH ACTIVE PFC
TYPICAL PERFORMANCE CHARACTERISTICS (continued)
VIN = 230VAC/50Hz, Low-side Buck-boost Converter, 30 LEDs in series, VOUT = 90V, ILED=200mA,
TA = 25°C, unless otherwise noted.
MP4054 Rev. 1.0
12/25/2014
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© 2014 MPS. All Rights Reserved.
8
MP4054 – NON-ISOLATED OFFLINE LED CONTROLLER WITH ACTIVE PFC
PIN FUNCTIONS
Description
Pin #
Name
1
VCC
Power Supply Input. Supplies power for the control signals and driving the high-current
power MOSFET. Bypass to ground with an external bulk capacitor (typically 4.7µF).
2
MULT
Multiplier Input. Connect to the tap of resistor divider between the rectified AC line and
GND. The half-wave sinusoid provides a reference signal for the internal-current-control
loop. MULT is used for brown-out protection detection.
3
NC
4
COMP
5
GND
6
FB
Feedback Input. If the accurate LED current is needed, connect this pin to the LEDcurrent-sensing resistor.
CS/ZCD
Current Sense and Zero-Current Detection. This is a MPS proprietary dual function pin.
When the gate driver turns on, CS/ZCD senses the MOSFET current. The difference
between the sensed voltage and the internal sinusoidal-current-reference determines
when the MOSFET turns off.
When the gate driver turns off, the zero crossing (after blanking time) triggers GATE turnon signal. Connect CS/ZCD to a resistor divider through a diode between the auxiliary
winding and GND.
Output over-voltage condition is detected through ZCD. During every turn-off interval, if
the ZCD voltage exceeds the over-voltage protection threshold, after the 1.6µs
(VMULT_O>0.3V) or 0.8µs (VMULT_O≤0.3V) blanking time, over-voltage protection is triggered
and the system stops switching until auto-restart.
CS/ZCD is used for over-current protection. If the sensing voltage reaches 2.46V (after
blanking time), the over-current protection is triggered and the system stops switching
until auto-restart.
A 10pF ceramic cap is recommended to connect CS/ZCD to GND to bypass the highfrequency noise. In order to reduce RC delay influence on the accuracy of the currentsensing signal, a 1kΩ down-side resistance (RZCD2 in Figure 7) from CS/ZCD is
recommended.
GATE
Gate Drive Output. This totem-pole output stage can drive a high-power MOSFET with a
peak current of 0.8A source and 1A sink. The high-voltage limit is clamped to 14.5V to
avoid excessive gate-drive voltage. The drive voltage is higher than 6.7V to guarantee
sufficient drive capacity.
7
8
MP4054 Rev. 1.0
12/25/2014
Do not connect this pin to any potential. Leave it floating.
Loop Compensation Input. Connect a compensation network to stabilize the LED driver
and maintain an accurate LED current.
Ground. Current return for the control signal and the gate-drive signal.
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9
MP4054 – NON-ISOLATED OFFLINE LED CONTROLLER WITH ACTIVE PFC
FUNCTION DIAGRAM
Figure 1: MP4054 Function Block Diagram
MP4054 Rev. 1.0
12/25/2014
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10
MP4054 – NON-ISOLATED OFFLINE LED CONTROLLER WITH ACTIVE PFC
OPERATION
The MP4054 is a non-isolated, offline LED
controller. It incorporates all the features of
high-performance LED lighting. The LED
current is controlled accurately with the realcurrent control method. Active power factor
correction (PFC) eliminates unwanted harmonic
noise on the AC line. The rich protection
features achieve high safety and reliability in
real application.
This virtually eliminates switch turn-on loss and
diode reverse-recovery losses, ensuring high
efficiency and low EMI noise.
The description as below is based on lowside Buck-boost solution, unless otherwise
noted.
Start Up
Initially, the VCC cap is charged by the start-up
resistor from the AC line. When VCC reaches
25.5V, the control logic activates and the gate
driver signal begins to switch; the power supply
is taken over by the auxiliary winding.
The chip shuts down when VCC drops below
9.5V.
The high hysteretic voltage allows for a small
VCC capacitor (typically 4.7μF) to shorten the
start-up time.
Figure 2: Valley Switching Mode
Valley Switching Mode
During the external MOSFET ON-time (tON), the
rectified-input voltage (VBUS) charges the
inductor (Lm) causing the inductor current (IL) to
increase linearly from zero to peak value (IPK).
When the MOSFET turns off, the energy stored
in the inductor is transferred to the output,
which activates the rectifier diode to power the
load. The inductor current (IL) decreases
linearly from its peak value to zero. When the
inductor current decreases to zero, the
MOSFET drain-source voltage starts oscillating,
which is caused by the magnetizing inductance
and parasitic capacitances—the voltage ring
also is reflected on the auxiliary winding (see
Figure 2). To improve current control precision,
the chip monitors when ZCD voltage falls to
zero twice before the next switching period. The
zero-current detector from CS/ZCD generates
GATE turn-on signal when the ZCD voltage
falls below 0.295V the second time (see Figure
3).
MP4054 Rev. 1.0
12/25/2014
Figure 3: Zero-Current Detector
LED Current Control
In low-side Buck-boost solution, the proprietary
real-current-control method allows the MP4054
to control the output LED current using inductor
current information. The mean output LED
current is calculated approximately as:
Io
VREF
2 RS
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11
MP4054 – NON-ISOLATED OFFLINE LED CONTROLLER WITH ACTIVE PFC
VREF—The feedback reference voltage
(typical 0.413V);
RS—The sensing resistor connected
between the MOSFET source and GND.
In high-side solution (including both Buck and
Buck-boost), the proprietary direct-current
control method allows the MP4054 to control
the LED current accurately. The mean value of
the output LED current is calculated
approximately as:
V
Io REF
RFB
RFB—The sensing resistor connected
between the FB RC filter and GND in highside solution
Power-Factor Correction (PFC)
MULT is connected to a pull-up resistor from
the rectified-instantaneous-line voltage; the
multiplier output is sinusoidal. This signal sets
the sinusoidal inductor peak current. This
achieves a high power factor (PF).
Multiplier output
Inductor current
Figure 4: Power-Factor Correction
The maximum output voltage of the multiplier is
clamped to 2.0V, setting the cycle-by-cycle
current limit.
VCC Under-Voltage Lockout (UVLO)
When the VCC voltage drops below the UVLO
threshold 9.5V, the IC stops switching and
shuts down; the operating current is very low
under this condition. VCC is then charged by
the external resistor from the AC line. Figure 5
shows the typical waveform of UVLO.
MP4054 Rev. 1.0
12/25/2014
Figure 5: VCC Under-Voltage Lockout
Auto Starter
The MP4054 integrates an auto-restart that
begins timing when the MOSFET turns off. If
ZCD fails to send a turn-on signal after 190µs, a
turn-on signal is initiated. This avoids an
unnecessary IC shut down if ZCD misses
detection.
Minimum Off Time
The MP4054 operates with variable switching
frequency. The frequency changes with the
input instantaneous line voltage. To limit the
maximum frequency and enhance EMI
performance, the chip employs an internal
minimum OFF-time of 5.5µs.
Leading-Edge Blanking (LEB)
Internal
leading-edge-blanking
(LEB)
is
employed to prevent a switching pulse from
terminating prematurely due to parasitic
capacitance discharging when the MOSFET
turns on. During the blanking time, the path
from CS/ZCD to the current comparator input is
blocked. Figure 6 shows the leading-edge
blanking time. The LEB time of OCP detection
is relatively short at 280ns.
VCS
tLEB =400 ns
t
Figure 6: Leading-Edge Blanking
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12
MP4054 – NON-ISOLATED OFFLINE LED CONTROLLER WITH ACTIVE PFC
Output Over-Voltage Protection (OVP)
Output
over-voltage
protection
prevents
component
damage
from
over-voltage
conditions. The auxiliary winding’s positive
plateau voltage is proportional to the output
voltage; the OVP uses the auxiliary-winding
voltage instead of directly monitoring the output
voltage.
Figure 7 shows the OVP circuit. Once the ZCD
voltage is higher than 5.1V and exceeds the
OVP blanking time (during the gate turn-off
interval), the OVP signal is latched, turning the
gate driver off. When VCC drops below UVLO,
the IC restarts.
The output OVP setting point is calculated as:
VOUT _ OVP
NAUX
R ZCD2
5.1V
NL R ZCD1 R ZCD2
VOUT_OVP—The
protection point;
NAUX—The auxiliary winding turns;
NL—The inductor winding turns.
output
over-voltage
Gate_OFF
CS/ZCD
Latch
OVP
Blanking time
5.1V
RZCD 2
0V
Sampling Here
t LE B _OV P
Figure 8: ZCD Voltage and OVP Sampler
Output Short-Circuit Protection (SCP)
If an output short occurs, ZCD cannot detect
the zero-current-crossing signal, so the 190μs
auto-restart timer triggers the MOSFET’s turnon signal. The switching frequency of the power
circuit drops to about 5kHz and the output
current is limited to its nominal current. The
auxiliary-winding voltage drops to follow the
output voltage, VCC drops to less than the
UVLO threshold, and then the system restarts.
This sequence limits both the output power and
IC temperature if an output short occurs.
Over-Current Protection (OCP)
Gate
+
-
VCS/ZCD
R1
RZCD 1
The over-current protection prevents device
damage from excessive current, such as a
inductor winding short circuit. If the CS/ZCD
voltage rises to 2.46V during the gate turn-on
interval (see Figure 9), the over-current
protection signal is latched, turning the gate
driver off. When VCC drops below UVLO, the
IC restarts.
Figure 7: OVP Sampling Unit
To prevent a voltage spike from an OVP mistrigger, OVP sampling has a tLEB_OVP blanking
period, typically 1.6µs when VMULT_O > 0.3V and
0.8µs when VMULT_O ≤ 0.3V (see Figure 8).
A current-limit resistor between the output of
the auxiliary winding and the ZCD resistor
divider also works as a suppresser to avoid an
OVP mis-trigger.
MP4054 Rev. 1.0
12/25/2014
Figure 9: OCP Sampling Unit
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13
MP4054 – NON-ISOLATED OFFLINE LED CONTROLLER WITH ACTIVE PFC
Brown-Out Protection
IC Thermal Shut Down
The MP4054 has brown-out protection; the
internal peak detector detects the peak value of
the rectified sinusoid waveform on MULT. If the
peak value is less than the brown-out protection
threshold, 0.3V for typically 42ms, MP4054
identifies this as a brown-out, dropping COMP
to zero and disabling the power circuit. If the
peak value exceeds 0.4V, the IC restarts and
the COMP voltage rises again softly. This
feature prevents the inductor and LED current
from saturating during fast ON/OFF switching
(see Figure 10).
To prevent thermal damage to the system and
IC, if internal temperatures exceed 150°C, the
MP4054 stops switching and the IC is latched
off until VCC drops below UVLO and restarts.
VCC
Brown out
happen
Vbus
Brown out
detected
Brown
out
recover
V peak_ Mult
Vcomp
Vgate
Figure 10: Brown-Out Protection Waveforms
MP4054 Rev. 1.0
12/25/2014
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14
MP4054 – NON-ISOLATED OFFLINE LED CONTROLLER WITH ACTIVE PFC
APPLICATION INFORMATION
Although isolated solutions can prevent electric
shock from the grid when touching the load,
they cause power loss and increase costs.
Non-isolated solutions achieve higher efficiency
and are highly cost-effective.
Generally, the flyback converter is used for
offline, isolated applications. For the nonisolated applications, a low-side buck-boost
topology is used. The MP4054 can operate in
non-isolated LED-lighting applications (see
Figure 16).
Operation of Low-Side Buck-Boost
The low-side buck-boost equates to a flyback
converter with a 1:1 turn ratio transformer. As
opposed to an isolated solution, there is not a
separate primary and secondary winding,
making a smaller core size. This saves cost and
improves the efficiency of the driver.
The Selection of FET & Rectifier Diode
Since it is just an inductor for non-isolated
solution, compared with isolated solution, at
same output voltage, the power FET can be
selected with lower voltage rating. But,
oppositely, the voltage rating of rectifier diodes
for output and aux-winding must be increased.
Improvement of RF EMI
C5 in Figure 16 is added for RF EMI
improvement. The recommended value is from
10nF to 68nF with 630V rating.
Improvement of PFC & THD
The 1:1 ratio reduces the converter’s duty cycle
using the same specifications. Based on the
PFC principle in an isolated solution, the
converter’s PF and THD drops. A non-isolated
solution is suitable particularly for high-output
voltage since the higher output voltage can
extend the duty cycle to improve PF, THD and
efficiency.
For a non-isolated solution with low-output
voltage, the tapped inductor can be applied to
improve the PF and THD.
MP4054 Rev. 1.0
12/25/2014
Figure 11: Tapped-Inductor for Low-Side BuckBoost Solution
Shown in Figure 11, the tapped-inductor
includes two windings (N1 & N2) and a tap to
connect the rectifier diode. When the power
FET is turned on, the current goes through both
of the windings. When the power FET is off,
only N1 conducts the current through the
rectifier diode. The stored energy of N2 is
released by flux couple. The tapped inductor
features a turn ratio similar to the transformer in
an isolated solution.
The nominal turns ratio is
n
N1 N2
1
N1
The duty cycle of the converter is extended by
the tapped inductor, which makes the improved
PF and THD available.
Like the transformer, the snubber is necessary
to clamp the voltage spike.
However, the non-dimmable solution usually
needs to cover the universal input range. The
input range is very wide, from 85VAC to
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15
MP4054 – NON-ISOLATED OFFLINE LED CONTROLLER WITH ACTIVE PFC
264VAC. MULT is used to detect the inputvoltage signal, but the resistor divider of MULT
is fixed. At high-line input, the signal for MULT
is very low, which results in an adverse affect
on the internal multiplier sampling; this affects
the PFC performance.
As shown in Figure 13, after adding the THD
improved circuitry, the MULT voltage rises. The
input current at the top of BUS is increased
while the input current at the zero-crossing is
reduced. This results in the input current
becoming more sinusoidal, improving THD.
Figure 12 shows an improved circuitry on the
MULT resistor divider; this adjusts the ratio of
the divider to enhance THD.
Operation of High-Side Buck/Buck-Boost
BUS
ZD1
RMULT1
RMULT3
MULT
Multiplier
RMULT2
COMP
CCOMP
Figure 12: THD Improved Circuitry
The ZD1 is a HV Zener diode. The common
voltage rating is from 80V to 130V.
At low line input, ZD1 does not conduct. The
MULT signal is:
VMULT
RMULT2
VBUS
RMULT1 RMULT2
When the input voltage rises above ZD1
threshold, RMULT3 is paralleled with RMULT1 to
increase the ratio of the divider; this raises the
MULT signal.
The MP4054 features FB pin, which is used to
receive the feedback signal of LED current
directly. So, the MP4054 can be designed in
high-side Buck or Buck-Boost application to
achieve excellent LED current accuracy
regulation, especially for very high load
regulation requirement.
Figure 17 is a 7.2W high-side Buck solution.
High-side Buck solution can achieve higher
efficiency. But the system just works @
VIN>VOUT based on step-down converter’s
operation. But the input voltage of PFC solution
is a sinusoid wave. When VIN1kV Surge Test
LED-
2
L3
2.2mH
D5
WSGC10MH
1000V/1A
C1
220nF/400V
2
3
R16
499k/1206
1
C11
3.3uF/400V
1
2
1
R3A
499k/1%/1206
R2
470k/1%/0.5W
L5
BEAD
1800@70MHz
R17
499k/1206
2
D6
1N5375B
82V
BD1
DF06S
4
CX1
100nF/275Vac
2
1
1
R15
R5
R8
2
1
D1
NS
VCC
2
2
1
R4
7.32k/1%
C4
2.2nF/50V
1
N
NTC1
NS
C5
NS
MULT
3
NTC
NC
4
COMP
GATE
CS/ZCD
FB
GND
R6
20/0805
8
1
R9
2.2k/1%
7
C7
10pF/50V
UUR2813
Q1
SMK0765F
650V/7A
R11
0.2/1%/1206
R10
NC/1206
6
R12
0.2/1%/1206
5
C6
2.2uF/10V
0805
85VAC-264VAC
C5
C12
68nF/630V
5
1
3
2
1
2
2
F1
250V/2A
U1
MP4027
MP4054
1
LED+
WUGF30J
600V/3A/SMB
Lm=287uH
2
C3
100pF/50V
RV1
L
R3B
499k/1%/1206
2
2
9.76k/1% BAV3004W
350V/0.2A
5.1M/1%
TVR10431
1
1
R7
0/1%/1206
D3
L4
600uH
D4
3
19Ts
1
20/1%/1206
1
36V/500mA
C9
330uF/63V
C8
68pF/630V/1206
2
D2
2
BAV3004W
350V/0.2A
C2
4.7uF/50V
30Ts
R13
100/1206
4
R18
2M/0.25W
L2
60mH
L1
600uH
2
C10
330uF/63V
R14
30k/1206
T1
1
Figure 16: T8 Driver, 85VAC to 265VAC Input, Low-side Buck-boost Converter, VO =36V, ILED=500mA
R3
5.1k/1206
L3
1.5mH/0.25A
C9
220uF/63V
STTH3R06U
C2
D5
R11
2/1%/1210
D1
STTH3R06U
600V/3A
R8
20/0805
R6
1M/1%/0.25W
R4
470k/0.5W
220nF/450V
BD1
MB6S
R12
NC
Q1
600V/4A
SMK0460I
D2
WUGC10JH
R14
1k/1%/1206
R2
5.1k/1206
1
D3
1
L1
0.47mH/0.9A
L2
0.47mH/0.9A
R1
5.1k/1206
BZT52C30
C3
4.7uF/50V
2
2
C4
27nF/50V
R5
7.68k/1%
RV1
SGND
C7
2.2nF/50V4
TVR10431
F1
250V/2A
3
2
SGND
NTC
NC
VCC
MULT
NTC
COMP
GATE
CS/ZCD
FB
GND
LED-1
GND
D4
WUGC10JH
600V/1A
R9
2.2k/1%
8
LED+1
36V/200mA
C8
220uF/63V
SGND
600V/1A
U1
MP4027
R13
30k/1206
R7
1k/1%
GND
CX1
22nF/275VAC
L4
825uH/EE13
R10
27k/1%
7
6
C6
470nF/16V
C1
10pF/50V
5
C5
2.2uF/6.3V
SGND
1
L
N
SGND
90VAC-265VAC
Figure 17: A19 Bulb Driver, 90VAC to 265VAC Input, High-side Buck Converter, VO =36V, ILED=200mA
MP4054 Rev. 1.0
12/25/2014
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18
MP4054 – NON-ISOLATED OFFLINE LED CONTROLLER WITH ACTIVE PFC
PACKAGE INFORMATION
TSOT23-8
See note 7
EXAMPLE
TOP MARK
PIN 1 ID
IAAAA
RECOMMENDED LAND PATTERN
TOP VIEW
SEATING PLANE
SEE DETAIL''A''
FRONT VIEW
SIDE VIEW
NOTE:
DETAIL ''A''
1) ALL DIMENSIONS ARE IN MILLIMETERS
.
2) PACKAGE LENGTH DOES NOT INCLUDE MOLD FLASH
,
PROTRUSION OR GATE BURR.
3) PACKAGE WIDTH DOES NOT INCLUDE INTERLEAD
FLASH OR PROTRUSION.
4) LEAD COPLANARITY(BOTTOM OF LEADS AFTER
FORMING) SHALL BE 0.10 MILLIMETERS MAX.
5) JEDEC REFERENCE IS MO-193, VARIATION BA.
6) DRAWING IS NOT TO SCALE.
7) PIN 1 IS LOWER LEFT PIN WHEN READING TOP MARK
FROM LEFT TO RIGHT, (SEE EXAMPLE TOP MARK)
NOTICE: The information in this document is subject to change without notice. Users should warrant and guarantee that third
party Intellectual Property rights are not infringed upon when integrating MPS products into any application. MPS will not
assume any legal responsibility for any said applications.
MP4054 Rev. 1.0
12/25/2014
www.MonolithicPower.com
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© 2014 MPS. All Rights Reserved.
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