MP6519
2.5V - 28V, 5A,
H-Bridge Current Regulator
The Future of Analog IC Technology
DESCRIPTION
FEATURES
The MP6519 is a monolithic, step-down,
current-source driver for applications that
require accurate and fast current-response
control. The MP6519 achieves up to 5A of
output current with excellent load and line
regulation over a wide input supply range.
The four integrated MOSFET H-bridge control
provide a fast dynamic load response and an
ultra-high efficiency solution. For ease of use,
the output polarity can be controlled by pulling
MODE high or low.
By setting the full-scale output current through
an external resistor, the output current can be
dimmed by the PWM input signal from 0 - 100%
of the full-scale current range.
Full protection features include load open, loadshort protection, over-current protection (OCP),
over-temperature protection (OTP), and input
over-voltage protection (OVP). The MP6519 is
available in a QFN-19 (3mmx3mm) package.
Wide 2.5V to 28V Operating Input Range
Up to 5A Output Load Current
± 2% Accuracy at Full-Scale Reference
65mΩ RDS(ON) for Each MOSFET of HBridge
100% Duty Cycle Operation of H-Bridge
30kHz to 300kHz Programmable Switching
Frequency
20kHz - 100kHz PWM Input for Current
Regulation
Programmable Full-Scale Current
Up to 94% Efficiency
Selectable Current Polarity Mode
Switching Auto-Disabled by PWM Input
Detection
1μA Shutdown Mode
Inherent Open-Load Protection
Cycle-by-Cycle Over-Current Protection
(OCP)
Output Short-Circuit Protection (SCP)
Input Over-Voltage Protection (OVP)
Over-Temperature Shutdown
Available in a QFN-19 (3mmx3mm)
Package
APPLICATIONS
Current Regulators
DC Motors
Solenoid/Actuators
All MPS parts are lead-free, halogen-free, and adhere to the RoHS
directive. For MPS green status, please visit the MPS website under
Quality Assurance. “MPS” and “The Future of Analog IC Technology” are
registered trademarks of Monolithic Power Systems, Inc.
MP6519 Rev.1.01
3/10/2020
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1
MP6519 – 2.5V TO 28V, 5A, H-BRIDGE CURRENT REGULATOR
TYPICAL APPLICATION
R2
BSTP
EN
C4
LP
VIN
2.5V to 28V
C1
Lo
Io
MODE
MP6519
LN
C5
R3
BSTN
PWM
FT
ISEN
IFB
FREQ
R1
R4
COMP
VCC
C2
AGND
ISET
C6
Optional
MP6519 Rev.1.01
3/10/2020
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C3
R5
2
MP6519 – 2.5V TO 28V, 5A, H-BRIDGE CURRENT REGULATOR
ORDERING INFORMATION
Part Number*
MP6519GQ
Package
QFN-19 (3mmx3mm)
Top Marking
See Below
* For Tape & Reel, add suffix –Z (e.g. MP6519GQ–Z)
TOP MARKING
ARU: Product code of MP6519GQ
Y: Year code
LLL: Lot number
PACKAGE REFERENCE
AGND
COMP
ISET
FREQ
PWM
VCC
FT
TOP VIEW
19
18
17
16
15
14
13
2
11
VIN
LN
3
10
LP
BSTN
4
5
6
7
8
9
BSTP
VIN
ISEN
MODE
ISEN
12
ISEN
1
EN
IFB
QFN-19 (3mmx3mm)
MP6519 Rev.1.01
3/10/2020
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3
MP6519 – 2.5V TO 28V, 5A, H-BRIDGE CURRENT REGULATOR
ABSOLUTE MAXIMUM RATINGS (1)
Supply voltage (VIN) ..................................... 35V
VLP, VLN .................................. -0.3V to VIN + 0.3V
VBSTP .......................................................VLP + 6V
VBSTN ...................................................... VLN + 6V
All other pins ................................... -0.3V to +6V
Continuous power dissipation (TA = +25°C) (2)
QFN-19 (3mmx3mm) .................................. 2.5W
Junction temperature ................................ 150°C
Lead temperature...................................... 260°C
Storage temperature .................-65°C to +150°C
Recommended Operating Conditions (3)
Supply voltage (VIN) ......................... 2.5V to 28V
Operating junction temp (TJ). ....-40°C to +125°C
MP6519 Rev.1.01
3/10/2020
θJA
θJC
Thermal Resistance (4)
QFN-19 (3mmx3mm) ............. 50 ....... 8 .... °C/W
NOTES:
1) Exceeding these ratings may damage the device.
2) The maximum allowable power dissipation is a function of the
maximum junction temperature TJ(MAX), the junction-toambient thermal resistance θJA, and the ambient temperature
TA. The maximum allowable continuous power dissipation at
any ambient temperature is calculated by PD(MAX)=(TJ(MAX)TA)/ θJA. Exceeding the maximum allowable power dissipation
produces an excessive die temperature, causing the regulator
to go into thermal shutdown. Internal thermal shutdown
circuitry protects the device from permanent damage.
3) The device is not guaranteed to function outside of its
operation conditions.
4) Measured on JESD51-7 4-layer board.
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4
MP6519 – 2.5V TO 28V, 5A, H-BRIDGE CURRENT REGULATOR
ELECTRICAL CHARACTERISTICS
VIN = 12V, TA = +25°C, unless otherwise noted.
Parameters
Symbol
Supply Voltage
VIN operating range
Turn-on threshold
Turn-on hysteretic voltage
IC Supply
Shutdown current
Quiescent current
VCC regulator voltage
VCC regulator drop output voltage
Logic
EN high threshold
EN low threshold
MODE input high threshold
MODE input low threshold
PWM high threshold
PWM low threshold
IC start-up delay
Switching Frequency
Switching frequency
Condition
VIN
VIN rising edge
IIN_SD
IIN_SBY
VVCC
EN = low
Standby mode
VIN > 5.2V
VIN < 5V, 20mA load
fs
Typ
2.5
VIN_ON
VIN_HY
VEN_High
VEN_Low
VEN_High
VEN_Low
VPWM_High
VPWM_Low
Tdelay
Min
2.3
0.15
4.5
370
5
100
Max
Units
28
2.45
V
V
V
1
450
5.5
μA
μA
V
mV
1.5
230
350
V
V
V
V
V
V
µs
0.4
1.5
0.4
1.5
0.4
EN active to switching
RFREQ = 75kΩ
RFREQ = 750kΩ
255
22
300
30
345
38
kHz
kHz
VREF_FB = 200mV
VREF_FB = 50mV
196
47
200
50
204
53
mV
mV
Current Reference
Current reference accuracy
Loop Compensation
Transconductance
Max source current
Max sink current
Power MOSFET
High-side MOSFET on resistance
Low-side MOSFET on resistance
Minimum on time
Bootstrap for High-Side Driver
Forward voltage for BST charge
BST UVLO
MP6519 Rev.1.01
3/10/2020
VREF_FB
GEA
270
50
50
42
42
Rising edge
65
65
200
0.5
2
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µA/V
µA
µA
93
93
mΩ
mΩ
ns
V
V
5
MP6519 – 2.5V TO 28V, 5A, H-BRIDGE CURRENT REGULATOR
ELECTRICAL CHARACTERISTICS (continued)
VIN = 12V, TA = +25°C, unless otherwise noted.
Parameters
Protection
Hiccup over-current threshold
Load short hiccup recovery timer
Latch-off over-current threshold
Input over-voltage threshold
Thermal shutdown (5)
Thermal shutdown hysteresis
Symbol
Condition
Min
Typ
Max
Units
RISET float
255
300
1
13
345
mV
ms
A
28.2
30
31
V
RISET float, RSEN = 40mΩ
VINOVP
150
20
°C
°C
NOTE:
5) Guaranteed by design.
MP6519 Rev.1.01
3/10/2020
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6
MP6519 – 2.5V TO 28V, 5A, H-BRIDGE CURRENT REGULATOR
TYPICAL PERFORMANCE CHARACTERISTICS
350
300
250
200
150
100
50
0
0 100 200 300 400 500 600 700 800
MP6519 Rev.1.01
3/10/2020
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MP6519 – 2.5V TO 28V, 5A, H-BRIDGE CURRENT REGULATOR
TYPICAL PERFORMANCE CHARACTERISTICS (continued)
VLP
20V/div.
VLP
20V/div.
VMODE
5V/div.
VMODE
5V/div.
VPWM
5V/div.
VPWM
5V/div.
IOUT
1A/div.
IOUT
1A/div.
VLP
20V/div.
VLP
20V/div.
VLP
20V/div.
VLN
20V/div.
VLN
20V/div.
VLN
20V/div.
VIN
20V/div.
VIN
20V/div.
IOUT
2A/div.
VIN
20V/div.
IOUT
2A/div.
IOUT
2A/div.
VLP
20V/div.
VLP
20V/div.
VLN
20V/div.
VLN
20V/div.
VEN
5V/div.
VEN
5V/div.
IOUT
2A/div.
IOUT
2A/div.
MP6519 Rev.1.01
3/10/2020
VLP
20V/div.
VLN
20V/div.
VIN
20V/div.
IOUT
2A/div.
VLP
20V/div.
VLN
20V/div.
VEN
5V/div.
IOUT
2A/div.
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MP6519 – 2.5V TO 28V, 5A, H-BRIDGE CURRENT REGULATOR
TYPICAL PERFORMANCE CHARACTERISTICS (continued)
VLP
20V/div.
VLP
20V/div.
VLP
20V/div.
VLN
20V/div.
VLN
20V/div.
VLN
20V/div.
VEN
5V/div.
IOUT
2A/div.
VPWM
5V/div.
VPWM
5V/div.
IOUT
1A/div.
IOUT
1A/div.
VLP
20V/div.
VLP
20V/div.
VLP
20V/div.
VLN
20V/div.
VLN
20V/div.
VLN
20V/div.
VPWM
5V/div.
VPWM
5V/div.
IOUT
1A/div.
VPWM
5V/div.
IOUT
2A/div.
IOUT
1A/div.
VLP
20V/div.
VLP
20V/div.
VLP
20V/div.
VLN
20V/div.
VLN
20V/div.
VLN
20V/div.
VPWM
5V/div.
IOUT
2A/div.
VPWM
5V/div.
VPWM
5V/div.
IOUT
2A/div.
IOUT
2A/div.
MP6519 Rev.1.01
3/10/2020
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9
MP6519 – 2.5V TO 28V, 5A, H-BRIDGE CURRENT REGULATOR
TYPICAL PERFORMANCE CHARACTERISTICS (continued)
VLP
20V/div.
VLP
20V/div.
VLN
20V/div.
VLN
20V/div.
VPWM
5V/div.
VPWM
5V/div.
IOUT
2A/div.
IOUT
2A/div.
MP6519 Rev.1.01
3/10/2020
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10
MP6519 – 2.5V TO 28V, 5A, H-BRIDGE CURRENT REGULATOR
PIN FUNCTIONS
Pin #
Name
1
2, 11
3
IFB
VIN
LN
4
BSTN
5
6, 7, 8
EN
ISEN
9
BSTP
10
LP
12
MODE
13
Description
Current sense signal feedback. Connect IFB and ISEN together.
Input supply.
Negative switching node of H-bridge.
Bootstrap pin for LN high-side MOSFET gate driver. Connect a capacitor between
BSTN and LN.
IC enable.
Current sense. Connect a current sensing resistor between ISEN and power ground.
Bootstrap pin for LP high-side MOSFET gate driver. Connect a capacitor between
BSTP and LP.
Positive switching node of H-bridge.
Current polarity setting. Assuming the current direction flowing from LP to LN is positive,
drive MODE high to run the current from LP to LN; drive MODE low to run the current from
LN to LP.
Fault indication output.
14
VCC
15
PWM
16
17
18
19
FREQ
ISET
COMP
AGND
MP6519 Rev.1.01
3/10/2020
is active low for fault conditions.
5V LDO output for internal driver and logic.
PWM signal input for current dimming. Apply a >20kHz PWM signal to PWM when
used.
Switching frequency setting. Connect a resistor from FREQ to GND.
Full-scale current reference setting. Connect a resistor to GND from ISET.
Loop compensation setting.
Ground for internal logic.
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11
MP6519 – 2.5V TO 28V, 5A, H-BRIDGE CURRENT REGULATOR
BLOCK DIAGRAM
Figure 1: Functional Block Diagram
MP6519 Rev.1.01
3/10/2020
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MP6519 – 2.5V TO 28V, 5A, H-BRIDGE CURRENT REGULATOR
OPERATION
The MP6519 is a current driver for applications
that need to control the accurate load current
and fast dynamic current response. The
MP6519 works in step-down mode with four
fully integrated MOSFET H-bridges to provide
small size and high efficiency. The full-scale
output current can be set by the external
resistor, and the current polarity can be
controlled by MODE to achieve a bidirectional
current setting.
H-Bridge General Operation
The MP6519 works in a four-MOSFET H-bridge
topology and uses pulse-width-modulation
(PWM) with average current control to achieve
a bidirectional current output and fast dynamic
current response. The switching frequency is
programmable from 30kHz to 300kHz.
In normal operation when enabled, the
MOSFETs M1 and M4 turn on and off in the
same sequence, and M2 and M3 turn on and
off in the same sequence. M1/M4 and M2/M3
turn on an off in complementary operation with
around 25ns of dead time to avoid device
damage caused by a shoot-through. There is
about 200ns of minimum on-time for all of the
MOSFET switches (M1/M4 and M2/M3).
Assuming the output current direction is set
positive by pulling MODE high, the output
current sensed by M2 and M4 is sent to the
error amplifier negative input. By comparing the
output current feedback signal with the current
reference signal at the error amplifier positive
node, the error amplifier outputs an appropriate
voltage value which is compared with a
sawtooth signal to provide a driver signal for
M1/M4 and M2/M3. The device can enter four
different modes described in the following
sections to control the working sequence.
Shutdown Mode
The MP6519 goes into shutdown mode when
pulling the EN signal low. In shutdown mode, all
circuits and blocks are disabled, and the
MP6519 consumes less than 1µA of shutdown
current. There is about 150ns of deglitch time
on EN to avoid a mistrigger.
MP6519 Rev.1.01
3/10/2020
Standby Mode
The MP6519 enters standby mode if either of
following conditions are met:
During start-up, the PWM signal on PWM is
low while EN is high.
After start-up in normal switching operation,
the PWM signal keeps low for >1ms if EN is
high.
In standby mode, the bandgap block and other
control blocks begin working except for the gate
drive block for the internal switching MOSFETs.
This way, the device stops switching to reduce
the quiescent current at no load. Meanwhile,
standby mode can minimize the time that the
output current tracks the reference signal of the
PWM input, which comes after the EN signal.
Since the MP6519 needs some time to
establish the bandgap signal and other
necessary control blocks, it is recommended
that the PWM signal comes at least 300µs after
the EN signal switches high.
Normal Switching Mode
If both the PWM and EN signals keep high, the
MP6519 enters normal switching mode
immediately. In this mode, the output feedback
current closely follows the reference signal,
which is received from the PWM input signal
through an R-C filter (see the Current Feedback
section on page 15 and the PWM Input Current
Dimming section on page 14).
The H-bridge MOSFETs work in a fixed
switching frequency (see the Switching
Frequency Setting section on page 14). The
output current polarity can be changed easily by
pulling MODE high or low (see the following
Current Polarity Mode section).
Current Polarity Mode
The current polarity is set by MODE. By pulling
MODE high, the current is positive, and the
current direction is from LP to LN. By pulling
MODE low, the current is negative, and the
current direction is from LN to LP. There is
about 150ns of deglitch on MODE to avoid a
mistrigger.
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13
MP6519 – 2.5V TO 28V, 5A, H-BRIDGE CURRENT REGULATOR
Full-Scale Current Setting
The full-scale current reference value is set by
connecting a resistor between ISET and GND.
When ISET is floating, the full-scale current
reference voltage is set to the default 200mV. If
a resistor is connected between ISET and GND,
the full-scale current reference voltage can be
reduced below 200mV to reduce power loss on
the feedback resistor. The IC needs about
0.3ms to detect whether a resistor is available
or not on ISET when the IC starts up for the first
time. During this time, the IC is not switching.
The relation of the full-scale current reference
voltage and RISET is shown in Equation (1):
V
REF_FULL
0.2*
40
RISET k
(1)
For example, if RISET is 80kΩ, the reference
voltage is 100mV. For better accuracy, 40kΩ to
80kΩ is recommended to achieve a 200mV to
100mV current reference voltage.
Start-Up Sequence
The IC needs about 0.3ms to detect
whether a resistor is available or not on
ISET when the IC starts up for the first time.
During this time, the IC is not switching. It is
recommended to apply a PWM signal at
least 0.3ms after the EN signal (see Figure
2 and Figure 3).
Figure 2: Positive Output Current Mode
EN
PWM
MODE
0
Output
Current
0
Figure 3: Negative Output Current Mode
Switching Frequency Setting
The H-bridge MOSFET switching frequency
is set by FREQ by connecting a resistor
between FREQ and GND. With a proper
resistor value, the switching frequency can
be set between 30kHz and 300kHz. A
higher switching frequency leads to a
smaller current ripple, but the MOSFET
switching loss is larger. Therefore, a tradeoff is needed for the design. The switching
frequency setting formula is shown in
Equation (2):
fFREQ
22500
RFREQ k
(2)
PWM Input Current Dimming
If the full-scale output current reference is set,
the actual output current reference sent to the
error amplifier can be further controlled by
applying a PWM input signal to PWM. This way,
VREF_FULL is chopped by the PWM input signal,
and the current reference voltage is received
from this chopped PWM voltage through the
internal low-pass filter. For a smaller output
current reference ripple, the input frequency of
PWM is recommended to be 20kHz to 100kHz.
Considering the full-scale reference, the
relationship between the actual output current
reference and duty cycle of the PWM input
(DPWM) is shown in Equation (3):
V
MP6519 Rev.1.01
3/10/2020
>1ms, enter standby mode
>0.3ms
REF_FB
0.2*
40
* DPWM
RISET k
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(3)
14
MP6519 – 2.5V TO 28V, 5A, H-BRIDGE CURRENT REGULATOR
Current Feedback
The current flowing through the load is sensed
through a resistor connected between IFB and
GND. This sensing voltage on IFB is sent to the
feedback block circuit and used to generate the
average feedback voltage (VIFB), which is equal
to the average output current multiplied by the
sensing resistor value (RIFB). VIFB is sent to the
error amplifier negative node and compared
with the output current reference voltage on the
error amplifier positive node. The output of the
error amplifier is COMP. The COMP voltage
(VCOMP) is used to generate the internal
MOSFET switch on and off times.
The simple block is shown in Figure 4.
Figure 4: Current Feedback Loop
VCC LDO Regulator
The IC employs an LDO regulator to provide a
constant voltage (5V) at VCC. The VCC voltage
is used for the internal power supply of the logic
circuit and driver circuit. When the input voltage
is high enough (larger than 5.2V), the VCC
output is 5V. When the input voltage drops
below 5V, the VCC voltage drops together with
the input voltage. The dropout voltage is around
100mV. If the VCC voltage drops below 2.15V,
the IC triggers a power reset sequence and
shuts down. The IC resumes normal operation
when VCC is higher than 2.3V.
High-Side MOSFET Driver
The high-side MOSFETs of M1 and M3 are Nchannel MOSFETs. When M1 and M3 turn on,
a bootstrap supply voltage across BSTP and
BSTN is needed. The bootstrap voltage is
generated by a combination of the internal
charge pump and a 5V VCC. This allows the IC
to work in 100% duty cycle to provide enough
driver voltage for the high-side MOSFETs (M1
and M3).
MP6519 Rev.1.01
3/10/2020
Over-Current Protection (OCP)
To provide robust protection during an overcurrent event, the IC uses a two-level protection
mode.
If the current flowing through the MOSFETs is
larger than 150% of the full-scale setting value
during two consecutive switching cycles, the IC
stops switching and triggers a power reset
sequence to restart after 1ms.
If the current flowing through the MOSFETs is
larger than 200% of the full-scale setting value,
the IC will latch off. If the high-side MOSFET
hits over-current, the high-side MOSFET is
turned off immediately and the Fault pin is
driven low. At the same time, the two low-side
MOSFETs are turned on for several
milliseconds and then the two low-side
MOSFETs are turned off and IC latches off. The
reverse will happen if the low-side MOSFET
hits over-current where the low-side MOSFET
is turned off immediately and the Fault pin is
driven low. And at the same time the high-side
MOSFETs are turned on for several
milliseconds and then the high-side MOSFETs
are turned off and IC latches off.
Input Over-Voltage Protection (OVP)
During operation, the energy stored in the load
current is delivered to the input side during the
free-wheeling time. If the input voltage and
output current are high enough, the energy sent
back to the input side causes the input voltage
to rise up. To avoid IC damage due to a high
voltage spike, the IC employs input voltage
protection. If the input voltage is higher than the
input
over-voltage
threshold
for
four
consecutive switching cycles, the IC stops
switching and latches off immediately.
Junction Over-Temperature Protection (OTP)
If the IC junction temperature (TJ) is higher than
150°C, the IC stops switching and resumes
normal operation when TJ drops below 130°C.
Fault Indication Output ( )
is a high-impedance
In normal operation,
open drain. If any fault occurs during operation,
is pulled low to indicate the fault condition
for the external system. Recycle the input
power or toggle the EN signal to remove the
fault latch condition.
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15
MP6519 – 2.5V TO 28V, 5A, H-BRIDGE CURRENT REGULATOR
Enable/Disable (EN)
To enable the IC, a logic-high signal needs to
be applied to EN, and the high-level signal time
needs to be higher than about 10µs. To shut
down the IC, pull EN to logic low, and the lowlevel signal needs to higher than 100ns.
MP6519 Rev.1.01
3/10/2020
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16
MP6519 – 2.5V TO 28V, 5A, H-BRIDGE CURRENT REGULATOR
APPLICATION INFORMATION
Selecting the Input Capacitor
The input capacitor reduces the surge current
drawn from the input supply and the switching
noise from the device. The input capacitor
impedance at the switching frequency should
be less than the input source impedance to
prevent the high-frequency switching current
from passing through to the input. Ceramic
capacitors with X5R or X7R dielectrics are
recommended for their low ESR and small
temperature coefficients. A higher value
capacitor is helpful for reducing input voltage
ripple and noise. For most applications, two
22µF ceramic capacitors in parallel are
sufficient. It is recommended to connect one
capacitor on each VIN pin.
Setting the Switching Frequency
A higher switching frequency leads to a smaller
current ripple but a higher switching loss of the
MOSFETs. Therefore, a trade-off is required for
the design. The switching frequency setting can
be calculated with Equation (7):
fFREQ
Selecting the Compensation Loop
The loop compensation components can be
used to make the closed loop stable and
achieve a better transient response (see Figure
5).
EA
If a resistor is connected between ISET and
GND, the full-scale output current reference
(VREF_FULL) can be calculated with Equation
(4):
(4)
If ISET is left floating, the current setting
formula is as shown in Equation (5):
I
OUT
0.2
RIFB
(5)
For example, if RISET is 80kΩ, then the
reference voltage is 100mV. For better
accuracy, 40kΩ to 80kΩ is recommended to
achieve a 200mV to 100mV current reference
voltage.
Setting the Feedback Resistor
The power loss of the sensing resistor can be
calculated with Equation (6):
P
LOSS_RIFB
VREF_FULL 2
RIFB
(6)
To guarantee a current reference, the
nominated power rating of the sensing resistor
is recommended to be twice the calculated
power loss with at least a 1% accuracy resistor.
MP6519 Rev.1.01
3/10/2020
(7)
Since the power loss of this resistor is small, a
resistor size 0603 or 0402 is sufficient.
Setting the Full-Scale Output Current
40
1
I OUT 0.2*
*
RISET k RIFB
22500
RFREQ k
IFB
gm
COMP
REF
Cz
Cp
R
Figure 5: Compensation Loop
The transfer function of the loop compensation
from the EA input to the EA output can be
calculated with Equation (8):
Gc (s)
gm
(Cz Cp )s
(1 sRCz )
CC
(1 sR z p )
Cz Cp
(8)
Where gm is the EA transconductance value.
The transfer function zero point is made up
from R and Cz. The pole point is made up from
R and the value of Cz in parallel with Cp.
Usually, for an inductive load with resistance,
the compensation zero can be set as the load
pole made of the load inductance (L) and its
resistance value. The compensation pole point
is usually set around the switching frequency
point to eliminate high-frequency noise. After
the zero and pole point of the compensation is
fixed, R can be used to increase the loop
bandwidth. 1/10 to 1/5 of the switching
frequency can be set as the close-loop
bandwidth to achieve a good system response.
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17
MP6519 – 2.5V TO 28V, 5A, H-BRIDGE CURRENT REGULATOR
PCB Layout Guidelines
Efficient PCB layout is critical for stable
operation. For best results, follow the guidelines
below.
1. Place the input capacitor close to VIN.
2. Use a wider copper for input, output, and
the GND connecting wire to improve
thermal performance.
3. Place as many GND vias near the output
and input capacitor as possible to improve
thermal performance.
4. Keep the IFB feedback signal far away from
noise sources.
MP6519 Rev.1.01
3/10/2020
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© 2020 MPS. All Rights Reserved.
18
MP6519 – 2.5V TO 28V, 5A, H-BRIDGE CURRENT REGULATOR
TYPICAL APPLICATION CIRCUIT
R2
BSTP
EN
C4
LP
VIN
2.5V to 28V
C1
Lo
Io
MODE
MP6519
LN
R3
C5
BSTN
PWM
FT
ISEN
IFB
FREQ
R1
R4
COMP
VCC
C2
AGND
ISET
C6
Optional
C3
R5
Figure 6: Typical Application
MP6519 Rev.1.01
3/10/2020
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© 2020 MPS. All Rights Reserved.
19
MP6519 – 2.5V TO 28V, 5A, H-BRIDGE CURRENT REGULATOR
PACKAGE INFORMATION
QFN-19 (3mmx3mm)
PIN 1 ID
MARKING
PIN 1 ID
° TYP
PIN 1 ID
INDEX AREA
BOTTOM VIEW
TOP VIEW
SIDE VIEW
NOTE:
°
1) LAND PATTERNS OF PIN2,3,10,11 AND 12 HAVE
THE SAME SHAPE.
2) ALL DIMENSIONS ARE IN MILLIMETERS.
3) LEAD COPLANARITY SHALL BE 0.10
MILLIMETERS MAX.
4) JEDEC REFERENCE IS MO-220.
5) DRAWING IS NOT TO SCALE.
RECOMMENDED LAND PATTERN
NOTICE: The information in this document is subject to change without notice. Please contact MPS for current specifications.
Users should warrant and guarantee that third party Intellectual Property rights are not infringed upon when integrating MPS
products into any application. MPS will not assume any legal responsibility for any said applications.
MP6519 Rev.1.01
3/10/2020
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© 2020 MPS. All Rights Reserved.
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