MP9487
100V Input, 3.5A, Switching Current Limit
Step-Down Converter
DESCRIPTION
FEATURES
The MP9487 is a high-voltage, step-down,
switching regulator that delivers up to 1A of
continuous current to the load. It integrates a
high-side, high-voltage, power MOSFET with a
current limit of 3.5A, typically. The wide 4.5V to
100V input range accommodates a variety of
step-down applications, making it ideal for
automotive, industry, and lighting applications.
Hysteretic voltage-mode control is employed for
very fast response. MPS’s proprietary feedback
control scheme minimizes the number of
required external components.
The switching frequency can be up to 1MHz,
allowing for small component size. Thermal
shutdown and short-circuit protection (SCP)
provide reliable and fault-tolerant operations. A
170µA quiescent current allows the MP9487 to
be used in battery-powered applications.
Wide 4.5V to 100V Input Range
3.5A Typical Peak Switching Current Limit
Hysteretic Control: No Compensation
Up to 1MHz Switching Frequency
Short-Circuit Protection (SCP) with
Integrated High-Side MOSFET
170μA Quiescent Current
Thermal Shutdown
Available in a SOIC-8 Package with an
Exposed Pad
APPLICATIONS
Scooters, E-Bike Control Power Supplies
Solar Energy Systems
Automotive System Power
Industrial Power Supplies
High-Power LED Drivers
All MPS parts are lead-free, halogen-free, and adhere to the RoHS directive. For
MPS green status, please visit the MPS website under Quality Assurance. “MPS”
and “The Future of Analog IC Technology” are registered trademarks of Monolithic
Power Systems, Inc.
The MP9487 is available in a SOIC-8 package
with an exposed pad.
TYPICAL APPLICATION
Efficiency vs. Output Current
C3
VIN
C1
EN
EN
TM
BST
D1
MP9487
GND
VOUT
SW
R1
FB
R2
C2
Efficiency(%)
VIN
L1
100
90
80
70
60
50
40
30
20
10
0
V OUT=5V, L=33uH
V in= 36V
V in= 60V
1
MP9487 Rev. 1.0
2/19/2019
10
100
Output Current(mA)
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1000
1
MP9487 – 100V INPUT, 3.5A, SWITCHING CURRENT LIMIT STEP-DOWN CONVERTER
ORDERING INFORMATION
Part Number*
Package
Top Marking
MP9487GN
SOIC-8 EP
See Below
* For Tape & Reel, add suffix –Z (e.g. MP9487GN–Z)
TOP MARKING
MP9487: part number
LLLLLLLL: lot number
MPS: MPS prefix
Y: year code
WW: week code
PACKAGE REFERENCE
TOP VIEW
FB
1
8
GND
NC
2
7
EN
VIN
3
6
TM
BST
4
5
SW
SOIC-8 EP
MP9487 Rev. 1.0
2/19/2019
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MP9487 – 100V INPUT, 3.5A, SWITCHING CURRENT LIMIT STEP-DOWN CONVERTER
PIN FUNCTIONS
SOIC-8 EP
Pin #
Name
1
FB
2
NC
3
VIN
4
BST
5
SW
6
TM
7
EN
8
GND
MP9487 Rev. 1.0
2/19/2019
Description
Feedback. FB is the input to the voltage hysteretic comparators. The average FB voltage
is maintained at 200mV by loop regulation.
No connection.
Input supply. VIN supplies power to all of the internal control circuitries, both BST
regulators, and the high-side switch. A decoupling capacitor to ground must be placed
close to VIN to minimize switching spikes.
Bootstrap. BST is the positive power supply for the internal, floating, high-side MOSFET
driver. Connect a bypass capacitor between BST and SW.
Switch node. SW is the output from the high-side switch. A low forward voltage Schottky
rectifier to ground is required. The rectifier must be placed close to SW to reduce switching
spikes.
Test mode pin for factory use only. Connect TM pin to EN pin in application.
Enable input. Pull EN below the specified threshold to shut down the MP9487. Pull EN
above the specified threshold or leave EN floating to enable the MP9487.
Ground. GND should be placed as close to the output capacitor as possible to avoid the
high-current switch paths. Connect the exposed pad to GND plane for optimal thermal
performance.
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MP9487 – 100V INPUT, 3.5A, SWITCHING CURRENT LIMIT STEP-DOWN CONVERTER
θJA
θJC
ABSOLUTE MAXIMUM RATINGS (1)
Thermal Resistance
Supply voltage (VIN) ...................-0.3V to +100V
Switch voltage (VSW) .................................. -0.5V
… ................. -0.5V(-7V for 10ns) to VIN + 0.5V
to VIN + 0.5V
BST to SW ......................................-0.3V to +6V
All other pins ...................................-0.3V to +6V
Junction temperature ................................150°C
Continuous power dissipation (TA = +25°C) (2)
............................................................... 3.6W (4)
Lead temperature .....................................260°C
Storage temperature ................ -65°C to +150°C
SOIC-8 EP
EV9487-N-00A (4) .................. 34 ........ 4 .... °C/W
JESD51-7 (5) .......................... 50 ....... 10... °C/W
Recommended Operating Conditions (3)
Supply voltage (VIN) ........................ 4.5V to 95V
EN and TM voltages ............................. 0V to 5V
Maximum switching frequency .................. 1MHz
Operating junction temp. (TJ) ... -40°C to +125°C
MP9487 Rev. 1.0
2/19/2019
NOTES:
1) Exceeding these ratings may damage the device.
2) The maximum allowable power dissipation is a function of the
maximum junction temperature TJ(MAX), the junction-toambient thermal resistance θJA, and the ambient temperature
TA. The maximum allowable continuous power dissipation at
any ambient temperature is calculated by PD(MAX)=(TJ(MAX)TA)/θJA. Exceeding the maximum allowable power dissipation
produces an excessive die temperature, causing the regulator
to go into thermal shutdown. Internal thermal shutdown
circuitry protects the device from permanent damage.
3) The device is not guaranteed to function outside of its operating
conditions.
4) Measured on EV9487-N-00A 2-layer 63mmx63mm board.
5) Measured on JESD51-7 4-layer board.
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4
MP9487 – 100V INPUT, 3.5A, SWITCHING CURRENT LIMIT STEP-DOWN CONVERTER
ELECTRICAL CHARACTERISTICS
VIN = 60V, TA = +25°C, unless otherwise noted. Specifications over temperature are guaranteed
by design and characterization.
Parameter
Symbol
VIN UVLO threshold
VIN UVLO hysteresis
Shutdown supply current
Quiescent supply current
Upper switch on resistance (6)
Upper switch leakage current
Current limit
EN up threshold
EN threshold hysteresis
EN input current
EN pull-up current
RDS(ON)
ISWLK
IPK
VENH
VENHY
IENI
IENS
Feedback voltage threshold high (6)
VFBH
Feedback voltage threshold low (6)
VFBL
FB input current
IFB
FB propagation delay to output
high(6)
TFBDH
FB propagation delay to output
high(6)
TFBDL
Thermal shutdown (7)
Condition
VEN = 0V
No load, TM = low,
VFB = 250mV
VBST - VSW = 5V
VEN = 0V, VSW = 0V
VFB = 0.15V
VEN = 5V
VEN = 2V
4.5V < VIN < 95V, VFB rising
from 0V until VSW < 30V
4.5V < VIN < 95V, VFB falling
from 0.25V until VSW > 30V
VFB = 5V or 0V
Falling edge of VFB from
0.25V to 0V to VSW rising
edge
Rising edge of VFB from 0V to
0.25V to VSW falling edge
Trigger thermal shutdown
Hysteresis
Min
Typ
Max
Units
3.6
4.0
0.4
2
4.35
5
V
V
µA
170
240
µA
2.9
1.4
500
0.01
3.5
1.55
320
0.01
2
1
3
mΩ
µA
A
V
mV
µA
µA
1
4.5
1.7
209
215
221
mV
179
185
191
mV
300
nA
-300
100
ns
100
ns
150
20
C
NOTES:
6) Guaranteed by design.
7) Guaranteed by characterization, not tested in production.
MP9487 Rev. 1.0
2/19/2019
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MP9487 – 100V INPUT, 3.5A, SWITCHING CURRENT LIMIT STEP-DOWN CONVERTER
TYPICAL CHARACTERISTICS
VIN = 60V, TA = +25°C, unless otherwise noted.
Shutdown Current vs. Input Voltage
Quiesvent Current vs. Input Voltage
EN=HIGH, TM=LOW, V FB=250mV
5
4.5
4
3.5
3
2.5
2
1.5
1
0.5
0
220
Input Current(uA)
Input Current(uA)
EN=LOW
4
17
30
43
56
69
82
210
200
190
180
95
4
17
30
Input Voltage(V)
56
69
82
95
Quiescent Current vs. Temperature
Shutdown Current vs. Temperature
V IN =95V, TM=LOW,EN=HIGH,VFB=250mV
V IN =95V, EN=LOW
20
220
16
210
In p ut C urrent(uA )
In p ut C urrent(uA )
43
Input Voltage(V)
12
8
4
200
190
180
0
-40 -20 0
-40 -20 0
20 40 60 80 100 120 140
20 40 60 80 100 120 140
Junction Temperature(oC)
J u nction Tem perature(o C )
EN Threshold vs. Temperature
UVLO Threshold vs. Temperature
2
4.5
rising
falling
4.1
3.9
1.7
E N T hreshold(V )
V in T hreshold(V )
4.3
1.4
1.1
rising
0.8
3.7
falling
0.5
3.5
-40 -20
0
20
40
60
80 100 120 140
J u nction Tem perature(o C )
MP9487 Rev. 1.0
2/19/2019
-40 -20
0
20
40
60
80 100 120 140
J u nction Tem perature(o C )
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MP9487 – 100V INPUT, 3.5A, SWITCHING CURRENT LIMIT STEP-DOWN CONVERTER
TYPICAL PERFORMANCE CHARACTERISTICS
VIN = 60V, VOUT = 5V, IOUT = 1A, L = 33μH, COUT = 100μF, TA = +25°C, unless otherwise noted.
100
90
80
70
60
50
40
30
20
10
0
Load Regulation
Regulation Error(%)
Efficiency(%)
Efficiency vs. Output Current
V in=36V
V in=60V
1
10
100
Output Current(mA)
1000
1
0.8
0.6
0.4
0.2
0
-0.2
-0.4
-0.6
-0.8
-1
V in= 36V
V in= 60V
0
200
400
600
800
1000
Output Current(mA)
Line Regulation
2
Iout= 1m A
Regulation Error(%)
1.5
Iout= 1000m A
1
0.5
0
-0.5
-1
-1.5
-2
0
10 20 30 40 50 60 70 80 90 100
Input Voltage(V)
MP9487 Rev. 1.0
2/19/2019
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MP9487 – 100V INPUT, 3.5A, SWITCHING CURRENT LIMIT STEP-DOWN CONVERTER
TYPICAL PERFORMANCE CHARACTERISTICS (continued)
VIN = 60V, VOUT = 5V, IOUT = 1A, L = 33μH, COUT = 100μF, TA = +25°C, unless otherwise noted.
Steady State
Steady State
IOUT = 0A
IOUT = 1A
CH1:
CH1:
VOUT/AC
VOUT/AC
100mV/div.
100mV/div.
CH2: VIN
50V/div.
CH2: VIN
50V/div.
CH3: VSW
50V/div.
CH3: VSW
50V/div.
CH4: IL
1A/div.
CH4: IL
2A/div.
4µs/div.
4µs/div.
Power On
Power On
IOUT = 0A
IOUT = 1A
CH1: VOUT
CH1: VOUT
2V/div.
2V/div.
CH2: VIN
50V/div.
CH2: VIN
50V/div.
CH3: VSW
50V/div.
CH3: VSW
50V/div.
CH4: IL
1A/div.
CH4: IL
1A/div.
20ms/div.
20ms/div.
Power Off
Power Off
IOUT = 0A
IOUT = 1A
CH1: VOUT
CH1: VOUT
2V/div.
2V/div.
CH2: VIN
50V/div.
CH2: VIN
50V/div.
CH3: VSW
10V/div.
CH3: VSW
50V/div.
CH4: IL
500mA/div.
CH4: IL
1A/div.
100ms/div.
MP9487 Rev. 1.0
2/19/2019
20ms/div.
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MP9487 – 100V INPUT, 3.5A, SWITCHING CURRENT LIMIT STEP-DOWN CONVERTER
TYPICAL PERFORMANCE CHARACTERISTICS (continued)
VIN = 60V, VOUT = 5V, IOUT = 1A, L = 33μH, COUT = 100μF, TA = +25°C, unless otherwise noted.
EN Start-Up
EN Start-Up
IOUT = 0A
IOUT = 1A
CH1: VOUT
CH1: VOUT
2V/div.
2V/div.
CH2: VEN
5V/div.
CH2: VEN
5V/div.
CH3: VSW
50V/div.
CH3: VSW
50V/div.
CH4: IL
1A/div.
CH4: IL
1A/div.
20ms/div.
20ms/div.
EN Shutdown
EN Shutdown
IOUT = 0A
IOUT = 1A
CH1: VOUT
2V/div.
CH1: VOUT
2V/div.
CH2: VEN
5V/div.
CH2: VEN
5V/div.
CH3: VSW
CH3: VSW
50V/div.
20V/div.
CH4: IL
1A/div.
CH4: IL
500mA/div.
100ms/div.
400µs/div.
SCP Entry
SCP Recovery
IOUT = 0A
IOUT = 0A
CH1: VOUT
CH1: VOUT
2V/div.
2V/div.
CH2: VIN
50V/div.
CH2: VIN
50V/div.
CH3: VSW
50V/div.
CH3: VSW
50V/div.
CH4: IL
1A/div.
CH4: IL
1A/div.
400µs/div.
MP9487 Rev. 1.0
2/19/2019
40ms/div.
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MP9487 – 100V INPUT, 3.5A, SWITCHING CURRENT LIMIT STEP-DOWN CONVERTER
TYPICAL PERFORMANCE CHARACTERISTICS (continued)
VIN = 60V, VOUT = 5V, IOUT = 1A, L = 33μH, COUT = 100μF, TA = +25°C, unless otherwise noted.
SCP Entry
SCP Recovery
IOUT = 1A
IOUT = 1A, E-load turn-on threshold = 0.32V
CH1: VOUT
CH1: VOUT
2V/div.
2V/div.
CH2: VIN
50V/div.
CH2: VIN
50V/div.
CH3: VSW
50V/div.
CH3: VSW
50V/div.
CH4: IL
2A/div.
CH4: IL
1A/div.
1ms/div.
20ms/div.
Load Transient
Load Transient
IOUT = 0A --> 1A @ 70mA/µs
IOUT=1A-->2A@70mA/µs
CH1:
VOUT/AC
50mV/div.
CH4: ILOAD
1A/div.
400µs/div.
MP9487 Rev. 1.0
2/19/2019
400µs/div.
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MP9487 – 100V INPUT, 3.5A, SWITCHING CURRENT LIMIT STEP-DOWN CONVERTER
BLOCK DIAGRAM
Figure 1: Function Block Diagram
MP9487 Rev. 1.0
2/19/2019
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MP9487 – 100V INPUT, 3.5A, SWITCHING CURRENT LIMIT STEP-DOWN CONVERTER
OPERATION
Hysteresis Current Control with Adaptive
Threshold Adjustment
The MP9487 operates in a hysteretic voltagecontrol mode to regulate the output voltage. FB
is connected to the tap of a resistor divider,
which determines the output voltage. The power
MOSFET is turned on when the FB voltage (VFB)
drops to 185mV and remains on until VFB rises to
215mV. The power MOSFET is turned off when
VFB rises to 215mV and remains off until VFB falls
to 185mV. The two thresholds of 215mV and
185mV are adjusted adaptively to compensate
for all the circuit delays, so the output voltage is
regulated with an average 200mV value at FB.
Enable (EN) Control
The MP9487 has a dedicated enable control pin
(EN) with positive logic. Its falling threshold is
1.23V, and its rising threshold is 1.55V (320mV
higher).
When floating, EN is pulled up to about 3V by an
internal 2µA current source, so it is enabled. A
current over 2µA is needed to pull EN down.
Floating Driver and Bootstrap Charging
The floating power MOSFET driver is powered
by an external bootstrap capacitor. This floating
driver has its own under-voltage lockout (UVLO)
protection. The UVLO rising threshold is 2.2V
with a threshold of 150mV.
Under-Voltage Lockout (UVLO)
Under-voltage lockout (UVLO) is implemented to
protect the chip from operating at an insufficient
supply voltage. The UVLO rising threshold is
about 4V, while its falling threshold is a
consistent 3.6V.
Thermal Shutdown
Thermal shutdown is implemented to prevent the
chip from operating at exceedingly high
temperatures. When the silicon die temperature
is higher than its upper threshold, the entire chip
shuts down. When the temperature is lower than
its lower threshold, the chip is enabled again.
Output Short Protection
The output voltage is well-regulated when VFB is
around 200mV. If the output is pulled low in overcurrent protection (OCP) or is shorted to GND
directly, VFB is low, even though the power
MOSFET is turned on. The MP9487 regards the
low VFB as a failure. The power MOSFET shuts
off if the failure time is longer than 10µs. The
MP9487 attempts operation again after a delay
of about 300µs.
The power MOSFET current is also accurately
sensed via a current sense MOSFET. If the
current is over the current limit, the IC is shut
down. This offers extra protection under outputshort conditions.
The bootstrap capacitor is charged and
regulated to about 5V by the dedicated internal
bootstrap regulator.
If the internal circuit does not have sufficient
voltage, and the bootstrap capacitor is not
sufficiently charged, extra external circuitry can
be used to ensure that the bootstrap voltage is in
the normal operating region. Refer to the
External Bootstrap Diode section on page 14 for
more details.
MP9487 Rev. 1.0
2/19/2019
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MP9487 – 100V INPUT, 3.5A, SWITCHING CURRENT LIMIT STEP-DOWN CONVERTER
APPLICATION INFORMATION
Setting the Output Voltage
The output voltage (VOUT) is set by a resistor
divider (R1 and R2) (see the Typical Application
on page 1). To achieve good noise immunity and
low power loss, R2 is recommended to be in the
range of 5kΩ to 50kΩ. R1 can then be
determined with Equation (1):
R1
VOUT VFB
R2
VFB
(1)
Where VFB is 0.2V, typically.
Output Capacitor and Frequency Setting
The output capacitor (COUT) is necessary for
achieving a smooth output voltage. The ESR of
the capacitor should be sufficiently large
compared to the capacitance; otherwise, the
system may behave in an unexpected way, and
the current ripple may be very high. VFB changes
from 185mV to 215mV when the power
MOSFET switches on. To charge the capacitor
and generate 215mV at FB, the system needs
ESR and some inductor current. For example,
for a 5V VOUT, if the forward capacitor is 0.1µF,
the suggested ESR range of the output capacitor
is 100mΩ to 250mΩ. Tantalum or aluminum
electrolytic capacitors with a small ceramic
capacitor are recommended.
A forward capacitor across R1 is recommended
when the output capacitor is tantalum or
aluminum electrolytic, which can set the desired
frequency if the output capacitor and ESR
cannot be changed. The forward capacitor can
reduce the output voltage ripple.
In some application, simply a forward capacitor
may not get proper frequency, then we can add
a forward resistor in series with the forward
capacitor or even more add a ceramic on the
output.
Selecting the Inductor
The inductor (L) is required to convert the
switching voltage to a smooth current to the load.
Although the output current is low, it is
recommended that the inductor current be
continuous in each switching period to prevent
reaching the current limit. Calculate the inductor
value with Equation (2):
MP9487 Rev. 1.0
2/19/2019
（V VOUT） VOUT
L IN
FSW IOUT VIN K
(2)
Where K is a coefficient of about 0.15 ~ 0.85.
Output Rectifier Diode
The output rectifier diode supplies current to the
inductor when the high-side switch is off. To
reduce losses due to the diode forward voltage
and recovery times, use a Schottky diode.
The average current through the diode can be
approximated with Equation (3):
V
ID IOUT x1 OUT
VIN
(3)
Choose a diode with a maximum reverse voltage
rating greater than the maximum input voltage
and a current rating is greater than the average
diode current.
Input Capacitor (CIN)
The input current to the step-down converter is
discontinuous and therefore requires a capacitor
to supply AC current to the step-down converter
while maintaining the DC input voltage. Use low
ESR capacitors for the best performance,
especially under high switching frequency
applications.
The RMS current through the input capacitor can
be calculated with Equation (4):
IIN _ AC IOUT x
VOUT
V
x(1 OUT )
VIN
VIN
(4)
With low ESR capacitors, the input voltage ripple
can be estimated with Equation (5):
VIN
IOUT VOUT
V
(1 OUT )
FSW CIN VIN
VIN
(5)
Choose an input capacitor with enough RMS
current rating and enough capacitance for small
input voltage ripples.
When electrolytic or tantalum capacitors are
applied, a small, high-quality ceramic capacitor
(i.e.: 0.1μF) should be placed as close to the IC
as possible.
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13
MP9487 – 100V INPUT, 3.5A, SWITCHING CURRENT LIMIT STEP-DOWN CONVERTER
External Bootstrap Diode
An external bootstrap diode may enhance the
efficiency of the converter (see Figure 2). An
external BST diode is recommended from the 5V
supply to BST in the following cases:
There is a 5V rail available in the system
VIN is not greater than 5V
VOUT is between 3.3V and 5V
This diode is also recommended for high duty
cycle operations (when VOUT / VIN > 65%) and
very high frequency (close to 1MHz)
applications.
The bootstrap diode can be a low-cost one, such
as IN4148 or BAT54.
5V
1. Place the input decoupling capacitor, catch
diode, and the MP9487 (VIN, SW, and
PGND) as close to each other as possible.
2. Keep the power traces very short and fairly
wide, especially for the SW node.
This can help greatly reduce voltage spikes
on the SW node and lower the EMI noise
level.
3. Run the feedback trace as far from the
inductor and noisy power traces (like the SW
node) as possible.
4. Place thermal vias with 15mil barrel diameter
and 40mil pitch (distance between the
centers) under the exposed pad to improve
thermal conduction.
BST
MP9487
PCB Layout Guidelines
Efficient PCB layout is critical for stable
operation. For best results, refer to Figure 3 and
follow the guidelines below.
0.1µF
SW
Via
Top Layer
Bottom Layer
VIN
C1A
C1B
C4
R1
R2
Figure 2: External Bootstrap Diode
U1
C3
C2B
D1
C2A
GND
L1
VOUT
Figure 3: Recommended Layout
MP9487 Rev. 1.0
2/19/2019
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14
MP9487 – 100V INPUT, 3.5A, SWITCHING CURRENT LIMIT STEP-DOWN CONVERTER
Design Example
Table 1 is a design example following the
application guidelines for the specifications
below.
Table 1: Design Example
8V to 95V
Vin
5V
Vout
0A to 1A
Continuous Iout
2A
Pulse Iout
The typical application circuit for VOUT = 5V in
Figure 4 shows the detailed application
schematic and is the basis for the typical
performance waveforms. For more detailed
device applications, please refer to the related
evaluation board datasheets.
MP9487 Rev. 1.0
2/19/2019
www.MonolithicPower.com
MPS Proprietary Information. Patent Protected. Unauthorized Photocopy and Duplication Prohibited.
© 2019 MPS. All Rights Reserved.
15
MP9487 – 100V INPUT, 3.5A, SWITCHING CURRENT LIMIT STEP-DOWN CONVERTER
TYPICAL APPLICATION CIRCUIT
C3 0.1µF
2.2µF/ 2.2µF/
100V 100V
VIN
C1A
C1B
EN
BST
VIN
EN
GND
C4 C2A
0.1µF 4.7µF
VOUT
SW
+
R1
D1
1A/100V 240kΩ
MP9487
TM
L1 33µH
C2B
100µF/10V
TR3C107K010C0200
FB
R2
10kΩ
Figure 4: VIN = 8 ~ 95V, VOUT = 5V, IOUT = 1A
C3 0.1uF
2.2uF/ 2.2uF/
100V 100V
VIN
C1A
EN
C1B
VIN
EN
TM
BST
C4 C2A
0.1uF 10uF
VOUT
SW
R1
D1
1A/100V 590k
MP9487
GND
L1 47uH
+
R3
C2B
100uF/25V
FB
R2
10k
4.7k
C2B: T491X107K025AT
Figure 5: VIN=15~95V, VOUT=12V, IOUT=1A
MP9487 Rev. 1.0
2/19/2019
www.MonolithicPower.com
MPS Proprietary Information. Patent Protected. Unauthorized Photocopy and Duplication Prohibited.
© 2019 MPS. All Rights Reserved.
16
MP9487 – 100V INPUT, 3.5A, SWITCHING CURRENT LIMIT STEP-DOWN CONVERTER
PACKAGE INFORMATION
SOIC-8 EP
NOTICE: The information in this document is subject to change without notice. Users should warrant and guarantee that third
party Intellectual Property rights are not infringed upon when integrating MPS products into any application. MPS will not assume
any legal responsibility for any said applications.
MP9487 Rev. 1.0
2/19/2019
www.MonolithicPower.com
MPS Proprietary Information. Patent Protected. Unauthorized Photocopy and Duplication Prohibited.
© 2019 MPS. All Rights Reserved.
17
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