74VHC4046N

74VHC4046 CMOS Phase Lock Loop October 1995 74VHC4046 CMOS Phase Lock Loop General Description The 74VHC4046 is a low power phase lock loop utilizing advanced silicon-gate CMOS technology to obtain high frequency operation both in the phase comparator and VCO sections This device contains a low power linear voltage controlled oscillator (VCO) a source follower and three phase comparators The three phase comparators have a common signal input and a common comparator input The signal input has a self biasing amplifier allowing signals to be either capacitively coupled to the phase comparators with a small signal or directly coupled with standard input logic levels This device is similar to the CD4046 except that the Zener diode of the metal gate CMOS device has been replaced with a third phase comparator Phase Comparator I is an exclusive OR (XOR) gate It provides a digital error signal that maintains a 90 phase shift between the VCO’s center frequency and the input signal (50% duty cycle input waveforms) This phase detector is more susceptible to locking onto harmonics of the input frequency than phase comparator I but provides better noise rejection Phase comparator III is an SR flip-flop gate It can be used to provide the phase comparator functions and is similar to the first comparator in performance Phase comparator II is an edge sensitive digital sequential network Two signal outputs are provided a comparator output and a phase pulse output The comparator output is a TRI-STATE output that provides a signal that locks the VCO output signal to the input signal with 0 phase shift between them This comparator is more susceptible to noise throwing the loop out of lock but is less likely to lock onto harmonics than the other two comparators In a typical application any one of the three comparators feed an external filter network which in turn feeds the VCO input This input is a very high impedance CMOS input which also drives the source follower The VCO’s operating frequency is set by three external components connected to the C1A C1B R1 and R2 pins An inhibit pin is provided to disable the VCO and the source follower providing a method of putting the IC in a low power state The source follower is a MOS transistor whose gate is connected to the VCO input and whose drain connects the Demodulator output This output normally is used by tying a resistor from pin 10 to ground and provides a means of looking at the VCO input without loading down modifying the characteristics of the PLL filter Features Y Y Y Y Y Low dynamic power consumption (VCC e 4 5V) Maximum VCO operating frequency 12 MHz (VCC e 4 5V) Fast comparator response time (VCC e 4 5V) Comparator I 25 ns Comparator II 30 ns Comparator III 25 ns VCO has high linearity and high temperature stability Pin and function compatible with the 74HC4046 Commercial 74VHC4046M 74VHC4046N Package Number M16A N16E Package Description 16-Lead Molded JEDEC SOIC 16-Lead Molded DIP Note Surface mount packages are also available on Tape and Reel Specify by appending the suffix letter ‘‘X’’ to the ordering code TRI-STATE is a registered trademark of National Semiconductor Corporation C1995 National Semiconductor Corporation TL F 11675 RRD-B30M125 Printed in U S A Block and Connection Diagrams TL F 11675 – 1 Pin Assignment for SOIC and PDIP TL F 11675 – 2 2 Absolute Maximum Ratings (Notes 1 2) b 0 5 to a 7 0V Supply Voltage (VCC) b 1 5 to VCC a 1 5V DC Input Voltage (VIN) b 0 5 to VCC a 0 5V DC Output Voltage (VOUT) g 20 mA Clamp Diode Current (IIK IOK) g 25 mA DC Output Current per pin (IOUT) g 50 mA DC VCC or GND Current per pin (ICC) b 65 C a 150 C Storage Temperature Range (TSTG) Power Dissipation (PD) (Note 3) 600 mW S O Package only 500 mW Lead Temperature (TL) (Soldering 10 seconds) 260 C DC Electrical Characteristics (Note 4) Symbol Parameter Conditions Operating Conditions Supply Voltage (VCC) DC Input or Output Voltage (VIN VOUT) Operating Temp Range (TA) 74VHC Input Rise or Fall Times (tr tf) VCC e 2 0V VCC e 4 5V VCC e 6 0V Min 2 0 Max 6 VCC Units V V b 40 a 85 C ns ns ns 1000 500 400 VCC 2 0V 4 5V 6 0V 2 0V 4 5V 6 0V TA e 25 C Typ 74VHC TA eb40 to 85 C Guaranteed Limits 15 3 15 42 05 1 35 18 19 44 59 3 84 5 34 01 01 01 0 33 0 33 g1 0 Units VIH Minimum High Level Input Voltage Maximum Low Level Input Voltage Minimum High Level Output Voltage VIN e VIH or VIL lIOUTl s20 mA 15 3 15 42 05 1 35 18 20 45 60 42 57 0 0 0 02 02 19 44 59 3 98 5 48 01 01 01 0 26 0 26 g0 1 V V V V V V V V V V V V V V V V mA mA mA mA mA VIL VOH 2 0V 4 5V 6 0V 4 5V 6 0V 2 0V 4 5V 6 0V 4 5V 6 0V 6 0V 6 0V 6 0V 6 0V 6 0V VIN e VIH or VIL lIOUTl s4 0 mA lIOUTl s5 2 mA VOL Maximum Low Level Output Voltage VIN e VIH or VIL lIOUTl s20 mA VIN e VIH or VIL lIOUTl s4 0 mA lIOUTl s5 2 mA IIN IIN IOZ ICC Maximum Input Current (Pins 3 5 9) Maximum Input Current (Pin 14) Maximum TRI-STATE Output Leakage Current (Pin 13) Maximum Quiescent Supply Current VIN e VCC or GND VIN e VCC or GND VOUT e VCC or GND VIN e VCC or GND IOUT e 0 mA VIN e VCC or GND Pin 14 Open Note 1 Maximum Ratings are those values beyond which damage to the device may occur Note 2 Unless otherwise specified all voltages are referenced to ground Note 3 Power Dissipation temperature derating 20 50 g 0 25 80 g2 5 30 600 40 750 65 1200 plastic ‘‘N’’ package b 12 mW C from 65 C to 85 C Note 4 For a power supply of 5V g 10% the worst case output voltages (VOH and VOL) occur for VHC at 4 5V Thus the 4 5V values should be used when designing with this supply Worst case VIH and VIL occur at VCC e 5 5V and 4 5V respectively (The VIH value at 5 5V is 3 85V ) The worst case leakage current (IIN ICC and IOZ) occur for CMOS at the higher voltage and so the 6 0V values should be used 3 AC Electrical Characteristics VCC e 2 0 to 6 0V Symbol Parameters AC Coupled Input Sensitivity Signal In tr tf Maximum Output Rise and Fall Time Maximum Input Capacitance Maximum Propagation Delay Conditions C (series) e 100 pF fIN e 500 kHz CL e 50 pF tr e tf e 6 ns (unless otherwise specified ) VCC 2 0V 4 5V 6 0V 2 0V 4 5V 6 0V 7 T e 25C Typ 25 50 135 30 9 8 100 150 250 75 15 12 74VHC 150 200 300 95 19 15 Units mV mV mV ns ns ns pF Guaranteed Limits CIN Phase Comparator I tPHL tPLH 3 3V 4 5V 6 0V 3 3V 4 5V 6 0V 3 3V 4 5V 6 0V 3 3V 4 5V 6 0V 3 3V 4 5V 6 0V 65 25 20 75 25 22 88 30 25 90 32 28 100 34 27 117 40 34 130 45 38 140 48 41 140 48 41 146 50 43 146 50 43 160 56 48 175 60 51 175 60 51 180 63 53 ns ns ns ns ns ns ns ns ns ns ns ns ns ns ns Phase Comparator II tPZL Maximum TRISTATE Enable Time Maximum TRISTATE Enable Time Maximum TRISTATE Disable Time Maximum Propagation Delay High to Low to Phase Pulses Maximum Propagation Delay Maximum Power Dissipation Capacitance Maximum Operating Frequency All Comparators VIN e VCC and GND tPZH tPHZ tPLZ tPHL tPLH Phase Comparator III tPHL tPLH 3 3V 4 5V 6 0V 75 25 22 130 117 40 34 146 50 43 ns ns ns pF CPD Voltage Controlled Oscillator (Specified to operate from VCC e 3 0V to 6 0V) fMAX C1 e 50 pF R1 e 100X R2 e % VCOin e VCC C1 e 0 pF R1 e 100X VCOin e VCC 4 5V 6 0V 4 5V 60 7 11 12 14 50 Rs e 20 kX Rs e 20 kX VCOin e 1 75V 2 25V 2 75V 4 5V 4 5V 0 65 01 0 75 V 0 75 13 15 45 7 MHz MHz MHz MHz % V Duty Cycle Demodulator Output Offset Voltage VCOin – Vdem Offset Variation 4 Typical Performance Characteristics Typical Center Frequency vs R1 C1 VCC e 4 5V Typical Center Frequency vs R1 C1 VCC e 6V TL F 11675 – 3 TL F 11675 – 4 Typical Offset Frequency vs R2 C1 VCC e 4 5V Typical Offset Frequency vs R2 C1 VCC e 6V TL F 11675 – 5 TL F 11675 – 6 5 Typical Performance Characteristics VHC4046 Typical VCO Power Dissipation Center Frequency vs R1 (Continued) VHC4046 Typical VCO Power Dissipation fmin vs R2 TL F 11675–7 TL F 11675 – 8 VHC4046 VCOin vs fout VCC e 4 5V VHC4046 VCOin vs fout VCC e 4 5V TL F 11675–9 TL F 11675 – 10 VHC4046 VCOout vs Temperature VCC e 4 5V VHC4046 VCOout vs Temperature VCC e 6V TL F 11675–11 TL F 11675 – 12 6 Typical Performance Characteristics VHC4046 Typical Source Follower Power Dissipation vs RS (Continued) Typical fmax fmin vs R2 R1 VCC e 4 5V 6V fmax fmin TL F 11675 – 13 TL F 11675 – 14 VHC4046 Typical VCO Linearity vs R1 C1 VHC4046 Typical VCO Linearity vs R1 C1 TL F 11675 – 15 TL F 11675 – 16 VCO WITHOUT OFFSET R2 e % VCO WITH OFFSET (a) FIGURE 1 TL F 11675 – 17 7 Comparator I R2 e % – Given f0 – Use f0 with curve titled center frequency vs R1 C to determine R1 and C1 R2 i % –Given f0 and fL –Calculate fmin from the equation fmin e fo b fL –Use fmin with curve titled offset frequency vs R2 C to determine R2 and C1 –Calculate fmax fmin from the equation fmax fmin e fo a fL fo b fL –Use fmax fmin with curve titled fmax fmin vs R2 R1 to determine ratio R2 R1 to obtain R1 (b) FIGURE 1 (Continued) R2 e % Comparator II – Given fmax – Calculate f0 from the equation fo e fmax 2 – Use f0 with curve titled center frequency vs R1 C to determine R1 and C1 III R2 i % – Given fmin and fmax – Use fmin with curve titled offset frequency vs R2 C to determine R2 and C1 – Calculate fmax fmin – Use fmax fmin with curve titled fmax fmin vs R2 R1 to determine ratio R2 R1 to obtain R1 Detailed Circuit Description VOLTAGE CONTROLLED OSCILLATOR SOURCE FOLLOWER The VCO requires two or three external components to operate These are R1 R2 C1 Resistor R1 and capacitor C1 are selected to determine the center frequency of the VCO R1 controls the lock range As R1’s resistance decreases the range of fmin to fmax increases Thus the VCO’s gain decreases As C1 is changed the offset (if used) of R2 and the center frequency is changed (See typical performance curves) R2 can be used to set the offset frequency with 0V at VCO input If R2 is omitted the VCO range is from 0Hz As R2 is decreased the offset frequency is increased The effect of R2 is shown in the design information table and typical performance curves By increasing the value of R2 the lock range of the PLL is offset above 0Hz and the gain (Volts rad ) does not change In general when offset is desired R2 and C1 should be chosen first and then R1 should be chosen to obtain the proper center frequency Internally the resistors set a current in a current mirror as shown in Figure 1 The mirrored current drives one side of TL F 11675 – 18 FIGURE 2 Logic Diagram for VCO 8 Detailed Circuit Description (Continued) the capacitor once the capacitor charges up to the threshold of the schmitt trigger the oscillator logic flips the capacitor over and causes the mirror to charge the opposite side of the capacitor The output from the internal logic is then taken to pin 4 The input to the VCO is a very high impedance CMOS input and so it will not load down the loop filter easing the filters design In order to make signals at the VCO input accessible without degrading the loop performance a source follower transistor is provided This transistor can be used by connecting a resistor to ground and its drain output will follow the VCO input signal An inhibit signal is provided to allow disabling of the VCO and the source follower This is useful if the internal VCO is not being used A logic high on inhibit disables the VCO and source follower The output of the VCO is a standard high speed CMOS output with an equivalent LSTTL fanout of 10 The VCO output is approximately a square wave This output can either directly feed the comparator input of the phase comparators or feed external prescalers (counters) to enable frequency synthesis PHASE COMPARATORS All three phase comparators share two inputs Signal In and Comparator In The Signal In has a special DC bias network that enables AC coupling of input signals If the signals are not AC coupled then this input requires logic levels the same as standard 74VHC The Comparator input is a standard digital input Both input structures are shown in Figure 3 The outputs of these comparators are essentially standard 74VHC voltage outputs (Comparator II is TRI-STATE ) TL F 11675-19 FIGURE 3 Logic Diagram for Phase Comparator I and the Common Input Circuit for All Three Comparators TL F 11675 – 20 FIGURE 4 Typical Phase Comparator I Waveforms 9 Detailed Circuit Description (Continued) Thus in normal operation VCC and ground voltage levels are fed to the loop filter This differs from some phase detectors which supply a current output to the loop filter and this should be considered in the design (The CD4046 also provides a voltage ) Figure 5 shows the state tables for all three comparators PHASE COMPARATOR I This comparator is a simple XOR gate similar to the 54 74HC86 and its operation is similar to an overdriven balanced modulator To maximize lock range the input frequencies must have a 50% duty cycle Typical input and output waveforms are shown in Figure 4 The output of the phase detector feeds the loop filter which averages the output voltage The frequency range upon which the PLL will lock onto if initially out of lock is defined as the capture range The capture range for phase detector I is dependent on the loop filter employed The capture range can be as large as the lock range which is equal to the VCO frequency range To see how the detector operates refer to Figure 4 When two square wave inputs are applied to this comparator an output waveform whose duty cycle is dependent on the phase difference between the two signals results As the phase difference increases the output duty cycle increases and the voltage after the loop filter increases Thus in order to achieve lock when the PLL input frequency increases the VCO input voltage must increase and the phase difference between comparator in and signal in will increase At an input frequency equal fmin the VCO input is at 0V and this requires the phase detector output to be ground hence the two input signals must be in phase When the input frequency is fmax then the VCO input must be VCC and the phase detector inputs must be 180 out of phase The XOR is more susceptible to locking onto harmonics of the signal input than the digital phase detector II This can be seen by noticing that a signal 2 times the VCO frequency results in the same output duty cycle as a signal equal the VCO frequency The difference is that the output frequency of the 2f example is twice that of the other example The loop filter and the VCO range should be designed to prevent locking on to harmonics PHASE COMPARATOR II This detector is a digital memory network It consists of four flip-flops and some gating logic a three state output and a phase pulse output as shown in Figure 6 This comparator acts only on the positive edges of the input signals and is thus independent of signal duty cycle Phase comparator II operates in such a way as to force the PLL into lock with 0 phase difference between the VCO output and the signal input positive waveform edges Figure 7 shows some typical loop waveforms First assume that the signal input phase is leading the comparator input This Phase Comparator State Diagrams TL F 11675 – 21 FIGURE 5 PLL State Tables 10 Detailed Circuit Description (Continued) TL F 11675 – 22 FIGURE 6 Logic Diagram for Phase Comparator II TL F 11675 – 23 FIGURE 7 Typical Phase Comparator II Output Waveforms 11 Detailed Circuit Description (Continued) means that the VCO’s frequency must be increased to bring its leading edge into proper phase alignment Thus the phase detector II output is set high This will cause the loop filter to charge up the VCO input increasing the VCO frequency Once the leading edge of the comparator input is detected the output goes TRI-STATE holding the VCO input at the loop filter voltage If the VCO still lags the signal then the phase detector will again charge up to VCO input for the time between the leading edges of both waveforms If the VCO leads the signal then when the leading edge of the VCO is seen the output of the phase comparator goes low This discharges the loop filter until the leading edge of the signal is detected at which time the output TRI-STATE itself again This has the effect of slowing down the VCO to again make the rising edges of both waveform coincident When the PLL is out of lock the VCO will be running either slower or faster than the signal input If it is running slower the phase detector will see more signal rising edges and so the output of the phase comparator will be high a majority of the time raising the VCO’s frequency Conversely if the VCO is running faster than the signal the output of the detector will be low most of the time and the VCO’s output frequency will be decreased As one can see when the PLL is locked the output of phase comparator II will be almost always TRI-STATE except for minor corrections at the leading edge of the waveforms When the detector is TRI-STATE the phase pulse output is high This output can be used to determine when the PLL is in the locked condition This detector has several interesting characteristics Over the entire VCO frequency range there is no phase difference between the comparator input and the signal input The lock range of the PLL is the same as the capture range Minimal power is consumed in the loop filter since in lock the detector output is a high impedance Also when no signal is present the detector will see only VCO leading edges and so the comparator output will stay low forcing the VCO to fmin operating frequency Phase comparator II is more susceptible to noise causing the phase lock loop to unlock If a noise pulse is seen on the signal input the comparator treats it as another positive edge of the signal and will cause the output to go high until the VCO leading edge is seen potentially for a whole signal input period This would cause the VCO to speed up during that time When using the phase comparator I the output of that phase detector would be disturbed for only the short duration of the noise spike and would cause less upset PHASE COMPARATOR III This comparator is a simple S-R Flip-Flop which can function as a phase comparator Figure 8 It has some similar characteristics to the edge sensitive comparator To see how this detector works assume input pulses are applied to the signal and comparator inputs as shown in Figure 9 When the signal input leads the comparator input the flop is set This will charge up the loop filter and cause the VCO to speed up bringing the comparator into phase with the signal input When using short pulses as input this comparator behaves very similar to the second comparator But one can see that if the signal input is a long pulse the output of the comparator will be forced to a one no matter how many comparator input pulses are received Also if the VCO input is a square wave (as it is) and the signal input is pulse then the VCO will force the comparator output low much of the time Therefore it is ideal to condition the signal and comparator input to short pulses This is most easily done by using a series capacitor TL F 11675 – 24 FIGURE 8 Phase Comparator III Logic Diagram TL F 11675 – 25 FIGURE 9 Typical Waveforms for Phase Comparator III 12 Ordering Information The device number is used to form part of a simplified purchasing code where the package type and temperature range are defined as follows TL F 11675 – 26 Physical Dimensions inches (millimeters) 16-Lead (0 150 Wide) Molded Small Outline Package JEDEC Order Number 74VHC4046M NS Package Number M16A 13 74VHC4046 CMOS Phase Lock Loop Physical Dimensions inches (millimeters) (Continued) Molded Dual-In-Line Package (N) Order Number 74VHC4046N NS Package Number N16E LIFE SUPPORT POLICY NATIONAL’S PRODUCTS ARE NOT AUTHORIZED FOR USE AS CRITICAL COMPONENTS IN LIFE SUPPORT DEVICES OR SYSTEMS WITHOUT THE EXPRESS WRITTEN APPROVAL OF THE PRESIDENT OF NATIONAL SEMICONDUCTOR CORPORATION As used herein 1 Life support devices or systems are devices or systems which (a) are intended for surgical implant into the body or (b) support or sustain life and whose failure to perform when properly used in accordance with instructions for use provided in the labeling can be reasonably expected to result in a significant injury to the user National Semiconductor Corporation 1111 West Bardin Road Arlington TX 76017 Tel 1(800) 272-9959 Fax 1(800) 737-7018 2 A critical component is any component of a life support device or system whose failure to perform can be reasonably expected to cause the failure of the life support device or system or to affect its safety or effectiveness National Semiconductor Europe Fax (a49) 0-180-530 85 86 Email cnjwge tevm2 nsc com Deutsch Tel (a49) 0-180-530 85 85 English Tel (a49) 0-180-532 78 32 Fran ais Tel (a49) 0-180-532 93 58 Italiano Tel (a49) 0-180-534 16 80 National Semiconductor Hong Kong Ltd 13th Floor Straight Block Ocean Centre 5 Canton Rd Tsimshatsui Kowloon Hong Kong Tel (852) 2737-1600 Fax (852) 2736-9960 National Semiconductor Japan Ltd Tel 81-043-299-2309 Fax 81-043-299-2408 National does not assume any responsibility for use of any circuitry described no circuit patent licenses are implied and National reserves the right at any time without notice to change said circuitry and specifications