LM7341MFE

LM7341 Rail-to-Rail Input/Output, ±15V, 4.6 MHz GBW, Operational Amplifier in SOT-23 Package October 13, 2008 LM7341 Rail-to-Rail Input/Output ±15V, 4.6 MHz GBW, Operational Amplifier in SOT-23 Package General Description The LM7341 is a rail-to-rail input and output amplifier in a small SOT-23 package with a wide supply voltage and temperature range. The LM7341 has a 4.6 MHz gain bandwidth and a 1.9 volt per microsecond slew rate, and draws 0.75 mA of supply current at no load. The LM7341 is tested at −40°C, 125°C and 25°C with modern automatic test equipment. Detailed performance specifications at 2.7V, ±5V, and ±15V and over a wide temperature range make the LM7341 a good choice for automotive, industrial, and other demanding applications. Greater than rail-to-rail input common mode range with a minimum 76 dB of common mode rejection at ±15V makes the LM7341 a good choice for both high and low side sensing applications. LM7341 performance is consistent over a wide voltage range, making the part useful for applications where the supply voltage can change, such as automotive electrical systems and battery powered electronics. The LM7341 uses a small SOT23-5 package, which takes up little board space, and can be placed near signal sources to reduce noise pickup. Features (VS = ±15V, TA = 25°C, typical values.) ■ Tiny 5-pin SOT-23 package saves space −15.3V to 15.3V ■ Greater than rail-to-rail input CMVR −14.84V to 14.86V ■ Rail-to-rail output swing 0.7 mA ■ Supply current 4.6 MHz ■ Gain bandwidth 1.9 V/µs ■ Slew Rate 2.7V to 32V ■ Wide supply range 106 dB ■ High power supply rejection ratio 115 dB ■ High common mode rejection ratio 106 dB ■ Excellent gain −40°C to 125°C ■ Temperature range ■ Tested at −40°C, 125°C and 25°C at 2.7V, ±5V and ±15V Applications ■ ■ ■ ■ ■ ■ ■ ■ ■ ■ ■ Automotive Industrial robotics Sensor output buffers Multiple voltage power supplies Reverse biasing of photodiodes Low current optocouplers High side sensing Comparator Battery chargers Test point output buffers Below ground current sensing Typical Performance Characteristics Open Loop Frequency Response Open Loop Frequency Response 20206046 20206047 © 2008 National Semiconductor Corporation 202060 www.national.com LM7341 Absolute Maximum Ratings (Note 1) If Military/Aerospace specified devices are required, please contact the National Semiconductor Sales Office/ Distributors for availability and specifications. ESD Tolerance (Note 2) Human Body Model Machine Model Charge-Device Model VIN Differential Voltage at Input/Output Pin Supply Voltage (VS = V+ − V−) Input Current Output Current(Note 3) 2000V 200V 1000V ±15V (V+) + 0.3V, (V−) −0.3V 35V ±10 mA ±20 mA Power Supply Current Soldering Information Infrared or Convection (20 sec) Wave Soldering Lead Temp. (10 sec.) Storage Temperature Range Junction Temperature (Note 4) 25 mA 235°C 260°C −65°C to 150°C 150°C Operating Ratings Supply Voltage (VS = − Temperature Range (Note 4) V+ V−) (Note 1) 2.5V to 32V −40°C to 125°C 325°C/W Package Thermal Resistance (θJA) 5-Pin SOT-23 2.7V Electrical Characteristics Unless otherwise specified, all limits guaranteed for TA = 25°C, V+ = 2.7V, V− = 0V, VCM = 0.5V, VOUT = 1.35V and RL > 1 MΩ to 1.35V. Boldface limits apply at the temperature extremes Symbol VOS TCVOS IB Parameter Input Offset Voltage Input Offset Voltage Temperature Drift Input Bias Current VCM = 0.5V VCM = 2.2V IOS CMRR Input Offset Current Common Mode Rejection Ratio VCM = 0.5V and VCM = 2.2V 0V ≤ VCM ≤ 1.0V 0V ≤ VCM ≤ 2.7V PSRR CMVR AVOL VOUT Power Supply Rejection Ratio Common Mode Voltage Range Open Loop Voltage Gain Output Voltage Swing High 2.7V ≤ VS ≤ 30V VCM = 0.5V CMRR > 60 dB 2.7 0.5V ≤ VO ≤ 2.2V RL = 10 kΩ to 1.35V RL = 10 kΩ to 1.35V VID = 100 mV RL = 2 kΩ to 1.35V VID = 100 mV Output Voltage Swing Low RL = 10 kΩ to 1.35V VID = −100 mV RL = 2 kΩ to 1.35V VID = −100 mV IOUT Output Current Sourcing, VOUT = 0V VID = 200 mV Sinking, VOUT = 0V VID = −200 mV IS SR Supply Current Slew Rate VCM = 0.5V and VCM = 2.2V ±1V Step 6 4 5 3 12 8 82 80 62 60 86 84 −180 −200 Conditions VCM = 0.5V and VCM = 2.2V Min (Note 6) −4 −5 Typ (Note 5) ±0.2 ±2 −90 30 1 106 80 106 −0.3 3.0 65 50 95 55 100 12 10 0.6 1.5 0.9 1.0 mA 120 150 150 200 120 150 150 200 0.0 dB 60 70 40 50 nA Max (Note 6) +4 +5 Units mV μV/°C nA dB V V/mV mV from either rail mA V/μs www.national.com 2 LM7341 Symbol GBW en in THD+N tPD tr tf Parameter Gain Bandwidth Input Referred Voltage Noise Density Input Referred Voltage Noise Density Total Harmonic Distortion + Noise Propagation Delay Rise Time Fall Time Conditions f = 100 kHz, RL = 100 kΩ f = 1 kHz f = 1 kHz f = 10 kHz Overdrive = 50 mV (Note 7) Overdrive = 1V (Note 7) 20% to 80% (Note 7) 80% to 20% (Note 7) Min (Note 6) Typ (Note 5) 3.6 35 0.28 −66 4 3 1 1 Max (Note 6) Units MHz nV/ pA/ dB µs µs µs ±5V Electrical Characteristics Unless otherwise specified, all limits guaranteed for TA = 25°C, V+ = +5V, V− = −5V, VCM = VOUT = 0V and RL > 1 MΩ to 0V. Boldface limits apply at the temperature extremes. Symbol VOS TCVOS IB Parameter Input Offset Voltage Input Offset Voltage Temperature Drift Input Bias Current VCM = −4.5V VCM = 4.5V IOS CMRR Input Offset Current Common Mode Rejection Ratio VCM = −4.5V and VCM = 4.5V −5V ≤ VCM ≤ 3V −5V ≤ VCM ≤ 5V PSRR CMVR AVOL VOUT Power Supply Rejection Ratio Common Mode Voltage Range Open Loop Voltage Gain Output Voltage Swing High 2.7V ≤ VS ≤ 30V, VCM = −4.5V CMRR ≥ 65 dB 5.0 −4V ≤ VO ≤ 4V RL = 10 kΩ to 0V RL = 10 kΩ to 0V, VID = 100 mV RL = 2 kΩ to 0V, VID = 100 mV Output Voltage Swing Low RL = 10 kΩ to 0V VID = −100 mV RL = 2 kΩ to 0V VID = −100 mV IOUT Output Current Sourcing, VOUT = −5V VID = 200 mV Sinking, VOUT = 5V VID = −200 mV IS SR GBW Supply Current Slew Rate Gain Bandwidth VCM = −4.5V and VCM = 4.5V ±4V Step f = 100 kHz, RL = 100 kΩ 6 4 6 4 20 12 84 82 72 70 86 84 −200 −250 Conditions VCM = −4.5V and VCM = 4.5V Min (Note 6) −4 −5 Typ (Note 5) ±0.2 ±2 −95 35 1 112 92 106 −5.3 5.3 110 80 170 90 210 11 12 0.65 1.7 4.0 1.0 1.1 mA 150 200 300 400 150 200 300 400 −5.0 dB 70 80 40 50 nA Max (Note 6) +4 +5 Units mV μV/°C nA dB V V/mV mV from either rail mA V/μs MHz 3 www.national.com LM7341 Symbol en in THD+N tPD tr tf Parameter Input Referred Voltage Noise Density Input Referred Voltage Noise Density Total Harmonic Distortion + Noise Propagation Delay Rise Time Fall Time f = 1 kHz f = 1 kHz Conditions Min (Note 6) Typ (Note 5) 33 0.26 −66 8 6 5 5 Max (Note 6) Units nV/ pA/ dB µs µs µs f = 10 kHz Overdrive = 50 mV (Note 7) Overdrive = 1V (Note 7) 20% to 80% (Note 7) 80% to 20% (Note 7) ±15V Electrical Characteristics Unless otherwise specified, all limits guaranteed for TA = 25°C, V+ = 15V, V− = −15V, VCM = VOUT = 0V and RL > 1 MΩ to 0V. Boldface limits apply at the temperature extremes Symbol VOS TCVOS IB Parameter Input Offset Voltage Input Offset Voltage Temperature Drift Input Bias Current VCM = −14.5V VCM = 14.5V IOS CMRR Input Offset Current Common Mode Rejection Ratio VCM = −14.5V and VCM = 14.5V −15V ≤ VCM ≤12V −15V ≤ VCM ≤ 15V PSRR CMVR AVOL VOUT Power Supply Rejection Ratio Common Mode Voltage Range Open Loop Voltage Gain Output Voltage Swing High Output Voltage Swing Low IOUT Output Current (Note 4) 2.7V ≤ VS ≤ 30V, VCM = −14.5V CMRR > 80 dB 15.0 −13V ≤ VO ≤ 13V RL = 10 kΩ to 0V RL = 10 kΩ to 0V VID = 100 mV RL = 10 kΩ to 0V VID = −100 mV Sourcing, VOUT = −15V VID = 200 mV Sinking, VOUT = 15V VID = −200 mV IS SR GBW en in THD+N tPD Supply Current Slew Rate Gain Bandwidth Input Referred Voltage Noise Density Input Referred Voltage Noise Density Total Harmonic Distortion + Noise Propagation Delay VCM = −14.5V and VCM = 14.5V ±12V Step f = 100 kHz, RL = 100 kΩ f = 1 kHz f = 1 kHz f = 10 kHz Overdrive = 50 mV (Note 7) Overdrive = 1V (Note 7) 5 3 8 5 25 15 84 82 78 76 86 84 −250 −300 Conditions VCM = −14.5V and VCM = 14.5V Min (Note 6) −4 −5 Typ (Note 5) ±0.2 ±2 −110 40 1 115 100 106 −15.3 15.3 200 135 160 10 13 0.7 1.9 4.6 31 0.27 −65 17 12 1.2 1.3 mA 300 400 300 400 −15.0 dB 80 90 40 50 nA Max (Note 6) +4 +5 Units mV μV/°C nA dB V V/mV mV from either rail mA V/μs MHz nV/ pA/ dB µs www.national.com 4 LM7341 Symbol tr tf Rise Time Fall Time Parameter Conditions 20% to 80% (Note 7) 80% to 20% (Note 7) Min (Note 6) Typ (Note 5) 13 13 Max (Note 6) Units µs µs Note 1: Absolute Maximum Ratings indicate limits beyond which damage to the device may occur. Operating Ratings indicate conditions for which the device is intended to be functional, but specific performance is not guaranteed. For guaranteed specifications and the test conditions, see the Electrical Characteristics. Note 2: Human Body Model, applicable std. MIL-STD-883, Method 3015.7. Machine Model, applicable std. JESD22-A115-A (ESD MM std. of JEDEC) Field-Induced Charge-Device Model, applicable std. JESD22-C101-C (ESD FICDM std. of JEDEC). Note 3: Applies to both single-supply and split-supply operation. Continuous short circuit operation at elevated ambient temperature can result in exceeding the maximum allowed junction temperature of 150°C. Note 4: The maximum power dissipation is a function of TJ(MAX), θJA. The maximum allowable power dissipation at any ambient temperature is PD = (TJ(MAX) − TA)/θJA. All numbers apply for packages soldered directly unto a PC board. Note 5: Typical values represent the most likely parametric norm as determined at the time of characterization. Actual typical values may vary over time and will also depend on the application and configuration. The typical values are not tested and are not guaranteed on shipped production material. Note 6: All limits are guaranteed by testing or statistical analysis. Note 7: The maximum differential voltage between the input pins is VIN Differential = ±15V. Connection Diagram 5-Pin SOT-23 20206002 Top View Ordering Information Package 5-Pin SOT-23 Part Number LM7341MF LM7341MFE LM7341MFX AV4A Package Marking Transport Media 1k Units Tape and Reel 250 Units Tape and Reel 3k Units Tape and Reel MF05A NSC Drawing 5 www.national.com LM7341 Typical Performance Characteristics Output Swing vs. Sourcing Current Output Swing vs. Sinking Current 20206030 20206033 Output Swing vs. Sourcing Current Output Swing vs. Sinking Current 20206031 20206034 Output Swing vs. Sourcing Current Output Swing vs. Sinking Current 20206032 20206035 www.national.com 6 LM7341 VOS Distribution VOS vs. VCM (Unit 1) 20206040 20206003 VOS vs. VCM (Unit 2) VOS vs. VCM (Unit 3) 20206004 20206008 VOS vs. VCM (Unit 1) VOS vs. VCM (Unit 2) 20206006 20206007 7 www.national.com LM7341 VOS vs. VCM (Unit 3) VOS vs. VCM (Unit 1) 20206011 20206010 VOS vs. VCM (Unit 2) VOS vs. VCM (Unit 3) 20206009 20206005 VOS vs. VS (Unit 1) VOS vs. VS (Unit 2) 20206012 20206013 www.national.com 8 LM7341 VOS vs. VS (Unit 3) VOS vs. VS (Unit 1) 20206014 20206015 VOS vs. VS (Unit 2) VOS vs. VS (Unit 3) 20206016 20206017 IBIAS vs. VCM IBIAS vs. VCM 20206018 20206019 9 www.national.com LM7341 IBIAS vs. VCM IBIAS vs. VS 20206020 20206021 IBIAS vs. VS IS vs. VCM 20206024 20206025 IS vs. VCM IS vs. VCM 20206026 20206027 www.national.com 10 LM7341 IS vs. VCM IS vs. VCM 20206028 20206029 Positive Output Swing vs. Supply Voltage Positive Output Swing vs. Supply Voltage 20206036 20206037 Negative Output Swing vs. Supply Voltage Negative Output Swing vs. Supply Voltage 20206038 20206039 11 www.national.com LM7341 Open Loop Frequency with Various Capacitive Load Open Loop Frequency with Various Resistive Load 20206044 20206045 Open Loop Frequency with Various Supply Voltage Open Loop Frequency Response with Various Temperatures 20206046 20206047 CMRR vs. Frequency +PSRR vs. Frequency 20206043 20206041 www.national.com 12 LM7341 -PSRR vs. Frequency Small Signal Step Response 20206051 20206042 Large Signal Step Response Input Referred Noise Density vs. Frequency 20206052 20206048 Input Referred Noise Density vs. Frequency Input Referred Noise Density vs. Frequency 20206049 20206050 13 www.national.com LM7341 THD+N vs. Frequency 20206053 Application Information GENERAL INFORMATION Low supply current and wide bandwidth, greater than rail-torail input range, full rail-to-rail output, good capacitive load driving ability, wide supply voltage and low distortion all make the LM7341 ideal for many diverse applications. The high common-mode rejection ratio and full rail-to-rail input range provides precision performance when operated in non-inverting applications where the common-mode error is added directly to the other system errors. CAPACITIVE LOAD DRIVING The LM7341 has the ability to drive large capacitive loads. For example, 1000 pF only reduces the phase margin to about 30 degrees. POWER DISSIPATION Although the LM7341 has internal output current limiting, shorting the output to ground when operating on a +30V power supply will cause the op amp to dissipate about 350 mW. This is a worst-case example. In the 5-pin SOT-23 package, the higher thermal resistance will cause a calculated rise of 113°C. This can raise the junction temperature to above the absolute maximum temperature of 150°C. Operating from split supplies greatly reduces the power dissipated when the output is shorted. Operating on ±15V supplies can only cause a temperature rise of 57°C in the 5-pin SOT-23 package, assuming the short is to ground. WIDE SUPPLY RANGE The high power-supply rejection ratio (PSRR) and common mode rejection ratio (CMRR) provide precision performance when operated on battery or other unregulated supplies. This advantage is further enhanced by the very wide supply range (2.5V–32V) offered by the LM7341. In situations where highly variable or unregulated supplies are present, the excellent PSRR and wide supply range of the LM7341 benefit the system designer with continued precision performance, even in such adverse supply conditions. SPECIFIC ADVANTAGES OF 5-Pin SOT-23 (TinyPak) The obvious advantage of the 5-pin SOT-23, TinyPak, is that it can save board space, a critical aspect of any portable or miniaturized system design. The need to decrease overall system size is inherent in any handheld, portable, or lightweight system application. Furthermore, the low profile can help in height limited designs, such as consumer hand-held remote controls, sub-notebook computers, and PCMCIA cards. An additional advantage of the tiny package is that it allows better system performance due to ease of package placement. Because the tiny package is so small, it can fit on the board right where the op amp needs to be placed for optimal performance, unconstrained by the usual space limitations. This optimal placement of the tiny package allows for many system enhancements, not easily achieved with the constraints of a larger package. For example, problems such as system noise due to undesired pickup of digital signals can be easily reduced or mitigated. This pick-up problem is often caused by long wires in the board layout going to or from an op amp. By placing the tiny package closer to the signal source and allowing the LM7341 output to drive the long wire, the signal becomes less sensitive to such pick-up. An overall reduction of system noise results. Often times system designers try to save space by using dual or quad op amps in their board layouts. This causes a complicated board layout due to the requirement of routing several signals to and from the same place on the board. Using the tiny op amp eliminates this problem. Additional space savings parts are available in tiny packages from National Semiconductor, including low power amplifiers, precision voltage references, and voltage regulators. LOW DISTORTION, HIGH OUTPUT DRIVE CAPABILITY The LM7341 offers superior low-distortion performance, with a total-harmonic-distortion-plus-noise of −66 dB at f = 10 kHz. The advantage offered by the LM7341 is its low distortion levels, even at high output current and low load resistance. www.national.com 14 LM7341 Typical Applications HANDHELD REMOTE CONTROLS The LM7341 offers outstanding specifications for applications requiring good speed/power trade-off. In applications such as remote control operation, where high bandwidth and low power consumption are needed. The LM7341 performance can easily meet these requirements. OPTICAL LINE ISOLATION FOR MODEMS The combination of the low distortion and good load driving capabilities of the LM7341 make it an excellent choice for driving opto-coupler circuits to achieve line isolation for modems. This technique prevents telephone line noise from coupling onto the modem signal. Superior isolation is achieved by coupling the signal optically from the computer modem to the telephone lines; however, this also requires a low distortion at relatively high currents. Due to its low distortion at high output drive currents, the LM7341 fulfills this need, in this and in other telecom applications. REMOTE MICROPHONE IN PERSONAL COMPUTERS Remote microphones in Personal Computers often utilize a microphone at the top of the monitor which must drive a long cable in a high noise environment. One method often used to reduce the nose is to lower the signal impedance, which reduces the noise pickup. In this configuration, the amplifier usually requires 30 dB–40 dB of gain, at bandwidths higher than most low-power CMOS parts can achieve. The LM7341 offers the tiny package, higher bandwidths, and greater output drive capability than other rail-to-rail input/output parts can provide for this application. LM7341 AS A COMPARATOR The LM7341 can also be used as a comparator and provides quite reasonable performance. Note however that unlike a typical comparator an op amp has a maximum allowed differential voltage between the input pins. For the LM7341, as stated in the Absolute Maximum Ratings section, this maximum voltage is VIN Differential = ±15V. Beyond this limit, even for a short time, damage to the device may occur. As an inverting comparator at VS = 30V and 1V of overdrive there is typically 12 μs of propagation delay. At VS = 30V and 50 mV of overdrive there is typically 17 µs of propagation delay. 20206054 FIGURE 1. Inverting Comparator Similarly a non-inverting comparator at VS = 30V and 1V of overdrive there is typically 12 µs of propagation delay. At VS = 30V and 50 mV of overdrive there is typically 17 μs of propagation delay. 20206055 FIGURE 2. Non-Inverting Comparator COMPARATOR WITH HYSTERESIS The basic comparator configuration may oscillate or produce a noisy output if the applied differential input voltage is near the comparator's offset voltage. This usually happens when the input signal is moving very slowly across the comparator's switching threshold. This problem can be prevented by the addition of hysteresis or positive feedback. 15 www.national.com LM7341 INVERTING COMPARATOR WITH HYSTERESIS The inverting comparator with hysteresis requires a three resistor network that is referenced to the supply voltage VCC of the comparator, as shown in Figure 3. When VIN at the inverting input is less than VA, the voltage at the non-inverting node of the comparator (VIN < VA), the output voltage is high (for simplicity assume VOUT switches as high as VCC). The three network resistors can be represented as R1||R3 in series with R2. The lower input trip voltage VA1 is defined as VA1 = VCCR2 / ((R1||R3) + R2) When VIN is greater than VA (VIN > VA), the output voltage is low, very close to ground. In this case the three network re- sistors can be presented as R2||R3 in series with R1. The upper trip voltage VA2 is defined as VA2 = VCC (R2||R3) / ((R1+ (R2||R3) The total hysteresis provided by the network is defined as Delta VA = VA1- VA2 For example to achieve 50 mV of hysteresis when VCC = 30V set R1 = 4.02 kΩ, R2 = 4.02 kΩ, and R3 = 1.21 MΩ. With these resistors selected the error due to input bias current is approximately 1 mV. To minimize this error it is best to use low resistor values on the inputs. 20206056 FIGURE 3. Inverting Comparator with Hysteresis www.national.com 16 LM7341 NON-INVERTING COMPARATOR WITH HYSTERESIS A non-inverting comparator with hysteresis requires a two resistor network, and a voltage reference (VREF) at the inverting input. When V IN is low, the output is also low. For the output to switch from low to high, VIN must rise up to VIN1 where VIN1 is calculated by VIN1 = R1*(VREF/R2) + VREF When VIN is high, the output is also high, to make the comparator switch back to it's low state, VIN must equal VREF before VA will again equal VREF . VIN can be calculated by VIN2 = (VREF (R1+ R2) - VCCR1)/R2 The hysteresis of this circuit is the difference between VIN1 and VIN2. Delta VIN = VCCR1/R2 For example to achieve 50 mV of hysteresis when VCC = 30V set R1 = 20Ω and R2 = 12.1 kΩ. 20206057 20206058 FIGURE 4. Non-Inverting Comparator with Hysteresis OTHER SOT-23 AMPLIFIERS The LM7321 is a rail-to-rail input and output amplifier that can tolerate unlimited capacitive load. It works from 2.7V to ±15V and across the −40°C to 125°C temperature range. It has 20 MHz gain-bandwidth, and is available in both 5-Pin SOT-23 and 8-Pin SOIC packages. The LM6211 is a 20 MHz part with CMOS input, which runs on 5V to 24V single supplies. It has rail-to-rail output and low noise. The LMP7701 is a rail-to-rail input and output precision part with an input voltage offset under 220 microvolts and low noise. It has 2.5 MHz bandwidth and works on 2.7V to 12V supplies. SMALLER SC70 AMPLIFIERS The LMV641 is a 10 MHz amplifier which uses only 140 micro amps of supply current. The input voltage offset is less than 0.5 mV. The LMV851 is an 8 MHz amplifier which uses only 0.4 mA supply current, and is available in the smaller SC70 package. The LMV851 also resists Electro Magnetic Interference (EMI) from mobile phones and similar high frequency sources. It works on 2.7V to 5.5 V supplies. Detailed information on these and a wide range of other parts can be found at www.national.com. 17 www.national.com LM7341 Physical Dimensions inches (millimeters) unless otherwise noted 5-Pin SOT-23 NS Package Number MF05A www.national.com 18 LM7341 Notes 19 www.national.com LM7341 Rail-to-Rail Input/Output, ±15V, 4.6 MHz GBW, Operational Amplifier in SOT-23 Package Notes For more National Semiconductor product information and proven design tools, visit the following Web sites at: Products Amplifiers Audio Clock Conditioners Data Converters Displays Ethernet Interface LVDS Power Management Switching Regulators LDOs LED Lighting PowerWise Serial Digital Interface (SDI) Temperature Sensors Wireless (PLL/VCO) www.national.com/amplifiers www.national.com/audio www.national.com/timing www.national.com/adc www.national.com/displays www.national.com/ethernet www.national.com/interface www.national.com/lvds www.national.com/power www.national.com/switchers www.national.com/ldo www.national.com/led www.national.com/powerwise www.national.com/sdi www.national.com/tempsensors www.national.com/wireless WEBENCH Analog University App Notes Distributors Green Compliance Packaging Design Support www.national.com/webench www.national.com/AU www.national.com/appnotes www.national.com/contacts www.national.com/quality/green www.national.com/packaging www.national.com/quality www.national.com/refdesigns www.national.com/feedback Quality and Reliability Reference Designs Feedback THE CONTENTS OF THIS DOCUMENT ARE PROVIDED IN CONNECTION WITH NATIONAL SEMICONDUCTOR CORPORATION (“NATIONAL”) PRODUCTS. NATIONAL MAKES NO REPRESENTATIONS OR WARRANTIES WITH RESPECT TO THE ACCURACY OR COMPLETENESS OF THE CONTENTS OF THIS PUBLICATION AND RESERVES THE RIGHT TO MAKE CHANGES TO SPECIFICATIONS AND PRODUCT DESCRIPTIONS AT ANY TIME WITHOUT NOTICE. NO LICENSE, WHETHER EXPRESS, IMPLIED, ARISING BY ESTOPPEL OR OTHERWISE, TO ANY INTELLECTUAL PROPERTY RIGHTS IS GRANTED BY THIS DOCUMENT. TESTING AND OTHER QUALITY CONTROLS ARE USED TO THE EXTENT NATIONAL DEEMS NECESSARY TO SUPPORT NATIONAL’S PRODUCT WARRANTY. EXCEPT WHERE MANDATED BY GOVERNMENT REQUIREMENTS, TESTING OF ALL PARAMETERS OF EACH PRODUCT IS NOT NECESSARILY PERFORMED. NATIONAL ASSUMES NO LIABILITY FOR APPLICATIONS ASSISTANCE OR BUYER PRODUCT DESIGN. BUYERS ARE RESPONSIBLE FOR THEIR PRODUCTS AND APPLICATIONS USING NATIONAL COMPONENTS. PRIOR TO USING OR DISTRIBUTING ANY PRODUCTS THAT INCLUDE NATIONAL COMPONENTS, BUYERS SHOULD PROVIDE ADEQUATE DESIGN, TESTING AND OPERATING SAFEGUARDS. EXCEPT AS PROVIDED IN NATIONAL’S TERMS AND CONDITIONS OF SALE FOR SUCH PRODUCTS, NATIONAL ASSUMES NO LIABILITY WHATSOEVER, AND NATIONAL DISCLAIMS ANY EXPRESS OR IMPLIED WARRANTY RELATING TO THE SALE AND/OR USE OF NATIONAL PRODUCTS INCLUDING LIABILITY OR WARRANTIES RELATING TO FITNESS FOR A PARTICULAR PURPOSE, MERCHANTABILITY, OR INFRINGEMENT OF ANY PATENT, COPYRIGHT OR OTHER INTELLECTUAL PROPERTY RIGHT. LIFE SUPPORT POLICY NATIONAL’S PRODUCTS ARE NOT AUTHORIZED FOR USE AS CRITICAL COMPONENTS IN LIFE SUPPORT DEVICES OR SYSTEMS WITHOUT THE EXPRESS PRIOR WRITTEN APPROVAL OF THE CHIEF EXECUTIVE OFFICER AND GENERAL COUNSEL OF NATIONAL SEMICONDUCTOR CORPORATION. As used herein: Life support devices or systems are devices which (a) are intended for surgical implant into the body, or (b) support or sustain life and whose failure to perform when properly used in accordance with instructions for use provided in the labeling can be reasonably expected to result in a significant injury to the user. A critical component is any component in a life support device or system whose failure to perform can be reasonably expected to cause the failure of the life support device or system or to affect its safety or effectiveness. National Semiconductor and the National Semiconductor logo are registered trademarks of National Semiconductor Corporation. All other brand or product names may be trademarks or registered trademarks of their respective holders. Copyright© 2008 National Semiconductor Corporation For the most current product information visit us at www.national.com National Semiconductor Americas Technical Support Center Email: support@nsc.com Tel: 1-800-272-9959 www.national.com National Semiconductor Europe Technical Support Center Email: europe.support@nsc.com German Tel: +49 (0) 180 5010 771 English Tel: +44 (0) 870 850 4288 National Semiconductor Asia Pacific Technical Support Center Email: ap.support@nsc.com National Semiconductor Japan Technical Support Center Email: jpn.feedback@nsc.com