LMC1992CCN

LMC1992 Digitally-Controlled Stereo Tone and Volume Circuit with Four-Channel Input Selector December 1994 LMC1992 Digitally-Controlled Stereo Tone and Volume Circuit with Four-Channel Input-Selector General Description The LMC1992 is a monolithic integrated circuit that provides four stereo inputs bass and treble tone controls and volume balance and front-rear fader controls These functions are digitally controlled through a three-wire communication interface All of the LMC1992s functions are achieved with only three external capacitors per channel It is designed for line level input signals (300 mV b 2V) and has a maximum gain of 0 dB The internal design is optimized for external capacitors having values of 0 1 mF or less This allows the use of chip capacitors for coupling and tone control functions Low noise and distortion result from using analog switches and thin-film silicon-chromium resistor networks in the signal path Volume and fader are at minimum and tone controls are flat when supply voltage is first applied Additional tone control can be achieved using the LMC835 stereo 7-band graphic equalizer connected to the LMC1992’s select-out select-in external processor loop Features Y Y Y Y Y Y Y Y Y Y Y Y Y Low noise and distortion Four stereo inputs 40 volume levels including mute 20 fader levels All attenuators have a 2 dB of attenuation per step Front back fade control External processor loop Only three external components per channel Serial programmable standard MICROWIRETM interface Single supply operation 6V to 12V supply voltage Protection address (similar to DS8906) DC-coupled inputs Single supply operation Applications Y Y Y Y Automotive audio systems Sound reinforcement systems Home entertainment stereo television and music reproduction systems Electronic music (MIDI) Block and Connection Diagrams TL H 10789 – 2 Order Number LMC1992CCN See NS Package Number N28B TL H 10789 – 1 Left channel shown Pin numbers in parentheses are for the right channel DNR is a registered trademark of National Semiconductor Corporation COPSTM and MICROWIRETM are trademarks of National Semiconductor Corporation C1995 National Semiconductor Corporation TL H 10789 RRD-B30M75 Printed in U S A Absolute Maximum Ratings (Notes 1 and 2) If Military Aerospace specified devices are required please contact the National Semiconductor Sales Office Distributors for availability and specifications 15V Voltage at Any Pin GND b 0 2V to V a a 0 2V Input Current at Any Pin (Note 3) 5 mA Package Input Current (Note 3) 20 mA Power Dissipation (Note 4) 500 mW Junction Temperature 125 C Supply Voltage (V a b GND) Storage Temperature Lead Temperature N Package Soldering 10 sec ESD Susceptibility (Note 5) Pins 9 10 11 19 20 21 b 65 C to a 150 C a 260 C 2000V 850V Operating Ratings (Notes 1 and 2) Temperature Range TMIN s TA s TMAX LMC1992CCN 0 C s TA s 70 C Supply Voltage Range (V a b Vb) 6V to 12V Electrical Characteristics The following specifications apply for V a e 8V fIN e 1 kHz input signal applied to channel 1 volume e 0 dB bass e 0 dB treble e 0 dB and faders e 0 dB unless otherwise specified All limits TA e TJ e 25 C Symbol IS VIN VOUT THD Parameter Supply Current Input Voltage Output Voltage Total Harmonic Distortion Clipping Level (1 0% THD) Select Out (Pins 8 22) Clipping Level (1 0% THD) Outputs (Pins 13 14 16 17) All Four Channels Volume Attenuator at 0 dB Input Level 0 3 Vrms Volume Attenuator at b20 dB Input Level 0 6 Vrms All Four Channels CCIR ARM Filter RS e 0X All Four Channels CCIR ARM Filter RS e 0X Volume Attenuator e b80 dB Pins 8 22 Pins 13 14 16 17 Pins 4 5 6 7 23 24 25 26 Pins 16 17 Volume Attenuation at 0101110100X (0 dB) (Absolute Gain) 01011000000 (80 dB) (Relative to Attenuation at the 0 dB setting) All Volume Attenuation Settings from 01011001010 (60 dB) to 0101110100X (0 dB) (Note 9) Fader Attenuation from 1XXX000000 (40 dB) to 1XXX1010X (0 dB) Pins 16 17 Fader Attenuation at 011XXX1010X (0 dB) (Absolute Gain) 011XXX00000 (40 dB) (Relative to Attenuation at the 0 dB setting) All Fader Attenuation Settings from 011XXX00000 (40 dB) to 011XXX1010X (0 dB) (Note 10) 23 12 Conditions Typical (Note 6) Limit (Note 7) 27 0 20 0 65 Units (Limit) mA (max) Vrms(min) Vrms(min) 0 15 0 03 65 50 100 80 2 b1 0 03 01 30 0 20 0 150 120 % (max) % (max) mVrms (max) mVrms (max) X (max) X (max) MX EnOUT EnOUT ROUT RIN Output Noise Output Noise DC Output Impedance DC Input Impedance Volume Attenuator Range b1 5 dB (max) dB (min) dB (min) dB (max) dB (max) 80 0 20 75 0 07 43 g1 0 Volume Step Size Channel-to-Channel Volume Tracking Error Fader Attenuation Range g0 5 b1 0 b1 5 dB (max) dB (min) dB (min) dB (max) 40 20 38 0 10 45 Fader Step Size 2 Electrical Characteristics The following specifications apply for V a e 8V fIN e 1 kHz input signal applied to channel 1 volume e 0 dB bass e 0 dB treble e 0 dB and faders e 0 dB unless otherwise specified All limits TA e TJ e 25 C (Continued) Symbol Parameter Bass Gain Range Bass Tracking Error Bass Step Size Treble Gain Range Treble Tracking Error Treble Step Size Frequency Response Channel Separation Input-Input Isolation PSRR fCLK VIN(1) VIN(0) Power Supply Rejection Ratio Clock Frequency Logic ‘‘1’’ Input Voltage Logic ‘‘0’’ Input Voltage Conditions fIN e 100 Hz Pins 14 16 fIN e 100 Hz Pins 14 16 fIN e 100 Hz Pins 14 16 (Relative to Previous Level) fIN e 10 kHz Pins 14 16 fIN e 10 kHz Pins 14 16 fIN e 10 kHz Pins 14 16 (Relative to Previous Level) b 3 dB b 0 3 dB (Relative to Signal Amplitude at 1 kHz) Typical (Note 6) g 12 g0 1 Limit (Note 7) g 10 0 g1 0 Units (Limit) dB (min) dB (max) dB (min) dB (max) dB (min) dB (max) dB (min) dB (max) kHz kHz (min) dB (min) dB (min) dB (min) MHz (max) V (min) V (max) 20 g 12 g0 1 10 30 g 10 0 g1 0 20 450 10 30 20 VIN e 1 0 Vrms VIN e 1 0 Vrms (Note 8) 8 VDC 100 mVP-P 100 Hz Sinewave Applied to Pin 28 Va e 97 90 40 10 13 04 70 70 31 05 20 08 Note 1 Absolute Maximum Ratings indicate limits beyond which damage to the device may occur Operating Ratings indicate conditions for which the device is functional but do not guarantee specific performance limits For guaranteed specifications and test conditions see the Electrical Characteristics The guaranteed specifications apply only for the test conditions listed Some performance characteristics may degrade when the device is not operated under the listed test conditions Note 2 All voltages are specified with respect to ground Note 3 When the input voltage (VIN) at any pin exceeds the power supply voltages (VIN k Vb or VIN l V a ) the absolute value of the current at that pin should be limited to 5 mA or less The 20 mA package input current limits the number of pins that can exceed the power supply voltages with 5 mA current limit to four Note 4 The maximum power dissipation must be de-rated at elevated temperatures and is dictated by TJMAX wJA and the ambient temperature TA The maximum allowable power dissipation is PD e (TJMAX b TA) iJA or the number given in the Absolute Maximum Ratings whichever is lower For the LMC1992CCN TJMAX e 125 C and the typical junction-to-ambient thermal resistance when board mounted is 67 C W Note 5 Human body model 100 pF discharged through a 1 5 kX resistor Note 6 Typicals are at TJ e 25 C and represent the most likely parametric norm Note 7 Limits are guaranteed to National’s AOQL (Average Outgoing Quality Level) Note 8 The Input-Input Isolation is tested by driving one input and measuring the front outputs when the undriven inputs are selected Note 9 The Volume Step Size is defined as the change in attenuation between any two adjacent volume attenuation settings The nominal Volume Step Size is 2 dB Note 10 The Fader Step Size is defined as the change in attenuation between any two adjacent fader attenuation settings The nominal Volume Step Size is 2 dB 3 Typical Performance Characteristics Quiescent Current vs Supply Voltage Maximum Output Swing vs Supply Voltage Output Noise Voltage vs Frequency TL H 10789–3 TL H 10789 – 4 TL H 10789 – 5 Total Harmonic Distortion vs Output AC Load Total Harmonic Distortion vs Select Out AC Load CCIR Output Noise Voltage vs Volume Setting TL H 10789–6 TL H 10789 – 7 TL H 10789 – 8 Channel Separation vs Frequency Total Harmonic Distortion vs Input Voltage Attenuation vs Frequency TL H 10789–9 TL H 10789 – 10 TL H 10789 – 11 4 Typical Performance Characteristics Tone Control Response with Equal Bass and Treble Control Settings (Continued) Tone Control Response with Reciprocal Bass and Treble Control Settings Treble Tone Control Response TL H 10789–12 TL H 10789 – 13 TL H 10789 – 14 Bass Tone Control Response Select In Impedance vs Frequency TL H 10789 – 15 TL H 10789 – 16 Connection Diagram TL H 10789 – 17 5 Pin Description DATA(1) This is the serial data input for communications sent by a controller The data rate has a maximum frequency of 500 kHz The LMC1992 requires 11 bits of data to control or change a function the first two bits a 1 and 0 select the LMC1992 the next three bits select a function and the final six bits set the function to a desired value The data must be valid on the rising edge of the CLOCK input signal The CLOCK input accepts a TTL or CMOS level clocking signal The input is used to clock the DATA input signal and determines when a data bit is valid This pin’s output signal is intended for the rear amplifiers in a four speaker stereo system The output can typically sink 350 mA FRONT OUT This pin’s output signal is intended for the (14 16) front amplifiers in a four speaker stereo system The output can typically sink 350 mA GROUND (15) This is the system ground connection V a (28) This is the power supply connection The LMC1992 is operational with supply voltages from 6V to 12V It is recommended that this pin is bypassed with 0 1 mF capacitor BYPASS (27) A 10 mF capacitor is connected between this pin and ground REAR OUT (13 17) CLOCK(2) This input accepts a logic low signal when a controller is addressing the LMC1992 When ENABLE is active the LMC1992 responds to input signals present on the DATA and CLOCK inputs INPUT 1 – 4 Four two-channel analog inputs are available (4 – 7 23 – 26) on the LMC1992 These pins should be dc-biased to mid-supply SELECT OUT The selected INPUT signal is available at this (8 22) output This feature allows the use of external signal processing such as noise reduction or graphic equalizers This output can typically sink 1 mA SELECT IN This is the input that an external signal proc(9 21) essor uses to return a signal to the LMC1992 TONE IN This is the input to the tone control amplifier (10 20) See the Application Information section titled ‘‘Tone Control Response’’ TONE OUT Tone control amplifier output See the Appli(11 19) cation Information section titled ‘‘Tone Control Response’’ OP AMP OUT This output is used externally with the tone (12 18) control capacitors Internally this output is applied to the volume attenuators ENABLE(3) General Information The LMC1992 is a CMOS bipolar high quality building block intended for high fidelity audio signal processing It is designed for line level input signals (300 mV b 2V) and has a maximum gain of b1 dB While the LMC1992 is manufactured with CMOS processing NPN transistors are used to build low noise op amps The combination of CMOS switches bipolar op amps and SiCr resistors make it possible to achieve an order of magnitude quality improvement over other bipolar circuits that use analog multipliers to accomplish gain adjustment The LMC1992 has internal decoding logic that allows a computer (mP) to communicate directly to the audio control circuitry through a standard MICROWIRE interface This three-wire interface consists of a DATA input line a CLOCK input line and an ENABLE line When the ENABLE line is low data can be serially shifted from the controller to the LMC1992 As the ENABLE line goes through the low-tohigh transition any additional data is ignored Data present in the internal shift register is latched and the instruction is executed Figure 1 shows the connection diagram of a typical LMC1992 application TL H 10789 – 18 FIGURE 1 Typical Connection Diagram 6 Applications Information MINIMUM LOAD IMPEDANCE The LMC1992 employs emitter-follower buffers at pins 8 and 22 (SELECT OUT) 13 and 14 (LEFT FRONT and REAR OUTPUTs) and 16 and 17 (RIGHT FRONT-andREAR OUTPUTs) that buffer output signals Typical bias current of 1 mA is used for the SELECT OUTPUT buffers and 350 mA for the LEFT-and-RIGHT FRONT-and-REAR OUTPUT buffers The Electrical Specifications table lists a maximum input signal of 2 3 Vrms (3 25 Vpeak) for 1% THD at the SELECT OUT pins This distortion level is achieved when the minimum ac load impedance seen by the SELECT OUT pin is 3 25 kX (3 25V 1 mA) For the LEFT-and-RIGHT FRONTand-REAR OUTPUTs the typical maximum output is 1 2 Vrms (1 55 Vpeak) Therefore the minimum load impedance is 4 43 kX (1 55 V 0 35 mA) Trying to use a lower impedance results in a clipped output signal Therefore the chance of clipping can be greatly reduced and much lower distortion levels can be achieved by using load impedances that are an order of magnitude higher than shown here For applications that require dc coupling and the INPUTs biased to V a 2 the minimum load impedance will differ from that detailed in the above discussion The emitter followers may be potentially operating at high currents because there is a dc voltage V a 2 b 0 7V at the SELECT OUT pins dc resistance to ground will result in increased current flow Latch-up may occur if the total emitter current exceeds 5 mA This current is a combination of the emitter follower’s 1 mA current source and 4 mA drawn by the external load Therefore to prevent this possibility the minimum dc load impedance should be Vpeak a (V a 2 b 0 7V) e 1638X 4 mA Vpeak e 3 25V V a e 8V To allow for variations and part tolerances 2 0 kX is a good choice for this minimum dc load impedance When dc coupling is used at the LEFT-and-RIGHT FRONTand-REAR OUTPUTs the output emitter followers will be operating at a nominal dc voltage of V a 2 b 2(0 7V) Latch-up may occur if the total emitter current exceeds 1 mA This current is a combination of the emitter follower’s 0 35 mA current source and 0 65 mA drawn by the external load Therefore to prevent this possibility the minimum dc load impedance should be Vpeak a (V a 2 b 2(0 7V)) e 9 kX 0 65 mA Vpeak e 3 25V V a e 8V TL H 10789 – 20 FIGURE 2 Input Bias Network To allow for variations and part tolerances 10 kX is a good choice for this minimum dc load impedance INPUT IMPEDANCE For ac coupled input signals the input impedance value is determined by bias resistor R1 as shown in Figure 2 A directly coupled input signal will see an emitter follower’s nominal input impedance of 2 MX The SELECT IN pins have an input impedance that varies with the BASS and TREBLE control settings The input impedance is 96 kX at dc and 27 kX at 1 kHz when the controls are set at 0 dB Minimum input impedance of 28 kX at dc and 24 kX at 1 kHz occurs when maximum boost is selected At 10 kHz the minimum input impedance with the tone controls flat is 8 kX and with the tone controls at maximum boost is 3 kX STEREO SIGNAL INPUTS When operating with a single supply voltage the stereo signal inputs must be dc biased to one-half of the supply voltage as shown in Figure 2 As an example with a supply voltage of 8V all signal sources should have a dc bias of 4V The maximum input signal level of 6 5 Vp-p (for 1% THD) would then swing from 0 75V to 7 25V Input-to-input crosstalk can be minimized by using a separate dc bias circuit for each stereo input pair EXTERNAL SIGNAL PROCESSING The signal present at the selected input will be available at the SELECT OUT pins 8 (left) and 22 (right) The dc bias voltage at those pins will be one base-emitter voltage approximately 0 7 Vdc below the source because of the internal emitter follower Therefore if the selected input has a bias of 4 0 Vdc the dc component at pins 8 and 22 will be about 3 3 Vdc The LMC1992’s SELECT OUT emitter followers allow additional signal sources using emitter follower outputs (such as multiple LMC1992s) to be ‘‘wired-ORed’’ together When this feature is in use the input channel of the LMC1992 not in use should be set to ‘‘open’’ input codes 01000XX0000 or 01000XX011X 7 Applications Information (Continued) TL H 10789 – 19 FIGURE 3 System Block Diagram Showing Inclusion of DNR Noise Reduction (LM1894) and Equalizer (LMC835) (One Channel Only LMC1992) The SELECT OUT pins (8 and 22) enable greater system design flexibility by providing a means to implement an external processing loop This loop can be used for noise reduction circuits such as DNR (LM1894) or mulit-band graphic equalizers (LMC835) It is important to ensure that if both are used the noise reduction circuitry precede the equalization circuits Failure to do so will result in improper operation of the noise reduction circuits The system shown in Figure 3 utilizes the external loop to include DNR and a multi-band equalizer AUDIO MUTE A mute function with attenuation of 100 dB is possible with the volume control set to b80 dB and the INPUT select code set to 01000XX0000 (open circuit) TONE CONTROL RESPONSE Base and treble tone controls are included in the LMC1992 The tone controls use just two external capacitors for each stereo channel Each has a corner frequency determined by the value of C2 and C3 (Figure 4) and internal resistors in the feedback loop of the internal tone amplifier The maximum amplitude boost or cut is determined by the data sent to the LMC1992 (see Table I) The typical tone control response shown in the Typical Performance Curves were generated with C2 e C3 e 0 0082 mF and show the response for each step When modifying the tone control response it is important to note that the ratio of C3 and C2 sets the mid-frequency gain Symmetrical tone response is achieved when C2 e C3 However with C2 e 2(C3) and the tone controls set to ‘‘flat’’ the frequency response will be flat at 20 Hz and 20 kHz and a 6 dB at 1 kHz The frequency where a tone control begins to deviate from a flat response will be referred to as the turn-over frequency With C e C2 e C3 the LMC1992’s treble turn-over frequency is nominally 1 2qC(14 2 kX) The base turn-over frequency is nominally 1 fBT e 2qC(27 7 kX) when maximum boost is chosen The inflection points (the frequencies where the boost or cut is within 3 dB of the final value) are for treble and bass fTT e fTI e 1 2qC(2 3 kX) fBI e 1 2qC(164 1 kX) 8 Applications Information (Continued) SERIAL COMMUNICATION INTERFACE Figure 5 shows the LMC1992’s timing diagram for its three wire MICROWIRE interface A controller’s data stream can be any length once the correct device address is received by the LMC1992 any number of data bits can be sent the last nine bits occurring before ENABLE goes high are used by the LMC1992 The first two bits in a valid data stream are decoded and used as device address bits The LMC1992 uses a unique address of 1 0 The LMC1992 will not respond to information on the DATA line if any other address is used This allows other MICROWIRE serially programmable devices to share the same three-wire communication bus When ENABLE goes high any further serial data is ignored and the contents of the shift register is transferred to the data latches Only when information is received by the data latches do any function or setting changes take place The first three of nine bits select one of the LMC1992s functions The remaining six bits set the selected function to the desired value or position A data bit is accepted as valid and clocked into an internal shift register on each rising edge of the signal appearing at the LMC1992s CLOCK input pin Proper data interpretation and operation is ensured when ENABLE makes its falling transition during the time when CLOCK is low Erroneous operation will result if the ENABLE signal makes its falling transition at any other time TL H 10789 – 22 FIGURE 4 The Tone Control Amplifier Increasing the values of C2 and C3 decreases the turnover and inflection frequencies i e the Tone Control Response Curves shown in Typical Performance Curves will shift left when C2 and C3 are increased and shift right when C2 and C3 are decreased With C2 e C3 e 0 0082 2 dB steps are achieved at 100 Hz and 10 kHz Changing C2 and C3 to 0 01 mF shifts the 2 dB per step frequency to 72 Hz and 8 3 kHz If the tone control capacitors’ size is decreased these frequencies will increase With C2 e C3 e 0 0068 mF the 2 dB steps take place at 130 Hz and 11 2 kHz FADER FUNCTION The four fader functions are all independently adjustable and therefore no balance control is needed Emulating a balance control is accomplished through software by simultaneously changing a channel’s front and rear faders by equal amounts To satisfy normal balance requirements the faders have an attenuation range of 40 dB TL H 10789 – 21 Note 1 Negative transition on ENABLE clears previous address Clock must be low during transition Note 2 Additional don’t care states may be inserted here for ease of programming (Optional ) Note 3 Positive transition on ENABLE latches in new data if the LMC1992 has been addressed Clock can either be high or low during transition FIGURE 5 Clocking Data into the Standard MICROWIRE Interface (Minimum Number of Bits in Data Stream) 9 Applications Information (Continued) TABLE I Programming Codes for LMC1992 A2 1 Address A1 A0 1 1 Function Left Rear Fader D5 X D4 MSB Data D3 N D2 N D1 N D0 LSB Values b 40 dB e X00000 b 20 dB e X01010 0 dB e X1010X b 40 dB e X00000 b 20 dB e X01010 0 dB e X1010X b 40 dB e X00000 b 20 dB e X01010 0 dB e X1010X b 40 dB e X00000 b 20 dB e X01010 0 dB e X1010X b 80 dB e 000000 b 40 dB e 010100 0 dB e 10100X b 12 dB e XX0000 FLAT e XX0110 a 12 dB e XX1100 b 12 dB e XX0000 FLAT e XX0110 a 12 dB e XX1100 1 1 0 Right Rear Fader X MSB N N N LSB 1 0 1 Left Front Fader X MSB N N N LSB 1 0 0 Right Front Fader X MSB N N N LSB 0 1 1 Volume MSB N N N N LSB 0 1 0 Treble X X MSB N N LSB 0 0 1 Bass X X MSB N N LSB 0 0 0 Input Select X X 0 MSB N LSB OPEN e XX0000 INPUT1 e XX0001 INPUT2 e XX0010 INPUT3 e XX0011 INPUT4 e XX0100 Note 1 All attenuators 2 dB step Note 2 Tone controls 2 dB step 100 Hz and 10 kHz Note 3 Use of data that deviates from the values shown in the table may result in erroneous results SERIAL DATA FORMAT Table I displays the required data format needed by the LMC1992 Not shown is the 2-bit device address (10) These two bits of information must precede the final ninebits used as the data word The first three of these nine bits is the function address The VOLUME TONE and FADER controls are designed to increment their settings (in 2 dB steps) as the control data is incremented by one LSB Disregarding the device address and the function address the VOLUME input code increases from 000000 (b80 dB) to 10100X (0 dB) The TONE controls’ input code increases from XX0000 (b12 dB) to XX0110 (0 dB) to XX1100 ( a 12 dB) The code for the FADERs starts from X00000 (b40 dB) and goes to X1010X (0 dB) The table shows that VOLUME is the only function that uses all six bits to choose that function’s setting The remaining functions use less than six bits the unused bits are shown as ‘‘X’’s (‘‘don’t care’’) While these ‘‘don’t care’’ bits have no effect on their respective function the LMC1992 must receive them for proper operation If neglected erroneous or unknown results will occur 10 Applications Information (Continued) DATA TRANSFER EXAMPLE The following routines based on the flowchart shown in Figure 6 are examples of COPSTM microcontroller instruction code that can be used to control the LMC1992 (see National Semiconductor’s COPS Microcontrollers Databook for more information) These routines arbitrarily select COPS register 0 for I O purposes When these routines are entered it is assumed that chip select is high SK (clock) is low and SO (data) is low These routines exit with chip select high and SK and SO low Output port G0 is arbitrarily chosen to send the chip select signal to the LMC1992 The 11 data bits needed to control the LMC1992 are assumed to be in the 4-bit registers 13–15 with the 4 MSBs in register 13 With this configuration there is an extra bit for a data stream that is 12 bits long As previously mentioned there can be any number of extra bits between the device address and the function address DATA TRANSFER ROUTINE 1 This general purpose routine handles all the overhead except loading data into registers 13–15 It sends the data according to the conditions discussed above The data will be lost at the conclusion of the routine This routine consumes only 17 ROM memory locations OUT1 LBI SC OGI LEI SEND LD XAS XIS JP RC OGI LEI RET 0 13 POINT TO START OF DATA WORD SET C TO ENABLE SK CLOCK SELECT EXTERNAL DEVICE G0 40 ENABLE SHIFT REGISTER OUTPUT DATA TRANSMISSION LOOP TURN-ON CLOCK SEND 15 0 DE-SELECT EXTERNAL DEVICE SET S0 TO 0 DATA TRANSFER ROUTINE 2 This routine performs the same function as routine 1 while preserving the contents of the data registers This routine takes only 21 ROM memory locations OUT1 LBI 0 13 POINT TO START OF DATA WORD SC SET C TO ENABLE SK CLOCK OGI 14 SELECT EXTERNAL DEVICE GO 40 LEI 8 ENABLE SHIFT REGISTER OUTPUT JP SEND2 SEND1 XAS SEND2 LD DATA TRANSMISSION LOOP XIS TURN-ON CLOCK JP SEND1 XAS SEND LAST DATA RC WAIT 4 CYCLES - DATA GOING OUT CLRA NOP XAS TURN SK CLOCK OFF OGI 15 DE-SELECT DEVICE LEI 0 SET S0 TO 0 RET 14 8 11 Applications Information (Continued) TL H 10789 – 23 FIGURE 6 General Data Transmission Flowchart to Send Serial Data to the LMC1992’s MICROWIRE Compatible Digital Inputs 12 13 LMC1992 Digitally-Controlled Stereo Tone and Volume Circuit with Four-Channel Input Selector Physical Dimensions inches (millimeters) Molded Dual-In-Line Package (N) Order Number LMC1992CCN NS Package Number N28B LIFE SUPPORT POLICY NATIONAL’S PRODUCTS ARE NOT AUTHORIZED FOR USE AS CRITICAL COMPONENTS IN LIFE SUPPORT DEVICES OR SYSTEMS WITHOUT THE EXPRESS WRITTEN APPROVAL OF THE PRESIDENT OF NATIONAL SEMICONDUCTOR CORPORATION As used herein 1 Life support devices or systems are devices or systems which (a) are intended for surgical implant into the body or (b) support or sustain life and whose failure to perform when properly used in accordance with instructions for use provided in the labeling can be reasonably expected to result in a significant injury to the user National Semiconductor Corporation 2900 Semiconductor Drive P O Box 58090 Santa Clara CA 95052-8090 Tel 1(800) 272-9959 TWX (910) 339-9240 National Semiconductor GmbH Livry-Gargan-Str 10 D-82256 F4urstenfeldbruck Germany Tel (81-41) 35-0 Telex 527649 Fax (81-41) 35-1 National Semiconductor Japan Ltd Sumitomo Chemical Engineering Center Bldg 7F 1-7-1 Nakase Mihama-Ku Chiba-City Ciba Prefecture 261 Tel (043) 299-2300 Fax (043) 299-2500 2 A critical component is any component of a life support device or system whose failure to perform can be reasonably expected to cause the failure of the life support device or system or to affect its safety or effectiveness National Semiconductor Hong Kong Ltd 13th Floor Straight Block Ocean Centre 5 Canton Rd Tsimshatsui Kowloon Hong Kong Tel (852) 2737-1600 Fax (852) 2736-9960 National Semiconductores Do Brazil Ltda Rue Deputado Lacorda Franco 120-3A Sao Paulo-SP Brazil 05418-000 Tel (55-11) 212-5066 Telex 391-1131931 NSBR BR Fax (55-11) 212-1181 National Semiconductor (Australia) Pty Ltd Building 16 Business Park Drive Monash Business Park Nottinghill Melbourne Victoria 3168 Australia Tel (3) 558-9999 Fax (3) 558-9998 National does not assume any responsibility for use of any circuitry described no circuit patent licenses are implied and National reserves the right at any time without notice to change said circuitry and specifications