LMH6733

LMH6733 Single Supply, 1.0 GHz, Triple Operational Amplifier January 2007 LMH6733 Single Supply, 1.0 GHz, Triple Operational Amplifier General Description The LMH6733 is a triple, wideband, operational amplifier designed specifically for use where high speed and low power are required. Input voltage range and output voltage swing are optimized for operation on supplies as low as 3V and up to ±6V. Benefiting from National’s current feedback architecture, the LMH6733 offers a gain range of ±1 to ±10 while providing stable operation without external compensation, even at unity gain. These amplifiers provide 650 MHz small input signal bandwidth at a gain of 2 V/V , a low 2.1 nV/ referred noise and only consume 5.5 mA (per amplifier) from a single 5V supply. The LMH6733 is offered in a 16-Pin SSOP package with flow through pinout for ease of layout and is also pin compatible with the LMH6738. Each amplifier has an individual shutdown pin. Features ■ Supply range 3 to 12V single supply ■ Supply range ±1.5V to ±6V split supply ■ 1.0 GHz −3 dB small signal bandwidth ■ ■ ■ ■ ■ ■ (AV = +1, VS = ±5V) 650 MHz −3 dB small signal bandwidth (AV = +2, VS = 5V) Low supply current (5.5 mA per op amp, VS = 5V) input noise voltage 2.1 nV/ 3750 V/μs slew rate 70 mA linear output current CMIR and output swing to 1V from each supply rail Applications ■ ■ ■ ■ ■ ■ ■ ■ ■ HDTV component video driver High resolution projectors Flash A/D driver D/A transimpedance buffer Wide dynamic range IF amp Radar/communication receivers DDS post-amps Wideband inverting summer Line driver Connection Diagram 16-Pin SSOP 20199110 Top View Ordering Information Package 16-pin SSOP Part Number LMH6733MQ LMH6733MQX Package Marking LH6733MQ Transport Media 95 Units/Rail 2.5k Units Tape and Reel NSC Drawing MQA16 VIP10™ is a trademark of National Semiconductor Corporation. © 2007 National Semiconductor Corporation 201991 www.national.com LMH6733 Absolute Maximum Ratings (Note 1) If Military/Aerospace specified devices are required, please contact the National Semiconductor Sales Office/ Distributors for availability and specifications. ESD Tolerance (Note 2) Human Body Model Machine Model Supply Voltage (V+ - V–) IOUT Common Mode Input Voltage Maximum Junction Temperature Storage Temperature Range 2000V 200V 13.2V (Note 3) ±VCC +150°C −65°C to +150°C (Note 5) Soldering Information Infrared or Convection (20 sec.) Wave Soldering (10 sec.) Storage Temperature Range 235°C 260°C −65°C to +150°C Operating Ratings Thermal Resistance Package 16-Pin SSOP Temperature Range (Note 4) Supply Voltage (V+ - V–) (Note 1) (θJC) 36°C/W −40°C 3V (θJA) 120°C/W +85°C to 12V 5V Electrical Characteristics Symbol UGBW SSBW SSBW LSBW 0.1 dB BW TRS SR ts te td Distortion HD2L HD3L VN ICN NCN DG DP VIO IBN IBI PSRR 2nd Harmonic Distortion 3rd Harmonic Distortion 0.1 dB Gain Flatness Parameter −3 dB Bandwidth −3 dB Bandwidth Frequency Domain Performance AV = +2, VCC = 5V, RL = 100Ω, RF = 340Ω; unless otherwise specified. Conditions Unity Gain, VOUT = 200 mVPP VOUT = 200 mVPP, RL = 100Ω VOUT = 200 mVPP, RL = 150Ω VOUT = 2 VPP VOUT = 200 mVPP Min Typ 870 650 685 480 320 MHz MHz Max Units MHz Time Domain Response Rise and Fall Time (10% to 90%) Slew Rate Settling Time to 0.1% Enable Time Disable Time 2V Step 2V Step 2V Step From Disable = Rising Edge From Disable = Falling Edge 2 VPP, 10 MHz 2 VPP, 10 MHz >10 MHz >10 MHz >10 MHz 4.43 MHz, RL = 150Ω 4.43 MHz, RL = 150Ω 0.8 1900 10 10 15 −63 −73 2.1 18.6 26.9 0.03 0.025 0.4 Non-Inverting Inverting +PSRR −PSRR 59 59 58 57 2 16.7 1.0 61 61 dB 2.0 2.5 28 32 17 19 ns V/µs ns ns ns dBc dBc Equivalent Input Noise Non-Inverting Voltage Inverting Current Non-Inverting Current Differential Gain Differential Phase Input Offset Voltage (Note 7) Input Bias Current (Note 7) Input Bias Current (Note 7) Power Supply Rejection Ratio (Note 7) nV/ pA/ pA/ % deg Video Performance Static, DC Performance mV µA μA www.national.com 2 LMH6733 Symbol CMRR XTLK ICC Parameter Common Mode Rejection Ratio (Note 7) Crosstalk Supply Current (Note 7) Supply Current Disabled V+ Conditions Min 52 51.5 Typ 54.5 −80 16.7 1.54 0.75 200 1 Max Units dB dB Input Referred, f = 10 MHz, Drive Channels A,C Measure Channel B All Three Amps Enabled, No Load RL = ∞ RL = ∞ 18 1.8 1.8 mA mA mA kΩ pF Ω Ω Supply Current Disabled V− Miscellaneous Performance RIN+ CIN+ RIN− RO VO Non-Inverting Input Resistance Non-Inverting Input Capacitance Inverting Input Impedance Output Impedance Output Voltage Range (Note 7) Output Impedance of Input Buffer. DC RL = 100Ω RL = ∞ 27 0.05 1.25-3.75 1.12-3.88 1.3-3.7 1.11-3.89 1.03-3.97 1.15-3.85 1.1-3.9 1.2-3.8 ±50 1.0–4.0 ±60 170 −72 −360 3.2 3.6 V CMIR IO ISC IIH IIL VDMAX VDMIM Common Mode Input Range (Note 7) Linear Output Current (Notes 3, 7) Short Circuit Current (Note 6) Disable Pin Bias Current High Disable Pin Bias Current Low Voltage for Disable Voltage for Enable CMRR > 40 dB VIN = 0V, VOUT < ±42 mV VIN = 2V Output Shorted to Ground Disable Pin = V+ Disable Pin = 0V Disable Pin ≤ VDMAX Disable Pin ≥ VDMIN (Note 5) Conditions Unity Gain, VOUT = 200 mVPP VOUT = 200 mVPP, RL = 100Ω VOUT = 200 mVPP, RL = 150Ω VOUT = 2 VPP VOUT = 200 mVPP 2V Step 5V Step 4V Step 2V Step From Disable = Rising Edge From Disable = Falling Edge 2 VPP, 10 MHz 2 VPP, 10 MHz >10 MHz >10 MHz V mA mA μA μA V V ±5V Electrical Characteristics Symbol UGBW SSBW SSBW LSBW 0.1 dB BW 0.1 dB Gain Flatness Time Domain Response TRS TRL SR ts te td Distortion HD2L HD3L VN ICN 2nd Harmonic Distortion 3rd Harmonic Distortion Non-Inverting Voltage Inverting Current Rise and Fall Time (10% to 90%) Slew Rate Settling Time to 0.1% Enable Time Disable Time Parameter −3 dB Bandwidth −3 dB Bandwidth Frequency Domain Performance AV = +2, VCC = ±5V, RL = 100Ω, RF = 383Ω; unless otherwise specified. Min Typ 1000 830 950 600 350 0.7 0.8 3750 10 10 15 −72 −63 2.1 18.6 MHz MHz Max Units MHz ns V/µs ns ns ns dBc dBc Equivalent Input Noise nV/ pA/ 3 www.national.com LMH6733 Symbol NCN DG DP VIO IBN IBI PSRR CMRR XTLK ICC Video Performance Parameter Non-Inverting Current Differential Gain Differential Phase Input Offset Voltage (Note 7) Input Bias Current (Note 7) Input Bias Current (Note 7) Power Supply Rejection Ratio (Note 7) Common Mode Rejection Ratio (Note 7) Crosstalk Supply Current (Note 7) Supply Current Disabled V+ Supply Current Disabled V− >10 MHz Conditions Min Typ 26.9 0.03 0.03 0.6 Max Units pA/ % Deg 4.43 MHz, RL = 150Ω 4.43 MHz, RL = 150Ω Static, DC Performance 2.2 2.5 19 24 23 26 mV µA μA dB dB dB 20.8 22.0 1.8 1.8 Non-Inverting Inverting +PSRR −PSRR −14 −19 3.5 5 59 58 53 52.5 61.5 61 55 −80 19.5 1.54 0.75 200 1 Input Referred, f = 10 MHz, Drive Channels A,C Measure Channel B All Three Amps Enabled, No Load RL = ∞ RL = ∞ mA mA mA kΩ pF Ω Ω V V mA mA μA μA V V Miscellaneous Performance RIN+ CIN+ RIN− RO VO Non-Inverting Input Resistance Non-Inverting Input Capacitance Inverting Input Impedance Output Impedance Output Voltage Range (Note 7) Output Impedance of Input Buffer DC RL = 100Ω RL = ∞ CMIR IO ISC IIH IIL VDMAX VDMIM Common Mode Input Range (Note 7) Linear Output Current (Notes 3, 7) Short Circuit Current (Note 6) Disable Pin Bias Current High Disable Pin Bias Current Low Voltage for Disable Voltage for Enable CMRR > 43 dB VIN = 0V, VOUT < ±42 mV VIN = 2V Output Shorted to Ground Disable Pin = V+ Disable Pin = 0V Disable Pin ≤ VDMAX Disable Pin ≥ VDMIN ±3.55 ±3.5 ±3.85 ±3.9 ±3.8 70 30 0.05 ±3.7 ±4.0 ±4.0 ±80 237 −72 −360 3.2 3.6 Note 1: Absolute Maximum Ratings indicate limits beyond which damage to the device may occur. Operating Ratings indicate conditions for which the device is intended to be functional, but specific performance is not guaranteed. For guaranteed specifications, see the Electrical Characteristics tables. Note 2: Human Body Model, applicable std. MIL-STD-883, Method 3015.7. Machine Model, applicable std. JESD22-A115-A (ESD MM std. of JEDEC) Field-Induced Charge-Device Model, applicable std. JESD22-C101-C (ESD FICDM std. of JEDEC). Note 3: The maximum output current (IOUT) is determined by device power dissipation limitations. See the Power Dissipation section of the Applications Information for more details. Note 4: The maximum power dissipation is a function of TJ(MAX), θJA. The maximum allowable power dissipation at any ambient temperature is PD = (TJ(MAX) – TA)/ θJA. All numbers apply for packages soldered directly onto a PC Board. Note 5: Electrical Table values apply only for factory testing conditions at the temperature indicated. Factory testing conditions result in very limited self-heating of the device such that TJ = TA. No guarantee of parametric performance is indicated in the electrical tables under conditions of internal self-heating where TJ > TA. Note 6: Short circuit current should be limited in duration to no more than 10 seconds. See the Power Dissipation section of the Application Section for more details. Note 7: Parameter 100% production tested at 25° C. www.national.com 4 LMH6733 Typical Performance Characteristics specified). Large Signal Frequency Response AV = +2, VCC = 5V, RL = 100Ω, RF = 340Ω; unless otherwise Large Signal Frequency Response 20199111 20199112 Small Signal Frequency Response Frequency Response vs. VOUT 20199113 20199114 Frequency Response vs. Supply Voltage Gain Flatness 20199115 20199116 5 www.national.com LMH6733 Pulse Response Crosstalk vs. Frequency 20199128 20199121 Distortion vs. Frequency Distortion vs. Output Voltage 20199133 20199134 Small Signal Frequency Response vs. RL Frequency Response vs. Capacitive Load 20199135 20199136 www.national.com 6 LMH6733 Series Output Resistance vs. Capacitive Load PSRR vs. Frequency 20199137 20199138 CMRR vs. Frequency Closed Loop Output Impedance |Z| 20199139 20199140 Disabled Channel Isolation vs. Frequency Disable Timing 20199141 20199142 7 www.national.com LMH6733 DC Errors vs. Temperature Open Loop Transimpedance 20199143 20199145 Input Noise vs. Frequency 20199146 Typical Performance Characteristics specified). Large Signal Frequency Response AV = +2, VCC = ±5V, RL = 100Ω, RF = 383Ω; unless otherwise Large Signal Frequency Response 20199122 20199123 www.national.com 8 LMH6733 Small Signal Frequency Response Frequency Response vs. VOUT 20199124 20199125 Frequency Response vs. Supply Voltage Gain Flatness 20199126 20199127 Pulse Response Crosstalk vs. Frequency 20199128 20199129 9 www.national.com LMH6733 Distortion vs. Output Voltage Distortion vs. Frequency 20199130 20199131 DC Errors vs. Temperature 20199144 www.national.com 10 LMH6733 Application Information 20199105 FIGURE 1. Recommended Non-Inverting Gain Circuit 20199103 FIGURE 3. Recommended RF vs. Gain See Figure 3 for selecting a feedback resistor value for gains of ±1 to ±10. Since each application is slightly different it is worth some experimentation to find the optimal RF for a given circuit. In general a value of RF that produces about 0.1 dB of peaking is the best compromise between stability and maximal bandwidth. Note that it is not possible to use a current feedback amplifier with the output shorted directly to the inverting input. The buffer configuration of the LMH6733 requires a 324Ω feedback resistor for stable operation. The LMH6733 has been optimized for high speed operation. As shown in Figure 3 the suggested value for RF decreases for higher gains. Due to the impedance of the input buffer there is a practical limit for how small RF can go, based on the lowest practical value of RG. This limitation applies to both inverting and non-inverting configurations. For the LMH6733 the input resistance of the inverting input is approximately 30Ω and 20Ω is a practical (but not hard and fast) lower limit for RG. The LMH6733 begins to operate in a gain bandwidth limited fashion in the region where RG is nearly equal to the input buffer impedance. Note that the amplifier will operate with RG values well below 20Ω, however results may be substantially different than predicted from ideal models. In particular the voltage potential between the inverting and noninverting inputs cannot be expected to remain small. Inverting gain applications that require impedance matched inputs may limit gain flexibility somewhat (especially if maximum bandwidth is required). The impedance seen by the source is RG || RT (RT is optional). The value of RG is RF /gain. Thus for an inverting gain of −5 V/V and an optimal value for RF the input impedance is equal to 55Ω. Using a termination resistor this can be brought down to match a 25Ω source; however, a 150Ω source cannot be matched. To match a 150Ω source would require using a 1050Ω feedback resistor and would result in reduced bandwidth. For more information see Application Note OA-13 which describes the relationship between RF and closed-loop frequency response for current feedback operational amplifiers. The value for the inverting input impedance for the LMH6733 is approximately 30Ω. The LMH6733 is designed for optimum performance at gains of +1 to +10 V/V and −1 to −9 V/V. Higher gain configurations are still useful; however, the bandwidth will fall as gain is increased, much like a typical voltage feedback amplifier. 20199106 FIGURE 2. Recommended Inverting Gain Circuit GENERAL INFORMATION The LMH6733 is a high speed current feedback amplifier, optimized for very high speed and low distortion. The LMH6733 has no internal ground reference so single or split supply configurations are both equally useful. FEEDBACK RESISTOR SELECTION One of the key benefits of a current feedback operational amplifier is the ability to maintain optimum frequency response independent of gain by using the appropriate values for the feedback resistor (RF). The Electrical Characteristics and Typical Performance plots specify an RF of 340Ω, a gain of +2 V/V and ±2.5V power supplies (unless otherwise specified). Generally, lowering RF from its recommended value will peak the frequency response and extend the bandwidth while increasing the value of RF will cause the frequency response to roll off faster. Reducing the value of RF too far below its recommended value will cause overshoot, ringing and, eventually, oscillation. 11 www.national.com LMH6733 ACTIVE FILTER The choice of reactive components requires much attention when using any current feedback operational amplifier as an active filter. Reducing the feedback impedance, especially at higher frequencies, will almost certainly cause stability problems. Likewise capacitance on the inverting input should be avoided. See Application Notes OA-7 and OA-26 for more information on Active Filter applications for Current Feedback Op Amps. When using the LMH6733 as a low pass filter the value of RF can be substantially reduced from the value recommended in the RF vs. Gain charts. The benefit of reducing RF is increased gain at higher frequencies, which improves attenuation in the stop band. Stability problems are avoided because in the stop band additional device bandwidth is used to cancel the input signal rather than amplify it. The benefit of this change depends on the particulars of the circuit design. With a high pass filter configuration reducing RF will likely result in device instability and is not recommended. 20199108 FIGURE 5. Decoupling Capacitive Loads DRIVING CAPACITIVE LOADS Capacitive output loading applications will benefit from the use of a series output resistor ROUT. Figure 5 shows the use of a series output resistor, ROUT, to stabilize the amplifier output under capacitive loading. Capacitive loads of 5 to 120 pF are the most critical, causing ringing, frequency response peaking and possible oscillation. The chart “Frequency Response vs. Capacitive Load” give a recommended value for selecting a series output resistor for mitigating capacitive loads. The values suggested in the charts are selected for .5 dB or less of peaking in the frequency response. This gives a good compromise between settling time and bandwidth. For applications where maximum frequency response is needed and some peaking is tolerable, the value of ROUT can be reduced slightly from the recommended values. 20199107 FIGURE 4. Typical Video Application www.national.com 12 LMH6733 20199132 FIGURE 6. AC Coupled Single Supply Video Amplifier AC-COUPLED VIDEO The LMH6733 can be used as an AC-coupled single supply video amplifier for driving 75Ω coax with a gain of 2. The input signal is nominally 0.7V or 1.0V for component YPRPB and RGB, depending on the presence of a sync. R1, R2, and R3 simply set the input to the center of the input linear range while CIN AC couples the video onto the op amp’s input. As can be seen in Figure 6, amplifier U1 is used in a positive gain configuration set for a closed loop gain of 2. The feedback resistor RF is 340Ω. The gain resistor is created from the parallel combination of RG and R4, giving a Thevenin equivalent of 340Ω connected to 2.5V. The 75Ω back termination resistor RO divides the signal such that VOUT equals a buffered version of VIN. The back termination will eliminate any reflection of the signal that comes from the load. The input termination resistor, RT, is optional – it is used only if matching of the incoming line is necessary. In some applications, it is recommended that a small valued ceramic capacitor be used in parallel with CO which is itself electrolytic because of its rather large value. The ceramic cap will tend to shunt the inductive behavior of this electrolytic cap, CO, at higher frequencies for an improved overall, lowimpedance output. INVERTING INPUT PARASITIC CAPACITANCE Parasitic capacitance is any capacitance in a circuit that was not intentionally added. It comes about from electrical interaction between conductors. Parasitic capacitance can be reduced but never entirely eliminated. Most parasitic capacitances that cause problems are related to board layout or lack of termination on transmission lines. Please see the section on Layout Considerations for hints on reducing problems due to parasitic capacitances on board traces. Transmission lines should be terminated in their characteristic impedance at both ends. High speed amplifiers are sensitive to capacitance between the inverting input and ground or power supplies. This shows up as gain peaking at high frequency. The capacitor raises device gain at high frequencies by making RG appear smaller. Capacitive output loading will exaggerate this effect. In gen13 eral, avoid introducing unnecessary parasitic capacitance at both the inverting input and the output. One possible remedy for this effect is to slightly increase the value of the feedback (and gain set) resistor. This will tend to offset the high frequency gain peaking while leaving other parameters relatively unchanged. If the device has a capacitive load as well as inverting input capacitance using a series output resistor as described in the section on “Driving Capacitive Loads” will help. LAYOUT CONSIDERATIONS Whenever questions about layout arise, use the evaluation board as a guide. The LMH730275 is the evaluation board supplied with samples of the LMH6733. To reduce parasitic capacitances ground and power planes should be removed near the input and output pins. Components in the feedback loop should be placed as close to the device as possible. For long signal paths controlled impedance lines should be used, along with impedance matching elements at both ends. Bypass capacitors should be placed as close to the device as possible. Bypass capacitors from each rail to ground are applied in pairs. The larger electrolytic bypass capacitors can be located farther from the device, the smaller ceramic capacitors should be placed as close to the device as possible. The LMH6733 has multiple power and ground pins for enhanced supply bypassing. Every pin should ideally have a separate bypass capacitor. Sharing bypass capacitors may slightly degrade second order harmonic performance, especially if the supply traces are thin and /or long. In Figure 1 and Figure 2 CSS is optional, but is recommended for best second harmonic distortion. Another option to using CSS is to use pairs of .01 μF and .1 μF ceramic capacitors for each supply bypass. VIDEO PERFORMANCE The LMH6733 has been designed to provide excellent performance with production quality video signals in a wide variety of formats such as HDTV and High Resolution VGA. NTSC and PAL performance is nearly flawless. Best performance will be obtained with back terminated loads. The back www.national.com LMH6733 termination reduces reflections from the transmission line and effectively masks transmission line and other parasitic capacitances from the amplifier output stage. Figure 4 shows a typical configuration for driving a 75Ω cable. The amplifier is configured for a gain of two to make up for the 6 dB of loss in ROUT. 20199102 FIGURE 7. Maximum Power Dissipation POWER DISSIPATION The LMH6733 is optimized for maximum speed and performance in the small form factor of the standard SSOP-16 package. To achieve its high level of performance, the LMH6733 consumes an appreciable amount of quiescent current which cannot be neglected when considering the total package power dissipation limit. The quiescent current contributes to about 40° C rise in junction temperature when no additional heat sink is used (VS = ±5V, all 3 channels on). Therefore, it is easy to see that proper precautions need to be taken in order to make sure the junction temperature’s absolute maximum rating of 150°C is not violated. To ensure maximum output drive and highest performance, thermal shutdown is not provided. Therefore, it is of utmost importance to make sure that the TJMAX is never exceeded due to the overall power dissipation (all 3 channels). With the LMH6733 used in a back-terminated 75Ω RGB analog video system (with 2 VPP output voltage), the total power dissipation is around 305 mW of which 220 mW is due to the quiescent device dissipation (output black level at 0V). With no additional heat sink used, that puts the junction temperature to about 120° C when operated at 85°C ambient. To reduce the junction temperature many options are available. Forced air cooling is the easiest option. An external addon heat-sink can be added to the SSOP-16 package, or alternatively, additional board metal (copper) area can be utilized as heat-sink. An effective way to reduce the junction temperature for the SSOP-16 package (and other plastic packages) is to use the copper board area to conduct heat. With no enhancement the major heat flow path in this package is from the die through the metal lead frame (inside the package) and onto the surrounding copper through the interconnecting leads. Since high frequency performance requires limited metal near the device pins the best way to use board copper to remove heat is through the bottom of the package. A gap filler with high thermal conductivity can be used to conduct heat from the bottom of the package to copper on the circuit board. Vias to a ground or power plane on the back side of the circuit board will provide additional heat dissipation. A combination of front side copper and vias to the back side can be combined as well. Follow these steps to determine the maximum power dissipation for the LMH6733: 1. Calculate the quiescent (no-load) power: PAMP = ICC X (VS), where VS = V+-V− 2. Calculate the RMS power dissipated in the output stage: PD (rms) = rms ((VS - VOUT) X IOUT) where VOUT and IOUT are the voltage and the current across the external load and VS is the total supply voltage 3. Calculate the total RMS power: PT = PAMP+PD The maximum power that the LMH6733, package can dissipate at a given temperature can be derived with the following equation (See Figure 7): PMAX = (150°C/W– TAMB)/ θJA, where TAMB = ambient temperature (°C) and θJA = thermal resistance, from junction to ambient, for a given package (°C/W). For the SSOP package θJA is 120°C/W. ESD PROTECTION The LMH6733 is protected against electrostatic discharge (ESD) on all pins. The LMH6733 will survive 2000V Human Body Model and 200V Machine Model events. Under closed loop operation the ESD diodes have no affect on circuit performance. There are occasions, however, when the ESD diodes will be evident. If the LMH6733 is driven by a large signal while the device is powered down the ESD diodes will conduct. The current that flows through the ESD diodes will either exit the chip through the supply pins or will flow through the device, hence it is possible to power up a chip with a large signal applied to the input pins. Shorting the power pins to each other will prevent the chip from being powered up through the input. EVALUATION BOARDS National Semiconductor provides the following evaluation boards as a guide for high frequency layout and as an aid in device testing and characterization. Many of the datasheet plots were measured with these boards. Device LMH6733MQ Package SSOP Evaluation Board Part Number LMH730275 A bare evaluation board can be ordered when a sample request is placed with National Semiconductor. www.national.com 14 LMH6733 Physical Dimensions inches (millimeters) unless otherwise noted 16-Pin SSOP NS Package Number MQA16 15 www.national.com LMH6733 Single Supply, 1.0 GHz, Triple Operational Amplifier Notes THE CONTENTS OF THIS DOCUMENT ARE PROVIDED IN CONNECTION WITH NATIONAL SEMICONDUCTOR CORPORATION (“NATIONAL”) PRODUCTS. NATIONAL MAKES NO REPRESENTATIONS OR WARRANTIES WITH RESPECT TO THE ACCURACY OR COMPLETENESS OF THE CONTENTS OF THIS PUBLICATION AND RESERVES THE RIGHT TO MAKE CHANGES TO SPECIFICATIONS AND PRODUCT DESCRIPTIONS AT ANY TIME WITHOUT NOTICE. NO LICENSE, WHETHER EXPRESS, IMPLIED, ARISING BY ESTOPPEL OR OTHERWISE, TO ANY INTELLECTUAL PROPERTY RIGHTS IS GRANTED BY THIS DOCUMENT. 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All other brand or product names may be trademarks or registered trademarks of their respective holders. Copyright© 2007 National Semiconductor Corporation For the most current product information visit us at www.national.com National Semiconductor Americas Customer Support Center Email: new.feedback@nsc.com Tel: 1-800-272-9959 National Semiconductor Europe Customer Support Center Fax: +49 (0) 180-530-85-86 Email: europe.support@nsc.com Deutsch Tel: +49 (0) 69 9508 6208 English Tel: +49 (0) 870 24 0 2171 Français Tel: +33 (0) 1 41 91 8790 National Semiconductor Asia Pacific Customer Support Center Email: ap.support@nsc.com National Semiconductor Japan Customer Support Center Fax: 81-3-5639-7507 Email: jpn.feedback@nsc.com Tel: 81-3-5639-7560 www.national.com