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LP3905

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LP3905
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LP3905 - Power Management Unit For Low Power Handheld Applications - National Semiconductor
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LP3905 Power Management Unit For Low Power Handheld Applications August 2006 LP3905 Power Management Unit For Low Power Handheld Applications General Description LP3905 is a multi-functional Power Management Unit, optimized for low power handheld applications. This device integrates two 600mA DC/DC buck regulators and two 150mA linear regulators. Fixed and adjustable buck output versions are available. The LP3905 additionally features two enable pins for the device output control and is offered in an LLP package. Key Specifications Buck Regulators n Fixed and adjustable voltage options, range 1.0V to 3.3V * n Up to 90% Efficiency n Auto-switching PFM-PWM mode and fixed PWM mode n 2MHz PWM fixed switching frequency (Typ) n 600mA output current n ± 4% output voltage accuracy over temp. n Internal softstart n 2.2µH inductor, 10µF Input and 10µF output Caps Linear Regulators n Output options in the range 1.5V to 3.3V * n 13.5µVrms output voltage noise n PSRR - 70dB @ 1kHz n ± 3% output voltage accuracy over full line and load regulation n 0mA to 150mA output current n Cin = 1.0µF, Cout = 0.47µF for 100mA O/P Cin = 1.0µF, Cout = 1.0µF for 150mA O/P 80mV Dropout voltage * Fixed output voltage devices can be customized to fit system requirements. Please contact National Semiconductor Sales Office. Features n Two buck regulators for powering high current processor functions or peripheral devices n Two linear regulators for powering internal processor functions and I/Os n One enable pin for Buck1 and Linear Regulators 1 & 2 n Separate enable pin for Buck2 n Thermal and current overload protection n Small 14–Pin LLP package (4mm x 4mm x 0.8mm) Applications n n n n Baseband Processors Peripheral Processor (Video, Audio) I/O Power FPGA Power Typical Application Circuit 20152901 FIGURE 1. Typical Application Circuit – 14 Pin LLP Package © 2006 National Semiconductor Corporation DS201529 www.national.com LP3905 Block Diagram 20152902 FIGURE 2. Simplified Functional Diagram Connection Diagram 20152907 FIGURE 3. 14 Pin LLP Package www.national.com 2 LP3905 Connection Diagram Pin Descriptions Pin # 1 2 3 4 5 6 7 8 9 10 11 12 13 14 DAP Name EN2 TGND LDO2 VIN2 LDO1 GND EN1 FB1 GND_B1 SW1 VIN1 SW2 GND_B2 FB2 SGND (Continued) Description Enable Pin for Buck2 Ground Pin LDO2 Output Pin Input Power Terminal to LDO1 & 2 LDO1 Output Pin LDO1 & 2 Ground Pin Enable Pin for Buck1 and LDO1&2 Buck1 Feedback Pin Buck1 Ground Pin Buck1 Switch Pin Input Power Terminal to Buck1 & 2 Buck2 Switch Pin Buck2 Ground Pin Buck2 Feedback Pin Die Attach Pad (DAP) Package Marking Diagram 20152905 • The physical placement of the package marking will vary from part to part. • Date Code - UZXYTT format. ’U’ - Wafer fab code; ’Z’ - assembly site code; ’XY’ 2 digit date code; ’TT’ die run code • See National Web site for more info - http://www.national.com/quality/marking_conventions.html FIGURE 4. LP3905 14 Pin LLP Package Marking NS package number SDA14B Ordering Information Buck 1 [V] Buck 2 [V] LDO 1 [V] LDO 2 [V] 1.2 1.2 Fixed PWM ADJ 1.875 1.875 Fixed PWM ADJ 2.8 2.8 2.8 2.8 Order Number LP3905SD-00 LP3905SDX-00 LP3905SD-30 LP3905SDX-30 3.0 2.8 LP3905SD-A3 LP3905SDX-A3 3905-30 Package Marking 3905-00 Supplied As 1000 units, Tape-and-Reel 4500 units, Tape-and-Reel 1000 units, Tape-and-Reel 4500 units, Tape-and-Reel 1000 units, Tape-and-Reel 4500 units, Tape-and-Reel 3905-A3 3 www.national.com LP3905 Absolute Maximum Ratings (Note 1) If Military/Aerospace specified devices are required, please contact the National Semiconductor Sales Office/ Distributors for availability and specifications. VIN1,VIN2 FB1, FB2, EN1,EN2 (VIN Continuous Power Dissipation (Note 3) Junction Temperature (TJ-MAX) Storage Temperature Range Maximum Lead Temperature (Soldering, 10 sec.) ESD Rating (Note 4) Human Body Model: 2.5kV −0.2V to 6.0V (GND−0.2V) to + 0.2V) to 6.0V (max) Operating Ratings (Notes 1, 2) VIN1 (Buck1&2 Input Voltage),VIN2 (LDO1&2 Input Voltage) (Note 7) Recommended Load Current (Buck) Recommended Load Current (LDO) 3V to 5.5V 0mA to 600 mA 0mA to 100mA with 0.47uF O/P cap 0mA to 150mA with 1.0uF O/P cap −40˚C to +125˚C −40˚C to +85˚C Internally Limited +150˚C −65˚C to +150˚C 260˚C Junction Temperature (TJ) Range Ambient Temperature (TA) Range (Note 5) Thermal Properties Junction-to-Ambient Thermal Resistance (θJA) SDA14B package(Note 6) 37.3oC/W General Electrical Characteristics (Notes 2, 8, 9) Limits in standard typeface are for TJ = 25˚C. Limits in boldface type apply over the full junction temperature range (−40˚C ≤ TJ ≤ +125˚C). Unless otherwise noted, specifications apply to the LP3905 Typical Application Circuit (Figure. 1) Symbol Login Input Thresholds VIN IQ Input Voltage Range Shutdown Supply Current No load Supply Current (Note 15) All Circuits OFF except for POR and UVLO LDO1 & 2 and Buck1 & 2 on ( PWM only versions ) LDO1 & 2 and Buck1 & 2 on VIH VIL IEN VUVLO-R TSHUTDOWN Logic High Input Logic Low Input Enable (EN1,2) Input Current (Note 14) Battery Under Voltage Lock-Out Thermal Shutdown (Note 15) VIN = 3.0V to 5.5V VIN = 3.0V to 5.5V EN1/EN2 = 5.5V and VIN= 5.5V EN1/EN2 = 0V and VIN= 5.5V VIN Rising Temperature Hysteresis 2.1 5 0.001 2.7 160 20 1.2 0.4 8.5 0.1 3.1 3 6.5 140 7 5.5 10.0 250 10.0 mA V V µA µA V ˚C V µA Parameter Condition Min Typ Max Units www.national.com 4 LP3905 General Electrical Characteristics (Notes 2, 8, 9) Buck Regulator Electrical Characteristics (Continued) Buck 1 & 2 have a current rating of Imax= 600mA. Unless otherwise specified, limits are set with VIN = VEN1/2 = 3.8V, VOUT(Buck1)= Vnom1 , VOUT(Buck2)= Vnom2 and CIN= COUT=10µF. Limits in standard typeface are for TJ = 25˚C. Limits in boldface type apply over the full junction temperature range (−40˚C ≤ TJ ≤ +125˚C). Unless otherwise noted, specifications apply to the LP3905 Typical Application Circuit (Figure. 1) (Notes 2, 8) Symbol VFB VOUT Parameter Feedback Voltage Line Regulation Load Regulation RDSON (P) RDSON (N) ILIM FOSC η Pin-Pin Resistance for PFET Pin-Pin Resistance for NFET Switch Peak Current Limit Internal Oscillator Frequency Efficiency (Note 16) 3.0V ≤ VIN ≤ 5.5V IO = 1mA 100 mA ≤ IO ≤ 600mA VIN= VGS= 3.6V VIN= VGS= 3.6V (Note 15) Open Loop PWM Mode IOUT = 5mA, PFM mode (Note 15) IOUT = 300mA, PWM mode (Note 15) 88 90 650 Condition Min -4 0.045 0.002 380 250 1000 2 500 400 1220 Typ Max +4 Units % %/V %/mA mΩ mΩ mA MHz % LDO Regulator Electrical Characteristics The linear regulators have a current rating of Imax= 150mA with COUT = 1.0µF. A 100mA rating applies with COUT = 0.47µF. Unless otherwise specified, limits are set with VIN = 3.8V, VEN1/2 = 3.8V, CIN = 1µF, COUT = 0.47µF, IOUT = 1.0mA. Limits in standard typeface are for TJ = 25˚C. Limits in boldface type apply over the full junction temperature range (−40˚C ≤ TJ ≤ +125˚C). Unless otherwise noted, specifications apply to the LP3905 Typical Application Circuit (Figure. 1)(Notes 2, 8) Symbol ∆VOUT Parameter Output Voltage Tolerance Line Regulation Error Load Regulation Error ILOAD VDO ISC IOUT PSRR Load Current Dropout Voltage Short Circuit Current Limit Maximum Output Current Power Supply Rejection Ratio (Note 15) Conditions Over Full Line and Load Regulation VIN = 3.8V to 5.5V, IOUT = 1mA IOUT = 1 mA to 100mA (Notes 11, 15) IOUT = 100mA (Note 13) COUT = 1.0µF f = 100Hz, IOUT = 100mA f = 1kHz, IOUT = 100mA f = 10kHz, IOUT = 100mA f = 50kHz, IOUT = 100mA f = 100kHz, IOUT = 100mA en Output Noise Voltage (Note 15) BW = 10Hz to 100kHz, VIN = 4.2V Buck1 Turned ON with ILOAD= 0mA, Buck2 Turned OFF IOUT = 1mA 150 90 90 60 35 25 13.5 15.5 µVRMS dB 0 80 300 150 500 Min −3 0.05 0.003 Typ Max 3 Units % %/V %/mA mA mV mA mA IOUT = 100mA 5 www.national.com LP3905 General Electrical Characteristics (Notes 2, 8, 9) LDO Regulator Electrical Characteristics (Continued) (Continued) The linear regulators have a current rating of Imax= 150mA with COUT = 1.0µF. A 100mA rating applies with COUT = 0.47µF. Unless otherwise specified, limits are set with VIN = 3.8V, VEN1/2 = 3.8V, CIN = 1µF, COUT = 0.47µF, IOUT = 1.0mA. Limits in standard typeface are for TJ = 25˚C. Limits in boldface type apply over the full junction temperature range (−40˚C ≤ TJ ≤ +125˚C). Unless otherwise noted, specifications apply to the LP3905 Typical Application Circuit (Figure. 1)(Notes 2, 8) Parameter Line Transient (Note 15) Conditions VIN = (VOUT(NOM) + 1.0V) to (VOUT(NOM) + 1.6V) in 10µs, IOUT = 1 mA VIN = (VOUT(NOM) + 1.6V) to (VOUT(NOM) + 1.0V) in 10µs, IOUT = 1mA Load Transient (Note 15) IOUT = 1mA to 100mA in 10µs IOUT = 100mA to 1mA in 10µs IOUT = 1mA to 150mA in 10µs COUT = 1.0µF IOUT = 150mA to 1mA in 10µs COUT = 1.0µF Overshoot on Startup (Note 15) -100 35 20 mV -70 30 mV Min Typ Max Units Symbol ∆VOUT Transient Characteristics (Note 15) 6 mV 6 Electrical Characteristics Notes Note 1: Absolute Maximum Ratings indicate limits beyond which damage to the component may occur. Operating Ratings are conditions under which operation of the device is guaranteed. Operating Ratings do not imply guaranteed performance limits. For guaranteed performance limits and associated test conditions, see the Electrical Characteristics tables. Note 2: All voltages are with respect to the potential at the GND pin. Note 3: Internal thermal shutdown circuitry protects the device from permanent damage. Note 4: The Human body model is a 100 pF capacitor discharged through a 1.5 kΩ resistor into each pin. MIL-STD-883 3015.7 Note 5: In Applications where high power dissipation and/or poor package resistance is present, the maximum ambient temperature may have to be derated. Maximum ambient temperature (TA-MAX) is dependent on the maximum operating junction temperature (TJ-MAX), the maximum power dissipation of the device in the application (PD-MAX) and the junction to ambient thermal resistance of the package (θJA) in the application, as given by the following equation:TA-MAX= TJ-MAX− (θJAx PD-MAX). Note 6: Junction to ambient thermal resistance is highly dependent on board layout, PCB material environmental conditions and applications. In applications where high power dissipation exists, special care must be given to thermal dissipation issues in board design. The use of thermal vias under the pad may be required. For more on these topics, please refer to the Application Note: AN-1187: Leadless leadframe Package (LLP). Note 7: VIN1 and VIN2 should be tied together at all times for proper Power Up Note 8: Min and Max limits are guaranteed by design, test or statistical analysis. Typical numbers are not guaranteed, but do represent the most likely norm. Note 9: The parameters in the electrical characteristic table are tested at VIN= 3.8V unless otherwise specified. For performance over the input voltage range refer to datasheet curves. Note 10: CIN, COUT: Low-ESR Surface-Mount Ceramic Capacitors (MLCCs) used in setting electrical characteristics. Note 11: The device maintains a stable, regulated output voltage without a load. Note 12: Dropout voltage is the voltage difference between the input and the output at which the output voltage drops to 100 mV below its nominal value. Note 13: Short Circuit Current is measured with VOUT pulled to 0v and VIN worst case = 5,5V. Note 14: There is a 1 MΩ resistor between EN1,EN2 and ground on the device. Note 15: This specification is guaranteed by design. Note 16: For the adjustable version, feedback resistor values should be chosen for the divider network to ensure that at the desired output voltage the feedback pin is at 0.5V. See Buck Converter Applications Information. www.national.com 6 LP3905 Typical Application Circuit 20152911 FIGURE 5. Typical Application Circuit For Adjustable Device Functional Description POWER UP/DOWN PROCEDURE The LP3905 Bucks and LDOs are powered UP/DOWN with 2 control pins, EN1 and EN2. In order for the enable pins to operate, VIN1 and VIN2 should be set to a voltage level higher than VUVLO_R (specified in electrical characteristic). Once enabled, EN1 will turn on Buck1, LDO1 and LDO2. EN2 can independently be used to enable Buck2. Figure 6 illustrates the power UP/DOWN timing sequence of the LP3905 blocks for VEN≥ VIH (min) (enable) and VEN≤VIL (max) (disable). Both linear regulators have active pulldowns when the outputs are disabled. 20152904 EN1 and EN2 can be controlled fully independently. LDOs will be turned on only after Buck1 is powered up. LDOs are powered on simultaneously. In case EN1 and EN2 are enabled at the same time, power up of Buck2 is delayed by 50µs in order to minimize the inrush current from the battery. When EN1 and EN2 are disabled, the relevant output voltages are turned off. FIGURE 6. LP3905 Power UP/DOWN Timing Sequence 7 www.national.com LP3905 Functional Description DC/DC BUCK REGULATORS (Continued) consumption and a longer battery life. Shutdown mode turns off the device, offering the lowest current consumption . A fixed mode device is also available which is fixed in PWM mode for both low and high load currents. An adjustable voltage version is also avalable for which the output voltage can be selected by using two external resistors at each of the two buck outputs. Additional features include soft-start, under voltage protection, current overload protection, and thermal shutdown protection. The part uses an internal reference voltage of 0.5V. It is recommended to keep the part in shutdown until the input voltage is 3V or higher. The LP3905 Buck regulators are high efficiency step down DC-DC switching converters used for delivering a constant voltage from either a single Li-Ion or three cell NiMH/NiCd battery to portable devices such as cell phones and PDAs. Using a voltage mode architecture with synchronous rectification, the Buck Regulators have the ability to deliver up to 600 mA depending on the input voltage, output voltage, ambient temperature and the inductor chosen. There are three modes of operation depending on the current required - PWM, PFM, and shutdown. The standard device operates in PWM mode at load currents of approximately 80 mA or higher, having voltage tolerance of ± 4% with 90% efficiency or better. Lighter load currents cause the device to automatically switch into PFM for reduced current BUCK CONVERTER BLOCK DIAGRAM 20152918 FIGURE 7. Simplified Functional Diagram CIRCUIT OPERATION The LP3905 Buck regulators operate as follows. During the first portion of each switching cycle, the control block in the LP3905 turns on the internal PFET switch. This allows current to flow from the input through the inductor to the output filter capacitor and load. The inductor limits the current to a ramp with a slope of (VIN–VOUT)/L, by storing energy in a magnetic field. During the second portion of each cycle, the controller turns the PFET switch off, blocking current flow from the input, and then turns the NFET synchronous rectifier on. The inductor www.national.com 8 draws current from ground through the NFET to the output filter capacitor and load, which ramps the inductor current down with a slope of - VOUT/L. The output filter stores charge when the inductor current is high, and releases it when inductor current is low, smoothing the voltage across the load. The output voltage is regulated by modulating the PFET switch on time to control the average current sent to the load. The effect is identical to sending a duty-cycle modulated rectangular wave formed by the switch and synchronous LP3905 Functional Description (Continued) PFM OPERATION At very light loads, the converters enters PFM mode and operate with reduced switching frequency and supply current to maintain high efficiency. The Bucks will automatically transition into PFM mode when either of two conditions occurs for a duration of 32 or more clock cycles: A. The inductor current becomes discontinuous. B. The peak PMOS switch current drops below the IMODE level, rectifier at the SW pin to a low-pass filter formed by the inductor and output filter capacitor. The output voltage is equal to the average voltage at the SW pin. PWM OPERATION During PWM operation the converters operate as a voltagemode controllers with input voltage feed forward. This allows the converters to achieve good load and line regulation. The DC gain of the power stage is proportional to the input voltage. To eliminate this dependence, feed forward inversely proportional to the input voltage is introduced. While in PWM (Pulse Width Modulation) mode, the output voltage is regulated by switching at a constant frequency and then modulating the energy per cycle to control power to the load. At the beginning of each clock cycle the PFET switch is turned on and the inductor current ramps up until the comparator trips and the control logic turns off the switch. The current limit comparator can also turn off the switch in case the current limit of the PFET is exceeded. Then the NFET switch is turned on and the inductor current ramps down. The next cycle is initiated by the clock turning off the NFET and turning on the PFET. 20152961 20152922 FIGURE 9. Typical PFM Operation During PFM operation, the converter positions the output voltage slightly higher than the nominal output voltage during PWM operation, allowing additional headroom for voltage drop during a load transient from light to heavy load. The PFM comparators sense the output voltage via the feedback pin and control the switching of the output FETs such that the output voltage ramps between ~0.6% and ~1.7% above the nominal PWM output voltage. If the output voltage is below the ‘high’ PFM comparator threshold, the PMOS power switch is turned on. It remains on until the output voltage reaches the ‘high’ PFM threshold or the peak current exceeds the IPFM level set for PFM mode. The typical peak current in PFM mode is: 20152923 FIGURE 8. Typical PWM Operation Internal Synchronous Rectification While in PWM mode, if enabled, the Bucks use an internal NFET as a synchronous rectifier to reduce rectifier forward voltage drop and associated power loss. Synchronous rectification provides a significant improvement in efficiency whenever the output voltage is relatively low compared to the voltage drop across an ordinary rectifier diode. Current Limiting A current limit feature allows the LP3905 Bucks to protect Internal and external components during overload conditions. PWM mode implements current limiting using an internal comparator that trips at 1000 mA (typ). If the output is shorted to ground the device enters a timed current limit mode where the NFET is turned on for a longer duration until the inductor current falls below a low threshold, ensuring inductor current has more time to decay, thereby preventing runaway. 20152957 Once the PMOS power switch is turned off, the NMOS power switch is turned on until the inductor current ramps to zero. When the NMOS zero-current condition is detected, the NMOS power switch is turned off. If the output voltage is below the ‘high’ PFM comparator threshold ), the PMOS switch is again turned on and the cycle is repeated until the output reaches the desired level. Once the output reaches the ‘high’ PFM threshold, the NMOS switch is turned on briefly to ramp the inductor current to zero and then both output switches are turned off and the part enters an extremely low power mode. Quiescent supply current during this ‘sleep’ mode is 16µA (typ), which allows the part to achieve high efficiencies under extremely light load conditions. When the output drops below the ‘low’ PFM threshold, 9 www.national.com LP3905 Functional Description (Continued) the cycle repeats to restore the output voltage (average voltage in pfm mode) to ∼1.15% above the nominal PWM output voltage. If the load current should increase during PFM mode causing the output voltage to fall below the ‘low2’ PFM threshold, the part will automatically transition into fixed-frequency PWM mode. When VIN =2.8V the part transitions from PWM to PFM mode at ~35mA output current and from PFM to PWM mode at ~85mA , when VIN=3.6V, PWM to PFM transition happens at ~50mA and PFM to PWM transition happens at ~100mA, when VIN =4.5V, PWM to PFM transition happens at ~65mA and PFM to PWM transition happens at ~115mA. 20152903 FIGURE 10. Operation in PFM Mode and Transfer to PWM Mode SOFT START The LP3905 Buck Converters have a soft-start circuit that limits in-rush current during start-up. Additionally, in case EN1 and EN2 are enabled at the same time, a typical 500µs delay between Buck1 and Buck2 Power Up prevents any further Inrush current from the battery. During start-up the switch current limit is increased in steps. Soft start is activated only if EN goes from logic low to logic high after Vin reaches 3V. Soft start is implemented by increasing switch current limit in steps of 70mA, 140mA, 280mA and 1000mA (typ. switch current limit). The start-up time thereby depends on the output capacitor and load current demanded at start-up. Typical start-up times with 22µF output capacitor and 300mA load current is 400µs and with 1mA load current its 275µs. www.national.com 10 LP3905 Application Information DC/DC CONVERTORS Adjustable Buck - Output Voltage Selection The buck converter output voltage of the adjustable version device can be set via the selection of the external feedback resistor network forming the output feedback between the output voltage side of the Inductor and the FB pin and the FB Pin and GND. around 200kΩ to keep the current drawn through the resistor network well below the 16µA quiescent current level (PFM mode) but large enough that it is not susceptible to noise. If R2 is 200kΩ and with VFB at 0.5V, the current through the resistor feedback network will be 2.5µA. The formula for output voltage selection is VOUT - output voltage (Volts) - feedback voltage (0.5V) R1FB - feedback resistor from VOUT to FB R2FB - feedback resistor from FB to GND For any out voltage greater than or equal to 1.0V a zero should be added around 45 kHz by the addition of a capacitor C1. The formula for the calculation of C1 is: VFB 20152958 Adjustable Buck Converter Components VOUT will be adjusted to make the voltage at FB equal to 0.5V. The resistor from FB to ground (RFB2) should be For recommended component values see Table 1 TABLE 1. Buck Component Configurations for Various Output Voltage Values VOUT (V) 1.0 1.2 1.4 1.5 1.6 1.85 2.5 2.8 3.3 RFB1 (kΩ) 200 280 360 360 442 540 402 464 562 RFB2 (kΩ) 200 200 200 180 200 200 100 100 100 C1 (pF) 18 12 10 10 8.2 6.8 8.2 8.2 6.8 C2 (pF) none none none none none none none 33 33 L (µH) 2.2 2.2 2.2 2.2 2.2 2.2 2.2 2.2 2.2 COUT (µF) 10 10 10 10 10 10 10 10 10 Buck Inductor Selection There are two main considerations when choosing an inductor; the inductor should not saturate, and the inductor current ripple is small enough to achieve the desired output voltage ripple. Different saturation current rating specs are followed by different manufacturers so attention must be given to details. Saturation current ratings are typically specified at 25˚C so ratings at max ambient temperature of application should be requested from manufacturer. There are two methods to choose the inductor saturation current rating. Method 1: The saturation current is greater than the sum of the maximum load current and the worst case average to peak inductor current. This can be written as • IOUTMAX: maximum load current (600mA) • VIN: maximum input voltage in application • L : min inductor value including worst case tolerances (30% drop can be considered for method 1) • f : minimum switching frequency (1.6Mhz) • VOUT: output voltage Method 2: A more conservative and recommended approach is to choose an inductor that has saturation current rating greater than the max current limit of 1220mA. A 2.2µH inductor with a saturation current rating of at least 1250mA is recommended for most applications.The inductor’s resistance should be less than 0.3Ω for good efficiency. For low-cost applications, an unshielded bobbin inductor could be considered. For noise critical applications, a toroidal or shielded-bobbin inductor should be used. A good practice is to lay out the board with overlapping footprints of both types for design flexibility. This allows substitution of a low-noise shielded inductor, in the event that noise from low-cost bobbin models is unacceptable. • IRIPPLE: average to peak inductor current 11 www.national.com LP3905 Application Information (Continued) Buck DC/DC Convertor Input Capacitor Selection A ceramic input capacitor of 10µF, 6.3V is sufficient for most applications. Place the input capacitor as close as possible to the VIN pin of the device. A larger value may be used for improved input voltage filtering. Use X7R or X5R types, do not use Y5V. DC bias characteristics of ceramic capacitors must be considered when selecting case sizes like 0805 and 0603. The input filter capacitor supplies current to the PFET switch of the LP3905 in the first half of each cycle and reduces voltage ripple imposed on the input power source. A ceramic capacitor’s low ESR provides the best noise filtering of the input voltage spikes due to this rapidly changing current. Select a capacitor with sufficient ripple current rating. The input current ripple can be calculated as: Note that the output voltage ripple is dependent on the inductor current ripple and the equivalent series resistance of the output capacitor (RESR). The RESR is frequency dependent (as well as temperature dependent); make sure the value used for calculations is at the switching frequency of the part. LINEAR REGULATORS Capacitor Selection The LP3955 is designed to work with ceramic capacitors on the output to take advantage of the benefits they offer: for capacitance values in the range of 0.47µF to 10µF range, ceramic capacitors are the smallest, least expensive and have the lowest ESR values (which makes them best for eliminating high frequency noise). The ESR of a typical 1µFceramic capacitor is in the range of 20mW to 40mW, which easily meets the ESR requirement for stability by the LP3955. For both input and output capacitors careful interpretation of the capacitor specification is required to ensure correct device operation. The capacitor value can change greatly dependant on the conditions of operation and capacitor type. In particular the output capacitor selection should take account of all the capacitor parameters to ensure that the specification is met within the application. Capacitance value can vary with DC bias conditions as well as temperature and frequency of operation. Capacitor values will also show some decrease over time due to aging. The capacitor parameters are also dependant on the particular case size with smaller sizes giving poorer performance figures in general. As an example Figure 11 shows a typical graph showing a comparison of capacitor case sizes in a Capacitance vs. DC Bias plot. As shown in the graph, as a result of the DC Bias condition the capacitance value may drop below the minimum capacitance value given in the recommended capacitor table (0.7µF in this case). Note that the graph shows the capacitance out of spec for the 0402 case size capacitor at higher bias voltages. It is therefore recommended that the capacitor manufacturers’ specifications for the nominal value capacitor are consulted for all conditions as some capacitor sizes (e.g. 0402) may not be suitable in the actual application. DC/DC CONVERTOR OUTPUT CAPACITOR SELECTION Use a 10µF, 6.3V ceramic capacitor. Use X7R or X5R types, do not use Y5V. DC bias characteristics of ceramic capacitors must be considered when selecting case sizes like 0805 and 0603. DC bias characteristics vary from manufacturer to manufacturer and dc bias curves should be requested from them as part of the capacitor selection process. The output filter capacitor smoothes out current flow from the inductor to the load, helps maintain a steady output voltage during transient load changes and reduces output voltage ripple. These capacitors must be selected with sufficient capacitance and sufficiently low ESR to perform these functions. The output voltage ripple is caused by the charging and discharging of the output capacitor and also due to its RESR and can be calculated as: Voltage peak-to-peak ripple due to capacitance can be expressed as follows Voltage peak-to-peak ripple due to ESR can be expressed as follows VPP-ESR = (2 * IRIPPLE) * RESR Because these two components are out of phase the rms value can be used to get an approximate value of peak-topeak ripple. Voltage peak-to-peak ripple, root mean squared can be expressed as follows 20152906 FIGURE 11. Capacitor Performance (DC Bias) www.national.com 12 LP3905 Application Information (Continued) The ceramic capacitor’s capacitance can vary with temperature. The capacitor type X7R, which operates over a temperature range of -55˚C to +125˚C, will only vary the capacitance to within ± 15%. The capacitor type X5R has a similar tolerance over a reduced temperature range of -55˚C to +85˚C. Tantalum capacitors are less desirable than ceramic for use as output capacitors because they are more expensive when comparing equivalent capacitance and voltage ratings in the 1µF to 4.7µF range. Another important consideration is that tantalum capacitors have higher ESR values than equivalent size ceramics. This means that while it may be possible to find a tantalum capacitor with an ESR value within the stable range, it would have to be larger in capacitance (which means bigger and more costly ) than a ceramic capacitor with the same ESR value. It should also be noted that the ESR of a typical tantalum will increase about 2:1 as the temperature goes from 25˚C down to -40˚C, so some guard band must be allowed. LDO Input Capacitor An input capacitor is required for stability. The input capacitor should be at least equal to or greater than the output capacitor. It is recommended that a 1µF capacitor be connected between VIN2 input pin and ground (this capacitance value may be increased without limit). This capacitor must be located a distance of not more than 1cm from the input pin and returned to a clean analogue ground. Any good quality ceramic, tantalum, or film capacitor may be used at the input. Important: Tantalum capacitors can suffer catastrophic failures due to surge current when connected to a lowimpedance source of power (like a battery or a very large capacitor). If a tantalum capacitor is used at the input, it must be guaranteed by the manufacturer to have a surge current rating sufficient for the application. There are no requirements for the ESR (Equivalent Series Resistance) on the input capacitor, but tolerance and temperature coefficient must be considered when selecting the capacitor to ensure the capacitance will remain 1.0µF ± 30% over the entire operating voltage and temperature range. LDO Output Capacitor The LP3905 LDOs are designed specifically to work with very small ceramic output capacitors. A ceramic capacitor (dielectric types X5R or X7R) in the 0.47µF to 10µF range, and with ESR between 5mΩ to 500mΩ, is suitable in the application circuit. For this device the output capacitor should be connected between the LDO1 and LDO2 pins and a good ground connection and should be mounted within 1cm of the device. The output capacitor must meet the requirement for the minimum value of capacitance and also have an ESR value that is within the range 5mΩ to 500mΩ for stability. No-Load Stability The LP3905 LDOs will remain stable and in regulation with no external load. Enable Control A 1MΩ pulldown resistor ties the EN1/2 input to ground, this ensures that the device will remain off when the enable pin is left open circuit. To ensure proper operation, the signal source used to drive the EN1/2 input must be able to swing above and below the specified turn-on/off voltage thresholds listed in the Electrical Characteristics section under VIL and VIH. EN1 can be used to turn ON Buck1 and LDO1/2. In this case Buck1 will be turned on first. Once Buck1 is powered up, after a typical 150µs delay LDO1/2 will be turned on concurrently. 13 www.national.com LP3905 LP3905 Board Layout Considerations PC board layout is an important part of DC-DC converter design. Poor board layout can disrupt the performance of a DC-DC converter and surrounding circuitry by contributing to EMI, ground bounce, and resistive voltage loss in the traces. These can send erroneous signals to the DC-DC converter IC, resulting in poor regulation or instability. Good layout for the LP3905 can be implemented by following a few simple design rules. 1. Place the Buck inductor and filter capacitors close together and make the traces short. The traces between these components carry relatively high switching currents and act as antennas. Following this rule reduces radiated noise. Special care must be given to place the input filter capacitor very close to the VIN and GND pin. 2. Arrange the components so that the switching current loops curl in the same direction. During the first half of each cycle, current flows from the input filter capacitor through the LP3905 and inductor to the output filter capacitor and back through ground, forming a current loop. In the second half of each cycle, current is pulled up from ground through the LP3905 by the inductor to the output filter capacitor and then back through ground forming a second current loop. Routing these loops so the current curls in the same direction prevents magnetic field reversal between the two half-cycles and reduces radiated noise. 3. Connect the ground pins of the Bucks and filter capacitors together using generous component-side copper fill as a pseudo-ground plane. Then, connect this to the ground-plane (if one is used) with several vias. This 4. reduces ground-plane noise by preventing the switching currents from circulating through the ground plane. It also reduces ground bounce at the LP3905 by giving it a low-impedance ground connection. Use wide traces between the power components and for power connections to the DC-DC converter circuit. This reduces voltage errors caused by resistive losses across the traces. 5. Route noise sensitive traces, such as the voltage feedback path, away from noisy traces between the power components. The voltage feedback trace must remain close to the Buck circuits and should be direct but should be routed opposite to noisy components. This reduces EMI radiated onto the DC-DC converter’s own voltage feedback trace. A good approach is to route the feedback trace on another layer and to have a ground plane between the top layer and layer on which the feedback trace is routed. In the same manner for the adjustable part it is desired to have the feedback dividers on the bottom layer. 6. Place noise sensitive circuitry, such as radio IF blocks, away from the DC-DC converter, CMOS digital blocks and other noisy circuitry. Interference with noisesensitive circuitry in the system can be reduced through distance. In mobile phones, for example, a common practice is to place the DC-DC converters on one corner of the board, arrange the CMOS digital circuitry around it (since this also generates noise), and then place sensitive preamplifiers and IF stages on the diagonally opposing corner. Often, the sensitive circuitry is shielded with a metal pan and power to it is post-regulated to reduce conducted noise, using lowdropout linear regulators. www.national.com 14 LP3905 Power Management Unit For Low Power Handheld Applications Physical Dimensions inches (millimeters) unless otherwise noted 14 Pin LLP Package NS Package Number SDA14B National does not assume any responsibility for use of any circuitry described, no circuit patent licenses are implied and National reserves the right at any time without notice to change said circuitry and specifications. For the most current product information visit us at www.national.com. LIFE SUPPORT POLICY NATIONAL’S PRODUCTS ARE NOT AUTHORIZED FOR USE AS CRITICAL COMPONENTS IN LIFE SUPPORT DEVICES OR SYSTEMS WITHOUT THE EXPRESS WRITTEN APPROVAL OF THE PRESIDENT AND GENERAL COUNSEL OF NATIONAL SEMICONDUCTOR CORPORATION. As used herein: 1. Life support devices or systems are devices or systems which, (a) are intended for surgical implant into the body, or (b) support or sustain life, and whose failure to perform when properly used in accordance with instructions for use provided in the labeling, can be reasonably expected to result in a significant injury to the user. BANNED SUBSTANCE COMPLIANCE National Semiconductor follows the provisions of the Product Stewardship Guide for Customers (CSP-9-111C2) and Banned Substances and Materials of Interest Specification (CSP-9-111S2) for regulatory environmental compliance. Details may be found at: www.national.com/quality/green. Lead free products are RoHS compliant. National Semiconductor Americas Customer Support Center Email: new.feedback@nsc.com Tel: 1-800-272-9959 www.national.com National Semiconductor Europe Customer Support Center Fax: +49 (0) 180-530 85 86 Email: europe.support@nsc.com Deutsch Tel: +49 (0) 69 9508 6208 English Tel: +44 (0) 870 24 0 2171 Français Tel: +33 (0) 1 41 91 8790 National Semiconductor Asia Pacific Customer Support Center Email: ap.support@nsc.com National Semiconductor Japan Customer Support Center Fax: 81-3-5639-7507 Email: jpn.feedback@nsc.com Tel: 81-3-5639-7560 2. A critical component is any component of a life support device or system whose failure to perform can be reasonably expected to cause the failure of the life support device or system, or to affect its safety or effectiveness.

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