CS5253-1GDPR5

CS5253−1 3.0 A LDO 5−Pin Adjustable Linear Regulator This new very low dropout linear regulator reduces total power dissipation in the application. To achieve very low dropout, the internal pass transistor is powered separately from the control circuitry. Furthermore, with the control and power inputs tied together, this device can be used in single supply configuration and still offer a better dropout voltage than conventional PNP − NPN based LDO regulators. In this mode the dropout is determined by the minimum control voltage. The CS5253−1 is offered in a five−terminal D2PAK−5 package, which allows for the implementation of a remote−sense pin permitting very accurate regulation of output voltage directly at the load, where it counts, rather than at the regulator. This remote sensing feature virtually eliminates output voltage variations due to load changes and resistive voltage drops. Typical load regulation measured at the sense pin is less than 1.0 mV for an output voltage of 2.5 V with a load step of 10 mA to 3.0 A. The CS5253−1 has a very fast transient loop response which can be adjusted using a small capacitor on the Adjust pin. Internal protection circuitry provides for “bust−proof” operation, similar to three−terminal regulators. This circuitry, which includes overcurrent, short circuit, and over−temperature protection will self protect the regulator under all fault conditions. The CS5253−1 is ideal for generating a 2.5 V supply to power graphics controllers used on VGA cards. Features http://onsemi.com 1 5 D2PAK−5 DP SUFFIX CASE 936AC Tab = VOUT Pin 1. VSENSE 2. Adjust 3. VOUT 4. VCONTROL 5. VPOWER MARKING DIAGRAM CS 5253−1 AWLYWWG 1 • • • • • • • • • • • • • VOUT Range Is 1.25 V to 5.0 V @ 3.0 A VPOWER Dropout < 0.40 V @ 3.0 A VCONTROL Dropout < 1.05 V @ 3.0 A 1.0% Trimmed Reference Fast Transient Response Remote Voltage Sensing Thermal Shutdown Current Limit Short Circuit Protection Drop−In Replacement for EZ1582 Backwards Compatible with 3−Pin Regulators Very Low Dropout Reduces Total Power Consumption Pb−Free Package is Available* CS5253−1 A WL Y WW G = Device Code = Assembly Location = Wafer Lot = Year = Work Week = Pb−Free Package ORDERING INFORMATION Device CS5253−1GDP5 CS5253−1GDPR5 CS5253−1GDPR5G Package D2PAK−5 D2PAK−5 D2PAK−5 (Pb−Free) Shipping† 50 Units/Rail 750/Tape & Reel 750/Tape & Reel †For information on tape and reel specifications, including part orientation and tape sizes, please refer to our Tape and Reel Packaging Specifications Brochure, BRD8011/D. *For additional information on our Pb−Free strategy and soldering details, please download the ON Semiconductor Soldering and Mounting Techniques Reference Manual, SOLDERRM/D. © Semiconductor Components Industries, LLC, 2006 September, 2006− Rev. 11 1 Publication Order Number: CS5253−1/D CS5253−1 5.0 V VCONTROL CS5253−1 2.5 V @ 3.0 A 3.3 V VPOWER Adjust 10 mF 10 V 100 mF 5.0 V VSENSE 124 1.0% 124 1.0% Load 300 mF 5.0 V VOUT Figure 1. Application Diagram MAXIMUM RATINGS Rating VPOWER Input Voltage VCONTROL Input Voltage Operating Junction Temperature Range, TJ Storage Temperature Range ESD Damage Threshold Lead Temperature Soldering: Reflow: (SMD styles only) (Note 1) Value 6.0 13 0 to 150 −65 to +150 2.0 230 peak Unit V V °C °C kV °C Stresses exceeding Maximum Ratings may damage the device. Maximum Ratings are stress ratings only. Functional operation above the Recommended Operating Conditions is not implied. Extended exposure to stresses above the Recommended Operating Conditions may affect device reliability. 1. 60 second maximum above 183°C. ELECTRICAL CHARACTERISTICS (0°C ≤ TA ≤ 70°C; 0°C ≤ TJ ≤ 150°C; VSENSE = VOUT and VADJ = 0 V; unless otherwise specified.) Characteristic CS5253−1 Reference Voltage Line Regulation Load Regulation Minimum Load Current (Note 2) Control Pin Current (Note 3) Adjust Pin Current Current Limit Short Circuit Current VCONTROL = 2.75 V to 12 V, VPOWER = 2.05 V to 5.5 V, IOUT = 10 mA to 3.0 A VCONTROL = 2.5 V to 12 V, VPOWER = 1.75 V to 5.5 V, IOUT = 10 mA VCONTROL = 2.75 V, VPOWER = 2.05 V, IOUT = 10 mA to 3.0 A, with Remote Sense VCONTROL = 5.0 V, VPOWER = 3.3 V, DVOUT = +1.0% VCONTROL = 2.75 V, VPOWER = 2.05 V, IOUT = 100 mA VCONTROL = 2.75 V, VPOWER = 2.05 V, IOUT = 3.0 A VCONTROL = 2.75 V, VPOWER = 2.05 V, IOUT = 10 mA VCONTROL = 2.75 V, VPOWER = 2.05 V, DVOUT = −1.0% VCONTROL = 2.75 V, VPOWER = 2.05 V, VOUT = 0 V 1.237 (−1.0%) − − − − − − 3.1 2.0 1.250 0.02 0.04 5.0 6.0 35 60 4.0 3.5 1.263 (+1.0%) 0.2 0.3 10 10 120 120 − − V % % mA mA mA mA A A Test Conditions Min Typ Max Unit 2. The minimum load current is the minimum current required to maintain regulation. Normally the current in the resistor divider used to set the output voltage is selected to meet the minimum load current requirement. 3. The VCONTROL pin current is the drive current required for the output transistor. This current will track output current with roughly a 1:100 ratio. The minimum value is equal to the quiescent current of the device. http://onsemi.com 2 CS5253−1 ELECTRICAL CHARACTERISTICS (0°C ≤ TA ≤ 70°C; 0°C ≤ TJ ≤ 150°C; VSENSE = VOUT and VADJ = 0 V; unless otherwise specified.) Characteristic CS5253−1 Ripple Rejection (Note 4) Thermal Regulation VCONTROL Dropout Voltage (Minimum VCONTROL − VOUT) (Note 5) VPOWER Dropout Voltage (Minimum VPOWER − VOUT) (Note 5) RMS Output Noise Temperature Stability Thermal Shutdown (Note 6) Thermal Shutdown Hysteresis VCONTROL Supply Only Output Current VPOWER Supply Only Output Current VCONTROL = VPOWER = 3.25 V, VRIPPLE = 1.0 VP−P @ 120 Hz, IOUT = 4.0 A, CADJ = 0.1 mF 30 ms Pulse, TA = 25°C VPOWER = 2.05 V, IOUT = 100 mA VPOWER = 2.05 V, IOUT = 1.0 A VPOWER = 2.05 V, IOUT = 3.0 A VCONTROL = 2.75 V, IOUT = 100 mA VCONTROL = 2.75 V, IOUT = 1.0 A VCONTROL = 2.75 V, IOUT = 3.0 A Freq = 10 Hz to 10 kHz, TA = 25°C − − − VCONTROL = 13 V, VPOWER Not Connected, VADJ = VOUT = VSENSE = 0 V VPOWER = 6.0 V, VCONTROL Not Connected, VADJ = VOUT = VSENSE = 0 V 60 − − − − − − − − 0.5 150 − − − 80 0.002 0.90 1.00 1.05 0.05 0.15 0.40 0.003 − 180 25 − 0.1 − − 1.15 1.15 1.30 0.15 0.25 0.60 − − 210 − 50 1.0 dB %/W V V V V V V %VO UT Test Conditions Min Typ Max Unit % °C °C mA mA 4. This parameter is guaranteed by design and is not 100% production tested. 5. Dropout is defined as either the minimum control voltage (VCONTROL) or minimum power voltage (VPOWER) to output voltage differential required to maintain 1.0% regulation at a particular load current. 6. This parameter is guaranteed by design, but not parametrically tested in production. However, a 100% thermal shutdown functional test is performed on each part. PACKAGE PIN DESCRIPTION PIN # 1 2 PIN SYMBOL VSENSE Adjust FUNCTION This Kelvin sense pin allows for remote sensing of the output voltage at the load for improved regulation. It is internally connected to the positive input of the voltage sensing error amplifier. This pin is connected to the low side of the internally trimmed 1.0% bandgap reference voltage and carries a bias current of about 50 mA. A resistor divider from Adjust to VOUT and from Adjust to ground sets the output voltage. Also, transient response can be improved by adding a small bypass capacitor from this pin to ground. This pin is connected to the emitter of the power pass transistor and provides a regulated voltage capable of sourcing 3.0 A of current. This is the supply voltage for the regulator control circuitry. For the device to regulate, this voltage should be between 0.9 V and 1.3 V (depending on the output current) greater than the output voltage. The control pin current will be about 1.0% of the output current. This is the power input voltage. This pin is physically connected to the collector of the power pass transistor. For the device to regulate, this voltage should be between 0.1 V and 0.6 V greater than the output voltage depending on the output current. The output load current of 3.0 A is supplied through this pin. 3 4 VOUT VCONTROL 5 VPOWER http://onsemi.com 3 CS5253−1 VPOWER VCONTROL BIAS and TSD VREF − + EA IA + − VOUT VSENSE Adjust Figure 2. Block Diagram TYPICAL PERFORMANCE CHARACTERISTICS 1.253 1.252 Reference Voltage (V) 1.251 1.250 1.249 1.248 1.247 0 20 40 60 80 100 120 Load Regulation (%) 0.12 0.10 TJ = 120°C 0.08 0.06 0.04 0.02 0 0 0.5 1.0 1.5 2.0 TJ = 0°C TJ = 20°C 2.5 3.0 Junction Temperature (°C) Output Current (A) Figure 3. Reference Voltage vs Junction Temperature Figure 4. Load Regulation vs Output Current 5.0 VCONTROL = 5.0 V VPOWER = 3.3 V VOUT = 2.5 V CCONTROL = 10 mF CPOWER = 100 mF CADJ = 0.1 mF COUT = 300 mF VOUT 4.5 4.0 Output Current (A) 3.5 3.0 2.5 2.0 1.5 1.0 0.5 0 0 Measured at DVOUT = −1.0% ILOAD, 10 mA to 3.0 A 1 2 3 4 5 6 VPOWER − VOUT (V) Figure 5. Transient Response Figure 6. Output Current vs VPOWER − VOUT http://onsemi.com 4 CS5253−1 85 80 75 70 65 60 Minimum Load Current (mA) 1200 1150 1100 1050 1000 950 900 850 0 20 40 60 80 100 120 140 800 1.0 2.0 3.0 4.0 5.0 6.0 7.0 8.0 9.0 10 11 VPOWER = 3.3 V DVOUT = +1.0% IADJ (mA) Junction Temperature (°C) VCONTROL − VOUT (V) Figure 7. Adjust Pin Current vs Junction Temperature 3.9 Short Circuit Output current Limit (A) 3.8 3.7 3.6 3.5 3.4 3.3 VCONTROL = 2.75 V VPOWER = 2.05 V Ripple Rejection (dB) Figure 8. Minimum Load Current vs VCONTROL − VOUT 90 80 70 60 50 40 30 20 VIN − VOUT = 2.0 V IOUT = 4.0 A VRIPPLE = 1.0 VP−P COUT = 22 mF CADJ = 0.1 mF 102 103 104 105 106 0 20 40 60 80 100 120 140 10 101 Junction Temperature (°C) Frequency (Hz) Figure 9. Short Circuit Output Current vs Junction Temperature 12 10 8 IOUT (mA) 6 4 2 0 VCONTROL Dropout Voltage (mV) VCONTROL = 13 V VOUT = 0 V VPOWER Not Connected 1100 Figure 10. Ripple Rejection vs Frequency VPOWER = 2.05 V TJ = 0°C 1000 TJ = 20°C 900 TJ = 120°C 0 20 40 60 80 100 120 140 800 0 0.5 1.0 1.5 2.0 2.5 3.0 Junction Temperature (°C) Output Current (A) Figure 11. VCONTROL Only Output Current vs Junction Temperature Figure 12. VCONTROL Dropout Voltage vs Output Current http://onsemi.com 5 CS5253−1 500 450 VPOWER Dropout Voltage (V) 400 350 300 250 200 150 100 50 0 0 0.5 1.0 1.5 2.0 2.5 3.0 TJ = 20°C TJ = 0°C Minimum Load Current (mA) TJ = 120°C 916.4 916.3 916.2 916.1 916.0 915.9 915.8 915.7 915.6 915.5 915.4 0.5 1.5 2.5 VPOWER − VOUT (V) 3.5 4.5 VCONTROL = 5.0 V DVOUT = +1.0% Output Current (A) Figure 13. VPOWER Dropout Voltage vs Output Current 30 25 20 IOUT (mA) 15 10 5 0 VPOWER = 6.0 V VOUT = 0 V VCONTROL Not Connected ICONTROL (mA) Figure 14. Minimum Load Current vs VPOWER − VOUT 40 35 30 25 20 15 10 5 IOUT = 100 mA 0 20 40 60 80 100 120 140 IOUT = 1.0 A VCONTROL = 2.75 V VPOWER = 2.05 V IOUT = 3.0 A 0 20 40 60 80 100 120 140 0 Junction Temperature (°C) Junction Temperature (°C) Figure 15. VPOWER Only Output Current vs Junction Temperature 5.0 VPOWER = 3.3 V VCONTROL = 5.0 V VOUT = 2.5 V TA = 25°C 4.5 ESR (W) Figure 16. VCONTROL Supply Current vs Junction Temperature 6 5 4 Unstable 3 2 Stable Region 1 VPOWER = 3.3 V VCONTROL = 5.0 V ILOAD = 0 to 3.0 A VOUT = 2.5 V VOUT Shorted to VSENSE TJ = 0°C to 150°C Current Limit (A) 4.0 3.5 0 0.5 1.0 1.5 VOUT (V) 2.0 2.5 3.0 0 0 10 20 30 40 50 60 70 80 90 100 Capacitance (mF) Figure 17. Current Limit vs VOUT Figure 18. Stability vs ESR http://onsemi.com 6 CS5253−1 APPLICATIONS NOTES A resistor divider network R1 and R2 causes a fixed current The CS5253−1 linear regulator provides adjustable to flow to ground. This current creates a voltage across R2 voltages from 1.26 V to 5.0 V at currents up to 3.0 A. The that adds to the 1.260 V across R1 and sets the overall output regulator is protected against short circuits, and includes a voltage. The adjust pin current (typically 50 mA) also flows thermal shutdown circuit with hysteresis. The output, which through R2 and adds a small error that should be taken into is current limited, consists of a PNP−NPN transistor pair and account if precise adjustment of VOUT is necessary. The requires an output capacitor for stability. A detailed procedure output voltage is set according to the formula: for selecting this capacitor is included in the Stability R1 ) R2 VOUT + 1.260 V ) R2 IADJ R1 Considerations section. The term IADJ × R2 represents the error added by the adjust VPOWER Function pin current. R1 is chosen so that the minimum load current is The CS5253−1 utilizes a two supply approach to maximize at least 10 mA. R1 and R2 should be of the same composition efficiency. The collector of the power device is brought out for best tracking over temperature. The divider resistors to the VPOWER pin to minimize internal power dissipation should be placed physically as close to the load as possible. under high current loads. VCONTROL provides for the control While not required, a bypass capacitor connected between circuitry and the drive for the output NPN transistor. the adjust pin and ground will improve transient response and VCONTROL should be at least 1.0 V greater than the output ripple rejection. A 0.1 mF tantalum capacitor is recommended voltage. Special care has been taken to ensure that there are for “first cut” design. Value and type may be varied to no supply sequencing problems. The output voltage will not optimize performance vs. price. turn on until both supplies are operating. If the control voltage Other Adjustable Operation Considerations comes up first, the output current will be limited to about three The CS5253−1 linear regulator has an absolute maximum milliamperes until the power input voltage comes up. If the specification of 6.0 V for the voltage difference between power input voltage comes up first, the output will not turn on VPOWER and VOUT. However, the IC may be used to regulate at all until the control voltage comes up. The output can never voltages in excess of 6.0 V. The two main considerations in come up unregulated. such a design are the sequencing of power supplies and short The CS5253−1 can also be used as a single supply device with circuit capability. the control and power inputs tied together. In this mode, the Power supply sequencing should be such that the dropout will be determined by the minimum control voltage. VCONTROL supply is brought up coincidentally with or before Output Voltage Sensing the VPOWER supply. This allows the IC to begin charging the The CS5253−1 five terminal linear regulator includes a output capacitor as soon as the VPOWER to VOUT differential dedicated VSENSE function. This allows for true Kelvin is large enough that the pass transistor conducts. As VPOWER sensing of the output voltage. This feature can virtually increases, the pass transistor will remain in dropout, and eliminate errors in the output voltage due to load regulation. current is passed to the load until VOUT is in regulation. Regulation will be optimized at the point where the sense pin Further increase in the supply voltage brings the pass is tied to the output. transistor out of dropout. In this manner, any output voltage DESIGN GUIDELINES less than 13 V may be regulated, provided the VPOWER to Adjustable Operation VOUT differential is less than 6.0 V. In the case where This LDO adjustable regulator has an output voltage range VCONTROL and VPOWER are shorted, there is no theoretical of 1.26 V to 5.0 V. An external resistor divider sets the output limit to the regulated voltage as long as the VPOWER to VOUT voltage as shown in Figure 19. The regulator’s voltage differential of 6.0 V is not exceeded. sensing error amplifier maintains a fixed 1.260 V reference There is a possibility of damaging the IC when between the output pin and the adjust pin. VPOWER − VOUT is greater than 6.0 V if a short circuit 5.0 V occurs. Short circuit conditions will result in the immediate VCONTROL VOUT operation of the pass transistor outside of its safe operating area. Overvoltage stresses will then cause destruction of the 2.5 V CS5253−1 pass transistor before overcurrent or thermal shutdown @ 3.0 A 3.3 V circuitry can become active. Additional circuitry may be VPOWER VSENSE required to clamp the VPOWER to VOUT differential to less Adjust R1 than 6.0 V if fail safe operation is required. One possible clamp circuit is illustrated in Figure 20; however, the design of clamp circuitry must be done on an application by R2 application basis. Care must be taken to ensure the clamp actually protects the design. Components used in the clamp Figure 19. Typical Application Schematic. design must be able to withstand the short circuit condition The Resistor Divider Sets VOUT, With the Internal indefinitely while protecting the IC. 1.260 V Reference Dropped Across R1. THEORY OF OPERATION http://onsemi.com 7 CS5253−1 External Supply External Supply VCONTROL VSENSE CS5253−1 VPOWER VOUT VADJ where T is the time for the regulation loop to begin to respond. The very fast transient response time of the CS5253−1 allows the ESR effect to dominate. For microprocessor applications, it is customary to use an output capacitor network consisting of several tantalum and ceramic capacitors in parallel. This reduces the overall ESR and reduces the instantaneous output voltage drop under transient load conditions. The output capacitor network should be as close to the load as possible for the best transient response. Protection Diodes Figure 20. This Circuit Is an Example of How the CS5253−1 Can Be Short−Circuit Protected When Operating With VOUT > 6.0 V Stability Considerations The output compensation capacitor helps determine three main characteristics of a linear regulator: loop stability, startup delay, and load transient response. Different capacitor types vary widely in tolerance, Equivalent Series Resistance (ESR), Equivalent Series Inductance (ESI), and variation over temperature. Tantalum and aluminum electrolytic capacitors work best, with electrolytic capacitors being less expensive in general, but varying more in capacitor value and ESR over temperature. The CS5253−1 requires an output capacitor to guarantee loop stability. The Stability vs ESR graph in the typical performance section shows the minimum ESR needed to guarantee stability, but under ideal conditions. These include: having VOUT connected to VSENSE directly at the IC pins; the compensation capacitor located right at the pins with a minimum lead length; the adjust feedback resistor divider ground, (bottom of R2 in Figure 19), connected right at the capacitor ground; and with power supply decoupling capacitors located close to the IC pins. The actual performance will vary greatly with board layout for each application. In particular, the use of the remote sensing feature will require a larger capacitor with less ESR. For most applications, a minimum of 33 mF tantalum or 150 mF aluminum electrolytic, with an ESR less than 1.0 W over temperature, is recommended. Larger capacitors and lower ESR will improve stability. The load transient response, during the time it takes the regulator to respond, is also determined by the output capacitor. For large changes in load current, the ESR of the output capacitor causes an immediate drop in output voltage given by: There is then an additional drop in output voltage given by: DV + DI TC DV + DI ESR When large external capacitors are used with a linear regulator, it is sometimes necessary to add protection diodes. If the input voltage of the regulator gets shorted, the output capacitor will discharge into the output of the regulator. The discharge current depends on the value of the capacitor, the output voltage, and the rate at which VCONTROL drops. In the CS5253−1 regulator, the discharge path is through a large junction and protection diodes are not usually needed. If the regulator is used with large values of output capacitance and the input voltage is instantaneously shorted to ground, damage can occur. In this case, a diode connected as shown in Figure 21 is recommended. VCONTROL CS5253−1 VPOWER Adjust VOUT VSENSE Figure 21. Diode Protection Circuit A rule of thumb useful in determining if a protection diode is required is to solve for current: I+C T V where: I is the current flow out of the load capacitance when VCONTROL is shorted, C is the value of load capacitance V is the output voltage, and T is the time duration required for VCONTROL to transition from high to being shorted. If the calculated current is greater than or equal to the typical short circuit current value provided in the specifications, serious thought should be given to the use of a protection diode. http://onsemi.com 8 CS5253−1 Current Limit The internal current limit circuit limits the output current under excessive load conditions. Short Circuit Protection maximum junction temperature and the thermal resistance depend on the manufacturer and the package type. The maximum power dissipation for a regulator is: PD(max) + (VIN(max) * VOUT(min))IOUT(max) ) VIN(max) Iq The device includes short circuit protection circuitry that clamps the output current at approximately 500 mA less than its current limit value. This provides for a current foldback function, which reduces power dissipation under a direct shorted load. Thermal Shutdown The thermal shutdown circuitry is guaranteed by design to activate above a die junction temperature of approximately 150°C and to shut down the regulator output. This circuitry has 25°C of typical hysteresis, thereby allowing the regulator to recover from a thermal fault automatically. Calculating Power Dissipation and Heat Sink Requirements High power regulators such as the CS5253−1 usually operate at high junction temperatures. Therefore, it is important to calculate the power dissipation and junction temperatures accurately to ensure that an adequate heat sink is used. Since the package tab is connected to VOUT on the CS5253−1, electrical isolation may be required for some applications. Also, as with all high power packages, thermal compound in necessary to ensure proper heat flow. For added safety, this high current LDO includes an internal thermal shutdown circuit The thermal characteristics of an IC depend on the following four factors: junction temperature, ambient temperature, die power dissipation, and the thermal resistance from the die junction−to−ambient air. The maximum junction temperature can be determined by: TJ(max) + TA(max) ) PD(max) RqJA A heat sink effectively increases the surface area of the package to improve the flow of heat away from the IC and into the surrounding air. Each material in the heat flow path between the IC and the outside environment has a thermal resistance which is measured in degrees per watt. Like series electrical resistances, these thermal resistances are summed to determine the total thermal resistance between the die junction and the surrounding air, RqJA. This total thermal resistance is comprised of three components. These resistive terms are measured from junction to case (RqJC), case to heat sink (RqCS), and heat sink to ambient air (RqSA). The equation is: RqJA + RqJC ) RqCS ) RqSA The value for RqJC is 2.5°C/watt for the CS5253−1 in the D2PAK−5 package. For a high current regulator such as the CS5253−1 the majority of heat is generated in the power transistor section. The value for RqSA depends on the heat sink type, while the RqCS depends on factors such as package type, heat sink interface (is an insulator and thermal grease used?), and the contact area between the heat sink and the package. Once these calculations are complete, the maximum permissible value of RqJA can be calculated and the proper heat sink selected. For further discussion on heat sink selection, see our application note “Thermal Management,” document number AND8036/D, available through the Literature Distribution Center or via our website at http://www.onsemi.com. The maximum ambient temperature and the power dissipation are determined by the design while the http://onsemi.com 9 CS5253−1 PACKAGE DIMENSIONS D2PAK−5 DP SUFFIX CASE 936AC−01 ISSUE O A E K S B H W G D M L P R − A− N TERMINAL 6 U V NOTES: 1. DIMENSIONS AND TOLERANCING PER ANSI Y14.5M, 1982. 2. CONTROLLING DIMENSION: INCH. 3. PACKAGE OUTLINE EXCLUSIVE OF MOLD FLASH AND METAL BURR. 4. PACKAGE OUTLINE INCLUSIVE OF PLATING THICKNESS. 5. FOOT LENGTH MEASURED AT INTERCEPT POINT BETWEEN DATUM A AND LEAD SURFACE. INCHES MIN MAX 0.396 0.406 0.330 0.340 0.170 0.180 0.026 0.036 0.045 0.055 0.067 REF 0.580 0.620 0.055 0.066 0.000 0.010 0.098 0.108 0.017 0.023 0.090 0.110 0_ 8_ 0.095 0.105 0.30 REF 0.305 REF 0.010 MILLIMETERS MIN MAX 10.05 10.31 8.38 8.64 4.31 4.57 0.66 0.91 1.14 1.40 1.70 REF 14.73 15.75 1.40 1.68 0.00 0.25 2.49 2.74 0.43 0.58 2.29 2.79 0_ 8_ 2.41 2.67 7.62 REF 7.75 REF 0.25 C DIM A B C D E G H K L M N P R S U V W PACKAGE THERMAL DATA Parameter RqJC RqJA Typical Typical D2PAK−5 2.5 10−50* Unit °C/W °C/W *Depending on thermal properties of substrate. RqJA = RqJC + RqCA. ON Semiconductor and are registered trademarks of Semiconductor Components Industries, LLC (SCILLC). SCILLC reserves the right to make changes without further notice to any products herein. SCILLC makes no warranty, representation or guarantee regarding the suitability of its products for any particular purpose, nor does SCILLC assume any liability arising out of the application or use of any product or circuit, and specifically disclaims any and all liability, including without limitation special, consequential or incidental damages. “Typical” parameters which may be provided in SCILLC data sheets and/or specifications can and do vary in different applications and actual performance may vary over time. All operating parameters, including “Typicals” must be validated for each customer application by customer’s technical experts. SCILLC does not convey any license under its patent rights nor the rights of others. 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