NCL30060LED1GEVB

NCL30060GEVB Off‐line Critical Conduction Mode PFC LED Driver Evaluation Board User's Manual http://onsemi.com Value Unit Input Voltage Range Description 90 − 305 V rms Line Frequency Range 45 – 66 Hz 700 mA 10 – 41 V dc 25 W Output Current Output Voltage Range Maximum Output Power Power Factor (Typical) 0.99 − THDi (Typical) < 10 % Efficiency (Typical) 87.5 % EVAL BOARD USER’S MANUAL The compact evaluation board is constructed with through-hole components on the top and surface mount components on the bottom side. This driver was designed to meet safety agency requirements but has not been evaluated for compliance. When operating this board, observe safe standard working practices. High voltages are present and caution should be exercised when handling or probing various points to avoid personal injury or damage to the unit. Figures 1 and 2 illustrate the top and bottom sides of the evaluation board. AC input power connects to the block labeled J1. Terminals are marked “L” and “N” representing Line and Neutral leads. The LED load connects to the terminal block labeled J2 with polarity as marked. The anode of the LED load should be connected to “+” and the cathode to “−” terminal. Never connect LEDs to the driver while it is running or before the output capacitors discharge after removing input power. With no load connected, the output capacitors charge to > 44 V. Energy stored in the output capacitance can damage or shorten the effective life of the LEDs if improperly discharged into the LEDs. The schematic for the power section is shown in Figure 3, and dimming schematic is shown in Figure 4. Dimming control is accessible through the smaller connector labeled J31. Components have already been placed on the board to support standard 1−10 V dimming where a 10 V level provides full output current and 1 V or below reduces the LED current to a minimum level. The response between 1 and 10 V is linear in terms of LED current. This evaluation board will also support PWM dimming control by populating the board with the appropriate components as listed on the evaluation board Bill of Materials. The board was not intended to support both dimming methods simultaneously; therefore only components for one type of interface should be fitted at a time. The dimming interfaces are optional and do not require any connections if dimming is not required. This evaluation board does not support phase-cut or TRIAC dimming functions. Introduction The NCL30060 is intended to control a high performance critical conduction mode (CrM) LED driver providing high power factor and low total harmonic distortion of input current utilizing constant on-time control. This evaluation board provides constant current (CC) to the load over a wide LED string voltage range. The NCL30060 provides many features including high voltage start-up, direct drive for external power MOSFET, frequency dithering to reduce the EMI profile, maximum on-time protection, over voltage protection, and short circuit protection. These features work together to provide a robust LED driver solution packaged in a compact SO-7 case with one pin removed for improved creepage distance. As configured, this evaluation board provides 700 mA constant current at up to 25 W and directly interfaces to a string of LEDs. This evaluation board supports 1−10 V and PWM dimming control signals referenced to low voltage secondary circuits. The default configuration supports standard 1−10 V dimming. The evaluation board will support PWM dimming by populating alternate component positions provided on the PCB. An in-depth description of constant on-time control and performance of a single stage flyback LED driver can be found in the datasheet of a related controller, the NCL30000. This manual also addresses modifications to change the output current and output voltage ranges. The NCL30060 specification contains additional information on operation of the controller. Design calculations are presented in an Excel® Worksheet available at onsemi.com to aide in customized design applications. © Semiconductor Components Industries, LLC, 2014 May, 2014 − Rev. 0 1 Publication Order Number: EVBUM2240/D NCL30060GEVB Figure 1. NCL30060G Evaluation Board (Top Side) Figure 2. NCL30060G Evaluation Board (Bottom Side) http://onsemi.com 2 1 Neutral J1−2 Line RV1 V300LA4 CX1 N.F. C4 1 nF R10 51 kW D7 MMSD103 R1A 5.6 kW L2 6 mH 47 nF CX2 D12 MMSD103 1 2 3 4 R11 1 kW HV FB CS/ZCD RT VCC GND DRV 6 5 7 U1 NCL30060 D2 MRA4007 2.2 mH L3 R2 5.6 kW D4 MRA4007 C1 220 nF C13 22 pF 1 D3 MRA4007 R7 5.76 kW 4.7 nF C2 Q1 SPD06N80 Q1A N.F. 3 1 D5 ES1M 5 4 2 T1 CY 4.7 nF FL1 FL2 FL3 FL4 + + C7 100 pF Q5 MMBTA06 R19 24 kW R14 22 kW U4 R16 NCP431A 16 kW R15 22 kW R13 1 kW MURD320 D8 1 D1 MRA4007 R6 R1 5.6 kW U2 F1 FUSE 5.6 kW R4 100 kW D6 MMSD103 Q3 MMBT5550 D10 17 V C6 10 mF 3 R12 0.1 W http://onsemi.com PS2513−1 3 4 Figure 3. Power Stage Schematic 2 C11 680 mF C12 680 mF J1−1 1 2 3 4 VCC OUT2 IN2N IN2P R18 470 W R17 200 W OUT1 IN1N IN1P GND U3 LM2904 8 7 6 5 R24 0.1 W MBRA210 D13 D9 BAW56 Anode C9 100 nF VOUT R23 24 kW Cathode 1 J2−1 RTN Adjust C8 220 nF R22 1 kW J2−2 1 NCL30060GEVB Populate only one Interface Type at a time Control Input RTN 1 1 J31−2 +V J31−1 D31 MMSZ4689 Maximum Input 15 Vdc R42 1 MW R41 10 kW R31 1 kW 1 2 3 4 C41 1 nF − + 1 2 4 U42 NCP431A R44 2.2 kW R43 287 kW R33 10 kW C31 10 mF 1−10 Volt Dimming Interface U41 TLV271 3 5 U32 NCP431A R35 22 kW C43 1 nF Q41 MMBTA06 R6 Sets Minimum LED Current C42 100 nF R36 1 MW Affects Maximum LED Current R34 330 kW R47 75 kW U31A NL17SZ17 SC−88−5 R45 220 kW R46 6.2 kW R32 1 MW 2 PWM Dimming Interface R48 3.16 kW http://onsemi.com 5 Figure 4. Dimming Control Schematic R49 22 kW 4 U43 NCP431A R50 22 kW 100 Hz to 5 kHz Input Logic High = 2 to 5.5 V Logic Low < 0.6 V RTN Adjust Minimum Input Voltage = 13 V VOUT NCL30060GEVB NCL30060GEVB General Behavior/Waveforms The evaluation board is based on a single stage flyback converter. This topology provides isolation and high power factor utilizing a single power magnetic and switching device. Single stage converters require minimizing filter capacitance after the diode bridge and loop response less than 20 Hz to achieve high power factor and low THDi. Shown below are waveforms of Q1 switching MOSFET drain voltage and current as monitored across sense resistor R12. The evaluation board is operating with 25 W LED load. Note the scale factors were left unchanged between photos to highlight the relationship between drain voltage, current, and operating frequency. Figure 7. Drain Voltage and Current at 305 V ac Input The photo below is the drain voltage showing the envelope of the rectified sine wave input. The rectified sine shape provides high power factor performance. Figure 5. Drain Voltage and Current at 90 V ac Input Figure 8. Drain Voltage at 230 V ac with Slower Scan This converter operates in critical conduction mode (CrM) where the power switch turns on as soon as the transformer core is reset to provide maximum utilization of the transformer. This can be seen in Figure 9 which shows the bias winding voltage in the top trace and the switching MOSFET gate signal in the bottom trace. Figure 6. Drain Voltage and Current at 230 V ac Input http://onsemi.com 5 NCL30060GEVB The voltage on the transformer bias winding remains constant until the core is demagnetized, at which time the voltage begins to fall. When the voltage crosses the zero current detect (ZCD) threshold of 55 mV, the gate drive (DRV) is issued which turns on the MOSFET. The DRV signal remains high until the on-time expires and then DRV falls to a low state turning off the MOSFET. When the MOSFET turns off, the bias winding voltage returns to the high state. Typical Performance LED Current (mA) Figure 9. Bias Winding and DRV in CrM Operation 1000 90% 950 89% 900 88% 850 87% 800 86% 750 85% 700 84% 650 83% 600 82% LED Current 550 Efficiency 81% 500 80% 90 120 150 180 210 240 Input Voltage (Vac) Figure 10. Efficiency and Line Regulation http://onsemi.com 6 270 300 Efficiency (%) Figure 10 shows efficiency line regulation performance for the evaluation board. Figure 11 is a plot of load regulation with 115 V ac input. Note the converter enters protection modes for very low and very high output voltage. Power Factor and input current total harmonic distortion (THDi) is shown in Figure 12 for the evaluation board driving 12 LED load. Curves for both 50 Hz and 60 Hz operation are shown. NCL30060GEVB 50 45 40 Output Voltage (V) 35 30 25 20 15 10 5 0 0 100 200 300 400 500 600 700 800 Output Current (mA) 24 1.00 22 0.99 20 0.98 18 0.97 60 Hz THDi 50 Hz THDi 16 0.96 60 Hz PF 14 0.95 50 Hz PF 12 0.94 10 0.93 8 0.92 6 0.91 4 0.90 90 120 150 180 210 240 Input Voltage (Vac) Figure 12. Power Factor and THDi http://onsemi.com 7 270 300 Power Factor (PF) Input Current THD (%) Figure 11. Load Regulation NCL30060GEVB Setting Output Current Table 1. TRANSFORMER WIRE CONNECTIONS The LED output current is directly sensed to provide good regulation over a wide operating range. Current is sensed via a resistor (R24) placed in series with the negative output lead and the voltage across this resistor is compared to a reference to generate a feedback signal. The feedback signal is passed to the primary to control the on-time of the NCL30060 providing closed loop operation. The loop response of this single stage converter is low in order to provide high power factor and low THDi. At startup, the output current will overshoot until the control loop has time to respond. The amount of overshoot is controlled by a second feedback loop called the fast loop. This loop activates quickly at startup and limits the output current, but does not provide high power factor performance. After a delay, the main current loop takes over regulation at the target current while maintaining high power factor. The current threshold for the fast loop must be set higher than the peak of the LED ripple current to ensure optimal power factor performance. Resistors R16, R17, and R18 establish the proper reference levels for the main and fast current loops. As built, the reference for the main loop is 70 mV, and the fast loop is 100 mV. The LED output current, ILED, is given by the formula below: I LED + 70 mV R24 Transformer Wire Number Default PCB Wire Location (Series) PCB Location for Low Voltage (Parallel) FL1 H6 H6 FL2 H3 H2 FL3 H4 H5 FL4 H1 H1 Open Load Protection The evaluation board is configured as a current source; therefore the output voltage will increase until the current set point of 700 mA is achieved. If no load is connected, the output voltage would rise excessively and must be limited to avoid damage to the output capacitors. The NCL30060 ZCD input monitors the output voltage via the bias winding voltage which is related to the output voltage by the turns ratio of the transformer. R7, D7, and R11 form the path from the bias winding to the ZCD input. When the ZCD input reaches 6 V, the controller shuts off the MOSFET preventing excessive output voltage. The recommended value of R11 is 1 kW to provide proper response of the current sense function. R7 is selected to provide 6 V on the ZCD input when the LED output voltage reaches the open load protection threshold. C13 is a noise filter for ZCD operation. Shown in Figure 13 below is the bias winding in the top trace and the main secondary voltage in the lower trace. Note the right side showing a rising voltage when the MOSFET turns off. (eq. 1) The default value for R24 is 0.1 W, therefore the LED current will be 700 mA. ILED can also be set by adjusting the reference dividing resistors R16, R17, and R18. Ensure that the reference level on the fast loop is higher than the peak of the LED ripple current to avoid degrading the power factor. Adjusting Output Voltage Range The NCL30060 evaluation board was designed to cover a wide range of customer applications. As delivered, it is configured for 700 mA over a voltage range of 10 to 41 V. Lower voltage/higher current configurations can also be supported with a simple modification. The transformer secondary winding is comprised of two halves. The evaluation board default configuration is a series connection of the two secondary windings. For LED voltage applications of 9 to 20 V, the secondary windings should be changed to a parallel configuration. LED string voltages below 9 V will require an alternate transformer design which provides proper secondary bias voltage. The transformer secondary uses four wires (Flying Leads) from the magnetic to the PCB. Table 1 below shows the two possible configurations for secondary windings. Figure 13. Bias Winding Ringing Compared to Secondary Winding Waveform The ringing on the bias winding (top trace) compared to the secondary winding (lower trace) reveals an error http://onsemi.com 8 NCL30060GEVB introduced by the transformer leakage inductance. Monitoring the bias winding to detect output voltage directly would indicate a false open load condition. The NCL30060 measures the ZCD pin 2 ms after the MOSFET turns off to allow the ringing to subside and avoid erroneous readings caused by leakage inductance. When the NCL30060 detects an open load condition, the MOSFET is turned off and is held off for 1.25 ms, at which time another DRV pulse is issued. If the open load condition is still present, the MOSFET will be turned off again for 1.25 ms. Should four events occur in succession, the controller shuts down for 1 second to protect the system, and then attempts a restart. Qualifying four events avoids an interruption in operation due to disturbance such as surge or static discharge. Figure 14 below is the bias winding voltage in the top trace and the DRV in the lower trace during an open load condition. Note the 1.25 ms periods of no switching and after the fourth consecutive event the controller shuts off for the extended 1 second period. initiating the next switching cycle in CrM operation. Normal converter startup produces the same extended off-times as shorted output requiring differentiation between these two events for proper protection. High power factor operation further compounds detection of shorted output due to the fact the energy transfer follows the rectified sine envelope of the applied power. The extended off-time characteristic of a shorted output may only occur near the peaks of the sine envelope making a standard timer based solution not possible. A novel asymmetrical detection method accounts for the extended off-time occurring only at the peaks of the applied voltage. Further details on shorted output detection can be found in the NCL30060 datasheet. Shown below is the typical response of the evaluation board to a shorted output. This trace shows output current flowing for about 40 ms before the shorted output detection circuit shuts off the converter. After a 1 second delay, the converter attempts a restart. When the shorted output is removed, recovery is automatic. Figure 14. Open Load Protection Shutdown Figure 15. Current Pulses during Shorted Output The CS/ZCD pin monitors primary current during the MOSFET on-time and bias winding voltage during off-time. D7 is a blocking diode which allows this dual sensing. Note that capacitance on the CS/ZCD pin will affect converter operation. Typically, this pin cannot be directly monitored as probe capacitance can alter circuit timing. Additionally, board capacitance and recovery characteristics of D7 can affect converter operation. Best performance is achieved by selecting a low capacitance diode with recovery time of less than 35 ns for D7 to avoid residual voltage on the CS/ZCD pin as the converter naturally progresses from on-time to off-time. PCB traces should be kept as short as possible to avoid parasitic capacitance. Dimming Functions The NCL30060 evaluation board accepts dimming control functions through screw terminal connector J31. The board is factory configured for 1−10 V control, but can be easily modified for PWM dimming control by installing alternate components on the PCB. The dimming interface is referenced to the secondary ground, but does not share the negative lead of the LED load. Do not make a connection between the negative of J31 and the negative of output connector J2. This will interfere with LED current sensing. 1−10 Volt Dimming The typical 1−10 V dimming control for lighting provides full output when the dimming control is at 10 V and minimum output at 1 V or below. The interface on the NCL30060 evaluation board will accept a direct connection to a voltage source, such as a variable dc supply to achieve dimming over the 1 to 10 volt range. Multiple LED driver Shorted Output Protection During the on-time, energy is stored in the flyback transformer and during the off-time the energy is delivered to the secondary. When the converter is operating with low output voltage, the off-time is extended as it is the product of voltage and time which demagnetizes the transformer http://onsemi.com 9 NCL30060GEVB PWM Dimming boards can be connected in parallel allowing control of many lighting fixtures from one variable dc supply. The dimming interface will also support dimming control using a potentiometer noting that the evaluation board interface is capable of sourcing 10 V. (Note, a logarithmic taper potentiometer is suggested for more proportional light control with potentiometer setting.) Multiple fixtures can be connected together when using a potentiometer; however the adjustment region will be more compressed. This is due to multiple LED drivers where each dimming interface is contributing some current to the same potentiometer. An alternate approach to a potentiometer is a commercial 1−10 V dimming control. An example of this control is a potentiometer which has a transistor follower as a current buffer to minimize the effect of current sourced from multiple dimming interface circuits. The 1−10 volt dimming interface will work with all three control methods. The 1−10 volt dimming control injects a proportional signal into the current feedback loop essentially subtracting the control input proportionally from the feedback required from the LED current sense resistor. This provides a stable wide-range dimming control. 10 volts on the input provides zero output from the summing amplifier U41. R45 in conjunction with R44 and R46 results in zero current through R36 which means no modification to the current feedback. Therefore, full LED is applied to the load. A voltage higher than 10 V has no effect on the feedback loop. Maximum voltage at the dimming control input is 15 V. As the dimming control voltage is reduced, U41 amplifies the signal and raises the voltage on R36, which proportionally reduces the feedback signal from the sense resistor. U42 clamps this summed signal to 2.5 V when the dimming input is lowered to 1 V. Further reduction in dimming input voltage will have no effect due to the clamping of U42. The value of R36 determines the minimum current flowing through the LED load. The formula to calculate R36 is given below: R 23 ǒV U42 * KǓ R 36 + Where: K + V U4 K * I LED ǒR R 18 “Clamp” There is an area on the bottom side of the PCB labeled “Clamp”. These component locations are reserved for a future enhancement. The demo board is shipped without populating this area. (eq. 2) R 24 16 ) R 17 ) R 18 Components to support a PWM dimming input can be placed on the NCL30060 evaluation board in the designated area. Components used for 1−10 V dimming must be removed when using the PWM dimming input. The evaluation board converts the PWM signal to an analog level. Therefore the LED current responds to the average duty factor of the PWM signal being subtracted from the full LED current. For example, a PWM signal which is at the high state for 10% will result in 90% of the full LED current. A PWM signal which is at the high state 70% of the time will result in an LED current of 30% of maximum. U31 is a Schmitt trigger buffer which receives the PWM signal providing a fixed amplitude square wave with fast rise and fall times. R33 and C31 filter the PWM signal to an average level which is then impressed on R36. Since the PWM input is converted to an analog voltage to linearly dim the LED current, the PWM frequency is not critical. PWM frequencies from 100 Hz up to 20 kHz are acceptable. The control method functions the same as with the 1−10 V dimming. R31 and D31 limit the PWM dimming signal to 5.1 V protecting the input of U31. 12 V is the maximum input. R2 ensures if no PWM signal is applied, the LED current will be at the maximum level. R34 sets the maximum level when duty factor is 0%. If R34 is omitted, the maximum LED current will be slightly higher than the target value without the PWM dimming circuit. Ǔ (eq. 3) For the example evaluation board with minimum LED current of 120 mA, R36 is approximately 1 MW. http://onsemi.com 10 NCL30060GEVB Table 2. BILL OF MATERIALS Substitution Allowed Yes Designator Qty. Description Value Tolerance Footprint Manufacturer Manufacturer Part Number CY 1 Capacitor, Y5U X1Y1 4.7 nF, 250 VAC 20% Radial Panasonic CD16-E2GA472MYNS CX1 0 DNP − − Box − − − CX2 1 Metallized Polyester Film X1 47 nF, 300 VAC 20% Box Panasonic ECQ-U3A473MG Yes C2 1 Ceramic 4700 pf, 500 V 10% 1206 TDK CGJ5H4X7R2H472K115AA Yes C1 1 Metallized Polyester Film X1 220 nF, 300 VAC 20% Box Panasonic ECQ-U2A224ML Yes C4 1 Ceramic COG 1 nF, 50 V 10% 0603 TDK C1608COG1H102K080AA Yes C7 1 Ceramic COG 100 pF, 50 V 5% 0603 TDK C1608COG1H101J080AA Yes C6 1 Ceramic 10 mF, 35 V 15% 1206 TDK C3216X7R1V106M Yes C8 1 Ceramic X7R 220 nF, 50 V 10% 1206 TDK C3216X7R1H224K115AA Yes C9 1 Ceramic X7R 100 nF, 50 V 10% 0603 TDK C1608X7R1H104K080AA Yes C11, C12 2 Aluminum Electrolytic 680 mF, 63 V 20% Radial Nichicon UPW1J681MHD6 Yes C13 1 Ceramic NPO 22 pF, 50 V 5% 0603 TDK C11608C0G1H220J080AA Yes D1, D2, D3, D4 4 Rectifier 1000 V, 1 A − SMA ON Semiconductor MRA4007T3 No D5 1 Fast Rectifier 1 A 1000 V − SMA Micro Commercial ES1M Yes D6, D7 2 Diode 250 V, 200 mA − SOD123 ON Semiconductor MMSD103T1G No D8 1 RECTIFIER 200 V, 3 A − DPAK ON Semiconductor MURD320T4G No D9 1 Diode 70 V, 200 mA − SOT23 ON Semiconductor BAW56LT1G No D10 1 ZENER, Low Current 17 V 5% SOD123 ON Semiconductor MMSZ4704T1G No D12 1 Diode 250 V, 200 mA − SOD123 ON Semiconductor MMSD103T1G No D13 1 Schottky Rectifier 10 V, 2 A − SMA ON Semiconductor MBRA210LT3G No F1 1 Slow Blow TE5 Series 1A − Axial Littelfuse 36911000440 Yes J1, J2 2 2 Position Terminal Block − − Through Hole Wiedmuller 1716020000 Yes L2 1 Dual Coil 6 mH, 1.6 W, 500 mA 10% Through Hole Wurth Midcom 750311895 Yes L3 1 Drum Inductor 2.2 mH 10% Through Hole Wurth Midcom 768772222 Yes Q1 1 N-Channel MOSFET 800 V 6 A 0.9 W − DPAK Infineon SPD06N80C3 Yes Q1A 1 DNP − − TO-220 − − − Q3 1 NPN Transistor 140 V, 600 mA − SOT23 ON Semiconductor MMBT5550LT1G No Q5 1 NPN Driver Transistor 80 V, 500 mA − SOT23 ON Semiconductor MMBTA06LT1G No RV1 1 Varistor 300 V, 25 J − Radial Littelfuse V300LA4P Yes R1, R1A, R2, R6 4 Resistor 5.6 kW, 1/10 W 5% 0603 Panasonic ERJ-3GEYJ562V Yes R4 1 Resistor 100 kW, 1/4 W 5% 1206 Various Various Yes R7 1 Resistor 5.76 kW, 1/4 W 1% 1206 Various Various Yes R10 1 Resistor 51 kW, 1/10 W 1% 0603 Various Various Yes R11 1 Resistor 1 kW, 1/10 W 1% 0603 Various Various Yes R12 1 Resistor 0.1 W, 1/4 W 1% 1206 Rohm Semi MCR18EZHFLR100 Yes R13 1 Resistor 1 kW, 1/10 W 1% 0603 Various Various Yes R14 1 Resistor 22 kW, 1/4 W 5% 1206 Various Various Yes R15 1 Resistor 22 kW, 1/10 W 1% 0603 Various Various Yes R16 1 Resistor 16 kW, 1/10 W 1% 0603 Various Various Yes R17 1 Resistor 200 W, 1/10 W 1% 0603 Various Various Yes R18 1 Resistor 470 W, 1/10 W 1% 0603 Various Various Yes R19, R23 2 Resistor 24 kW, 1/10 W 1% 0603 Various Various Yes R22 1 Resistor 1 kW, 1/10 W 1% 0603 Various Various Yes R24 1 Resistor 0.1 W, 1/4 W 1% 1206 Rohm Semi MCR18EZHFLR100 Yes R36 1 Resistor 1 MW, 1/10 W 1% 0603 Various Various Yes T1 1 Transformer, 25 W XFMR − EFD25 Wurth Midcom 750314098 Rev01 Yes http://onsemi.com 11 NCL30060GEVB Table 2. BILL OF MATERIALS (continued) Substitution Allowed Designator Qty. Description Value Tolerance Footprint Manufacturer Manufacturer Part Number U1 1 Single Stage PFC LED Driver NCL30060 − SOIC7 ON Semiconductor NCL30060 No U2 1 Opto Coupler 80 V, 50 mA − SMT4 NEC Electronics PS2513L-1-A Yes U3 1 Dual Op Amp LM2904 − SOIC8 ON Semiconductor LM2904DR2G No U4 1 Programmable Reference NCP431AVSN 1% SOT23 ON Semiconductor NCP431AVSNT1G No 1−10 V DIMMING INTERFACE C41, C43 2 Ceramic COG 1 nF, 50 V 10% 0603 TDK C1608COG1H102K080AA Yes C42 1 Ceramic X7R 100 nF, 50 V 10% 0603 TDK C1608X7R1H104K080AA Yes J31 1 2 Pin Connector 2.54MM Pitch − Through Hole On Shore Technology OSTVN02A150 Yes Q41 1 NPN Driver Transistor 80 V, 500 mA − SOT23 ON Semiconductor MMBTA06LT1G No R41 1 Resistor 10 kW, 1/10 W 1% 0603 Various Various Yes R42 1 Resistor 1 MW, 1/10 W 1% 0603 Various Various Yes R43 1 Resistor 287 kW, 1/10 W 1% 0603 Various Various Yes R44 1 Resistor 2.2 kW, 1/10 W 1% 0603 Various Various Yes R45 1 Resistor 220 kW, 1/10 W 1% 0603 Various Various Yes R46 1 Resistor 6.2 kW, 1/10 W 1% 0603 Various Various Yes R47 1 Resistor 75 kW, 1/10 W 1% 0603 Various Various Yes R48 1 Resistor 3.16 kW, 1/10 W 1% 0603 Various Various Yes R49 1 Resistor 22 kW, 1/10 W 1% 0603 Various Various Yes R50 1 Resistor 22 kW, 1/4 W 5% 1206 Various Various Yes U41 1 op amp TLV271 − TSOP-5 ON Semiconductor TLV271SN1T1G No U42, U43 2 Programmable Reference NCP431AVSN 1% SOT23 ON Semiconductor NCP431AVSNT1G No OPTIONAL PWM DIMMING INTERFACE (DNP) C31 0 Ceramic X7S, DNP 10 mF, 6.3 V 20% 0603 TDK C1608X7S0J106M080AC Yes D31 0 ZENER, low current, DNP 5.1 V 5% SOD123 ON Semiconductor MMSZ4689T1G No R31 0 Resistor, DNP 1 kW, 1/10 W 1% 0603 Various Various Yes R32 0 Resistor, DNP 1 MW, 1/10 W 1% 0603 Various Various Yes R33 0 Resistor, DNP 10 kW, 1/10 W 1% 0603 Various Various Yes R34 0 Resistor, DNP 330 kW, 1/10 W 1% 0603 Various Various Yes R35 0 Resistor, DNP 22 kW, 1/4 W 5% 1206 Various Various Yes U31 0 Schmitt Buffer, DNP NL17SZ17 − SC-88A ON Semiconductor NL17SZ17DFT2G No U32 0 Programmable Reference, DNP NCP431AVSN 1% SOT23 ON Semiconductor NCP431AVSNT1G No NOTE: All devices are Pb-Free Microsoft Excel is a registered trademark of Microsoft Corporation. http://onsemi.com 12 onsemi, , and other names, marks, and brands are registered and/or common law trademarks of Semiconductor Components Industries, LLC dba “onsemi” or its affiliates and/or subsidiaries in the United States and/or other countries. onsemi owns the rights to a number of patents, trademarks, copyrights, trade secrets, and other intellectual property. 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PUBLICATION ORDERING INFORMATION LITERATURE FULFILLMENT: Email Requests to: orderlit@onsemi.com onsemi Website: www.onsemi.com ◊ TECHNICAL SUPPORT North American Technical Support: Voice Mail: 1 800−282−9855 Toll Free USA/Canada Phone: 011 421 33 790 2910 www.onsemi.com 1 Europe, Middle East and Africa Technical Support: Phone: 00421 33 790 2910 For additional information, please contact your local Sales Representative