NCP1396A, NCP1396B
Controller, High
Performance Resonant
Mode, with High and Low
Side Drivers
The NCP1396 A/B offers everything needed to build a reliable and
rugged resonant mode power supply. Its unique architecture includes
a 500 kHz Voltage Controlled Oscillator whose control mode
brings flexibility when an ORing function is a necessity, e.g. in
multiple feedback paths implementations. Thanks to its
proprietary high--voltage technology, the controller welcomes a
bootstrapped MOSFET driver for half--bridge applications accepting
bulk voltages up to 600 V. Protections featuring various
reaction times, e.g. immediate shutdown or timer--based event,
brown--out, broken opto--coupler detection etc., contribute to a
safer converter design, without engendering additional circuitry
complexity. An adjustable deadtime also helps lowering the shoot-through current contribution as the switching frequency increases.
Features
High-- frequency Operation from 50 kHz up to 500 kHz
600 V High-- Voltage Floating Driver
Selectable Minimum Switching Frequency with 3% Accuracy
Adjustable Deadtime from 100 ns to 2 ms.
Startup Sequence via an Adjustable Soft-- start
Brown-- out Protection for a Simpler PFC Association
Latched Input for Severe Fault Conditions, e.g. Over Temperature
or OVP
Timer-- based Input with Auto-- recovery Operation for Delayed
Event Reaction
Enable Input for Immediate Event Reaction or Simple ON/OFF
Control
VCC Operation up to 20 V
Low Startup Current of 300 mA
1 A / 0.5 A Peak Current Sink / Source Drive Capability
Common Collector Optocoupler Connection for Easier ORing
Internal Temperature Shutdown
B Version features 10 V VCC Startup Threshold
These are Pb-- Free Devices
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MARKING
DIAGRAMS
16
16
1
SO-- 16, LESS PIN 13
D SUFFIX
CASE 751AM
x
A
WL
Y
WW
G
NCP1396xG
AWLYWW
1
= A or B
= Assembly Location
= Wafer Lot
= Year
= Work Week
= Pb--Free Package
PIN CONNECTIONS
CSS 1
16 Vboot
Fmax 2
15 Mupper
14 HB
Ctimer 3
Rt 4
BO 5
12 VCC
FB 6
11 Mlower
DT 7
10 GND
Fast Fault 8
9
Slow Fault
(Top View)
ORDERING INFORMATION
See detailed ordering and shipping information in the package
dimensions section on page 24 of this data sheet.
Typical Applications
Flat Panel Display Power Converters
High Power AC/DC Adapters for Notebooks
Industrial and Medical Power Sources
Offline Battery Chargers
Semiconductor Components Industries, LLC, 2010
November, 2010 - Rev. 7
1
Publication Order Number:
NCP1396/D
NCP1396A, NCP1396B
HV
FB
R17
OVP
R8
R24
U3A
U5
1
16
2
15
3
14
R10
5
12
6
11
7
10
L1
C12
4
Rt
D1
R21
M2
C9
R19
Soft-start
R9 R14
Timer
9
R18
Skip
Selection
C2
C13
Slow Input
T1
D3
R13
BO
C11
U2B
R3
C1
C14
U1
R16
R22
R6
R12
R5
R1
FB
OVP
C4
U3B
D6
D7
+
C7
R4
D2
D9
C10
C8
+
R11
Fast
Input
Fmax
Vout
D8
R7
8
+
C6
M1
R20
U2A
D4
R23
C3
R2
DT
Figure 1. Typical Application Example
PIN FUNCTION DESCRIPTION
Pin No.
Pin Name
Function
Pin Description
1
CSS
Soft--start
2
Fmax
Frequency clamp
3
Ctimer
Timer duration
Sets the timer duration in presence of a fault
4
Rt
Timing resistor
Connecting a resistor to this pin, sets the minimum oscillator frequency
reached for VFB = 1 V
5
BO
Brown--Out
Detects low input voltage conditions. When brought above Vlatch, it fully
latches off the controller.
6
FB
Feedback
Injecting current in this pin increases the oscillation frequency up to Fmax.
7
DT
Dead--time
A simple resistor adjusts the dead--time width
8
Fast Fault
Quick fault detection
Fast shut--down pin. Upon release, a clean startup sequence occurs. Can be
used for skip cycle purposes.
9
Slow Fault
Slow fault detection
When asserted, the timer starts to countdown and shuts down the controller
at the end of its time duration.
10
GND
Analog ground
--
11
Mlower
Low side output
Drives the lower side MOSFET
12
VCC
Supplies the controller
13
--
--
14
HB
Half--bridge connection
15
Mupper
High side output
16
Vboot
Bootstrap pin
Select the soft--start duration
A resistor sets the maximum frequency excursion
The controller accepts up to 20 V
-Connects to the half--bridge output
Drives the higher side MOSFET
The floating VCC supply for the upper stage
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2
NCP1396A, NCP1396B
Vdd
Temperature
Shutdown
S
Imin
Vfb Vfb_off
D
+
--
Vref
Rt
Clk
R
+
IDT
Vref
Q
VCC
Management
C
VBOOT
Q
50% DC
DT Adj.
I = Imax for Vfb = 5.3 V
I = 0 for Vfb < Vfb_min
Vdd
FF
Mupper
BO
Reset
PON
Reset
Imax
Vfb = 5
SS
UVLO
Fault
Vdd
Fast
Fault
Timeout
Fault
Vref
HB
Itimer
Fmax
If FAULT Itimer else 0
Level
Shifter
+
--
Timer
NC
Timeout
Fault
+
Vref
PON
Reset
Fault
Vdd
VCC
ISS
Fault
SS
Mlower
+
--
FB
G=1
+
--
RFB
+
Vfb_fault
> 0 only
V = V(FB) -- Vfb_min
Vdd
GND
+
Vfb_min
-+
Vref
+
Deadtime
Adjustment
IDT
DT
Vref Fault
Vdd
20 ms Noise
Filter
IBO
BO
+
--
+
--
+
VBO
Slow
Fault
+
Vref Fault
Q
S
+
Vlatch
20 ms Noise
Filter
+
-
Figure 2. Internal Circuit Architecture
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3
Q
R
PON Reset
20 ns Noise
Filter
Fast
Fault
NCP1396A, NCP1396B
MAXIMUM RATINGS
Rating
Symbol
Value
Unit
High Voltage bridge pin, pin 14
VBRIDGE
--1 to 600
V
Floating supply voltage
VBOOT-VBRIDGE
0 to 20
V
High side output voltage
VDRV_HI
VBRIDGE--0.3 to
VBOOT+0.3
V
Low side output voltage
VDRV_LO
--0.3 to VCC + 0.3
V
dVBRIDGE/dt
50
V/ns
VCC
20
V
--
--0.3 to 10
V
RθJA
130
C/W
Allowable output slew rate
Power Supply voltage, pin 12
Maximum voltage, all pins (except pin 11 and 10)
Thermal Resistance -- Junction--to--Air, SOIC version
Operating Junction Temperature Range
TJ
--40 to +125
C
Maximum Junction Temperature
TJMAX
+150
C
Storage Temperature Range
TSTG
--60 to +150
C
ESD Capability, Human Body Model (All pins except HV Pins)
--
2
kV
ESD Capability, Machine Model
--
200
V
Stresses exceeding Maximum Ratings may damage the device. Maximum Ratings are stress ratings only. Functional operation above the
Recommended Operating Conditions is not implied. Extended exposure to stresses above the Recommended Operating Conditions may affect
device reliability.
1. This device series contains ESD protection and exceeds the following tests:
Human Body Model 2000V per JESD22--A114--B
Machine Model Method 200V per JESD22--A115--A.
2. This device meets latch--up tests defined by JEDEC Standard JESD78.
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4
NCP1396A, NCP1396B
ELECTRICAL CHARACTERISTICS
(For typical values TJ = 25C, for min/max values TJ = --40C to +125C, Max TJ = 150C, VCC = 12 V, unless otherwise noted.)
Pin
Symbol
Min
Typ
Max
Unit
Turn--on threshold level, VCC going up – A version
12
VCCON
12.3
13.4
14.3
V
Turn--on threshold level, VCC going up – B version
12
VCCON
9.5
10.5
11.5
V
Minimum operating voltage after turn--on
12
VCC(min)
8.5
9.5
10.5
V
16--14
VbootON
8
9
10
V
16--14
Vboot(min)
7.4
8.4
9.4
V
12
Istartup
---
---
300
350
mA
VCC level at which the internal logic gets reset
12
VCCreset
--
6.5
--
V
Internal IC consumption, no output load on pin 15/14 – 11/10, Fsw =
300 kHz
12
ICC1
--
4
--
mA
Internal IC consumption, 1 nF output load on pin 15/14 – 11/10, Fsw =
300 kHz
12
ICC2
--
11
--
mA
Consumption in fault mode (All drivers disabled, VCC > VCC(min) )
12
ICC3
--
1.2
--
mA
Pin
Symbol
Min
Typ
Max
Unit
Minimum switching frequency, Rt = 18 kΩ on pin 4, Vpin 6 = 0.8 V, DT =
300 ns
4
Fsw min
58.2
60
61.8
kHz
Maximum switching frequency, Rfmax = 1.3 kΩ on pin 2, Vpin 6 > 5.3 V,
Rt = 18 kΩ, DT = 300 ns
2
Fsw max
425
500
575
kHz
Feedback pin swing above which Δf = 0
6
FBSW
--
5.3
--
V
11--15
DC
48
50
52
%
--
Tdel
--
20
--
ms
Pin
Symbol
Min
Typ
Max
Unit
Characteristic
SUPPLY SECTION
Startup voltage on the floating section
Cutoff voltage on the floating section
Startup current, VCC < VCCON
0C < TJ < +125C
--40C < TJ < +125C
VOLTAGE CONTROL OSCILLATOR (VCO)
Characteristic
Operating duty--cycle symmetry
Delay before any driver re--start in fault mode
FEEDBACK SECTION
Characteristic
Internal pull--down resistor
6
Rfb
--
20
--
kΩ
Voltage on pin 6 below which the FB level has no VCO action
6
Vfb_min
--
1.2
--
V
Voltage on pin 6 below which the controller considers a fault
6
Vfb_off
--
0.6
--
V
Pin
Symbol
Min
Typ
Max
Unit
Output voltage rise--time @ CL = 1 nF, 10--90% of output signal
15--14/1
1--10
Tr
--
40
--
ns
Output voltage fall--time @ CL = 1 nF, 10--90% of output signal
15--14/1
1--10
Tf
--
20
--
ns
Source resistance
15--14/1
1--10
ROH
--
13
--
Ω
Sink resistance
15--14/1
1--10
ROL
--
5.5
--
Ω
Dead time with RDT = 10 kΩ from pin 7 to GND
7
T_dead
250
300
340
ns
Maximum dead--time with RDT = 82 kΩ from pin 7 to GND
7
T_dead--max
--
2
--
ms
Minimum dead--time, RDT = 3 kΩ from pin 7 to GND
7
T_dead--min
--
100
--
ns
14,
15,16
IHV_LEAK
--
--
5
mA
DRIVE OUTPUT
Characteristic
Leakage current on high voltage pins to GND
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5
NCP1396A, NCP1396B
ELECTRICAL CHARACTERISTICS
(For typical values TJ = 25C, for min/max values TJ = --40C to +125C, Max TJ = 150C, VCC = 12 V, unless otherwise noted.)
TIMERS
Pin
Symbol
Min
Typ
Max
Unit
Timer charge current
3
Itimer
--
160
--
mA
Timer duration with a 1 mF capacitor and a 1 MΩ resistor
3
T--timer
--
25
--
ms
Timer recurrence in permanent fault, same values as above
3
T--timerR
--
1.4
--
s
Voltage at which pin 3 stops output pulses
3
VtimerON
3.5
4
4.4
V
Voltage at which pin 3 re--starts output pulses
3
VtimerOFF
0.9
1
1.1
V
Soft--start ending voltage
1
VSS
--
2
--
V
1
ISS
80
75
110
110
125
130
mA
1
T--SS
--
1.8
--
ms
Pin
Symbol
Min
Typ
Max
Unit
Reference voltage for fast input (Note 4)
8--9
VrefFaultF
1.00
1.05
1.10
V
Hysteresis for fast input (Note 4)
8--9
HysteFaultF
--
80
--
mV
8--9
VrefFaultS
0.95
0.92
1.00
1.00
1.05
1.05
V
8--9
HysteFaultS
--
60
--
mV
Characteristic
Soft--start charge current
0C < TJ < +125C
--40C < TJ < +125C
Soft--start duration with a 100 nF capacitor (Note 3)
PROTECTION
Characteristic
Reference voltage for slow input
0C < TJ < +125C
--40C < TJ < +125C
Hysteresis for slow input
Propagation delay for fast fault input drive shutdown
8
TpFault
--
55
90
ns
Brown--Out input bias current
5
IBObias
--
0.02
--
mA
Brown--Out level (Note 4)
5
VBO
0.99
1.04
1.09
V
Hysteresis current, Vpin5 > VBO – A version
0C < TJ < +125C
--40C < TJ < +125C
5
IBO_A
21.5
19
26.5
26.5
31.5
33
mA
Hysteresis current, Vpin5 > VBO – B version
0C < TJ < +125C
--40C < TJ < +125C
5
IBO_B
86
80
106
106
126
132
mA
Latching voltage
5
Vlatch
3.6
4
4.4
V
Temperature shutdown
--
TSD
140
--
--
C
Hysteresis
--
TSDhyste
--
30
--
C
3. The A version does not activate soft--start (unless the feedback pin voltage is below 0.6 V) when the fast--fault is released, this is for skip cycle
implementation. The B version does activate the soft--start upon release of the fast--fault input for any feedback conditions.
4. Guaranteed by design
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NCP1396A, NCP1396B
TYPICAL CHARACTERISTICS -- A VERSION
13.55
9.60
13.5
9.58
9.56
13.45
9.54
VCC(min) (V)
VCC(on) (V)
13.4
13.35
13.3
13.25
9.52
9.50
9.48
9.46
9.44
13.2
9.42
13.15
9.40
13.1
--40 --25 --10
5
20
35
50
65
80
95
9.38
--40 --25 --10
110 125
5
TEMPERATURE (C)
35
50
65
80
95 110 125
80
95 110 125
Figure 4. VCC(min)
60.2
501
60.1
500
60.0
499
FREQUENCY (kHz)
FREQUENCY (kHz)
Figure 3. VCC(on)
59.9
59.8
59.7
59.6
59.5
498
497
496
495
494
59.4
--40 --25 --10
5
20
35
50
65
80
493
--40 --25 --10
95 110 125
5
TEMPERATURE (C)
20
35
50
65
TEMPERATURE (C)
Figure 5. Fsw min
Figure 6. Fsw max
29
1.060
27
1.055
1.050
VrefFaultFF (V)
25
RFB (kΩ)
20
TEMPERATURE (C)
23
21
19
1.045
1.040
1.035
1.030
17
1.025
15
--40 --25 --10
5
20
35
50
65
80
95
1.020
--40 --25 --10
110 125
TEMPERATURE (C)
5
20
35
50
65
80
95 110 125
TEMPERATURE (C)
Figure 8. Fast Fault (VrefFaultF)
Figure 7. Pulldown Resistor (RFB)
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NCP1396A, NCP1396B
20
8.0
19
7.5
18
7.0
17
6.5
ROL (Ω)
ROH (Ω)
TYPICAL CHARACTERISTICS -- A VERSION
16
15
6.0
5.5
14
5.0
13
4.5
12
4.0
11
--40 --25 --10
5
20
35
50
65
80
95
3.5
--40 --25 --10
110 125
5
TEMPERATURE (C)
Figure 9. Source Resistance (ROH)
108
295
294
106
293
DT_nom (ns)
DT_min (ns)
50
65
80
95 110 125
296
107
105
104
103
292
291
290
102
289
101
288
100
287
5
20
35
50
65
80
286
--40 --25 --10
95 110 125
5
TEMPERATURE (C)
20
35
50
65
80
95 110 125
TEMPERATURE (C)
Figure 11. T_dead_min
Figure 12. T_dead_nom
3.960
1.970
3.955
1.968
3.950
3.945
Vlatch (V)
DT_max (ms)
1.966
1.964
1.962
3.940
3.935
3.930
3.925
3.920
1.960
1.958
--40 --25 --10
35
Figure 10. Sink Resistance (ROL)
109
99
--40 --25 --10
20
TEMPERATURE (C)
5
20
35
50
65
80
95
3.915
3.910
--40 --25 --10
110 125
TEMPERATURE (C)
5
20
35
50
65
80
95 110 125
TEMPERATURE (C)
Figure 14. Latch Level (Vlatch)
Figure 13. T_dead_max
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NCP1396A, NCP1396B
TYPICAL CHARACTERISTICS -- A VERSION
1.045
26.8
26.6
1.040
26.4
26.2
VBO (V)
IBO (mA)
1.035
1.030
26.0
25.8
25.6
25.4
1.025
25.2
1.020
--40 --25 --10
5
20
35
50
65
80
25.0
--40 --25 --10
110 125
95
TEMPERATURE (C)
5
20
35
50
65
80
95 110 125
TEMPERATURE (C)
Figure 15. Brown--Out Reference (VBO)
Figure 16. Brown--Out Hysteresis Current (IBO)
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NCP1396A, NCP1396B
TYPICAL CHARACTERISTICS -- B VERSION
10.65
9.56
9.54
10.60
9.52
9.50
VCC(min) (V)
VCC(on) (V)
10.55
10.50
10.45
9.48
9.46
9.44
9.42
9.40
10.40
9.38
10.35
--40 --25 --10
5
20
35
50
65
80
95
9.36
--40 --25 --10
110 125
5
TEMPERATURE (C)
35
50
65
80
95 110 125
80
95 110 125
Figure 18. VCC(min)
60.1
502
60.0
501
59.9
FREQUENCY (kHz)
FREQUENCY (kHz)
Figure 17. VCC(on)
59.8
59.7
59.6
59.5
500
499
498
497
496
59.4
59.3
--40 --25 --10
5
20
35
50
65
80
495
--40 --25 --10
95 110 125
5
TEMPERATURE (C)
20
35
50
65
TEMPERATURE (C)
Figure 19. Fsw min
Figure 20. Fsw max
29
1.060
27
1.055
25
1.050
VrefFaultFF (V)
RFB (kΩ)
20
TEMPERATURE (C)
23
21
19
1.045
1.040
1.035
1.030
17
15
--40 --25 --10
5
20
35
50
65
80
95
110 125
1.025
--40 --25 --10
TEMPERATURE (C)
5
20
35
50
65
80
95 110 125
TEMPERATURE (C)
Figure 22. Fast Fault (VrefFaultF)
Figure 21. Pulldown Resistor (RFB)
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NCP1396A, NCP1396B
19
8.0
18
7.5
17
7.0
16
6.5
ROL (Ω)
ROH (Ω)
TYPICAL CHARACTERISTICS -- B VERSION
15
14
6.0
5.5
13
5.0
12
4.5
11
4.0
10
--40 --25 --10
5
20
35
50
65
80
95
3.5
--40 --25 --10
110 125
5
TEMPERATURE (C)
108
294
107
293
106
292
105
291
104
103
102
286
99
285
50
65
80
284
--40 --25 --10
95 110 125
5
TEMPERATURE (C)
95 110 125
20
35
50
65
80
95 110 125
TEMPERATURE (C)
Figure 25. T_dead_min
Figure 26. T_dead_nom
3.980
1.970
3.975
1.968
3.970
3.965
Vlatch (V)
DT_max (ms)
1.966
1.964
1.962
3.960
3.955
3.950
3.945
3.940
1.960
1.958
--40 --25 --10
80
288
100
35
65
290
287
20
50
289
101
5
35
Figure 24. Sink Resistance (ROL)
DT_nom (ns)
DT_min (ns)
Figure 23. Source Resistance (ROH)
98
--40 --25 --10
20
TEMPERATURE (C)
5
20
35
50
65
80
95
110 125
3.935
3.930
--40 --25 --10
TEMPERATURE (C)
5
20
35
50
65
80
95 110 125
TEMPERATURE (C)
Figure 28. Latch Level (Vlatch)
Figure 27. T_dead_max
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NCP1396A, NCP1396B
TYPICAL CHARACTERISTICS -- B VERSION
107
1.050
106
1.045
105
VBO (V)
IBO (mA)
1.040
1.035
104
103
102
101
1.030
100
1.025
--40 --25 --10
5
20
35
50
65
80
110 125
95
99
--40 --25 --10
TEMPERATURE (C)
5
20
35
50
65
80
95 110 125
TEMPERATURE (C)
Figure 29. Brown--Out Reference (VBO)
Figure 30. Brown--Out Hysteresis Current (IBO)
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12
NCP1396A, NCP1396B
Application Information
The NCP1396 A/B includes all necessary features to help
building a rugged and safe switch-- mode power supply
featuring an extremely low standby power. The below
bullets detail the benefits brought by implementing the
NCP1396 controller:
Wide frequency range: A high-- speed Voltage
Control Oscillator allows an output frequency
excursion from 50 kHz up to 500 kHz on Mlower and
Mupper outputs.
Adjustable dead-- time: Thanks to a single resistor
wired to ground, the user has the ability to include
some dead-- time, helping to fight cross-- conduction
between the upper and the lower transistor.
Adjustable soft-- start: Every time the controller starts
to operate (power on), the switching frequency is
pushed to the programmed maximum value and slowly
moves down toward the minimum frequency, until the
feedback loop closes. The soft-- start sequence is
activated in the following cases: a) normal startup
b) back to operation from an off state: during hiccup
faulty mode, brown-- out or temperature shutdown
(TSD). In the NCP1396A, the soft-- start is not
activated back to operation from the fast fault input,
unless the feedback pin voltage is below 0.6 V. To the
opposite, in the B version, the soft-- start is always
activated back from the fast fault input whatever the
feedback level is.
Adjustable minimum and maximum frequency
excursion: In resonant applications, it is important to
stay away from the resonating peak to keep operating
the converter in the right region. Thanks to a single
external resistor, the designer can program its lowest
frequency point, obtained in lack of feedback voltage
(during the startup sequence or in short-- circuit
conditions). Internally trimmed capacitors offer a 3%
precision on the selection of the minimum switching
frequency. The adjustable upper stop being less
precise to 15%.
Low startup current: When directly powered from
the high-- voltage DC rail, the device only requires
300 mA to start-- up. In case of an auxiliary supply, the
B version offers a lower start-- up threshold to cope
with a 12 V dc rail.
Brown-- Out detection: To avoid operation from a low
input voltage, it is interesting to prevent the controller
from switching if the high-- voltage rail is not within
the right boundaries. Also, when teamed with a PFC
front-- end circuitry, the brown-- out detection can
ensure a clean start-- up sequence with soft-- start,
ensuring that the PFC is stabilized before energizing
the resonant tank. The A version features a 26.5 mA
hysteresis current for the lowest consumption and the
B version slightly increases this current to 100 mA in
order to improve the noise immunity.
Adjustable fault timer duration: When a fault is
detected on the slow fault input or when the FB path is
broken, a timer starts to charge an external capacitor.
If the fault is removed, the timer opens the charging
path and nothing happens. When the timer reaches its
selected duration (via a capacitor on pin 3), all pulses
are stopped. The controller now waits for the
discharge via an external resistor of pin 3 capacitor to
issue a new clean startup sequence with soft-- start.
Cumulative fault events: In the NCP1396A/B, the
timer capacitor is not reset when the fault disappears.
It actually integrates the information and cumulates
the occurrences. A resistor placed in parallel with the
capacitor will offer a simple way to adjust the
discharge rate and thus the auto-- recovery retry rate.
Fast and slow fault detection: In some application,
subject to heavy load transients, it is interesting to
give a certain time to the fault circuit, before
activating the protection. On the other hands, some
critical faults cannot accept any delay before a
corrective action is taken. For this reason, the
NCP1396A/B includes a fast fault and a slow fault
input. Upon assertion, the fast fault immediately stops
all pulses and stays in the position as long as the
driving signal is high. When released low (the fault
has gone), the controller has several choices: in the A
version, pulses are back to a level imposed by the
feedback pin without soft-- start, but in the B version,
pulses are back through a regular soft-- start sequence.
Skip cycle possibility: The absence of soft-- start on
the NCP1396A fast fault input offers an easy way to
implement skip cycle when power saving features are
necessary. A simple resistive connection from the
feedback pin to the fast fault input, and skip can be
implemented.
Broken feedback loop detection: Upon start-- up or
any time during operation, if the FB signal is missing,
the timer starts to charge a capacitor. If the loop is
really broken, the FB level does not grow-- up before
the timer ends counting. The controller then stops all
pulses and waits that the timer pin voltage collapses to
1 V typically before a new attempt to re-- start, via the
soft-- start. If the optocoupler is permanently broken, a
hiccup takes place.
Finally, two circuit versions, A and B: The A and B
versions differ because of the following changes:
1. The startup thresholds are different, the A starts
to pulse for VCC = 13.3 V whereas the B pulses
for VCC = 10.5 V. The turn off levels are the same
however. The A is recommended for consumer
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13
NCP1396A, NCP1396B
Voltage--Controlled Oscillator
products where the designer can use an external
startup resistor, whereas the B is more
recommended for industrial / medical
applications where a 12 V auxiliary supply
directly powers the chip.
2. The A version does not activate the soft-- start
upon release of the fast fault input. This is to let
the designer implement skip cycle. To the
opposite, the B version goes back to operation
upon the fast fault pin release via a soft-- start
sequence.
The VCO section features a high-- speed circuitry
allowing operation from 100 kHz up to 1 MHz. However,
as a division by two internally creates the two Q and Q
outputs, the final effective signal on output Mlower and
Mupper switches between 50 kHz and 500 kHz. The VCO
is configured in such a way that if the feedback pin goes up,
the switching frequency also goes up. Figure 31 shows the
architecture of this oscillator.
FBinternal
Vdd
+
Imin
Vref
max
0 to I_Fmax
S
D
+
-
Rt
Rt sets
Fmin for V(FB) = 0
max
Fsw
Cint
Q
Clk
Q
R
+
Vdd
IDT
Vref
Imin
A
B
DT
Rdt sets
the dead--time
VCC
Vdd
Fmax
Fmax sets
the maximum Fsw
FB
+
Rfb
20 k
Vb_off
Vfb < Vb_off
Start fault timer
+
Figure 31. The Simplified VCO Architecture
The designer needs to program the maximum switching
frequency and the minimum switching frequency. In LLC
configurations, for circuits working above the resonant
frequency, a high precision is required on the minimum
frequency, hence the 3% specification. This minimum
switching frequency is actually reached when no feedback
closes the loop. It can happen during the startup sequence,
a strong output transient loading or in a short-- circuit
condition. By installing a resistor from pin 4 to GND, the
minimum frequency is set. Using the same philosophy,
wiring a resistor from pin 2 to GND will set the maximum
frequency excursion. To improve the circuit protection
features, we have purposely created a dead zone, where the
feedback loop has no action. This is typically below 1.2 V.
Figure 32 details the arrangement where the internal
voltage (that drives the VCO) varies between 0 and 2.3 V.
However, to create this swing, the feedback pin (to which
the optocoupler emitter connects), will need to swing
typically between 1.2 V and 5.3 V.
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14
NCP1396A, NCP1396B
VCC
F Mu&Lu
No variations
Fmax
FB
450 kHz
+
--
R1
11.3 k
ΔFsw = 300 kHz
+
R3
100 k
D1
2.3 V
R2
8.7 k
Vref
0.5 V
Fmin
150 kHz
Fmax
VFB
Rfmax
Fault
area
5.3 V
1.2 V ΔVFB = 4.1 V
0.6 V
Figure 34. Here a different minimum frequency was
programmed as well as a maximum frequency
excursion
Figure 32. The OPAMP Arrangement Limits the
VCO Modulation Signal between 0.5 and 2.3 V
This techniques allows us to detect a fault on the
converter in case the FB pin cannot rise above 0.6 V (to
actually close the loop) in less than a duration imposed by
the programmable timer. Please refer to the fault section for
detailed operation of this mode.
As shown on Figure 32, the internal dynamics of the
VCO control voltage will be constrained between 0.5 V
and 2.3 V, whereas the feedback loop will drive pin 6 (FB)
between 1.2 V and 5.3 V. If we take the default FB pin
excursion numbers, 1.2 V = 50 kHz, 5.3 V = 500 kHz, then
the VCO maximum slope will be:
Please note that the previous small-- signal VCO slope has
now been reduced to 300 k / 4.1 = 73 kHz / V on Mupper
and Mlower outputs. This offers a mean to magnify the
feedback excursion on systems where the load range does
not generate a wide switching frequency excursion. Thanks
to this option, we will see how it becomes possible to
observe the feedback level and implement skip cycle at
light loads. It is important to note that the frequency
evolution does not have a real linear relationship with the
feedback voltage. This is due to the deadtime presence
which stays constant as the switching period changes.
The selection of the three setting resistors (Fmax, Fmin
deadtime) requires the usage of the selection charts
displayed below:
500 k − 50 k
= 109.7 kHz∕V
4.1
Figures 33 and 34 portray the frequency evolution
depending on the feedback pin voltage level in a different
frequency clamp combination.
650
F Mu&Lu
No variations
Fmax
450
Fmax (kHz)
500 kHz
ΔFsw = 450 kHz
Fmin
1.2 V ΔVFB = 4.1 V
350
Fmin = 200 kHz
250
150
50 kHz
VFB
Fault
area
VCC = 12 V
FB = 6.5 V
DT = 300 ns
550
50
5.3 V
Fmin = 50 kHz
1.5 3.5
5.5
7.5
9.5
11.5 13.5
15.5 17.5
RFmax (kΩ)
0.6 V
Figure 35. Maximum Switching Frequency Resistor
Selection Depending on the Adopted Minimum
Switching Frequency
Figure 33. Maximal Default Excursion, Rt =
22 kΩ on pin 4 and Rfmax = 1.3 kΩ on pin 2
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NCP1396A, NCP1396B
500
ORing Capability
If for any particular reason, there is a need for a
frequency variation linked to an event appearance (instead
of abruptly stopping pulses), then the FB pin lends itself
very well to the addition of other sweeping loops. Several
diodes can easily be used perform the job in case of reaction
to a fault event or to regulate on the output current (CC
operation). Figure 39 shows how to do it.
VCC = 12 V
FB = 1 V
DT = 300 ns
450
400
Fmin (kHz)
350
300
250
VCC
200
150
100
1
3
5
7
RFmin (kΩ)
9
11
In1
Figure 36. Minimum Switching Frequency Resistor
Selection (Fmin = 100 kHz to 500 kHz)
In2
FB
VCO
20 k
100
VCC = 12 V
FB = 1 V
DT = 300 ns
90
80
Figure 39. Thanks to the FB Configuration, Loop
ORing is Easy to Implement
Dead--time Control
Fmin (kHz)
70
Dead-- time control is an absolute necessity when the
half-- bridge configuration comes to play. The dead-- time
technique consists in inserting a period during which both
high and low side switches are off. Of course, the
dead-- time amount differs depending on the switching
frequency, hence the ability to adjust it on this controller.
The option ranges between 100 ns and 2 ms. The dead-- time
is actually made by controlling the oscillator discharge
current. Figure 40 portrays a simplified VCO circuit based
on Figure 31.
60
50
40
30
20
10
15
20
25 30
35
RFmin (kΩ)
40
45
50
55
Figure 37. Minimum Switching Frequency Resistor
Selection (Fmin = 20 kHz to 100 kHz)
DT (ns)
2000
1900
1800
1700
1600
1500
1400
1300
1200
1100
1000
900
800
700
600
500
400
300
200
100
3.5
Vcc = 12 V
13.5
23.5
33.5 43.5
Rdt (kΩ)
53.5
63.5
73.5 83.5
Figure 38. Dead--Time Resistor Selection
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NCP1396A, NCP1396B
Vdd
Icharge:
Fsw min + Fsw max
S
D
+
Ct
Clk
--
Idis
Q
Q
R
+
3 V--1 V
Vref
DT
RDT
A
Figure 40. Dead--time Generation
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B
NCP1396A, NCP1396B
During the discharge time, the clock comparator is high
and un-- validates the AND gates: both outputs are low.
When the comparator goes back to the low level, during the
timing capacitor Ct recharge time, A and B outputs are
validated. By connecting a resistor RDT to ground, it
creates a current whose image serves to discharge the Ct
capacitor: we control the dead-- time. The typical range
evolves between 100 ns (RDT = 3.5 kΩ) and 2 ms (RDT =
83.5 kΩ). Figure 43 shows the typical waveforms.
over the VCO lead as soon as the output voltage has reached
the target. If not, then the minimum switching frequency is
reached and a fault is detected on the feedback pin
(typically below 600 mV). Figure 41 depicts a typical
frequency evolution with soft-- start.
Fsw
Fmax
Soft--start Sequence
If no FB
Action
Plot1
Ires1 in Amperes
In resonant controllers, a soft-- start is needed to avoid
suddenly applying the full current into the resonating
circuit. In this controller, a soft-- start capacitor connects to
pin 1 and offers a smooth frequency variation upon
start-- up: when the circuit starts to pulse, the VCO is pushed
to the maximum switching frequency imposed by pin 2.
Then, it linearly decreases its frequency toward the
minimum frequency selected by a resistor on pin 4. Of
course, practically, the feedback loop is suppose to take
Fmin
Vss
Soft--start Duration
Figure 41. Soft--start Behavior
20.0
10.0
0
--10.0
--20.0
Ires
SS
Action
Plot2
Vout in Volts
177
Target is
Reached
175
Vout
173
171
169
200 m
1.00 m
600 m
1.40 m
1.80 m
time in seconds
Figure 42. A Typical Start--up Sequence on a LLC Converter
Please note that the soft-- start will be activated in the
following conditions:
- A startup sequence
- During auto-- recovery burst mode
- A brown-- out recovery
- A temperature shutdown recovery
The fast fault input undergoes a special treatment. Since
we want to implement skip cycle through the fast fault
input on the NCP1396A, we cannot activate the soft-- start
every time the feedback pin stops the operations in low
power mode. Therefore, when the fast fault pin is released,
no soft-- start occurs to offer the best skip cycle behavior.
However, it is very possible to combine skip cycle and true
fast fault input, e.g. via ORing diodes driving pin 6. In that
case, if a signal maintains the fast fault input high long
enough to bring the feedback level down (that is to say
below 0.6 V) since the output voltage starts to fall down,
then the soft-- start is activated after the release of the pin.
In the B version tailored to operate from an auxiliary 12 V
power supply, the soft-- start is always activated upon the
fast fault input release, whatever the feedback condition is.
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NCP1396A, NCP1396B
Plot1
Vct in Volts
4.00
3.00
2.00
1.00
Ct Voltage
0
Plot2
Clock in Volts
16.0
Clock Pulses
12.0
DT
8.00
4.00
0
DT
Plot3
Difference in Volts
8.00
DT
4.00
0
--4.00
A -- B
--8.00
56.2 m
65.9 m
75.7 m
time in seconds
85.4 m
95.1 m
Figure 43. Typical Oscillator Waveforms
Brown--Out Protection
Vbulk
The Brown-- Out circuitry (BO) offers a way to protect the
resonant converter from low DC input voltages. Below a
given level, the controller blocks the output pulses, above
it, it authorizes them. The internal circuitry, depicted by
Figure 44, offers a way to observe the high-- voltage (HV)
rail. A resistive divider made of Rupper and Rlower, brings
a portion of the HV rail on pin 5. Below the turn-- on level,
the 26.5 mA current source IBO is off. Therefore, the
turn-- on level solely depends on the division ratio brought
by the resistive divider.
Rupper
Vdd
ON/OFF
IBO
BO
+
--
BO
Rlower
+
VBO
Figure 44. The Internal Brown--out Configuration with
an Offset Current Source
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450
16.0
350
12.0
250
Vcmp in Volts
Plot1 Vin in Volts
NCP1396A, NCP1396B
351 Volts
250 Volts
Vin
8.0
150
4.0
50
0
BO
20 m
60 m
100 m
140 m
180 m
time in seconds
Figure 45. Simulation Results for 350 / 250 ON / OFF Levels
To the contrary, when the internal BO signal is high
(Mlower and Mupper pulse), the IBO source is activated
and creates a hysteresis. As a result, it becomes possible to
select the turn-- on and turn-- off levels via a few lines of
algebra:
IBO is off
V(+) = V bulk1 ×
R lower
R lower + R upper
If we decide to turn-- on our converter for Vbulk1 equals
350 V and turn it off for Vbulk2 equals 250 V, then for A
version (IBO_A = 26.5 mA, VBO = 1.04 V) we obtain:
Rupper = 3.77 MΩ
Rlower = 11.25 kΩ
The bridge power dissipation is 4002 / 3.781 MΩ = 42 mW
when front-- end PFC stage delivers 400 V.
Figure 45 simulation result confirms our calculations.
(eq. 1)
IBO is on
V(+) = V bulk2 ×
R lower
R lower + R upper
+ IBO ×
(eq. 2)
R lower × R upper
R lower + R upper
Latch--off Protection
There are some situations where the converter shall be
fully turned-- off and stay latched. This can happen in
presence of an over-- voltage (the feedback loop is drifting)
or when an over temperature is detected. Thanks to the
addition of a comparator on the BO pin, a simple external
circuit can lift up this pin above VLATCH (4 V typical) and
permanently disable pulses. The VCC needs to be cycled
down below 6.5 V typically to reset the controller.
We can now extract Rlower from equation 1 and plug it into
equation 2, then solve for Rupper:
R upper = R lower ×
R lower = VBO ×
V bulk1 − VBO
VBO
V bulk1 − V bulk2
IBO × (V bulk1 − VBO)
VCC
(eq. 3)
(eq. 4)
Vbulk
20 ms
RC
+
--
Q1
Vout
To permanent
latch
+
Vlatch
Rupper
IBO
Vdd
BO
NTC
Rlower
+
VBO
+
--
BO
Figure 46. Adding a comparator on the BO pin offers a way to latch--off the controller
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NCP1396A, NCP1396B
On Figure 46, Q1 is blocked and does not bother the BO
measurement as long as the NTC and the optocoupler are
not activated. As soon as the secondary optocoupler senses
an OVP condition, or the NTC reacts to a high ambient
temperature, Q1 base is brought to ground and the BO pin
goes up, permanently latching off the controller.
pulses are immediately stopped. When the input is
released, the controller performs a clean startup
sequence including a soft-- start period.
- Slow events input: this input serves as a delayed
shutdown, where an event like a transient overload
does not immediately stopped pulses but start a timer.
If the event duration lasts longer than what the timer
imposes, then all pulses are disabled. The voltage on
the timer capacitor (pin 3) starts to decrease until it
reaches 1 V. The decrease rate is actually depending
on the resistor the user will put in parallel with the
capacitor, giving another flexibility during design.
Figure 47 depicts the architecture of the fault circuitry.
Protection Circuitry
This resonant controller differs from competitors thanks
to its protection features. The device can react to various
inputs like:
- Fast events input: like an over-- current condition, a
need to shut down (sleep mode) or a way to force a
controlled burst mode (skip cycle at low output
power): as soon as the input level exceeds 1 V typical,
Vdd
Itimer
Ctimer
UVLO
1 = fault
0 = ok
Reset
+ -
VtimerON
VtimerOFF
Rtimer
+
-
ON/OFF
+
Average
Input
Current
Slow Fault
To Primary
Current Sensing
Circuitry
+
Vref Fault
1 = ok
0 = fault
Ctimer
VCC
+
Vref Fault
+
FB
FB
1 = ok
0 = fault
Reset
DRIVING
LOGIC
Fast Fault
SS
Skip
A
A
B
B
Figure 47. This circuit combines a slow and fast input for improved protection features
Slow Input
On this circuit, the slow input goes to a comparator.
When this input exceeds 1 V typical, the current source
Itimer turns on, charging the external capacitor Ctimer. If
the fault duration is long enough, when Ctimer voltage
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NCP1396A, NCP1396B
reaches the VtimerON level (4 V typical), then all pulses
are stopped. If the fault input signal is still present, then the
controller permanently stays off and the voltage on the
timer capacitor does not move (Itimer is on and the voltage
is clamped to 5 V). If the fault input signal is removed
(because pulses are off for instance), Itimer turns off and
the capacitor slowly discharges to ground via a resistor
installed in parallel with it. As a result, the designer can
easily determine the time during which the power supply
stays locked by playing on Rtimer. Now, when the timer
capacitor voltage reaches 1 V typical (VtimerOFF), the
comparator instructs the internal logic to issues pulses as on
a clean soft-- start sequence (soft-- start is activated). Please
note that the discharge resistor can not be lower than 4 V
/ Itimer otherwise the voltage on Ctimer will not reach the
turn-- off voltage of 4 V.
In both cases, when the fault is validated, both outputs
Mlower and Mupper are internally pulled down to ground.
On Figure 46 example, a voltage proportional to primary
current, once averaged, gives an image of the input power
in case Vin is kept constant via a PFC circuit. If the output
loading increases above a certain level, the voltage on this
pin will pass the 1 V threshold and start the timer. If the
overload stays there, after a few tens of milli-- seconds,
switching pulses will disappear and a protective
auto-- recovery cycle will take place. Adjusting the resistor
R in parallel with the timer capacitor will give the
flexibility to adjust the fault burst mode.
SMPS Stops
4V
Fault is Gone
SMPS Re--starts
1V
Reset at Re--start
Figure 48. A resistor can easily program the capacitor discharge time
can be designed to lose regulation in light load conditions,
forcing the FB level to increase. When it reaches the
programmed level, it triggers the fast fault input and stops
pulses. Then Vout slowly drops, the loop reacts by
decreasing the feedback level which, in turn, unlocks the
pulses, Vout goes up again and so on: we are in skip cycle
mode.
VCC
FB
Startup Behavior
Fast Fault
When the VCC voltage grows-- up, the internal current
consumption is kept to Istrup, allowing to crank-- up the
converter via a resistor connected to the bulk capacitor.
When VCC reaches the VCC(on) level, output Mlower goes
high first and then output Mupper. This sequence will
always be the same whatever triggers the pulse delivery:
fault, OFF to ON etc Pulsing the output Mlower high first
gives an immediate charge of the bootstrap capacitor.
Then, the rest of pulses follow, delivered at the highest
switching value, set by the resistor on pin 2. The soft-- start
capacitor ensures a smooth frequency decrease to either the
programmed minimum value (in case of fault) or to a value
corresponding to the operating point if the feedback loop
closes first. Figure 50 shows typical signals evolution at
power on.
Figure 49. Skip cycle can be implemented via two
resistors on the FB pin to the Fast fault input
Fast Input
The fast input is not affected by a delayed action. As soon
as its voltage exceeds 1 V typical, all pulses are off and
maintained off as long as the fault is present. When the pin
is released, pulses come back and the soft-- start is activated.
Thanks to the low activation level of 1 V, this pin can
observe the feedback pin via a resistive divided and thus
implement skip cycle operation. The resonant converter
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NCP1396A, NCP1396B
VCC(on)
VCC(min)
Vcc from an auxiliary supply
SS
FB
TSS
TSS
Fault!
0.6 V
A&B
A
Timer
B
A
B
4V
Slopes are similar
1V
Figure 50. At power on, output A is first activated and the frequency slowly decreases via the soft--start capacitor
Figure 50 depicts an auto-- recovery situation, where the
timer has triggered the end of output pulses. In that case, the
VCC level was given by an auxiliary power supply, hence
its stability during the hiccup. A similar situation can arise
if the user selects a more traditional startup method, with
an auxiliary winding. In that case, the VCC(min) comparator
stops the output pulses whenever it is activated, that is to
say, when VCC falls below 10 V typical. At this time, the
VCC pin still receives its bias current from the startup
resistor and heads toward VCC(on) via the VCC capacitor.
When the voltage reaches VCC(on), a standard sequence
takes place, involving a soft-- start. Figure 51 portrays this
behavior.
VCC(on)
VCC(min)
VCC from a
Startup Resistor
Fault is
Released
Fault!
SS
FB
TSS
TSS
0.6 V
A&B
A
Timer
B
A
B
4V
1V
Figure 51. When the VCC is too low, all pulses are stopped until VCC goes back to the startup voltage
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NCP1396A, NCP1396B
As described in the data-- sheet, two startup levels
VCC(on) are available, via two circuit versions. The
NCP1396 features sufficient hysteresis (3 V typically) to
allow a classical startup method with a resistor connected
to the bulk capacitor. Then, at the end of the startup
sequence, an auxiliary winding is supposed to take over the
controller supply voltage. To the opposite, for applications
where the resonant controller is powered from a standby
power supply, the startup level is 10 V typically and allows
for the direct a connection from a 12 V source. Thanks to
this NCP1396B, simple ON/OFF operation is therefore
feasible.
The High--voltage Driver
The driver features a traditional bootstrap circuitry,
requiring an external high-- voltage diode for the capacitor
refueling path. Figure 52 shows the internal architecture of
the high-- voltage section.
HV
B
Pulse
Trigger
Vboot
Level
Shifter
S
cboot
Mupper
Q
Q
R
HB
UVLO
dboot
VCC
Fault
Mlower
Delay
A
aux
VCC
+
GND
Figure 52. The Internal High--voltage Section of the NCP1396
The device incorporates an upper UVLO circuitry that
makes sure enough Vgs is available for the upper side
MOSFET. The B and A outputs are delivered by the
internal logic, as Figure 47 testifies. A delay is inserted in
the lower rail to ensure good matching between these
propagating signals.
As stated in the maximum rating section, the floating
portion can go up to 600 VDC and makes the IC perfectly
suitable for offline applications featuring a 400 V PFC
front-- end stage.
ORDERING INFORMATION
Device
Package
Shipping†
NCP1396ADR2G
SOIC--16, Less Pin 13
(Pb--Free)
2500 / Tape & Reel
NCP1396BDR2G
SOIC--16, Less Pin 13
(Pb--Free)
2500 / Tape & Reel
†For information on tape and reel specifications, including part orientation and tape sizes, please refer to our Tape and Reel Packaging Specification
Brochure, BRD8011/D.
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MECHANICAL CASE OUTLINE
PACKAGE DIMENSIONS
SOIC−16 NB, LESS PIN 13
CASE 751AM−01
ISSUE O
DATE 20 AUG 2007
SCALE 1:1
D
16
A B
9
E
H
0.25
M
B
M
1
8
e
15X
C
b
C
L
15X
0.25
M
T A
S
B
DIM
A
A1
b
C
D
E
e
H
h
L
M
S
A1
SEATING
PLANE
NOTES:
1. DIMENSIONING AND TOLERANCING PER ASME
Y14.5M, 1994.
2. CONTROLLING DIMENSION: MILLIMETERS.
3. DIMENSION b DOES NOT INCLUDE DAMBAR
PROTRUSION. ALLOWABLE PROTRUSION SHALL BE
0.13 TOTAL IN EXCESS OF THE b DIMENSION AT
MAXIMUM MATERIAL CONDITION.
4. DIMENSIONS D AND E DO NOT INCLUDE MOLD
PROTRUSIONS.
5. MAXIMUM MOLD PROTRUSION 0.15 PER SIDE.
h x 45 _
A
M
GENERIC
MARKING DIAGRAM*
SOLDERING FOOTPRINT
16
6.40
15X
XXXXXXXXXG
AWLYWW
1.12
1
16
1
15X
0.58
1.27
PITCH
8
MILLIMETERS
MIN
MAX
1.35
1.75
0.10
0.25
0.35
0.49
0.19
0.25
9.80
10.00
3.80
4.00
1.27 BSC
5.80
6.20
0.25
0.50
0.40
1.25
0_
7_
9
XXXXX
A
WL
Y
WW
G
= Specific Device Code
= Assembly Location
= Wafer Lot
= Year
= Work Week
= Pb−Free Package
*This information is generic. Please refer
to device data sheet for actual part
marking. Pb−Free indicator, “G”, may
or not be present.
DIMENSIONS: MILLIMETERS
DOCUMENT NUMBER:
DESCRIPTION:
98AON25333D
SOIC−16 NB, LESS PIN 13
Electronic versions are uncontrolled except when accessed directly from the Document Repository.
Printed versions are uncontrolled except when stamped “CONTROLLED COPY” in red.
PAGE 1 OF 1
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