NCP81162
Current Balancing Phase
Doubler
The NCP81162 is a current balancing, 3−level PWM input, phase
doubler. The part is intended to double the number of phases directly
controlled by ON Semiconductor PWM controllers that have 3−level
PWM output signals. The NCP81162 monitors the current of two
phases to determine which of those two phases should receive the
next PWM pulse output sent by the controller. This maintains
effective current balance even during dynamic loading of the output.
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QFN16
MN SUFFIX
CASE 485AE
Features
•
•
•
•
•
•
Works with Controllers having 3−level PWM Outputs
Reproduces 3−level PWM Signals to Drivers
Very Short Delay
Doubles Single−phase to 2−phase
Multiple Doublers can Double N Phases to 2 x N Phases
These Devices are Pb−Free, Halogen Free/BFR Free and are RoHS
Compliant
Applications
• High Current Multiphase Applications
• Expand the Single−phase Rail of a Dual Rail Controller to 2 Phases
MARKING DIAGRAM
16
1
81162
ALYWG
G
81162
A
L
Y
W
G
= Specific Device Code
= Assembly Location
= Wafer Lot
= Year
= Work Week
= Pb−Free Package
(Note: Microdot may be in either location)
VCCD
PWMB
PWMA
MID_AB
PIN DESCRIPTIONS
1
CSPB
CSNB
CSPA
CSNA
PWM_BP
GND
RDY
DRVON
PWM_IN
VCCA
MID_HL
DBL_EN
EN
(Top View)
ORDERING INFORMATION
Device
Package
Shipping†
NCP81162MNR2G
QFN16
(Pb−Free)
3000 / Tape & Reel
†For information on tape and reel specifications,
including part orientation and tape sizes, please
refer to our Tape and Reel Packaging Specification
Brochure, BRD8011/D.
© Semiconductor Components Industries, LLC, 2014
June, 2014 − Rev. 2
1
Publication Order Number:
NCP81162/D
NCP81162
CBSTB
100nF
NCP81161
1
2
3
4
VCC
R2
1
VCC
CSPB
CSNB
CSPA
CSNA
VOUT
11
COUT
10
9
CCSA
100nF
RCSA
RDCM
10M
VIN
CBSTA
(optional)
14
DRVON
3
4
VCC
C3
R3
1
RCSP1B
BST
HG
PWM
SW
EN
GND
LG
VCC
PAD
100nF
10K
RCSP1A
100nF
CSN1
10K
RCSN1A
10
RCSN1B
CCSN1
10nF
10
RPH2A
RPH2B
FROM OTHER
PHASES
RPH1B
RPH1A
CSSUM
TO CONTROLLER
RREF1A
CSREF
10
RREF1B
10
RREF2A
10
RREF2B
CCSREF
10nF
100nF
NCP81161
FROM CONTROLLER
TO CONTROLLER CCSP1
5
CCSB
100nF
2
CSP1
6
12
1
PWM
7
100nF
8
RDY
PWM_IN
EN
R1
10K
PWM_BP
DBL_EN
8
RCSB
13
MID_AB
15
NCP81162
7
4
MID_HL
RDY
DRVON
3
EN
VCCA
6
2
5
1
VCCD
PWMB
100nF
PWMA
16
C1
C2
BST
HG
PWM
SW
EN
GND
LG
VCC
PAD
FROM OTHER
PHASES
10
Figure 1. Application Schematic
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8
7
6
5
NCP81162
Table 1. PIN LIST DESCRIPTION
Pin No.
Symbol
Description
1
VCCA
2
MID_HL
Logic input. When high, the PWMA and PWMB mid−state output voltages are higher.
3
DBL_EN
Logic input. When high, PWM_IN pulses are distributed to the phase with lower output current. When low,
all PWM_IN pulses are sent to the PWMA output and the PWMB output is held at mid−state.
4
EN
5
RDY
6
DRVON
Logic input. After enabling, PWMA & PWMB outputs are active when DRVON is high.
7
PWM_IN
Logic input. The controller PWM output which will actively control PWMA & PWMB
8
PWM_BP
Logic input. When high, both PWMA and PWMB follow PWM_IN.
5 V Analog Supply
Logic input. Once EN & DRVON are simultaneously high, the NCP81162 is enabled.
Open collector output. When a pullup resistor is attached, a high output indicates PWMA & PWMB will
respond to the PWM_IN input.
9
CSNA
Phase A negative differential current sense input
10
CSPA
Phase A positive differential current sense input
11
CSNB
Phase B negative differential current sense input
12
CSPB
Phase B positive differential current sense input
13
MID_AB
Logic input. If high, the doubler PWM output that is low when PWM_IN is high will not transition to mid−
state upon the first PWM_IN H³MID transition.
14
PWMA
3−level doubler PWM output A
15
PWMB
3−level doubler PWM output B
16
VCCD
Power supply input for PWMA & PWMB outputs and internal digital circuitry
FLAG
GND
Power supply return (QFN Flag)
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NCP81162
Table 2. MAXIMUM RATINGS
Rating
Symbol
Value
Unit
TJ(max)
125
°C
TSTG
−40 to 150
°C
Input Voltage Range (Note 1)
Maximum Junction Temperature
Storage Temperature Range
ESD Capability, Human Body Model (Note 2)
ESDHBM
2
kV
ESD Capability, Machine Model (Note 2)
ESDMM
200
V
TSLD
260
°C
Lead Temperature Soldering
Reflow (SMD Styles Only), Pb−Free Versions (Note 3)
Stresses exceeding those listed in the Maximum Ratings table may damage the device. If any of these limits are exceeded, device functionality
should not be assumed, damage may occur and reliability may be affected.
1. Refer to MAXIMUM ELECTRICAL RATINGS.
2. This device series incorporates ESD protection and is tested by the following methods:
ESD Human Body Model tested per AEC−Q100−002 (EIA/JESD22−A114)
ESD Machine Model tested per AEC−Q100−003 (EIA/JESD22−A115)
Latchup Current Maximum Rating: v150 mA per JEDEC standard: JESD78
3. For information, please refer to our Soldering and Mounting Techniques Reference Manual, SOLDERRM/D
Table 3. MAXIMUM ELECTRICAL RATINGS
Pin Name
VMAX
VMIN
ISOURCE
ISINK
VCCA, VCCD
6.5 V
−0.3 V
N/A
N/A
PWMA PWMB
N/A
N/A
10 mA
10 mA
RDY
6.5 V
−0.3 V
NA
10 mA
All Other Pins
VCCA + 0.3 V
−0.3 V
N/A
N/A
*All signals referenced to GND unless noted otherwise.
Table 4. THERMAL CHARACTERISTICS
Rating
Symbol
Value
RqJA
RyJL
107
42
Unit
°C/W
Thermal Characteristics, QFN16, 3 x 3 mm (Note 4)
Thermal Resistance, Junction−to−Air (Note 5)
Thermal Resistance, Junction−to−Lead (Note 5)
4. JESD 51−5 (1S2P Direct−Attach Method) with 0 LFM.
5. Values based on copper area of 645 mm2 (or 1 in2) of 1 oz copper thickness and FR4 PCB substrate.
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NCP81162
Table 5. ELECTRICAL CHARACTERISTICS:
Unless otherwise stated: −40°C < TA < 125°C; 4.75 V < VCCA & VCCD < 5.25 V; CVCC = 0.1 mF
Parameter
Test Condition
Min
Typ
Max
Units
EN = high, PWM_IN freq =
500 kHz, PWMA/B load 20 pF
1.6
2.0
mA
EN = low
10
VCCA rising
3.7
BIAS SUPPLY
VCCA + VCCD Quiescent Current
mA
VCCA UVLO
VCCA UVLO Threshold
VCCA falling
3.3
VCCA UVLO Hysteresis
Power ON Reset Release Delay
EN = H; Time from rising VCCA
UVLO clearing to when PWMA &
PWMB go to Mid−state
3.95
V
3.5
V
200
mV
85
ms
EN INPUT
1.0
mA
0.8
V
Enable High Input Leakage Current
External 1K pull−up to 3.3 V
Upper Threshold
VUPPER
Lower Threshold
VLOWER
Total Hysteresis
VUPPER – VLOWER
100
mV
Power On Reset Release Delay
From EN ³ H to
PWMA/PWMB = Mid−state
85
ms
Calibration Time
From EN ³ H to
RDY = Open
250
500
ms
DRVON = H;
From EN ³ H to PWMA/PWMB
follow PWM_IN
250
500
ms
DRVON = L;
From EN ³ L to
RDY = L & PWMA/PWMB = Open
380
Disable Delay
−
0.4
V
ns
RDY OUTPUT
Output Low Saturation Voltage
EN = DRVON = L;
IVR_RDY = 3 mA
−
−
0.3
V
Output High Leakage
EN = H; VRDY = VCC
−
−
1
mA
DRVON INPUT
Threshold
Hysteresis
PWMA & PWMB Response Delay
VCCD/2
V
313
mV
DRVON rising
244
ns
DRVON falling
44
ns
PWM_IN INPUT
Input Bias Current
400
nA
Rising High Threshold
3.4
V
Falling High MID State Threshold
2.7
Rising Low MID State Threshold
V
1.3
Falling Low Threshold
0.7
Rise & Fall Times
V
V
12
ns
Product parametric performance is indicated in the Electrical Characteristics for the listed test conditions, unless otherwise noted. Product
performance may not be indicated by the Electrical Characteristics if operated under different conditions.
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NCP81162
Table 5. ELECTRICAL CHARACTERISTICS:
Unless otherwise stated: −40°C < TA < 125°C; 4.75 V < VCCA & VCCD < 5.25 V; CVCC = 0.1 mF
Parameter
Test Condition
Min
Typ
VCCD−0.2
VCCD
Max
Units
PWMA PWMB OUTPUTS
Output High Voltage
Sourcing 500 mA
Output Low Voltage
Sinking 500 mA
0.2
V
Output MID−State Voltage
MID_HL = GND
1.4
1.6
V
MID_HL = VCCA
1.9
2.1
V
10
ns
50
ns
GND
V
10% to 90% Rise and Fall Time
(not tested in production)
CL (PCB) = 20 pF,
DVo = GND to VCCA
PWM_IN Response Delay
PWM_IN L ³ H or H ³ L
15
PWM_IN X ³ Mid
37
ns
PWM_IN Mid ³ X
24
ns
PWM_IN pulsewidth > 15 ns
2
ns
Pulsewidth Difference from PWM_IN
DIFFERENTIAL CURRENT SENSE COMPARATOR
CSP Input Voltage Range
−0.3
−
2.0
V
CSN Input Voltage Range
−0.3
−
2.0
V
Offset Accuracy
−1.25
1.25
mV
Input Bias Current
−400
400
nA
−
PWM_BP INPUT
Threshold
VCCD/2
V
Hysteresis
250
mV
PWMA/PWMB Response Delay
14
ns
Threshold
VCCD/2
V
Hysteresis
220
mV
MID_HL & MID_AB INPUTS
DBL_EN
Threshold
1.95
V
Hysteresis
100
mV
Product parametric performance is indicated in the Electrical Characteristics for the listed test conditions, unless otherwise noted. Product
performance may not be indicated by the Electrical Characteristics if operated under different conditions.
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NCP81162
Table 6. LOGIC TABLE
Inputs
Outputs
VCC
MID_AB
DBL_EN
EN
DRVON
PWM_IN
PWM_BP
RDY
PWMA
PWMB
L
X
X
X
X
X
X
L
OPEN
OPEN
X
X
X
L
L
X
X
L
OPEN
OPEN
H
X
X
H
L
X
X
MID (Note 6)
MID (Note 6)
H
X
X
H
X
X
X
H
X
L
X (Note 8)
H
H
L
H
MID
H
X
L
X (Note 8)
H
MID
L
MID
MID
H
X
L
X (Note 8)
H
L
L
L
MID
H
X
H
X (Note 8)
H
X−>>H
L
H (Note 9)
H (Note 10)
H
L
H
X (Note 8)
H
H−>>MID
L
MID
MID
H
H
H
X (Note 8)
H
H−>>MID
L
MID (Note 11)
MID (Note 11)
H
X
H
X (Note 8)
H
L−>>MID
L
MID
MID
H
X
H
X (Note 8)
H
L
L
L
L
H
X
H
X (Note 8)
H
H
H
H
H
H
X
H
X (Note 8)
H
MID
H
MID
MID
H
X
H
X (Note 8)
H
L
H
L
L
6. Following Power−on−reset release delay after VCC & EN are both high
7. Following calibration delay after VCC & EN are both high
8. EN and DRVON never both L after both simultaneously H
9. If CSPA−CSNA < CSPB−CSNB; otherwise: previous state (MID or L)
10. If CSPB−CSNB < CSPA−CSNA; otherwise: previous state (MID or L)
11. If was H; otherwise: previous state (MID or L)
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OPEN (Note 7)
NCP81162
3.7 V
VCC
UVLO
EN
Calibration Time
RDY
PWM_IN
DRVON
PWMA
HIGH−Z
HIGH−Z
PWMB
HIGH−Z
HIGH−Z
Figure 2. Startup Timing Diagram
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NCP81162
General
one of the two doubler PWM outputs. This alternating
allocation is produced by monitoring the instantaneous
current of both inductors, and reproducing the entire PWM
input pulse at the PWM output having lower current at the
moment the PWM input rises. Alternating of PWM output
pulses stops, in order to swap the phase order, if the current
in the phase receiving the last pulse is still less than the
current in the other phase at the moment the next PWM
input pulse arrives. During both steady state and dynamic
loading, the current is thereby balanced on a pulse by pulse
basis.
The NCP81162 is a phase doubler IC specifically
designed to distribute a 3−level PWM signal output from
a controller to two phases. The doubler allocates the PWM
pulses between the phases based on current feedback, in
order to maintain cycle−by−cycle current balance.
PWM Doubling Function
The NCP81162 steers an incoming PWM pulse from the
controller to the phase with lower current, in order to
maintain current balance. During steady state loading,
every second input pulse is usually allocated to the same
PWM_IN
PWMA
PWMB
MAXIMUM
PERSISTENT
CURRENT
IMBALANCE
WITHOUT
SWAPPING
=T*Vo/(2L)
AVERAGE PHASE B CURRENT
AVERAGE PHASE A CURRENT
T
PERSISTENT CURRENT BALANCE IN STEADY STATE
Figure 3. Persistent Current Balance in Steady State
PWM_IN
PWMA
PWMB
MAXIMUM
PERSISTENT
CURRENT
IMBALANCE
WITHOUT
SWAPPING
=T*Vo/(2L)
AVERAGE PHASE A CURRENT
AVERAGE PHASE B CURRENT
T
INSTANTANEOUS
PHASE B
CURRENT
INSTANTANEOUS
PHASE B
CURRENT
Figure 4. Gradual Change of Current Balance Past Limit
If current gradually becomes unbalanced due to slight
differences in phase resistance, duty cycle, or some other
cause, the instantaneous current of the phase that received
the last PWM pulse may eventually not have risen above
the current of the other phase during the on time. Since the
NCP81162 continues to steer each incoming PWM pulse to
the phase with lowest instantaneous current (in this case,
the same phase that received the last pulse), two
consecutive PWM_IN pulses will be steered to the same
phase (see Figure 4). Although current balance is changed
in the proper direction, the resulting new current balance
may be close to the opposite limit of imbalance, and
additional current balance changes may occur.
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NCP81162
PWMA
PWMB
MAXIMUM
PERSISTENT
CURRENT
IMBALANCE
WITHOUT
SWAPPING
=T*Vo/(2L)
AVERAGE PHASE A CURRENT
AVERAGE PHASE B CURRENT
LOAD TRANSIENT CAUSES PULSES TO NOT ALTERNATE
Figure 5. Sudden Change of Current Balance Past Limit
When a sudden change in either load current or input
voltage occurs, phase currents can quickly become
unbalanced. The NCP81162 immediately responds to an
imbalance if it is enough that the current of one phase never
exceeds the other (See Figure 5).
If the system is operating in a DCM mode, PWM
allocation will continue to be based on the current sense
PWM_IN
feedback. If the current in both phases is zero when the
PWM pulse arrives at the doubler, the phase which receives
it may be randomly selected or have a tendency to favor one
phase, based on the input offset of the current comparator.
0
PWMA
0
PWMB
0
CURRENT
COMPARATOR
OUTPUT
INDUCTOR
CURRENT
ZERO
Figure 6. Discontinuous Current with Phase Current Overlap
When the PWM_IN input signal transitions only
between mid−level and high, the PWMA and PWMB
outputs also only transition between mid−level and high.
This allows inductor current to become discontinuous
(DCM) if the power stage synchronous rectifier is
controlled by a driver with Zero Current Detection (ZCD),
or Diode Emulation capability. If DCM operation is
required, the controller must not implement the ZCD
function. This is because phase currents are summed at the
controller CS input − preventing it from sensing zero
current until the sum of the currents is zero, which for 180°
out of phase currents does not occur until average current
is below zero.
By splitting current into 2 phases, DCM and the
associated increased efficiency will occur at a higher load
current than a single phase operating at the same frequency.
This is because the current in each phase is lower when load
current is shared between 2 phases and each phase achieves
DCM independently.
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NCP81162
PWM_IN
PWMA
0
0
PWMB
0
CURRENT
COMPARATOR
OUTPUT
INDUCTOR
CURRENT
ZERO
Figure 7. Discontinuous Current with no Phase Current Overlap – No CS Biasing
PWM_IN
0
PWMA
0
PWMB
0
CURRENT
COMPARATOR
OUTPUT
INDUCTOR
CURRENT
ZERO
Figure 8. Discontinuous Current with no Phase Current Overlap − CS Biasing
If activation of only 1 phase is desired when DCM phase
currents do not overlap, a small offset can be introduced
into the NCP81162 current sense network by use of RDCM
shown in Figure 1. This resistor should be the highest value
that reliably forces off one phase during DCM, since the
slight current imbalance thereby created will also exist at
higher load currents. Sufficient offset should result from a
RDCM value of Vout x RCSA/0.0004.
PWM_IN
DOUBLER
PWM OUTPUT
A OR B
OTHER
DOUBLER
PWM OUTPUT
B OR A
Figure 9. Response to PWM_IN High to Mid when MID_AB is High
When MID_AB is High, only the high PWM output
responds to a PWM_IN high−to−mid transition. When
MID_AB is high, the low PWM output does not respond to
a PWM_IN high−to−mid transition.
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NCP81162
PWM_IN
DOUBLER
PWM OUTPUT
A OR B
OTHER
DOUBLER
PWM OUTPUT
B OR A
Figure 10. Response to PWM_IN High to Mid when MID_AB is Low
When MID_AB is Low, both PWMA and PWMB
outputs respond to a PWM_IN high−to−mid transition.
Only when MID_AB is low does the low PWM output
respond to a PWM_IN high−to−mid transition by going to
mid−level.
PHASE
CURRENTS
CURRENT
COMPARISON
A>B
B>A
A>B
B>A
A>B
B>A
PWM_IN
PWMA
PWMB
Figure 11. PWMA and PWMB Responses to PWM_IN Low to Mid Transition
In some cases, such as overcurrent, the controller must
shut off all power stages by setting the PWM to the
mid−level. Both PWM output always follow a PWM_IN
Low−to−Mid level transition. Current in each phase is
prevented from going negative by the ZCD or Diode
Emulation function of the gate driver.
After both EN and DRVON have been high
simultaneously, both EN and DRVON must
simultaneously be low in order to completely power down
the NCP81162.
DRVON Input
DRVON low keeps PWMA and PWMB in the mid−state
if EN is high. After both EN and DRVON have been high
simultaneously, both EN and DRVON must
simultaneously be low in order to completely power down
the NCP81162.
EN Input
The EN input should be connected to the controller
Enable input so that the NCP81162 autocalibration ends
and is ready to receive PWM pulses before the controller
starts to send them. If the DRVON input is low when EN
goes high, NCP81162 autocalibration is initiated, and the
NCP81162 will stop pulling down the RDY output when
autocalibration is finished. If the DRVON input is high
when EN goes high, the PWMA and PWMB outputs
respond to PWM_IN as soon as autocalibration is finished.
DBL_EN input
Connecting the DBL_EN input to VCC enables the
doubling function. Connecting DBL_EN to ground will
cause PWMA to follow every PWM_IN transition.
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NCP81162
When using inductor current sensing, the output of a
correctly designed RC network will reproduce both the AC
and DC components of the phase current, which is applied
to the doubler CSP and CSN pins corresponding to the
doubler PWM output controlling that phase. Select the
CSN capacitor to maintain the value of RCSN in the range
of 3k to10k. Select the C based on the equation CCSN =
L/(DCR*RCSN).
DBL_EN connected to ground causes PWMB to be held at
mid−state.
PWM_BP Input
When the PWM_BP input is high, both PWMA and
PWMB to follow every PWM_IN input transition. When
PWM_BP is low, the PWM_IN signal appears only at the
PWM output of the low current phase.
RCSN
CSNx
When the MID_HL input is connected to VCC, the
mid−level voltage of both PWMA and PWMB is
compatible with gate drivers having input thresholds
optimized for 5 V, 3−level PWM signals. When the
MID_HL input is connected to ground, the mid−level
voltage of both PWMA and PWMB is compatible with gate
drivers having input thresholds optimized for 3.3 V,
3−level PWM signals.
CSPx
MID_HL Input
CCSN
VOUT
SWNx
DCR
1
LPHASE
2
Figure 12.
MID_AB Input
When the MID_AB input is connected to VCC, only the
PWM output that is high will go to mid−level when
PWM_IN transitions from high to mid−level. When the
MID_AB input is connected to ground, both PWM outputs
will go to mid−level when PWM_IN transitions from high
to mid−level.
Layout Notes
The NCP81162 has differential current monitoring. This
improves signal integrity and reduces noise issues related
to layout for easy design use. To insure proper function
there are some general rules to follow. Always place the
inductor current sense RC filters as close to the doubler
CSN and CSP pins as possible. Place the VCC decoupling
caps as close as possible to the doubler VCC pins. Avoid
routing the PWMA and PWMB signals next to the SWNA
and SWNB signals.
It is important that the layout of the A and B power
channels match well to help maximize the steady state
current sharing accuracy. The doubling function will swap
the phase angles when necessary to improve current
balance.
Input Under−Voltage Protection
The doubler is protected against under−voltage on the
VCCA pin. The VCCA and VCCD pins should be tied
together on the Printed Circuit Board.
Dual−Input Differential Current Comparator
The NCP81162 has a low offset differential comparator
to compare the instantaneous phase currents for the
purpose of balancing their currents. The incoming PWM
pulse is routed to the phase having lower current at the
instant of PWM_IN low to high transition.
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NCP81162
PACKAGE DIMENSIONS
QFN16 3x3, 0.5P
CASE 485AE−01
ISSUE A
D
ÇÇ
ÇÇ
PIN 1
LOCATION
L
A
B
NOTES:
1. DIMENSIONING AND TOLERANCING PER
ASME Y14.5M, 1994.
2. CONTROLLING DIMENSION: MILLIMETERS.
3. DIMENSION b APPLIES TO PLATED
TERMINAL AND IS MEASURED BETWEEN
0.25 AND 0.30 MM FROM TERMINAL.
4. COPLANARITY APPLIES TO THE EXPOSED
PAD AS WELL AS THE TERMINALS.
5. OUTLINE MEETS JEDEC DIMENSIONS PER
MO−220, VARIATION VEED−6.
L
L1
DETAIL A
ALTERNATE TERMINAL
CONSTRUCTIONS
E
ÉÉÉ
ÇÇ
ÉÉ
ÉÉÉ
EXPOSED Cu
0.15 C
TOP VIEW
0.15 C
MOLD CMPD
A3
A1
0.10 C
DETAIL B
DETAIL B
(A3)
ALTERNATE
CONSTRUCTIONS
A
16 X
SEATING
PLANE
0.08 C
SIDE VIEW
A1
DIM
A
A1
A3
b
D
D2
E
E2
e
K
L
L1
MILLIMETERS
MIN
NOM
MAX
0.80
0.90
1.00
0.00
0.03
0.05
0.20 REF
0.18
0.25
0.30
3.00 BSC
1.25
1.40
1.55
3.00 BSC
1.25
1.40
1.55
0.50 BSC
0.20
−−−
−−−
0.30
0.40
0.50
0.00
−−−
0.15
C
D2
16X
L
DETAIL A
16X
e
5
NOTE 5
EXPOSED PAD
8
4
9
1
12
E2
K
16
16X
0.10 C A B
0.05 C
13
b
BOTTOM VIEW
NOTE 3
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