EL5144, EL5146, EL5244, EL5246, EL5444
®
Data Sheet
April 13, 2005
100MHz Single-Supply Rail-to-Rail
Amplifiers
Features
• Rail-to-rail output swing
The EL5144 series amplifiers are voltage-feedback, high
speed, rail-to-rail amplifiers designed to operate on a single
+5V supply. They offer unity gain stability with an unloaded 3dB bandwidth of 100MHz. The input common-mode voltage
range extends from the negative rail to within 1.5V of the
positive rail. Driving a 75Ω double terminated coaxial cable,
the EL5144 series amplifiers drive to within 150mV of either
rail. The 200V/µs slew rate and 0.1%/0.1° differential
gain/differential phase makes these parts ideal for composite
and component video applications. With their voltagefeedback architecture, these amplifiers can accept reactive
feedback networks, allowing them to be used in analog
filtering applications These amplifiers will source 90mA and
sink 65mA.
• -3dB bandwidth = 100MHz
• Single-supply +5V operation
• Power-down to 2.6µA
• Large input common-mode range 0V < VCM < 3.5V
• Diff gain/phase = 0.1%/0.1°
• Low power 35mW per amplifier
• Space-saving SOT23-5, MSOP8 & 10, & QSOP16
packages
• Pb-Free available (RoHS compliant)
Applications
The EL5146 and EL5246 have a power-savings disable
feature. Applying a standard TTL low logic level to the CE
(Chip Enable) pin reduces the supply current to 2.6µA within
10ns. Turn-on time is 500ns, allowing true break-beforemake conditions for multiplexing applications. Allowing the
CE pin to float or applying a high logic level will enable the
amplifier.
• Video amplifiers
For applications where board space is critical, singles are
offered in a 5-pin SOT-23 package, duals in 8- and 10-pin
MSOP packages, and quads in a 16-pin QSOP package.
Singles, duals, and quads are also available in industrystandard pinouts in SO and PDIP packages. All parts
operate over the industrial temperature range of -40°C to
+85°C.
• High speed communications
1
FN7177.1
• 5V analog signal processing
• Multiplexers
• Line drivers
• Portable computers
• Sample & hold amplifiers
• Comparators
CAUTION: These devices are sensitive to electrostatic discharge; follow proper IC Handling Procedures.
1-888-INTERSIL or 1-888-352-6832 | Intersil (and design) is a registered trademark of Intersil Americas Inc.
Copyright Intersil Americas Inc. 2003, 2005. All Rights Reserved
All other trademarks mentioned are the property of their respective owners.
EL5144, EL5146, EL5244, EL5246, EL5444
Ordering Information (Continued)
Ordering Information
PART NUMBER
PACKAGE
TAPE & REEL PKG. DWG. #
PART NUMBER
PACKAGE
TAPE & REEL PKG. DWG. #
EL5246CYZ
(See Note)
10-Pin MSOP
(Pb-free)
-
MDP0043
EL5246CYZ-T7
(See Note)
10-Pin MSOP
(Pb-free)
7”
MDP0043
MDP0038
10-Pin MSOP
(Pb-free)
MDP0043
MDP0038
EL5246CYZ-T13
(See Note)
13”
7” (250 pcs)
EL5444CN
14-Pin PDIP
-
MDP0031
8-Pin PDIP
-
MDP0031
EL5444CS
14-Pin SOIC
-
MDP0027
EL5146CS
8-Pin SOIC
-
MDP0027
EL5444CS-T7
14-Pin SOIC
7”
MDP0027
EL5146CS-T7
8-Pin SOIC
7”
MDP0027
EL5444CS-T13
14-Pin SOIC
13”
MDP0027
EL5146CS-T13
8-Pin SOIC
13”
MDP0027
-
MDP0027
14-Pin SOIC
(Pb-free)
MDP0027
8-Pin SOIC
(Pb-free)
EL5444CSZ
(See Note)
-
EL5146CSZ
(See Note)
7”
MDP0027
14-Pin SOIC
(Pb-free)
MDP0027
8-Pin SOIC
(Pb-free)
EL5444CSZ-T7
(See Note)
7”
EL5146CSZ-T7
(See Note)
13”
MDP0027
14-Pin SOIC
(Pb-free)
MDP0027
8-Pin SOIC
(Pb-free)
EL5444CSZ-T13
(See Note)
13”
EL5146CSZ-T13
(See Note)
EL5444CU
16-Pin QSOP
-
MDP0040
EL5244CN
8-Pin PDIP
-
MDP0031
EL5444CU-T13
16-Pin QSOP
13”
MDP0040
EL5244CS
8-Pin SOIC
-
MDP0027
7”
MDP0027
16-Pin QSOP
(Pb-free)
MDP0040
8-Pin SOIC
EL5444CUZ
(See Note)
-
EL5244CS-T7
EL5244CS-T13
8-Pin SOIC
13”
MDP0027
MDP0040
8-Pin SOIC
(Pb-free)
-
MDP0027
16-Pin QSOP
(Pb-free)
7”
EL5244CSZ
(See Note)
EL5444CUZ-T7
(See Note)
MDP0040
8-Pin SOIC
(Pb-free)
7”
16-Pin QSOP
(Pb-free)
13”
EL5244CSZ-T7
(See Note)
EL5444CUZ-T13
(See Note)
EL5244CSZ-T13
(See Note)
8-Pin SOIC
(Pb-free)
13”
MDP0027
EL5244CY
8-Pin MSOP
-
MDP0043
EL5244CY-T13
8-Pin MSOP
13”
MDP0043
EL5244CYZ
(See Note)
8-Pin MSOP
(Pb-free)
-
MDP0043
EL5244CYZ-T7
(See Note)
8-Pin MSOP
(Pb-free)
7”
MDP0043
EL5244CYZ-T13
(See Note)
8-Pin MSOP
(Pb-free)
13”
MDP0043
EL5246CN
14-Pin PDIP
-
MDP0031
EL5246CS
14-Pin SOIC
-
MDP0027
EL5246CS-T7
14-Pin SOIC
7”
MDP0027
EL5246CS-T13
14-Pin SOIC
13”
MDP0027
EL5246CSZ
(See Note)
14-Pin SOIC
(Pb-free)
-
MDP0027
EL5246CSZ-T7
(See Note)
14-Pin SOIC
(Pb-free)
7”
MDP0027
EL5246CSZ-T13
(See Note)
14-Pin SOIC
(Pb-free)
13”
MDP0027
EL5246CY
10-Pin MSOP
-
MDP0043
EL5246CY-T13
10-Pin MSOP
13”
MDP0043
EL5144CW-T7
5-Pin SOT-23*
7” (3K pcs)
MDP0038
EL5144CW-T7A
5-Pin SOT-23*
7” (250 pcs)
MDP0038
EL5144CWZ-T7
(See Note)
5-Pin SOT-23*
(Pb-free)
7” (3K pcs)
EL5144CWZ-T7A
(See Note)
5-Pin SOT-23*
(Pb-free)
EL5146CN
2
MDP0027
*EL5144CW symbol is .Jxxx where xxx represents date
NOTE: Intersil Pb-free products employ special Pb-free material
sets; molding compounds/die attach materials and 100% matte tin
plate termination finish, which are RoHS compliant and compatible
with both SnPb and Pb-free soldering operations. Intersil Pb-free
products are MSL classified at Pb-free peak reflow temperatures that
meet or exceed the Pb-free requirements of IPC/JEDEC J STD-020.
EL5144, EL5146, EL5244, EL5246, EL5444
s
Pinouts
EL5146 & EL5146
(8-PIN SO, PDIP)
TOP VIEW
EL5144
(5-PIN SOT-23)
TOP VIEW
OUT
1
GND
2
5
+
4
IN-
1
INA-
2
-
8
VS
INA+
1
7
OUTB
CEA
2
6
INB-
GND
3
5
INB+
CEB
4
INB+
5
+
INA+
3
-
GND
+
4
1
IN-
2
IN+
3
GND
4
-
10 INA+
+
-
+
8
CE
7
VS
6
OUT
5
NC
EL5246
(14-PIN SOIC, PDIP)
TOP VIEW
EL5246
(10-PIN MSOP)
TOP VIEW
EL5244
(8-PIN SOIC, PDIP, MSOP)
TOP VIEW
OUTA
NC
-
3
IN+
VS
INA+
1
NC
2
14 INA-
9
OUTA
8
VS
CEA
3
12 NC
7
OUTB
GND
4
11 VS
6
INB-
CEB
5
10 NC
NC
6
INB+
7
13 OUTA
+
+
-
9
OUTB
8
INB-
EL5444
(16-PIN QSOP)
TOP VIEW
EL5444
(14-PIN SOIC, PDIP)
TOP VIEW
INA-
2
15 IND-
12
IND+
INA+
3
14 IND+
4
11
GND
VS
4
13 GND
INB+
5
10
INC+
VS
5
12 GND
INB-
6
9
INC-
INB+
6
11 INC+
OUTB
7
8
OUTC
INB-
7
OUTB
8
-
+
-
+
-
+
3
-
VS
+
3
-
INA+
+
13
-
2
+
INA-
-
IND-
OUTD
+
16 OUTD
14
-
1
1
+
OUTA
OUTA
10 INC-
9
OUTC
EL5144, EL5146, EL5244, EL5246, EL5444
Absolute Maximum Ratings (TA = 25°C)
Pin Voltages. . . . . . . . . . . . . . . . . . . . . . . . . GND -0.5V to VS +0.5V
Storage Temperature . . . . . . . . . . . . . . . . . . . . . . . .-65°C to +150°C
Operating Temperature . . . . . . . . . . . . . . . . . . . . . . .-40°C to +85°C
Supply Voltage between VS and GND . . . . . . . . . . . . . . . . . . . . .+6V
Maximum Continuous Output Current . . . . . . . . . . . . . . . . . . . 50mA
Power Dissipation . . . . . . . . . . . . . . . . . . . . . . . . . . . . . See Curves
CAUTION: Stresses above those listed in “Absolute Maximum Ratings” may cause permanent damage to the device. This is a stress only rating and operation of the
device at these or any other conditions above those indicated in the operational sections of this specification is not implied.
IMPORTANT NOTE: All parameters having Min/Max specifications are guaranteed. Typical values are for information purposes only. Unless otherwise noted, all tests
are at the specified temperature and are pulsed tests, therefore: TJ = TC = TA
Electrical Specifications
PARAMETER
VS = +5V, GND = 0V, TA = 25°C, CE = +2V, unless otherwise specified.
DESCRIPTION
CONDITIONS
MIN
TYP
MAX
UNIT
AC PERFORMANCE
dG
Differential Gain Error (Note 1)
G = 2, RL = 150Ω to 2.5V, RF = 1kΩ
dP
Differential Phase Error (Note 1)
G = 2, RL = 150Ω to 2.5V, RF = 1kΩ
0.1
°
BW
Bandwidth
-3dB, G = 1, RL = 10kΩ, RF = 0
100
MHz
-3dB, G = 1, RL = 150Ω, RF = 0
60
MHz
±0.1dB, G = 1, RL = 150Ω to GND, RF = 0
8
MHz
60
MHz
200
V/µs
35
ns
BW1
Bandwidth
GBWP
Gain Bandwidth Product
SR
Slew Rate
G = 1, RL = 150Ω to GND, RF = 0, VO = 0.5V
to 3.5V
tS
Settling Time
to 0.1%, VOUT = 0V to 3V
0.1
150
%
DC PERFORMANCE
AVOL
VOS
Open Loop Voltage Gain
Offset Voltage
TCVOS
Input Offset Voltage Temperature
Coefficient
IB
Input Bias Current
RL = no load, VOUT = 0.5V to 3V
54
65
dB
RL = 150Ω to GND, VOUT = 0.5V to 3V
40
50
dB
VCM = 1V, SOT23-5 and MSOP packages
25
mV
VCM = 1V, All other packages
15
mV
10
VCM = 0V & 3.5V
2
mV/°C
100
nA
3.5
V
INPUT CHARACTERISTICS
CMIR
Common Mode Input Range
CMRR ≥ 47dB
0
CMRR
Common Mode Rejection Ratio
DC, VCM = 0 to 3.0V
50
60
dB
DC, VCM = 0 to 3.5V
47
60
dB
RIN
Input Resistance
1.5
GΩ
CIN
Input Capacitance
1.5
pF
OUTPUT CHARACTERISTICS
VOP
VON
Positive Output Voltage Swing
Negative Output Voltage Swing
RL = 150Ω to 2.5V (Note 2)
4.70
4.85
V
RL = 150Ω to GND (Note 2)
4.20
4.65
V
RL = 1kΩ to 2.5V (Note 2)
4.95
4.97
V
RL = 150Ω to 2.5V (Note 2)
0.15
RL = 150Ω to GND (Note 2)
0
RL = 1kΩ to 2.5V (Note 2)
0.30
V
V
0.03
0.05
V
+IOUT
Positive Output Current
RL = 10Ω to 2.5V
60
90
120
mA
-IOUT
Negative Output Current
RL = 10Ω to 2.5V
-50
-65
-80
mA
ENABLE (EL5146 & EL5246 ONLY)
4
EL5144, EL5146, EL5244, EL5246, EL5444
Electrical Specifications
PARAMETER
VS = +5V, GND = 0V, TA = 25°C, CE = +2V, unless otherwise specified. (Continued)
DESCRIPTION
CONDITIONS
MIN
TYP
MAX
UNIT
tEN
Enable Time
EL5146, EL5246
500
ns
tDIS
Disable Time
EL5146, EL5246
10
ns
IIHCE
CE pin Input High Current
CE = 5V, EL5146, EL5246
0.003
1
mA
IILCE
CE pin Input Low Current
CE = 0V, EL5146, EL5246
-1.2
-3
mA
VIHCE
CE pin Input High Voltage for Power EL5146, EL5246
Up
VILCE
CE pin Input Low Voltage for Power EL5146, EL5246
Down
2.0
V
0.8
V
SUPPLY
IsON
Supply Current - Enabled (per
amplifier)
No load, VIN = 0V, CE = 5V
7
8.8
mA
IsOFF
Supply Current - Disabled (per
amplifier)
No load, VIN = 0V, CE = 0V
2.6
5
mA
PSOR
Power Supply Operating Range
4.75
5.0
5.25
V
PSRR
Power Supply Rejection Ratio
50
60
DC, VS = 4.75V to 5.25V
NOTES:
1. Standard NTSC test, AC signal amplitude = 286mVP-P, f = 3.8MHz, VOUT is swept from 0.8V to 3.4V, RL is DC-coupled.
2. RL is total load resistance due to feedback resistor and load resistor.
5
dB
EL5144, EL5146, EL5244, EL5246, EL5444
Typical Performance Curves
Non-Inverting Frequency Response (Gain)
Non-Inverting Frequency Response (Phase)
2
0
AV=1, RF=0Ω
0
-45
AV=2, RF=1kΩ
-2
Phase (°)
Normalized Magnitude (dB)
AV=1, RF=0Ω
AV=5.6, RF=1kΩ
-4
AV=5.6, RF=1kΩ
-90
AV=2, RF=1kΩ
-135
-6
VCM=1.5V
RL=150Ω
VCM=1.5V
RL=150Ω
-180
-8
1M
10M
100M
1M
10M
Frequency (Hz)
100M
Frequency (Hz)
Inverting Frequency Response (Gain)
Inverting Frequency Response (Phase)
2
AV=-1
135
AV=-2
-2
Phase (°)
Normalized Magnitude (dB)
180
AV=-1
0
AV=-5.6
-4
AV=-2
90
AV=-5.6
45
-6
VCM=1.5V
RF=1kΩ
RL=150Ω
VCM=1.5V
RF=1kΩ
RL=150Ω
0
-8
1M
10M
100M
1M
10M
Frequency (Hz)
3dB Bandwidth vs Die Temperature for Various Gains
3dB Bandwidth vs Die Temperature for Various Gains
100
150
RL=150Ω
RL=10kΩ
120
3dB Bandwidth (MHz)
3dB Bandwidth (MHz)
80
AV=1, RF=0Ω
60
40
AV=2, RF=1kΩ
20
0
-55
100M
Frequency (Hz)
25
60
AV=2, RF=1kΩ
AV=5.6, RF=1kΩ
65
Die Temperature (°C)
6
90
30
AV=5.6, RF=1kΩ
-15
AV=1, RF=0Ω
105
145
0
-55
-15
25
65
Die Temperature (°C)
105
145
EL5144, EL5146, EL5244, EL5246, EL5444
Typical Performance Curves
(Continued)
Frequency Response for Various RL
VCM=1.5V
RF=0Ω
AV=1
VCM=1.5V
RL=150Ω
AV=1
8
Normalized Magnitude (dB)
4
Normalized Magnitude (dB)
Frequency Response for Various CL
RL=10kΩ
2
0
RL=520Ω
-2
RL=150Ω
-4
CL=100pF
CL=47pF
4
0
CL=22pF
-4
CL=0pF
-8
1M
10M
100M
1M
10M
Frequency (Hz)
100M
Frequency (Hz)
Frequency Response for Various RF and RG
Group Delay vs Frequency
10
RF=RG=2kΩ
RF=RG=1kΩ
0
-2
RF=RG=560Ω
-4
6
4
AV=1
RF=1Ω
2
VCM=1.5V
RL=150Ω
AV=2
-6
AV=2
RF=1kΩ
8
Group Delay (ns)
Normalized Magnitude (dB)
2
1M
10M
0
1M
100M
10M
100M
Frequency (Hz)
Frequency (Hz)
Open Loop Gain and Phase vs Frequency
Open Loop Voltage Gain vs Die Temperature
0
80
45
70
RL=1kΩ
Phase
90
40
RL=150Ω
135
Gain
20
180
Phase (°)
Gain (dB)
60
Open Loop Gain (dB)
80
No Load
60
50
RL=150Ω
40
0
1k
10k
100k
1M
Frequency (Hz)
7
10M
225
100M
30
-55
-15
25
65
Die Temperature (°C)
105
145
EL5144, EL5146, EL5244, EL5246, EL5444
Typical Performance Curves
(Continued)
Voltage Noise vs Frequency - Video Amp
Closed Loop Output Impedance vs Frequency
10k
200
Closed Loop (ZO)
Voltage Noise (nV/√Hz)
RF=0Ω
AV=2
1k
100
20
2
0.2
10
10
100
10k
1k
100k
1M
10M
100M
10k
100k
Frequency (Hz)
1M
10M
100M
Frequency (Hz)
Offset Voltage vs Die Temperature
(6 Typical Samples)
PSRR and CMRR vs Frequency
20
12
PSRR, CMRR (dB)
Offset Voltage (mV)
0
6
0
-6
CMRR
-20
PSRR-40
PSRR+
-60
-12
-55
-15
25
65
105
-80
1k
145
10k
Die Temperature (°C)
Output Voltage Swing vs Frequency for THD < 1%
1M
10M
100M
Output Voltage Swing vs Frequency for THD < 0.1%
5
RF=1kΩ
AV=2
4
RL=500Ω to 2.5V
3
RL=150Ω to 2.5V
2
1
0
1M
10M
Frequency (Hz)
8
100M
Output Voltage Swing (VPP)
5
Output Voltage Swing (VPP)
100k
Frequency (Hz)
RF=1kΩ
AV=2
4
3
RL=500Ω to 2.5V
2
1
RL=150Ω to 2.5V
0
1M
10M
Frequency (Hz)
100M
EL5144, EL5146, EL5244, EL5246, EL5444
Typical Performance Curves
(Continued)
Large Signal Pulse Response (Single Supply)
Small Signal Pulse Response (Single Supply)
1.9
VS=5V
RL=150Ω to 0V
RF=1kΩ
AV=2
3
Output Voltage (V)
Output Voltage (V)
4
2
1
0
VS=5V
RL=150Ω to 0V
RF=1kΩ
AV=2
1.7
1.5
1.3
1.1
Time (20ns/div)
Time (20ns/div)
Large Signal Pulse Response (Split Supplies)
Small Signal Pulse Response (Split Supply)
0.4
VS=±2.5V
RL=150Ω to 0V
RF=1kΩ
AV=2
2
Output Voltage (V)
Output Voltage (V)
4
0
-2
-4
VS=±2.5V
RL=150Ω to 0V
RF=1kΩ
AV=2
0.2
0
-0.2
-0.4
Time (20ns/div)
Time (20ns/div)
Settling Time vs Settling Accuracy
Slew Rate vs Die Temperature
250
100
Settling Time (ns)
80
Slew Rate (V/µs)
RL=1kΩ
RF=500Ω
AV=-1
VSTEP=3V
60
40
200
20
0
0.01
0.1
Settling Accuracy (%)
9
1
150
-55
-15
25
65
Die Temperature (°C)
105
145
EL5144, EL5146, EL5244, EL5246, EL5444
Typical Performance Curves
(Continued)
Differential Phase for RL Tied to 0V
Differential Gain for RL Tied to 0V
RF=0Ω
AV=1
RF=0Ω
AV=1
0.2
Differential Phase (°)
Differential Gain (%)
0.08
0.04
RL=10kΩ
0
RL=150Ω
-0.04
-0.08
0.1
RL=10kΩ
0
RL=150Ω
-0.1
-0.2
0.25
1.75
3.25
0.25
VOUT (V)
Differential Gain for RL Tied to 2.5V
Differential Phase (°)
Differential Gain (%)
RF=0Ω
AV=1
0.2
0.1
0
RL=10kΩ
-0.1
RL=150Ω
-0.2
0.1
RL=10kΩ
0
-0.1
RL=150Ω
-0.2
0.5
2
3.5
0.5
2
VOUT (V)
0.2
Differential Phase for RL Tied to 0V
RF=1kΩ
AV=2
0.1
0
0.2
Differential Phase (°)
RL=150Ω
3.5
VOUT (V)
Differential Gain for RL Tied to 0V
Differential Gain (%)
3.25
Differential Phase for RL Tied to 2.5V
RF=0Ω
AV=1
0.2
1.75
VOUT (V)
RL=10kΩ
-0.1
-0.2
RF=1kΩ
AV=2
RL=150Ω
0.1
0
RL=10kΩ
-0.1
-0.2
0.5
2
VOUT (V)
10
3.5
0.5
2
VOUT (V)
3.5
EL5144, EL5146, EL5244, EL5246, EL5444
Typical Performance Curves
(Continued)
Differential Gain for RL Tied to 2.5V
RF=1kΩ
AV=2
RF=1kΩ
AV=2
0.2
0.1
Differential Phase (°)
0.2
Differential Gain (%)
Differential Phase for RL Tied to 2.5V
RL=150Ω
0
-0.1
RL=10kΩ
-0.2
RL=10kΩ
0.1
0
RL=150Ω
-0.1
-0.2
0.5
3.5
2
0.5
VOUT (V)
2nd and 3rd Harmonic Distortion vs Frequency
2nd and 3rd Harmonic Distortion vs Frequency
-25
-25
-45
HD3
-35
HD3
Distortion (dBc)
Distortion (dBc)
-35
HD2
-55
-65
-45
HD2
-55
-65
-75
1M
VOUT=0.25V to 2.25V
RL=100Ω to 0V
10M
100M
10M
100M
Frequency (Hz)
2nd and 3rd Harmonic Distortion vs. Frequency
Channel to Channel Crosstalk - Duals and Quads
(Worst Channel)
-25
0
HD3
-20
Crosstalk (dB)
-35
-45
-55
VOUT=0.5V to 2.5V
RL=100Ω to 0V
-75
1M
Frequency (Hz)
Distortion (dBc)
3.5
2
VOUT (V)
HD2
-65
-40
-60
-80
VOUT
VOUT
=1V
=1V
to to
3V
=100Ω to 0V
RL3V
-75
1M
10M
Frequency (Hz)
11
100M
-100
100k
1M
10M
Frequency (Hz)
100M
EL5144, EL5146, EL5244, EL5246, EL5444
Typical Performance Curves
(Continued)
Supply Current (per Amp) vs Supply Voltage
Output Current vs Die Temperature
120
RL=10Ω to 2.5V
8
Output Current (mA)
Supply Current (mA)
100
6
4
2
Source
80
60
Sink
40
0
0
1
2
3
4
20
-55
5
-15
Supply Current - ON (per Amp) vs Die Temperature
65
105
145
105
145
105
145
Supply Current - OFF (per Amp) vs Die
Temperature
9
5
8
4
Supply Current (µA)
Supply Current (mA)
25
Die Temperature (°C)
Supply Voltage (V)
7
6
5
3
2
1
4
-55
25
-15
65
105
0
-55
145
-15
Die Temperature (°C)
25
65
Die Temperature (°C)
Positive Output Voltage Swing vs Die Temperature
Negative Output Voltage Swing vs Die
Temperature
5
0.5
RL=150Ω
0.4
Output Voltage (V)
Output Voltage (V)
4.9
RL=150Ω to 2.5V
4.8
4.7
RL=150Ω to 0V
4.6
0.3
0.2
RL=150Ω to 2.5V
0.1
RL=150Ω to 0V
4.5
-55
-15
25
65
Die Temperature (°C)
12
105
145
0
-55
-15
25
65
Die Temperature (°C)
EL5144, EL5146, EL5244, EL5246, EL5444
Typical Performance Curves
(Continued)
Output Voltage from Either Rail vs Die
Temperature for Various Effective RLOAD
OFF Isolation - EL5146 & EL5246
300
-20
Output Voltage (V)
Effective RLOAD=1kΩ
10
Ω
Effective RLOAD=5k
1
-55
25
65
105
-60
EL5246CS
-80
EL5246CN
-100
Effective RLOAD = RL//RF to VS/2
-15
EL5146CS &
EL5146CN
-40
Magnitude (dBc)
Effective RLO
100
50Ω
AD=1
-120
10k
145
100k
Die Temperature (°C)
Maximum Power Dissipation vs. Ambient
Temperature Singles (TJMAX = 150°C)
PDIP, ΘJA = 110°C/W
1.6
Power Dissipation (W)
Power Dissipation (W)
100M
2.5
SOIC, ΘJA = 161°C/W
1.2
0.8
0.4
0
-50
-20
10
40
70
100
Ambient Temperature (°C)
2.5
PDIP-14, ΘJA = 83°C/W
1.5
1.0
SOIC-14, ΘJA = 118°C/W
QSOP-16, ΘJA = 158°C/W
0
-50
-20
10
40
Ambient Temperature (°C)
13
PDIP-8, ΘJA = 107°C/W
SOIC-14, ΘJA = 120°C/W
1.5
1.0
0.5
0
-50
SOIC-8, ΘJA = 159°C/W
MSOP-8,10, ΘJA = 206°C/W
-20
10
40
Ambient Temperature (°C)
Maximum Power Dissipation vs. Ambient
Temperature Quads (TJMAX = 150°C)
2.0
PDIP-14, ΘJA = 87°C/W
2.0
SOT23-5, ΘJA = 256°C/W
Power Dissipation (W)
10M
Maximum Power Dissipation vs. Ambient
Temperature Duals (TJMAX = 150°C)
2.0
0.5
1M
Frequency (Hz)
70
100
70
100
EL5144, EL5146, EL5244, EL5246, EL5444
Pin Descriptions
5-PIN
SOT23
8-PIN
SO/PDIP/
8-PIN
MSOP
SO/PDIP
16-PIN
MSOP
14-PIN
14-PIN
SO/PDIP SO/PDIP
16-PIN
QSOP
NAME
FUNCTION
5
7
8
8
11
4
4,5
VS
Positive Power
Supply
2
4
4
3
4
11
12,13
GND
Ground or
Negative Power
Supply
3
3
IN+
EQUIVALENT CIRCUIT
Noninverting
Input
VS
GND
Circuit 1
4
2
IN-
1
6
OUT
Inverting Input
(Reference Circuit 1)
Amplifier Output
VS
GND
Circuit 2
3
1
1
3
3
INA+
Amplifier A
Noninverting
Input
(Reference Circuit 1)
2
10
14
2
2
INA-
Amplifier A
Inverting Input
(Reference Circuit 1)
1
9
13
1
1
OUTA
Amplifier A
Output
(Reference Circuit 2)
5
5
7
5
6
INB+
Amplifier B
Noninverting
Input
(Reference Circuit 1)
6
6
8
6
7
INB-
Amplifier B
Inverting Input
(Reference Circuit 1)
7
7
9
7
8
OUTB
Amplifier B
Output
(Reference Circuit 2)
10
11
INC+
Amplifier C
Noninverting
Input
(Reference Circuit 1)
9
10
INC-
Amplifier C
Inverting Input
(Reference Circuit 1)
8
9
OUTC
Amplifier C
Output
(Reference Circuit 2)
12
14
IND+
Amplifier D
Noninverting
Input
(Reference Circuit 1)
13
15
IND-
Amplifier D
Inverting Input
(Reference Circuit 1)
14
EL5144, EL5146, EL5244, EL5246, EL5444
Pin Descriptions
5-PIN
SOT23
(Continued)
8-PIN
SO/PDIP/
8-PIN
MSOP
SO/PDIP
16-PIN
MSOP
14-PIN
14-PIN
SO/PDIP SO/PDIP
14
8
16-PIN
QSOP
NAME
16
OUTD
CE
FUNCTION
Amplifier D
Output
EQUIVALENT CIRCUIT
(Reference Circuit 2)
Enable (Enabled
when high)
VS
+
–
1.4V
GND
Circuit 3
1,5
2
3
CEA
Enable Amplifier (Reference Circuit 3)
A (Enabled
when high)
4
5
CEB
Enable Amplifier (Reference Circuit 3)
B (Enabled
when high)
2,6,
10,12
NC
Description of Operation and Applications
Information
Product Description
The EL5144 series is a family of wide bandwidth, single
supply, low power, rail-to-rail output, voltage feedback
operational amplifiers. The family includes single, dual, and
quad configurations. The singles and duals are available with
a power down pin to reduce power to 2.6µA typically. All the
amplifiers are internally compensated for closed loop
feedback gains of +1 or greater. Larger gains are acceptable
but bandwidth will be reduced according to the familiar GainBandwidth Product.
Connected in voltage follower mode and driving a high
impedance load, the EL5144 series has a -3dB bandwidth of
100MHz. Driving a 150Ω load, they have a -3dB bandwidth
of 60MHz while maintaining a 200V/µs slew rate. The input
common mode voltage range includes ground while the
output can swing rail to rail.
Power Supply Bypassing and Printed Circuit
Board Layout
As with any high-frequency device, good printed circuit
board layout is necessary for optimum performance. Ground
plane construction is highly recommended. Lead lengths
should be as short as possible. The power supply pin must
be well bypassed to reduce the risk of oscillation For normal
single supply operation, where the GND pin is connected to
the ground plane, a single 4.7µF tantalum capacitor in
parallel with a 0.1µF ceramic capacitor from VS to GND will
15
No Connect. Not
internally
connected.
suffice. This same capacitor combination should be placed
at each supply pin to ground if split supplies are to be used.
In this case, the GND pin becomes the negative supply rail.
For good AC performance, parasitic capacitance should be
kept to a minimum. Use of wire wound resistors should be
avoided because of their additional series inductance. Use of
sockets, particularly for the SO package, should be avoided
if possible. Sockets add parasitic inductance and
capacitance that can result in compromised performance.
Input, Output, and Supply Voltage Range
The EL5144 series has been designed to operate with a
single supply voltage of 5V. Split supplies can be used so
long as their total range is 5V.
The amplifiers have an input common mode voltage range
that includes the negative supply (GND pin) and extends to
within 1.5V of the positive supply (VS pin). They are
specified over this range.
The output of the EL5144 series amplifiers can swing rail to
rail. As the load resistance becomes lower in value, the
ability to drive close to each rail is reduced. However, even
with an effective 150Ω load resistor connected to a voltage
halfway between the supply rails, the output will swing to
within 150mV of either rail.
EL5144, EL5146, EL5244, EL5246, EL5444
Figure 1 shows the output of the EL5144 series amplifier
swinging rail to rail with RF = 1kΩ, AV = +2 and RL = 1MΩ.
Figure 2 is with RL = 150Ω.
5V
0V
FIGURE 1.
5V
Video Performance
For good video signal integrity, an amplifier is required to
maintain the same output impedance and the same
frequency response as DC levels are changed at the output.
This can be difficult when driving a standard video load of
150Ω, because of the change in output current with DC level.
A look at the Differential Gain and Differential Phase curves
for various supply and loading conditions will help you obtain
optimal performance. Curves are provided for AV = +1 and
+2, and RL = 150Ω and 10kΩ tied both to ground as well as
2.5V. As with all video amplifiers, there is a common mode
sweet spot for optimum differential gain/differential phase.
For example, with AV = +2 and RL = 150Ω tied to 2.5V, and
the output common mode voltage kept between 0.8V and
3.2V, dG/dP is a very low 0.1%/0.1°. This condition
corresponds to driving an AC-coupled, double terminated
75Ω coaxial cable. With AV = +1, RL = 150Ω tied to ground,
and the video level kept between 0.85V and 2.95V, these
amplifiers provide dG/dP performance of 0.05%/0.20°. This
condition is representative of using the EL5144 series
amplifier as a buffer driving a DC coupled, double
terminated, 75Ω coaxial cable. Driving high impedance
loads, such as signals on computer video cards, gives
similar or better dG/dP performance as driving cables.
Driving Cables and Capacitive Loads
0V
FIGURE 2.
Choice of Feedback Resistor, RF
These amplifiers are optimized for applications that require a
gain of +1. Hence, no feedback resistor is required.
However, for gains greater than +1, the feedback resistor
forms a pole with the input capacitance. As this pole
becomes larger, phase margin is reduced. This causes
ringing in the time domain and peaking in the frequency
domain. Therefore, RF has some maximum value that
should not be exceeded for optimum performance. If a large
value of RF must be used, a small capacitor in the few
picofarad range in parallel with RF can help to reduce this
ringing and peaking at the expense of reducing the
bandwidth.
As far as the output stage of the amplifier is concerned, RF +
RG appear in parallel with RL for gains other than +1. As this
combination gets smaller, the bandwidth falls off.
Consequently, RF also has a minimum value that should not
be exceeded for optimum performance.
For AV = +1, RF = 0Ω is optimum. For AV = -1 or +2 (noise
gain of 2), optimum response is obtained with RF between
300Ω and 1kΩ. For AV = -4 or +5 (noise gain of 5), keep RF
between 300Ω and 15kΩ.
16
The EL5144 series amplifiers can drive 50pF loads in
parallel with 150Ω with 4dB of peaking and 100pF with 7dB
of peaking. If less peaking is desired in these applications, a
small series resistor (usually between 5Ω and 50Ω) can be
placed in series with the output to eliminate most peaking.
However, this will obviously reduce the gain slightly. If your
gain is greater than 1, the gain resistor (RG) can then be
chosen to make up for any gain loss which may be created
by this additional resistor at the output. Another method of
reducing peaking is to add a “snubber” circuit at the output. A
snubber is a resistor in a series with a capacitor, 150Ω and
100pF being typical values. The advantage of a snubber is
that it does not draw DC load current.
When used as a cable driver, double termination is always
recommended for reflection-free performance. For those
applications, the back-termination series resistor will decouple the EL5144 series amplifier from the cable and allow
extensive capacitive drive. However, other applications may
have high capacitive loads without a back-termination
resistor. Again, a small series resistor at the output can
reduce peaking.
Disable/Power-Down
The EL5146 and EL5246 amplifiers can be disabled, placing
its output in a high-impedance state. Turn off time is only
10ns and turn on time is around 500ns. When disabled, the
amplifier’s supply current is reduced to 2.6µA typically,
thereby effectively eliminating power consumption. The
amplifier’s power down can be controlled by standard TTL or
CMOS signal levels at the CE pin. The applied logic signal is
EL5144, EL5146, EL5244, EL5246, EL5444
relative to the GND pin. Letting the CE pin float will enable
the amplifier. Hence, the 8-pin PDIP and SOIC single amps
are pin compatible with standard amplifiers that don’t have a
power down feature.
Short Circuit Current Limit
The EL5144 series amplifiers do not have internal short
circuit protection circuitry. Short circuit current of 90mA
sourcing and 65mA sinking typically will flow if the output is
trying to drive high or low but is shorted to half way between
the rails. If an output is shorted indefinitely, the power
dissipation could easily increase such that the part will be
destroyed. Maximum reliability is maintained if the output
current never exceeds ±50mA. This limit is set by internal
metal interconnect limitations. Obviously, short circuit
conditions must not remain or the internal metal connections
will be destroyed.
Power Dissipation
With the high output drive capability of the EL5144 series
amplifiers, it is possible to exceed the 150°C Absolute
Maximum junction temperature under certain load current
conditions. Therefore, it is important to calculate the
maximum junction temperature for the application to
determine if load conditions or package type need to be
modified for the amplifier to remain in the safe operating
area.
The maximum power dissipation allowed in a package is
determined according to:
If we set the two PDMAX equations equal to each other, we
can solve for RL:
V OUT × ( V S - V OUT )
R L = -------------------------------------------------------------------------------------------- T JMAX - T AMAX
--------------------------------------------- - ( V S × I SMAX )
N × θ JA
Assuming worst case conditions of TA = +85°C,
VOUT = VS/2V, VS = 5.5V, and ISMAX = 8.8mA per amplifier,
below is a table of all packages and the minimum RL
allowed.
PART
PACKAGE
MINIMUM RL
EL5144CW
SOT23-5
37
EL5146CS
SOIC-8
21
EL5146CN
PDIP-8
14
EL5244CS
SOIC-8
48
EL5244CN
PDIP-8
30
EL5244CY
MSOP-8
69
EL5246CY
MSOP-10
69
EL5246CS
SOIC-14
34
EL5246CN
PDIP-14
23
EL5444CU
QSOP-16
139
EL5444CS
SOIC-14
85
EL5444CN
PDIP-14
51
EL5144 Series Comparator Application
T JMAX - T AMAX
PD MAX = -------------------------------------------θ JA
The EL5144 series amplifier can be used as a very fast,
single supply comparator. Most op amps used as a
comparator allow only slow speed operation because of
output saturation issues. The EL5144 series amplifier
doesn’t suffer from output saturation issues. Figure 3 shows
the amplifier implemented as a comparator. Figure 4 is a
where:
TJMAX = Maximum junction temperature
TAMAX = Maximum ambient temperature
θJA = Thermal resistance of the package
PDMAX = Maximum power dissipation in the package
The maximum power dissipation actually produced by an IC
is the total quiescent supply current times the total power
supply voltage, plus the power in the IC due to the load, or:
V OUT
PD MAX = N × V S × I SMAX + ( V S - V OUT ) × ---------------R
L
where:
N = Number of amplifiers in the package
VS = Total supply voltage
ISMAX = Maximum supply current per amplifier
VOUT = Maximum output voltage of the application
RL = Load resistance tied to ground
17
EL5144, EL5146, EL5244, EL5246, EL5444
graph of propagation delay vs. overdrive as a square wave is
presented at the input of the comparator.
directly together. Isolation resistors at each output are not
necessary.
+5V
1
VIN
+
–
2
3
VIN 1
3VPP
10MHz
8
EL5146
0.1µF
7
+
6
+2.5V
2
VOUT
14
+
3
RL
4
1
VOUT
13
12
EL5246
5
+5V
4
11
5
10
Select
FIGURE 3.
6
VIN 2
2.4VPP
5MHz
Propagation Delay vs. Overdrive for Amplifier
Used as a Comparator
+
-
7
4.7µF
0.1µF
9
150Ω
8
1000
Propagation Delay (ns)
FIGURE 5.
5V
Negative Going Signal
100
VOUT
Positive Going Signal
0V
10
0.01
0.1
1.0
Overdrive (V)
5V
Select
0V
FIGURE 4.
FIGURE 6.
Multiplexing with the EL5144 Series Amplifier
Besides normal power down usage, the CE pin on the
EL5146 and EL5246 series amplifiers also allow for
multiplexing applications. Figure 5 shows an EL5246 with its
outputs tied together, driving a back terminated 75Ω video
load. A 3VP-P 10MHz sine wave is applied at Amp A input,
and a 2.4VP-P 5MHz square wave to Amp B. Figure 6
shows the SELECT signal that is applied, and the resulting
output waveform at VOUT. Observe the break-before-make
operation of the multiplexing. Amp A is on and VIN1 is being
passed through to the output of the amplifier. Then Amp A
turns off in about 10ns. The output decays to ground with an
RLCL time constants. 500ns later, Amp B turns on and VIN2
is passed through to the output. This break-before-make
operation ensures that more than one amplifier isn’t trying to
drive the bus at the same time. Notice the outputs are tied
18
Free Running Oscillator Application
Figure 7 is an EL5144 configured as a free running oscillator.
To first order, ROSC and COSC determine the frequency of
oscillation according to:
0.72
F OSC = --------------------------------------R OSC × C OSC
For rail to rail output swings, maximum frequency of
oscillation is around 15MHz. If reduced output swings are
acceptable, 25MHz can be achieved. Figure 8 shows the
EL5144, EL5146, EL5244, EL5246, EL5444
oscillator for ROSC = 510Ω, COSC = 240pF and
FOSC = 6MHz.
470K
+5V
1
5
470K
0.1µF
+
2
3
ROSC
4
470K
COSC
FIGURE 7.
5V
VOUT
0V
FIGURE 8.
5V
0V
FIGURE 9.
All Intersil U.S. products are manufactured, assembled and tested utilizing ISO9000 quality systems.
Intersil Corporation’s quality certifications can be viewed at www.intersil.com/design/quality
Intersil products are sold by description only. Intersil Corporation reserves the right to make changes in circuit design, software and/or specifications at any time without
notice. Accordingly, the reader is cautioned to verify that data sheets are current before placing orders. Information furnished by Intersil is believed to be accurate and
reliable. However, no responsibility is assumed by Intersil or its subsidiaries for its use; nor for any infringements of patents or other rights of third parties which may result
from its use. No license is granted by implication or otherwise under any patent or patent rights of Intersil or its subsidiaries.
For information regarding Intersil Corporation and its products, see www.intersil.com
19
工商网监
湘ICP备2023018690号
