HI5662/6IN

DATASHEET HI5662 FN4317 Rev 2.00 February 1999 Dual 8-Bit, 60MSPS A/D Converter with Internal Voltage Reference The HI5662 is a monolithic, dual 8-Bit, 60MSPS analog-todigital converter fabricated in an advanced CMOS process. It is designed for high speed applications where integration, bandwidth and accuracy are essential. The HI5662 reaches a new level of multi-channel integration. The fully pipeline architecture and an innovative input stage enable the HI5662 to accept a variety of input configurations, singleended or fully differential. Only one external clock is necessary to drive both converters and an internal band-gap voltage reference is provided. This allows the system designer to realize an increased level of system integration resulting in decreased cost and power dissipation. Features • Sampling Rate . . . . . . . . . . . . . . . . . . . . . . . . . . . 60MSPS • 7.8 Bits at fIN = 10MHz • Low Power at 60MSPS . . . . . . . . . . . . . . . . . . . . 650mW • Wide Full Power Input Bandwidth . . . . . . . . . . . . 250MHz • Excellent Channel-to-Channel Isolation . . . . . . . . . .>75dB • On-Chip Sample and Hold Amplifiers • Internal Band-Gap Voltage Reference . . . . . . . . . . . . 2.5V • Fully Differential or Single-Ended Analog Inputs The HI5662 has excellent dynamic performance while consuming only 650mW power at 60MSPS. The A/D only requires a single +5V power supply and encode clock. Data output latches are provided which present valid data to the output bus with a latency of 6 clock cycles. • Single Supply Voltage Operation . . . . . . . . . . . . . . . . .+5V For those customers needing dual channel 10-bit resolution, please refer to the HI5762. For single channel 10-bit applications, please refer to the HI5767. • Dual 8-Bit A/D Converters on a Monolithic Chip • TTL/CMOS Compatible Digital Inputs • CMOS Compatible Digital Outputs. . . . . . . . . . . . 3.0/5.0V • Offset Binary Digital Data Output Format Applications • Wireless Local Loop Ordering Information PART NUMBER HI5662/6IN TEMP. RANGE (oC) -40 to 85 HI5662EVAL2 25 • PSK and QAM I and Q Demodulators PACKAGE 44 Ld MQFP Evaluation Platform PKG. NO. Q44.10x10 • Medical Imaging • High Speed Data Acquisition Pinout QVDC QIN- QIN+ AVCC1 VROUT NC VRIN AGND IIN+ IVDC 44 43 42 41 40 39 38 37 36 35 34 33 2 32 AGND ID7 3 31 QD7 ID6 4 30 QD6 ID5 5 29 QD5 ID4 6 28 QD4 ID3 7 27 QD3 DVCC3 8 26 DVCC3 DGND 9 25 DGND ID2 10 24 QD2 ID1 11 23 12 13 14 15 16 17 18 19 20 21 22 QD1 AVCC2 QD0 NC NC DGND DVCC2 CLK DVCC1 NC DGND ID0 AVCC2 1 NC AGND FN4317 Rev 2.00 February 1999 IIN- HI5662 (MQFP) TOP VIEW Page 1 of 15 HI5662 Functional Block Diagram I/QIN- I/QVDC BIAS I/QIN+ S/H STAGE 1 2-BIT FLASH 2-BIT DAC +  DVCC3 X2 I/QD7 (MSB) I/QD6 DIGITAL DELAY AND DIGITAL ERROR CORRECTION STAGE M-1 I/QD5 I/QD4 I/QD3 2-BIT FLASH 2-BIT DAC I/QD2 I/QD1 +  I/QD0 (LSB) - X2 STAGE M 2-BIT FLASH I or Q CHANNEL VREFOUT VREFIN CLOCK REFERENCE AVCC1,2 FN4317 Rev 2.00 February 1999 AGND DVCC1,2 CLK DGND Page 2 of 15 HI5662 Typical Application Schematic HI5662 IIN + (42) IIN + (44) IVDC IIN - (43) IIN - QIN + (36) QIN + (34) QVDC QIN - (35) QIN - 0.1F (LSB) ID0 (12) ID0 ID1 (11) ID1 ID2 (10) ID2 ID3 (7) ID3 ID4 (6) ID4 ID5 (5) ID5 ID6 (4) ID6 (MSB) ID7 (3) ID7 (LSB) QD0 (22) QD0 QD1 (23) QD1 QD2 (24) QD2 QD3 (27) QD3 QD4 (28) QD4 QD5 (29) QD5 QD6 (30) QD6 (MSB) QD7 (31) QD7 (40) VRIN (38) VROUT CLK (17) CLOCK DVCC3 (8,26) (13,14,20,21,39) NC +5V + 10F (37) AVCC1 DVCC2 (18) (2,32) AVCC2 DVCC1 (16) 0.1F (1,33,41) AGND BNC AGND DGND FN4317 Rev 2.00 February 1999 + 10F +5V or +3V 0.1F + 10F +5V 0.1F DGND (9,15,19,25) 10F AND 0.1F CAPS ARE PLACED AS CLOSE TO PART AS POSSIBLE Page 3 of 15 HI5662 Pin Descriptions PIN NO. NAME 1 AGND 2 AVCC2 3 DESCRIPTION PIN NO. NAME Analog Ground 24 QD2 Analog Supply (+5.0V) 25 DGND Digital Ground ID7 I-Channel, Data Bit 7 Output (MSB) 26 DVCC3 4 ID6 I-Channel, Data Bit 6 Output Digital Output Supply (+3.0V or +5.0V) 5 ID5 I-Channel, Data Bit 5 Output 27 QD3 Q-Channel, Data Bit 3 Output 6 ID4 I-Channel Data Bit 4 Output 28 QD4 Q-Channel, Data Bit 4 Output 7 ID3 I-Channel, Data Bit 3 Output 29 QD5 Q-Channel, Data Bit 5 Output 8 DVCC3 Digital Output Supply (+3.0V or +5.0V) 30 QD6 Q-Channel, Data Bit 6 Output 31 QD7 9 DGND Digital Ground Q-Channel, Data Bit 7 Output (MSB) 10 ID2 I-Channel, Data Bit 2 Output 32 AVCC2 Analog Supply (+5.0V) 11 ID1 I-Channel, Data Bit 1 Output 33 AGND Analog Ground 12 ID0 I-Channel, Data Bit 0 Output (LSB) 34 QVDC Q-Channel DC Bias Voltage Output 13 NC No Connect 35 QIN- Q-Channel Negative Analog Input 14 NC No Connect 36 QIN+ Q-Channel Positive Analog Input 15 DGND Digital Ground 37 AVCC1 Analog Supply (+5.0V) 16 DVCC1 Digital Supply (+5.0V) 38 VROUT +2.5V Reference Voltage Output 17 CLK 39 NC 18 DVCC2 Digital Supply (+5.0V) 40 VRIN +2.5V Reference Voltage Input 19 DGND Digital Ground 41 AGND Analog Ground 20 NC No Connect 42 IIN+ I-Channel Positive Analog Input 21 NC No Connect 43 IIN- I-Channel Negative Analog Input 22 QD0 Q-Channel, Data Bit 0 Output (LSB) 44 IVDC 23 QD1 Q-Channel, Data Bit 1 Output FN4317 Rev 2.00 February 1999 Sample Clock Input DESCRIPTION Q-Channel, Data Bit 2 Output No Connect I-Channel DC Bias Voltage Output Page 4 of 15 HI5662 Absolute Maximum Ratings TA = 25oC Thermal Information Supply Voltage, AVCC or DVCC to AGND or DGND . . . . . . . . . . .6V DGND to AGND . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 0.3V Digital I/O Pins . . . . . . . . . . . . . . . . . . . . . . . . . . . . . DGND to DVCC Analog I/O Pins . . . . . . . . . . . . . . . . . . . . . . . . . . . . AGND to AVCC Thermal Resistance (Typical, Note 1) Operating Conditions JA (oC/W) HI5662/6IN . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 75 Maximum Junction Temperature . . . . . . . . . . . . . . . . . . . . . . .150oC Maximum Storage Temperature Range . . . . . . . . . . -65oC to 150oC Maximum Lead Temperature (Soldering 10s) . . . . . . . . . . . . .300oC (Lead Tips Only) Temperature Range HI5662/6IN . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . -40oC to 85oC CAUTION: Stresses above those listed in “Absolute Maximum Ratings” may cause permanent damage to the device. This is a stress only rating and operation of the device at these or any other conditions above those indicated in the operational sections of this specification is not implied. NOTE: 1. JA is measured with the component mounted on an evaluation PC board in free air. Electrical Specifications AVCC1,2 = DVCC1,2 = +5.0V, DVCC3 = +3.0V; VRIN = 2.50V; fS = 60MSPS at 50% Duty Cycle; CL = 10pF; TA = 25oC; Differential Analog Input; Unless Otherwise Specified PARAMETER TEST CONDITIONS MIN TYP MAX UNITS 8 - - Bits ACCURACY Resolution Integral Linearity Error, INL fIN = 10MHz - ±0.5 - LSB Differential Linearity Error, DNL (Guaranteed No Missing Codes) fIN = 10MHz - 0.2 1.0 LSB Offset Error, VOS fIN = DC -10 - +10 LSB Full Scale Error, FSE fIN = DC - 1 - LSB Minimum Conversion Rate No Missing Codes - 1 - MSPS Maximum Conversion Rate No Missing Codes 60 - - MSPS Effective Number of Bits, ENOB fIN = 10MHz fIN = 10MHz, Single Ended Analog Input 7.5 7.0 7.8 7.7 - Bits Bits Signal to Noise and Distortion Ratio, SINAD RMS Signal = -------------------------------------------------------------RMS Noise + Distortion fIN = 10MHz - 48.7 - dB Signal to Noise Ratio, SNR RMS Signal = ------------------------------RMS Noise fIN = 10MHz - 48 - dB Total Harmonic Distortion, THD fIN = 10MHz - -66 - dBc 2nd Harmonic Distortion fIN = 10MHz - -71 - dBc 3rd Harmonic Distortion fIN = 10MHz - -71 - dBc Spurious Free Dynamic Range, SFDR fIN = 10MHz - 71 - dBc Intermodulation Distortion, IMD f1 = 1MHz, f2 = 1.02MHz - 64 - dBc I/Q Channel Crosstalk - -75 -60 dBc I/Q Channel Offset Match - 2.5 - LSB I/Q Channel Full Scale Error Match - 2.5 - LSB DYNAMIC CHARACTERISTICS Transient Response (Note 2) - 1 - Cycle Over-Voltage Recovery 0.2V Overdrive (Note 2) - 1 - Cycle FN4317 Rev 2.00 February 1999 Page 5 of 15 HI5662 Electrical Specifications AVCC1,2 = DVCC1,2 = +5.0V, DVCC3 = +3.0V; VRIN = 2.50V; fS = 60MSPS at 50% Duty Cycle; CL = 10pF; TA = 25oC; Differential Analog Input; Unless Otherwise Specified (Continued) PARAMETER TEST CONDITIONS MIN TYP MAX UNITS Maximum Peak-to-Peak Differential Analog Input Range (VIN+ - VIN-) - 0.5 - V Maximum Peak-to-Peak Single-Ended Analog Input Range - 1.0 - V ANALOG INPUT Analog Input Resistance, RIN+ or RIN- VIN+, VIN- = VREF, DC - 1 - M Analog Input Capacitance, CIN+ or CIN- VIN+, VIN- = 2.5V, DC - 10 - pF Analog Input Bias Current, IB+ or IB- VIN+, VIN- = VREF-, VREF+, DC (Notes 2, 3) -10 - 10 A Differential Analog Input Bias Current IBDIFF = (IB+ - IB-) (Notes 2, 3) -0.5 - +0.5 A Full Power Input Bandwidth, FPBW (Note 2) - 250 - MHz Analog Input Common Mode Voltage Range (VIN+ + VIN-) / 2 Differential Mode (Note 2) 0.25 - 4.75 V 2.35 2.5 2.65 V Reference Output Current, IROUT - 2 4 mA Reference Temperature Coefficient - -400 - ppm/oC - 2.5 - V INTERNAL VOLTAGE REFERENCE Reference Output Voltage, VROUT (Loaded) REFERENCE VOLTAGE INPUT Reference Voltage Input, VRIN Total Reference Resistance, RRIN with VRIN = 2.5V - 1.25 - k Reference Current, IRIN with VRIN = 2.5V - 2 - mA DC Bias Voltage Output, VDC - 3.0 - V Maximum Output Current - - 0.4 mA DC BIAS VOLTAGE SAMPLING CLOCK INPUT Input Logic High Voltage, VIH CLK 2.0 - - V Input Logic Low Voltage, VIL CLK - - 0.8 V Input Logic High Current, IIH CLK, VIH = 5V -10.0 - +10.0 A Input Logic Low Current, IIL CLK, VIL = 0V -10.0 - +10.0 A Input Capacitance, CIN CLK - 7 - pF DIGITAL OUTPUTS Output Logic High Voltage, VOH IOH = 100A; DVCC3 = 5V 4.0 - - V Output Logic Low Voltage, VOL IOL = 100A; DVCC3 = 5V - - 0.8 V Output Logic High Voltage, VOH IOH = 100A; DVCC3 = 3V 2.4 - - V Output Logic Low Voltage, VOL IOL = 100A; DVCC3 = 3V - - 0.5 V - 7 - pF Aperture Delay, tAP - 5 - ns Aperture Jitter, tAJ - 5 - psRMS Data Output Hold, tH - 10.7 - ns Output Capacitance, COUT TIMING CHARACTERISTICS FN4317 Rev 2.00 February 1999 Page 6 of 15 HI5662 Electrical Specifications AVCC1,2 = DVCC1,2 = +5.0V, DVCC3 = +3.0V; VRIN = 2.50V; fS = 60MSPS at 50% Duty Cycle; CL = 10pF; TA = 25oC; Differential Analog Input; Unless Otherwise Specified (Continued) PARAMETER TEST CONDITIONS Data Output Delay, tOD MIN TYP MAX UNITS - 11.7 - ns Data Latency, tLAT For a Valid Sample (Note 2) 6 6 6 Cycles Power-Up Initialization Data Invalid Time (Note 2) - - 20 Cycles Sample Clock Pulse Width (Low) (Note 2) 7.5 8.3 - ns Sample Clock Pulse Width (High) (Note 2) 7.5 8.3 - ns 5 Sample Clock Duty Cycle Variation % POWER SUPPLY CHARACTERISTICS Analog Supply Voltage, AVCC (Note 2) 4.75 5.0 5.25 V Digital Supply Voltage, DVCC1 and DVCC2 (Note 2) 4.75 5.0 5.25 V Digital Output Supply Voltage, DVCC3 At 3.0V (Note 2) 2.7 3.0 3.3 V At 5.0V (Note 2) 4.75 5.0 5.25 V - 130 - mA - 650 670 mW Supply Current, ICC fS = 60MSPS Power Dissipation Offset Error Sensitivity, VOS AVCC or DVCC = 5V 5% - 0.125 - LSB Gain Error Sensitivity, FSE AVCC or DVCC = 5V 5% - 0.15 - LSB NOTES: 2. Parameter guaranteed by design or characterization and not production tested. 3. With the clock low and DC input. FN4317 Rev 2.00 February 1999 Page 7 of 15 HI5662 Timing Waveforms ANALOG INPUT CLOCK INPUT SN - 1 HN - 1 SN HN SN + 1 HN + 1 SN + 2 SN + 5 HN + 5 S N + 6 HN + 6 S N + 7 HN + 7 S N + 8 HN + 8 INPUT S/H 1ST STAGE B1 , N - 1 2ND STAGE B2 , N - 2 M-th STAGE B1 , N B2 , N - 1 B9 , N - 5 DATA OUTPUT B1 , N + 1 B1 , N + 5 B2 , N + 4 B2 , N B9 , N - 4 DN - 6 B1 , N + 4 B9 , N DN - 5 B1 , N + 6 B2 , N + 5 B9 , N + 1 DN - 1 B1 , N + 7 B2 , N + 6 B9 , N + 2 DN B9 , N + 3 DN + 1 DN + 2 tLAT NOTES: 4. SN : N-th sampling period. 5. HN : N-th holding period. 6. BM , N : M-th stage digital output corresponding to N-th sampled input. 7. DN : Final data output corresponding to N-th sampled input. FIGURE 1. HI5662 INTERNAL CIRCUIT TIMING ANALOG INPUT tAP tAJ CLOCK INPUT 1.5V 1.5V tOD tH DATA OUTPUT 2.4V DATA N-1 0.5V DATA N FIGURE 2. HI5662 INPUT-TO-OUTPUT TIMING FN4317 Rev 2.00 February 1999 Page 8 of 15 HI5662 50 50 7 44 44 6 38 SNR (dB) 8 SINAD (dB) ENOB (BITS) Typical Performance Curves 38 fS = 60MSPS TA = 25oC 5 1 32 100 10 INPUT FREQUENCY (MHz) 32 fS = 60MSPS TA = 25oC 1 10 INPUT FREQUENCY (MHz) FIGURE 3. EFFECTIVE NUMBER OF BITS (ENOB) AND SINAD vs INPUT FREQUENCY FIGURE 4. SNR vs INPUT FREQUENCY 70 90 85 60 -2HD 80 50 -THD (dBc) dB dBc 75 -3HD 70 65 -THD 40 30 SNR (dB) OR SINAD (dB) 60 55 20 fS = 60MSPS TA = 25oC 1 10 INPUT FREQUENCY (MHz) 10 -40 100 -30 -20 INPUT LEVEL (dBFS) -10 0 FIGURE 5. -THD, -2HD AND -3HD vs INPUT FREQUENCY FIGURE 6. SINAD, SNR AND -THD vs INPUT AMPLITUDE 8 150 140 130 120 110 100 90 80 70 60 50 40 30 20 10 0 SUPPLY CURRENT (mA) ENOB (BITS) 50 100 7 6 fS = 60MSPS 1MHz < fIN < 15MHz TA = 25oC 5 40 42 44 46 48 50 52 54 56 58 DUTY CYCLE (%, tHI /tCLK) FIGURE 7. EFFECTIVE NUMBER OF BITS (ENOB) vs SAMPLE CLOCK DUTY CYCLE FN4317 Rev 2.00 February 1999 60 1MHz < fIN < 15MHz TA = 25oC ICC AICC DICC1 DICC2 DICC3 10 20 30 40 fS (MSPS) 50 60 FIGURE 8. SUPPLY CURRENT vs SAMPLE CLOCK FREQUENCY Page 9 of 15 70 HI5662 Typical Performance Curves (Continued) 3.10 2.49 2.48 DC BIAS VOLTAGE, I/Q VDC (V) INTERNAL REFERENCE VOLTAGE, VROUT (V) 2.50 2.47 2.46 2.45 2.44 2.43 2.42 2.41 2.40 -40 -20 0 20 40 TEMPERATURE (oC) 60 3.00 2.95 IVDC -40 0 20 40 TEMPERATURE (oC) 60 80 140 ICC SUPPLY CURRENT (mA) 120 12.5 tOD (ns) -20 FIGURE 10. DC BIAS VOLTAGE (I/QVDC) vs TEMPERATURE 13.0 tOD 12.0 11.5 11.0 QVDC 2.90 2.85 80 FIGURE 9. INTERNAL REFERENCE VOLTAGE (VROUT) vs TEMPERATURE 3.05 -40 -20 0 20 40 TEMPERATURE (oC) 60 80 FIGURE 11. DATA OUTPUT DELAY (tOD) vs TEMPERATURE fS = 60MSPS 1MHz < fIN < 15MHz 100 80 AICC 60 40 DICC1 20 DICC2 0 -40 DICC3 -20 0 20 40 TEMPERATURE (oC) 60 FIGURE 12. SUPPLY CURRENT vs TEMPERATURE 0 fS = 60MSPS fIN = 10MHz TA = 25oC -10 -20 -30 dB -40 -50 -60 -70 -80 -90 -100 0 100 200 300 400 500 600 700 FREQUENCY (BIN) 800 900 1023 FIGURE 13. 2048 POINT FFT PLOT FN4317 Rev 2.00 February 1999 Page 10 of 15 80 HI5662 TABLE 1. A/D CODE TABLE OFFSET BINARY OUTPUT CODE DIFFERENTIAL INPUT VOLTAGE (I/QIN+ - I/QIN-) I/QD7 I/QD6 I/QD5 I/QD4 I/QD3 I/QD2 I/QD1 I/QD0 0.498291V 1 1 1 1 1 1 1 1 0.494385V 1 1 1 1 1 1 1 0 16LSB 2.19727mV 1 0 0 0 0 0 0 0 16LSB CODE CENTER DESCRIPTION +Full Scale (+FS) -7/16LSB +FS +9/ -7/ 17 / 16LSB MSB LSB -1.70898mV 0 1 1 1 1 1 1 1 -FS + 19/16LSB -0.493896V 0 0 0 0 0 0 0 1 -Full Scale (-FS) + 9/16LSB -0.497803V 0 0 0 0 0 0 0 0 NOTE: 8. The voltages listed above represent the ideal center of each output code shown with VREFIN = +2.5V. Detailed Description Theory of Operation The HI5662 is a dual 8-bit fully differential sampling pipeline A/D converter with digital error correction logic. Figure 14 depicts the circuit for the front end differential-in-differential-out sample-and-hold (S/H) amplifiers. The switches are controlled by an internal sampling clock which is a non-overlapping two phase signal, 1 and 2 , derived from the master sampling clock. During the sampling phase, 1 , the input signal is applied to the sampling capacitors, CS . At the same time the holding capacitors, CH , are discharged to analog ground. At the falling edge of 1 the input signal is sampled on the bottom plates of the sampling capacitors. In the next clock phase, 2 , the two bottom plates of the sampling capacitors are connected together and the holding capacitors are switched to the op-amp output nodes. The charge then redistributes between CS and CH completing one sample-and-hold cycle. The front end sample-and-hold output is a fully-differential, sampled-data representation of the analog input. The circuit not only performs the sample-and-hold function but will also convert a single-ended input to a fully-differential output for the converter core. During the sampling phase, the I/QIN pins see only the on-resistance of a switch and CS . The relatively small values of these components result in a typical full power input bandwidth of 250MHz for the converter. 1 I/QIN+ 1 1 1 CS 2 I/QIN- CH -+ VOUT+ +- VOUT- CS 1 CH 1 FIGURE 14. ANALOG INPUT SAMPLE-AND-HOLD FN4317 Rev 2.00 February 1999 As illustrated in the functional block diagram and the timing diagram in Figure 1, identical pipeline subconverter stages, each containing a two-bit flash converter and a two-bit multiplying digital-to-analog converter, follow the S/H circuit with the last stage being a two bit flash converter. Each converter stage in the pipeline will be sampling in one phase and amplifying in the other clock phase. Each individual subconverter clock signal is offset by 180 degrees from the previous stage clock signal resulting in alternate stages in the pipeline performing the same operation. The output of each of the identical two-bit subconverter stages is a two-bit digital word containing a supplementary bit to be used by the digital error correction logic. The output of each subconverter stage is input to a digital delay line which is controlled by the internal sampling clock. The function of the digital delay line is to time align the digital outputs of the identical two-bit subconverter stages with the corresponding output of the last stage flash converter before applying the results to the digital error correction logic. The digital error correction logic uses the supplementary bits to correct any error that may exist before generating the final eight bit digital data output of the converter. Because of the pipeline nature of this converter, the digital data representing an analog input sample is output to the digital data bus following the 6th cycle of the clock after the analog sample is taken (see the timing diagram in Figure 1). This time delay is specified as the data latency. After the data latency time, the digital data representing each succeeding analog sample is output during the following clock cycle. The digital output data is provided in offset binary format (see Table 1, A/D Code Table). Internal Reference Voltage Output, VREFOUT The HI5662 is equipped with an internal reference voltage generator, therefore, no external reference voltage is required. VROUT must be connected to VRIN when using the internal reference voltage. Page 11 of 15 HI5662 An internal band-gap reference voltage followed by an amplifier/buffer generates the precision +2.5V reference voltage used by the converter. A band-gap reference circuit is used to generate a precision +1.25V internal reference voltage. This voltage is then amplified by a wide-band uncompensated operational amplifier connected in a gain-of-two configuration. An external, user-supplied, 0.1F capacitor connected from the VROUT output pin to analog ground is used to set the dominant pole and to maintain the stability of the operational amplifier. Reference Voltage Input, VREFIN The HI5662 is designed to accept a +2.5V reference voltage source at the VRIN input pin. Typical operation of the converter requires VRIN to be set at +2.5V. The HI5662 is tested with VRIN connected to VROUT yielding a fully differential analog input voltage range of 0.5V. The user does have the option of supplying an external +2.5V reference voltage. As a result of the high input impedance presented at the VRIN input pin, 1.25k typically, the external reference voltage being used is only required to source 2mA of reference input current. In the situation where an external reference voltage will be used an external 0.1F capacitor must be connected from the VROUT output pin to analog ground in order to maintain the stability of the internal operational amplifier. In order to minimize overall converter noise it is recommended that adequate high frequency decoupling be provided at the reference voltage input pin, VRIN . Analog Input, Differential Connection The analog input of the HI5662 is a differential input that can be configured in various ways depending on the signal source and the required level of performance. A fully differential connection (Figure 15 and Figure 16) will deliver the best performance from the converter. I/QIN+ VIN R an AC coupled differential input. This low output impedance voltage source is not designed to be a reference but makes an excellent DC bias source and stays well within the analog input common mode voltage range over temperature. For the AC coupled differential input (Figure 15) and with VRIN connected to VROUT, full scale is achieved when the VIN and -VIN input signals are 0.5VP-P , with -VIN being 180 degrees out of phase with VIN . The converter will be at positive full scale when the I/QIN+ input is at VDC + 0.25V and the I/QIN- input is at VDC - 0.25V (I/QIN+ - I/QIN- = +0.5V). Conversely, the converter will be at negative full scale when the I/QIN+ input is equal to VDC - 0.25V and I/QIN- is at VDC + 0.25V (I/QIN+ - I/QIN- = -0.5V). The analog input can be DC coupled (Figure 16) as long as the inputs are within the analog input common mode voltage range (0.25V  VDC  4.75V). VIN I/QIN+ VDC R HI5662 I/QVDC -VIN R VDC I/QIN- FIGURE 16. DC COUPLED DIFFERENTIAL INPUT The resistors, R, in Figure 16 are not absolutely necessary but may be used as load setting resistors. A capacitor, C, connected from I/QIN+ to I/QIN- will help filter any high frequency noise on the inputs, also improving performance. Values around 20pF are sufficient and can be used on AC coupled inputs as well. Note, however, that the value of capacitor C chosen must take into account the highest frequency component of the analog input signal. Analog Input, Single-Ended Connection The configuration shown in Figure 17 may be used with a single ended AC coupled input. HI5662 I/QVDC I/QIN+ VIN R R -VIN C VDC HI5662 I/QINI/QIN- FIGURE 15. AC COUPLED DIFFERENTIAL INPUT Since the HI5662 is powered by a single +5V analog supply, the analog input is limited to be between ground and +5V. For the differential input connection this implies the analog input common mode voltage can range from 0.25V to 4.75V. The performance of the ADC does not change significantly with the value of the analog input common mode voltage. A DC voltage source, I/QVDC , equal to 3.0V (typical), is made available to the user to help simplify circuit design when using FN4317 Rev 2.00 February 1999 FIGURE 17. AC COUPLED SINGLE ENDED INPUT Again, with VRIN connected to VROUT, if VIN is a 1VP-P sinewave, then I/QIN+ is a 1.0VP-P sinewave riding on a positive voltage equal to VDC . The converter will be at positive full scale when I/QIN+ is at VDC + 0.5V (I/QIN+ - I/QIN- = +0.5V) and will be at negative full scale when I/QIN+ is equal to VDC - 0.5V (I/QIN+ - I/QIN- = -0.5V). Sufficient headroom must be provided such that the input voltage never goes above +5V or Page 12 of 15 HI5662 below AGND. In this case, VDC could range between 0.5V and 4.5V without a significant change in ADC performance. The simplest way to produce VDC is to use the DC bias source, I/QVDC , of the HI5662. should also have good high frequency decoupling capacitors mounted as close as possible to the converter. If the part is powered off a single supply then the analog supply can be isolated by a ferrite bead from the digital supply. The single ended analog input can be DC coupled (Figure 18) as long as the input is within the analog input common mode voltage range. Refer to the application note “Using Intersil High Speed A/D Converters” (AN9214) for additional considerations when using high speed converters. VIN I/QIN+ VDC Offset Error (VOS) R HI5662 C VDC I/QIN- FIGURE 18. DC COUPLED SINGLE ENDED INPUT The resistor, R, in Figure 18 is not absolutely necessary but may be used as a load setting resistor. A capacitor, C, connected from I/QIN+ to I/QIN- will help filter any high frequency noise on the inputs, also improving performance. Values around 20pF are sufficient and can be used on AC coupled inputs as well. Note, however, that the value of capacitor C chosen must take into account the highest frequency component of the analog input signal. A single ended source may give better overall system performance if it is first converted to differential before driving the HI5662. Sampling Clock Requirements The HI5662 sampling clock input provides a standard highspeed interface to external TTL/CMOS logic families. In order to ensure rated performance of the HI5662, the duty cycle of the clock should be held at 50% 5%. It must also have low jitter and operate at standard TTL/CMOS levels. Performance of the HI5662 will only be guaranteed at conversion rates above 1MSPS (Typ). This ensures proper performance of the internal dynamic circuits. Similarly, when power is first applied to the converter, a maximum of 20 cycles at a sample rate above 1MSPS must to be performed before valid data is available. Supply and Ground Considerations The HI5662 has separate analog and digital supply and ground pins to keep digital noise out of the analog signal path. The digital data outputs also have a separate supply pin, DVCC3 , which can be powered from a 3.0V or 5.0V supply. This allows the outputs to interface with 3.0V logic if so desired. The part should be mounted on a board that provides separate low impedance connections for the analog and digital supplies and grounds. For best performance, the supplies to the HI5662 should be driven by clean, linear regulated supplies. The board FN4317 Rev 2.00 February 1999 Static Performance Definitions The midscale code transition should occur at a level 1 / 4LSB above half-scale. Offset is defined as the deviation of the actual code transition from this point. Full-Scale Error (FSE) The last code transition should occur for an analog input that is 3 / LSB below Positive Full Scale (+FS) with the offset error 4 removed. Full scale error is defined as the deviation of the actual code transition from this point. Differential Linearity Error (DNL) DNL is the worst case deviation of a code width from the ideal value of 1LSB. Integral Linearity Error (INL) INL is the worst case deviation of a code center from a best fit straight line calculated from the measured data. Power Supply Sensitivity Each of the power supplies are moved plus and minus 5% and the shift in the offset and full scale error (in LSBs) is noted. Dynamic Performance Definitions Fast Fourier Transform (FFT) techniques are used to evaluate the dynamic performance of the HI5662. A low distortion sine wave is applied to the input, it is coherently sampled, and the output is stored in RAM. The data is then transformed into the frequency domain with an FFT and analyzed to evaluate the dynamic performance of the A/D. The sine wave input to the part is typically -0.5dB down from full scale for all these tests. SNR and SINAD are quoted in dB. The distortion numbers are quoted in dBc (decibels with respect to carrier) and DO NOT include any correction factors for normalizing to full scale. The Effective Number of Bits (ENOB) is calculated from the SINAD data by: ENOB = (SINAD - 1.76 + VCORR) / 6.02, where: VCORR = 0.5dB (Typical). VCORR adjusts the SINAD, and hence the ENOB, for the amount the analog input signal is backed off from full scale. Page 13 of 15 HI5662 Signal To Noise and Distortion Ratio (SINAD) I/Q Channel Crosstalk SINAD is the ratio of the measured RMS signal to RMS sum of all the other spectral components below the Nyquist frequency, fS/2, excluding DC. I/Q Channel Crosstalk is a measure of the amount of channel separation or isolation between the two A/D converter cores contained within the dual converter package. The measurement consists of stimulating one channel of the converter with a fullscale input signal and then measuring the amount that signal is below, in dBc, a fullscale signal on the opposite channel. Signal To Noise Ratio (SNR) SNR is the ratio of the measured RMS signal to RMS noise at a specified input and sampling frequency. The noise is the RMS sum of all of the spectral components below fS /2 excluding the fundamental, the first five harmonics and DC. Timing Definitions Total Harmonic Distortion (THD) Refer to Figure 1 and Figure 2 for these definitions. THD is the ratio of the RMS sum of the first 5 harmonic components to the RMS value of the fundamental input signal. Aperture Delay (tAP) This is the ratio of the RMS value of the applicable harmonic component to the RMS value of the fundamental input signal. Aperture delay is the time delay between the external sample command (the falling edge of the clock) and the time at which the signal is actually sampled. This delay is due to internal clock path propagation delays. Spurious Free Dynamic Range (SFDR) Aperture Jitter (tAJ) SFDR is the ratio of the fundamental RMS amplitude to the RMS amplitude of the next largest spectral component in the spectrum below fS /2. Aperture jitter is the RMS variation in the aperture delay due to variation of internal clock path delays. Intermodulation Distortion (IMD) Data hold time is the time to where the previous data (N - 1) is no longer valid. 2nd and 3rd Harmonic Distortion Nonlinearities in the signal path will tend to generate intermodulation products when two tones, f1 and f2 , are present at the inputs. The ratio of the measured signal to the distortion terms is calculated. The terms included in the calculation are (f1+f2), (f1-f2), (2f1), (2f2), (2f1+f2), (2f1-f2), (f1+2f2), (f1-2f2). The ADC is tested with each tone 6dB below full scale. Transient Response Transient response is measured by providing a full-scale transition to the analog input of the ADC and measuring the number of cycles it takes for the output code to settle within 10bit accuracy. Over-Voltage Recovery Over-Voltage Recovery is measured by providing a full-scale transition to the analog input of the ADC which overdrives the input by 200mV, and measuring the number of cycles it takes for the output code to settle within 10-bit accuracy. Full Power Input Bandwidth (FPBW) Full power input bandwidth is the analog input frequency at which the amplitude of the digitally reconstructed output has decreased 3dB below the amplitude of the input sine wave. The input sine wave has an amplitude which swings from -FS to +FS. The bandwidth given is measured at the specified sampling frequency. FN4317 Rev 2.00 February 1999 Data Hold Time (tH) Data Output Delay Time (tOD) Data output delay time is the time to where the new data (N) is valid. Data Latency (tLAT) After the analog sample is taken, the digital data representing an analog input sample is output to the digital data bus following the 6th cycle of the clock after the analog sample is taken. This is due to the pipeline nature of the converter where the analog sample has to ripple through the internal subconverter stages. This delay is specified as the data latency. After the data latency time, the digital data representing each succeeding analog sample is output during the following clock cycle. The digital data lags the analog input sample by 6 sample clock cycles. Power-Up Initialization This time is defined as the maximum number of clock cycles that are required to initialize the converter at power-up. The requirement arises from the need to initialize the dynamic circuits within the converter. Page 14 of 15 Notice 1. Descriptions of circuits, software and other related information in this document are provided only to illustrate the operation of semiconductor products and application examples. You are fully responsible for the incorporation or any other use of the circuits, software, and information in the design of your product or system. Renesas Electronics disclaims any and all liability for any losses and damages incurred by you or third parties arising from the use of these circuits, software, or information. 2. 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