HI5767/6IBZ

NOT RECOMMENDED FOR NEW DESIGNS NO RECOMMENDED REPLACEMENT contact our Technical Support Center at 1-888-INTERSIL or www.intersil.com/tsc HI5767 DATASHEET 10-Bit, 20/40/60MSPS A/D Converter with Internal Voltage Reference The HI5767 is a monolithic, 10-bit, analog-to-digital converter fabricated in a CMOS process. It is designed for high speed applications where wide bandwidth and low power consumption are essential. Its high sample clock rate is made possible by a fully differential pipelined architecture with both an internal sample and hold and internal band-gap voltage reference. The 250MHz Full Power Input Bandwidth and superior high frequency performance of the HI5767 converter make it an excellent choice for implementing Digital IF architectures in communications applications. FN4319 Rev 6.00 March 30, 2005 Features • Sampling Rate . . . . . . . . . . . . . . . . . . . . . . 20/40/60MSPS • 8.8 Bits at fIN = 10MHz, fS = 40MSPS • Low Power at 40MSPS . . . . . . . . . . . . . . . . . . . . .310mW • Wide Full Power Input Bandwidth . . . . . . . . . . . . 250MHz • On-Chip Sample and Hold • Internal 2.5V Band-Gap Voltage Reference • Fully Differential or Single-Ended Analog Input • Single Supply Voltage . . . . . . . . . . . . . . . . . . . . . . . . .+5V The HI5767 has excellent dynamic performance while consuming only 310mW power at 40MSPS. Data output latches are provided which present valid data to the output bus with a latency of 7 clock cycles. • TTL/CMOS Compatible Digital Inputs The HI5767 is offered in 20MSPS, 40MSPS and 60MSPS sampling rates. • Pb-Free Available (RoHS Compliant) • CMOS Compatible Digital Outputs. . . . . . . . . . . 3.0V/5.0V • Offset Binary or Two’s Complement Output Format Applications Pinout • Digital Communication Systems HI5767 (SOIC, SSOP) TOP VIEW • QAM Demodulators • Professional Video Digitizing DVCC1 1 28 D0 DGND 2 27 D1 DVCC1 3 26 D2 DGND 4 25 D3 AVCC 5 AGND 6 24 D4 VREFIN 7 VREFOUT 8 22 CLK 21 DGND 20 D5 VIN- 10 VDC 11 19 D6 AGND 12 17 D8 AVCC 13 16 D9 FN4319 Rev 6.00 March 30, 2005 • High Speed Data Acquisition 23 DVCC2 VIN+ 9 OE 14 • Medical Imaging 18 D7 15 DFS Page 1 of 15 HI5767 Ordering Information PART NUMBER TEMP. RANGE (oC) PACKAGE PKG. DWG. # SAMPLING RATE (MSPS) HI5767/2CB 0 to 70 28 Ld SOIC M28.3 20 HI5767/2CBZ (See Note) 0 to 70 28 Ld SOIC (Pb-free) M28.3 20 HI5767/4CB* 0 to 70 28 Ld SOIC M28.3 40 HI5767/4CBZ* (See Note) 0 to 70 28 Ld SOIC (Pb-free) M28.3 40 HI5767/6CB* 0 to 70 28 Ld SOIC M28.3 60 HI5767/6CBZ* (See Note) 0 to 70 28 Ld SOIC (Pb-free) M28.3 60 HI5767/6IB -40 to 85 28 Ld SOIC M28.3 60 HI5767/6IBZ (See Note) -40 to 85 28 Ld SOIC (Pb-free) M28.3 60 HI5767/2CA 0 to 70 28 Ld SSOP M28.15 20 HI5767/2CAZ (See Note) 0 to 70 28 Ld SSOP (Pb-free) M28.15 20 HI5767/2IA -40 to 85 28 Ld SSOP M28.15 20 HI5767/2IAZ (See Note) -40 to 85 28 Ld SSOP (Pb-free) M28.15 20 HI5767/4CA 0 to 70 28 Ld SSOP M28.15 40 HI5767/4CAZ (See Note) 0 to 70 28 Ld SSOP (Pb-free) M28.15 40 HI5767/6CA 0 to 70 28 Ld SSOP M28.15 60 HI5767/6CAZ (See Note) 0 to 70 28 Ld SSOP (Pb-free) M28.15 60 HI5767EVAL1 25 Evaluation Board 60 HI5767EVAL2 25 Evaluation Board 60 * Add “-T” suffix for tape and reel. NOTE: Intersil Pb-free products employ special Pb-free material sets; molding compounds/die attach materials and 100% matte tin plate termination finish, which are RoHS compliant and compatible with both SnPb and Pb-free soldering operations. Intersil Pb-free products are MSL classified at Pb-free peak reflow temperatures that meet or exceed the Pb-free requirements of IPC/JEDEC J STD-020. FN4319 Rev 6.00 March 30, 2005 Page 2 of 15 HI5767 Functional Block Diagram VDC CLOCK BIAS CLK VINVIN+ REFERENCE S/H VREFOUT VREFIN STAGE 1 DFS 2-BIT FLASH 2-BIT DAC OE +  DVCC2 X2 D9 (MSB) D8 D7 D6 DIGITAL DELAY AND DIGITAL ERROR CORRECTION STAGE 8 D5 D4 D3 2-BIT FLASH 2-BIT DAC D2 D1 +  D0 (LSB) - X2 DGND2 STAGE 9 2-BIT FLASH AVCC FN4319 Rev 6.00 March 30, 2005 AGND DVCC1 DGND1 Page 3 of 15 HI5767 Typical Application Schematic HI5767 VREFIN (7) VREFOUT (8) 0.1F (LSB) (28) D0 D0 (27) D1 D1 (26) D2 D2 (25) D3 D3 (24) D4 D4 DGND1 (2) (20) D5 D5 DGND1 (4) (19) D6 D6 DGND2 (21) (18) D7 D7 (17) D8 D8 (MSB) (16) D9 D9 AGND (12) AGND (6) VIN + VIN + (9) VIN - CLOCK (3) DVCC1 VIN - (10) (23) DVCC2 CLK (22) (13) AVCC DFS (15) (5) AVCC AGND BNC 10F AND 0.1F CAPS ARE PLACED AS CLOSE TO PART AS POSSIBLE (1) DVCC1 VDC (11) DGND OE (14) 0.1F + 10F 0.1F + 10F +5V +5V Pin Descriptions PIN NO. NAME Digital Supply (+5.0V) 15 DFS Data Format Select Input DGND1 Digital Ground 16 D9 Data Bit 9 Output (MSB) 3 DVCC1 Digital Supply (+5.0V) 17 D8 Data Bit 8 Output 4 DGND1 Digital Ground 18 D7 Data Bit 7 Output 5 AVCC Analog Supply (+5.0V) 19 D6 Data Bit 6 Output 6 AGND Analog Ground 20 D5 Data Bit 5 Output 7 VREFIN +2.5V Reference Voltage Input 21 DGND2 8 VREFOUT +2.5V Reference Voltage Output 22 CLK 9 VIN+ Positive Analog Input 23 DVCC2 10 VIN- Negative Analog Input 24 D4 Data Bit 4 Output 11 VDC DC Bias Voltage Output 25 D3 Data Bit 3 Output 12 AGND Analog Ground 26 D2 Data Bit 2 Output 13 AVCC Analog Supply (+5.0V) 27 D1 Data Bit 1 Output 14 OE Digital Output Enable Control Input 28 D0 Data Bit 0 Output (LSB) PIN NO. NAME 1 DVCC1 2 FN4319 Rev 6.00 March 30, 2005 DESCRIPTION DESCRIPTION Digital Ground Sample Clock Input Digital Output Supply (+3.0V or +5.0V) Page 4 of 15 HI5767 Absolute Maximum Ratings TA = 25oC Thermal Information Supply Voltage, AVCC or DVCC to AGND or DGND . . . . . . . . . . .6V DGND to AGND . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 0.3V Digital I/O Pins . . . . . . . . . . . . . . . . . . . . . . . . . . . . . DGND to DVCC Analog I/O Pins . . . . . . . . . . . . . . . . . . . . . . . . . . . . AGND to AVCC Thermal Resistance (Typical, Note 1) Operating Conditions Temperature Range HI5767/xCx. . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 0oC to 70oC HI5767/xIx . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . -40oC to 85oC JA (oC/W) SOIC Package . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 75 SSOP Package . . . . . . . . . . . . . . . . . . . . . . . . . . . . 100 Maximum Junction Temperature . . . . . . . . . . . . . . . . . . . . . . .150oC Maximum Storage Temperature Range . . . . . . . . . -65oC to 150oC Maximum Lead Temperature (Soldering 10s) . . . . . . . . . . . . .300oC (SOIC - Lead Tips Only) CAUTION: Stresses above those listed in “Absolute Maximum Ratings” may cause permanent damage to the device. This is a stress only rating and operation of the device at these or any other conditions above those indicated in the operational sections of this specification is not implied. NOTE: 1. JA is measured with the component mounted on an evaluation PC board in free air. Electrical Specifications AVCC = DVCC1 = 5.0V, DVCC2 = 3.0V; VREFIN = VREFOUT; fS = 40MSPS at 50% Duty Cycle; CL = 10pF; TA = 25oC; Differential Analog Input; Typical Values are Test Results at 25oC, Unless Otherwise Specified PARAMETER TEST CONDITIONS MIN TYP MAX UNITS 10 - - Bits ACCURACY Resolution Integral Linearity Error, INL fIN = 1MHz Sinewave - 0.75 1.75 LSB Differential Linearity Error, DNL (Guaranteed No Missing Codes) fIN = 1MHz Sinewave - 0.35 1.0 LSB Offset Error, VOS fIN = DC -40 - 40 LSB Full Scale Error, FSE fIN = DC - 4 - LSB No Missing Codes - 0.5 1 MSPS HI5767/2 No Missing Codes 20 - - MSPS HI5767/4 No Missing Codes 40 - - MSPS HI5767/6 No Missing Codes 60 - - MSPS HI5767/2 fS = 20MSPS, fIN = 10MHz 8.7 9 - Bits HI5767/4 fS = 40MSPS, fIN = 10MHz 8.55 8.8 - Bits HI5767/6 fS = 60MSPS, fIN = 10MHz 8.1 8.4 - Bits HI5767/2 fS = 20MSPS, fIN = 10MHz - 55.9 - dB HI5767/4 fS = 40MSPS, fIN = 10MHz - 54.7 - dB HI5767/6 fS = 60MSPS, fIN = 10MHz - 53.8 - dB HI5767/2 fS = 20MSPS, fIN = 10MHz - 55.9 - dB HI5767/4 fS = 40MSPS, fIN = 10MHz - 55 - dB HI5767/6 fS = 60MSPS, fIN = 10MHz - 54 - dB fS = 20MSPS, fIN = 10MHz - -71 - dBc DYNAMIC CHARACTERISTICS Minimum Conversion Rate Maximum Conversion Rate Effective Number of Bits, ENOB Signal to Noise and Distortion Ratio, SINAD RMS Signal = -------------------------------------------------------------RMS Noise + Distortion Signal to Noise Ratio, SNR RMS Signal = ------------------------------RMS Noise Total Harmonic Distortion, THD HI5767/2 FN4319 Rev 6.00 March 30, 2005 Page 5 of 15 HI5767 Electrical Specifications AVCC = DVCC1 = 5.0V, DVCC2 = 3.0V; VREFIN = VREFOUT; fS = 40MSPS at 50% Duty Cycle; CL = 10pF; TA = 25oC; Differential Analog Input; Typical Values are Test Results at 25oC, Unless Otherwise Specified (Continued) PARAMETER TEST CONDITIONS MIN TYP MAX UNITS HI5767/4 fS = 40MSPS, fIN = 10MHz - -65 - dBc HI5767/6 fS = 60MSPS, fIN = 10MHz - -64.5 - dBc HI5767/2 fS = 20MSPS, fIN = 10MHz - -76 - dBc HI5767/4 fS = 40MSPS, fIN = 10MHz - -73 - dBc HI5767/6 fS = 60MSPS, fIN = 10MHz - -70 - dBc HI5767/2 fS = 20MSPS, fIN = 10MHz - -80 - dBc HI5767/4 fS = 40MSPS, fIN = 10MHz - -69 - dBc HI5767/6 fS = 60MSPS, fIN = 10MHz - -67 - dBc HI5767/2 fS = 20MSPS, fIN = 10MHz - 76 - dBc HI5767/4 fS = 40MSPS, fIN = 10MHz - 69 - dBc HI5767/6 fS = 60MSPS, fIN = 10MHz - 67 - dBc Intermodulation Distortion, IMD f1 = 1MHz, f2 = 1.02MHz - 64 - dBc Differential Gain Error fS = 17.72MHz, 6 Step, Mod Ramp - 0.5 - % Differential Phase Error fS = 17.72MHz, 6 Step, Mod Ramp - 0.2 - Degree 2nd Harmonic Distortion 3rd Harmonic Distortion Spurious Free Dynamic Range, SFDR Transient Response (Note 2) - 1 - Cycle Over-Voltage Recovery 0.2V Overdrive (Note 2) - 1 - Cycle Maximum Peak-to-Peak Differential Analog Input Range (VIN+ - VIN-) - 0.5 - V Maximum Peak-to-Peak Single-Ended Analog Input Range - 1.0 - V - 1 - M - 10 - pF ANALOG INPUT Analog Input Resistance, RIN (Note 3) Analog Input Capacitance, CIN Analog Input Bias Current, IB+ or IB- (Note 3) -10 - +10 A Differential Analog Input Bias Current IBDIFF = (IB+ - IB-) (Note 3) - 0.5 - A - 250 - MHz 0.25 - 4.75 V Reference Voltage Output, VREFOUT (Loaded) - 2.5 - V Reference Output Current, IREFOUT - 1 2 mA Reference Temperature Coefficient - 120 - ppm/oC Full Power Input Bandwidth, FPBW Analog Input Common Mode Voltage Range (VIN+ + VIN-) / 2 Differential Mode (Note 2) INTERNAL REFERENCE VOLTAGE REFERENCE VOLTAGE INPUT Reference Voltage Input, VREFIN - 2.5 - V Total Reference Resistance, RREFIN - 2.5 - k Reference Input Current, IREFIN - 1 - mA - 3.0 - V DC BIAS VOLTAGE DC Bias Voltage Output, VDC FN4319 Rev 6.00 March 30, 2005 Page 6 of 15 HI5767 Electrical Specifications AVCC = DVCC1 = 5.0V, DVCC2 = 3.0V; VREFIN = VREFOUT; fS = 40MSPS at 50% Duty Cycle; CL = 10pF; TA = 25oC; Differential Analog Input; Typical Values are Test Results at 25oC, Unless Otherwise Specified (Continued) PARAMETER TEST CONDITIONS Maximum Output Current MIN TYP MAX UNITS - - 0.2 mA DIGITAL INPUTS Input Logic High Voltage, VIH CLK, DFS, OE 2.0 - - V Input Logic Low Voltage, VIL CLK, DFS, OE - - 0.8 V Input Logic High Current, IIH CLK, DFS, OE, VIH = 5V -10.0 - +10.0 A Input Logic Low Current, IIL CLK, DFS, OE, VIL = 0V -10.0 - +10.0 A - 7 - pF Input Capacitance, CIN DIGITAL OUTPUTS Output Logic High Voltage, VOH IOH = 100A; DVCC2 = 5V 4.0 - - V Output Logic Low Voltage, VOL IOL = 100A; DVCC2 = 5V - - 0.8 V Output Three-State Leakage Current, IOZ VO = 0/5V; DVCC2 = 5V -10 1 10 A Output Logic High Voltage, VOH IOH = 100A; DVCC2 = 3V 2.4 - - V Output Logic Low Voltage, VOL IOL = 100A; DVCC2 = 3V Output Three-State Leakage Current, IOZ VO = 0/5V; DVCC2 = 3V - - 0.5 V -10 1 10 A - 10 - pF Aperture Delay, tAP - 5 - ns Aperture Jitter, tAJ - 5 - psRMS Data Output Hold, tH - 5 - ns Data Output Delay, tOD - 6 - ns Data Output Enable Time, tEN - 5 - ns Data Output Enable Time, tDIS - 5 - ns Output Capacitance, COUT TIMING CHARACTERISTICS Data Latency, tLAT For a Valid Sample (Note 2) - - 7 Cycles Power-Up Initialization Data Invalid Time (Note 2) - - 20 Cycles Sample Clock Pulse Width (Low) fS = 40MSPS 11.3 12.5 - ns Sample Clock Pulse Width (High) fS = 40MSPS 11.3 12.5 - ns Sample Clock Duty Cycle Variation fS = 40MSPS - 5 - % Analog Supply Voltage, AVCC 4.75 5.0 5.25 V Digital Supply Voltage, DVCC1 4.75 5.0 5.25 V At 3.0V 2.7 3.0 3.3 V At 5.0V 4.75 5.0 5.25 V - 62 - mA POWER SUPPLY CHARACTERISTICS Digital Output Supply Voltage, DVCC2 Supply Current, ICC fIN = 1MHz and DFS = “0” Power Dissipation fIN = 1MHz and DFS = “0” - 310 - mW Offset Error Sensitivity, VOS AVCC or DVCC = 5V 5% - 0.7 - LSB Gain Error Sensitivity, FSE AVCC or DVCC = 5V 5% - 0.1 - LSB NOTES: 2. Parameter guaranteed by design or characterization and not production tested. 3. With the clock low and DC input. FN4319 Rev 6.00 March 30, 2005 Page 7 of 15 HI5767 Timing Waveforms ANALOG INPUT tAP tAJ CLOCK INPUT 1.5V 1.5V tOD tH 2.4V DATA OUTPUT DATA N-1 DATA N 0.5V FIGURE 1. INPUT TO OUTPUT TIMING Typical Performance Curves 9.5 60 59 fIN = 1MHz 9.0 fIN = 5MHz fIN = 1MHz fIN = 5MHz fIN = 10MHz 8.0 fIN = 15MHz 47 7.5 SNR (dB) 53 8.5 SINAD (dB) ENOB (BITS) 55 50 fIN = 10MHz 45 fIN = 15MHz 7.0 TA = 25oC 6.5 10 20 TA = 25oC 30 40 50 60 40 10 41 80 70 20 SAMPLING FREQUENCY (MSPS) FIGURE 2. EFFECTIVE NUMBER OF BITS (ENOB) AND SINAD vs SAMPLING FREQUENCY 80 75 60 70 80 fIN = 1MHz fIN = 5MHz fIN = 5MHz 70 SFDR (dBc) 70 -THD (dBc) 50 75 fIN = 1MHz 65 fIN = 10MHz 55 20 30 40 50 60 fIN = 10MHz 60 TA = 25oC 70 SAMPLING FREQUENCY (MSPS) FIGURE 4. -THD vs SAMPLING FREQUENCY FN4319 Rev 6.00 March 30, 2005 fIN = 15MHz 65 55 fIN = 15MHz TA = 25oC 50 10 40 FIGURE 3. SNR vs SAMPLING FREQUENCY 80 60 30 SAMPLING FREQUENCY (MSPS) 80 50 10 20 30 40 50 60 70 SAMPLING FREQUENCY (MSPS) FIGURE 5. SFDR vs SAMPLING FREQUENCY Page 8 of 15 80 HI5767 Typical Performance Curves (Continued) 9.5 9.1 20MSPS 9.0 9.0 8.0 60MSPS 7.5 20MSPS 8.9 40MSPS ENOB (BITS) ENOB (BITS) 8.5 7.0 8.8 TA = 25oC, fIN = 10MHz DIFFERENTIAL ANALOG INPUT 8.7 8.6 40MSPS 6.5 8.5 6.0 5.5 30 8.4 TA = 25oC, fIN = 10MHz 35 40 45 50 55 60 65 60MSPS 8.3 0.25 0.75 70 1.25 1.75 DUTY CYCLE (%, tH/tCLK) 3.25 3.75 4.25 4.75 FIGURE 7. EFFECTIVE NUMBER OF BITS (ENOB) vs ANALOG INPUT COMMON MODE VOLTAGE 80 9.2 20MSPS ICC 70 9.0 60 AICC 50 40 30 ENOB (BITS) SUPPLY CURRENT (mA) 2.75 VCM (V) FIGURE 6. EFFECTIVE NUMBER OF BITS (ENOB) vs SAMPLE CLOCK DUTY CYCLE TA = 25oC, 1MHz < fIN < 15MHz 0 10 8.8 40MSPS 8.6 8.4 DICC1 20 60MSPS fIN = 10MHz, VREFIN = VREFOUT DIFFERENTIAL ANALOG INPUT 8.2 10 DICC2 15 20 25 30 35 40 45 50 55 8.0 -40 60 -20 0 20 60 40 80 TEMPERATURE (oC) fS (MSPS) FIGURE 8. SUPPLY CURRENT vs SAMPLE CLOCK FREQUENCY FIGURE 9. EFFECTIVE NUMBER OF BITS (ENOB) vs TEMPERATURE 2.530 3.1 2.525 VREFOUT VDC (V) REFERENCE VOLTAGE, (VREFOUT) (V) 2.25 2.520 3.0 VDC 2.515 2.510 -40 -20 0 20 40 60 80 TEMPERATURE (oC) FIGURE 10. INTERNAL REFERENCE VOLTAGE (VREFOUT) vs TEMPERATURE FN4319 Rev 6.00 March 30, 2005 2.9 -40 -20 0 20 40 60 80 TEMPERATURE (oC) FIGURE 11. DC BIAS VOLTAGE (VDC) vs TEMPERATURE Page 9 of 15 HI5767 Typical Performance Curves (Continued) 6.5 80 ICC SUPPLY CURRENT (mA) 70 6.0 tOD (ns) tOD 5.5 5.0 60 50 40 30 -20 0 20 60 40 80 60MSPS, fIN = 10MHz, AVCC = DVCC1 = 5V DVCC2 = 3V DICC1 20 10 4.5 -40 AICC DICC2 0 -40 -20 0 TEMPERATURE (oC) 20 60 40 TEMPERATURE (oC) FIGURE 12. DATA OUTPUT DELAY (tOD) vs TEMPERATURE FIGURE 13. SUPPLY CURRENT vs TEMPERATURE 0 -10 OUTPUT LEVEL (dB) -20 -30 1 TA = 25oC, fS = 60MSPS, fIN = 10MHz -40 VIN+ -50 -70 VIN- -80 -90 0 100 200 300 400 500 600 700 800 900 1 1 CS 2 -60 -100 1 CH -+ VOUT+ +- VOUT- CS 1 CH 1 1023 FREQUENCY (BIN) FIGURE 14. 2048 POINT FFT PLOT FN4319 Rev 6.00 March 30, 2005 FIGURE 15. ANALOG INPUT SAMPLE-AND-HOLD Page 10 of 15 80 HI5767 TABLE 1. A/D CODE TABLE OFFSET BINARY OUTPUT CODE (DFS LOW) CODE CENTER DESCRIPTION +Full Scale (+FS) 1/ LSB 4 D9 D8 D7 D6 D5 D4 D3 D2 0.499756V 1 1 1 1 1 1 1 1 L S B L S B M S B D1 D0 D9 D8 D7 D6 D5 D4 D3 D2 D1 D0 1 1 0 1 1 1 1 1 1 1 1 1 M S B DIFFERENTIAL INPUT VOLTAGE (VIN+ - VIN-) TWO’S COMPLEMENT OUTPUT CODE (DFS HIGH) +FS - 11/4 LSB 0.498779V 1 1 1 1 1 1 1 1 1 0 0 1 1 1 1 1 1 1 1 0 +3/4 LSB 732.422V 1 0 0 0 0 0 0 0 0 0 0 0 0 0 0 0 0 0 0 0 -1/4 LSB -244.141V 0 1 1 1 1 1 1 1 1 1 1 1 1 1 1 1 1 1 1 1 -FS + 13/4 LSB -0.498291V 0 0 0 0 0 0 0 0 0 1 1 0 0 0 0 0 0 0 0 1 -Full Scale (-FS) + 3/ LSB 4 -0.499268V 0 0 0 0 0 0 0 0 0 0 1 0 0 0 0 0 0 0 0 0 NOTE: 4. The voltages listed above represent the ideal center of each output code shown with VREFIN = +2.5V. Detailed Description Theory of Operation The HI5767 is a 10-bit fully differential sampling pipeline A/D converter with digital error correction logic. Figure 16 depicts the circuit for the front end differential-in-differential-out sample-andhold (S/H). The switches are controlled by an internal sampling clock which is a non-overlapping two phase signal1 and 2 , derived from the master sampling clock. During the sampling phase, 1 , the input signal is applied to the sampling capacitors, CS . At the same time the holding capacitors, CH , are discharged to analog ground. At the falling edge of 1 the input signal is sampled on the bottom plates of the sampling capacitors. In the next clock phase,2 , the two bottom plates of the sampling capacitors are connected together and the holding capacitors are switched to the op-amp output nodes. The charge then redistributes between CS and CH completing one sample-andhold cycle. The front end sample-and-hold output is a fullydifferential, sampled-data representation of the analog input. The circuit not only performs the sample-and-hold function but will also convert a single-ended input to a fully-differential output for the converter core. During the sampling phase, the VIN pins see only the on-resistance of a switch and CS . The relatively small values of these components result in a typical full power input bandwidth of 250MHz for the converter. As illustrated in the functional block diagram and the timing diagram in Figure 1, eight identical pipeline subconverter stages, each containing a two-bit flash converter and a two-bit multiplying digital-to-analog converter, follow the S/H circuit with the ninth stage being a two bit flash converter. Each converter stage in the pipeline will be sampling in one phase and amplifying in the other clock phase. Each individual subconverter clock signal is offset by 180 degrees from the previous stage clock signal resulting in alternate stages in the pipeline performing the same operation. FN4319 Rev 6.00 March 30, 2005 The output of each of the eight identical two-bit subconverter stages is a two-bit digital word containing a supplementary bit to be used by the digital error correction logic. The output of each subconverter stage is input to a digital delay line which is controlled by the internal sampling clock. The function of the digital delay line is to time align the digital outputs of the eight identical two-bit subconverter stages with the corresponding output of the ninth stage flash converter before applying the eighteen bit result to the digital error correction logic. The digital error correction logic uses the supplementary bits to correct any error that may exist before generating the final ten bit digital data output of the converter. Because of the pipeline nature of this converter, the digital data representing an analog input sample is output to the digital data bus on the 7th cycle of the clock after the analog sample is taken. This time delay is specified as the data latency. After the data latency time, the digital data representing each succeeding analog sample is output during the following clock cycle. The digital output data is synchronized to the external sampling clock by a double buffered latching technique. The digital output data is available in two’s complement or offset binary format depending on the state of the Data Format Select (DFS) control input (see Table 1, A/D Code Table). Internal Reference Voltage Output, VREFOUT The HI5767 is equipped with an internal reference voltage generator, therefore, no external reference voltage is required. VREFOUT must be connected to VREFIN when using the internal reference voltage. An internal band-gap reference voltage followed by an amplifier/buffer generates the precision +2.5V reference voltage used by the converter. A 4:1 array of substrate PNPs generates the “delta-VBE” and a two-stage op-amp closes the loop to create an internal +1.25V band-gap reference voltage. This voltage is then amplified by a wideband uncompensated operational amplifier connected in a gain-of-two Page 11 of 15 HI5767 configuration. An external, user-supplied, 0.1F capacitor connected from the VREFOUT output pin to analog ground is used to set the dominant pole and to maintain the stability of the operational amplifier. Reference Voltage Input, VREFIN The HI5767 is designed to accept a +2.5V reference voltage source at the VREFIN input pin. Typical operation of the converter requires VREFIN to be set at +2.5V. The HI5767 is tested with VREFIN connected to VREFOUT yielding a fully differential analog input voltage range of 0.5V. The user does have the option of supplying an external +2.5V reference voltage. As a result of the high input impedance presented at the VREFIN input pin, 2.5k typically, the external reference voltage being used is only required to source 1mA of reference input current. In the situation where an external reference voltage will be used an external 0.1F capacitor must be connected from the VREFOUT output pin to analog ground in order to maintain the stability of the internal operational amplifier. In order to minimize overall converter noise it is recommended that adequate high frequency decoupling be provided at the reference voltage input pin, VREFIN . Analog Input, Differential Connection The analog input to the HI5767 is a differential input that can be configured in various ways depending on the signal source and the required level of performance. A fully differential connection (Figure 17 and Figure 18) will deliver the best performance from the converter. VIN+ VIN R The analog input can be DC coupled (Figure 18) as long as the inputs are within the analog input common mode voltage range (0.25V  VDC  4.75V). VIN VIN+ VDC R C HI5767 VDC R -VIN VDC VIN- FIGURE 17. DC COUPLED DIFFERENTIAL INPUT The resistors, R, in Figure 18 are not absolutely necessary but may be used as load setting resistors. A capacitor, C, connected from VIN+ to VIN- will help filter any high frequency noise on the inputs, also improving performance. Values around 20pF are sufficient and can be used on AC coupled inputs as well. Note, however, that the value of capacitor C chosen must take into account the highest frequency component of the analog input signal. Analog Input, Single-Ended Connection The configuration shown in Figure 19 may be used with a single ended AC coupled input. HI5767 VDC R -VIN VIN and -VIN input signals are 0.5VP-P , with -VIN being 180 degrees out of phase with VIN . The converter will be at positive full scale when the VIN+ input is at VDC + 0.25V and the VIN- input is at VDC - 0.25V (VIN+ - VIN- = +0.5V). Conversely, the converter will be at negative full scale when the VIN+ input is equal to VDC - 0.25V and VIN- is at VDC + 0.25V (VIN+ - VIN= -0.5V). VIN+ VIN R VDC VIN- HI5767 VIN- FIGURE 16. AC COUPLED DIFFERENTIAL INPUT Since the HI5767 is powered by a single +5V analog supply, the analog input is limited to be between ground and +5V. For the differential input connection this implies the analog input common mode voltage can range from 0.25V to 4.75V. The performance of the ADC does not change significantly with the value of the analog input common mode voltage. A DC voltage source, VDC , equal to 3.2V (typical), is made available to the user to help simplify circuit design when using an AC coupled differential input. This low output impedance voltage source is not designed to be a reference but makes an excellent DC bias source and stays well within the analog input common mode voltage range over temperature. For the AC coupled differential input (Figure 17) and with VREFIN connected to VREFOUT , full scale is achieved when the FN4319 Rev 6.00 March 30, 2005 FIGURE 18. AC COUPLED SINGLE ENDED INPUT Again, with VREFIN connected to VREFOUT, if VIN is a 1VP-P sinewave, then VIN+ is a 1.0VP-P sinewave riding on a positive voltage equal to VDC. The converter will be at positive full scale when VIN+ is at VDC + 0.5V (VIN+ - VIN- = +0.5V) and will be at negative full scale when VIN+ is equal to VDC - 0.5V (VIN+ - VIN- = -0.5V). Sufficient headroom must be provided such that the input voltage never goes above +5V or below AGND. In this case, VDC could range between 0.5V and 4.5V without a significant change in ADC performance. The simplest way to produce VDC is to use the DC bias source, VDC, output of the HI5767. The single ended analog input can be DC coupled (Figure 20) as long as the input is within the analog input common mode voltage range. Page 12 of 15 HI5767 VIN VIN+ VDC R HI5767 C VDC VIN- FIGURE 19. DC COUPLED SINGLE ENDED INPUT The resistor, R, in Figure 20 is not absolutely necessary but may be used as a load setting resistor. A capacitor, C, connected from VIN+ to VIN- will help filter any high frequency noise on the inputs, also improving performance. Values around 20pF are sufficient and can be used on AC coupled inputs as well. Note, however, that the value of capacitor C chosen must take into account the highest frequency component of the analog input signal. A single ended source may give better overall system performance if it is first converted to differential before driving the HI5767. Digital Output Control and Clock Requirements The HI5767 provides a standard high-speed interface to external TTL logic families. The part should be mounted on a board that provides separate low impedance connections for the analog and digital supplies and grounds. For best performance, the supplies to the HI5767 should be driven by clean, linear regulated supplies. The board should also have good high frequency decoupling capacitors mounted as close as possible to the converter. If the part is powered off a single supply, then the analog supply should be isolated with a ferrite bead from the digital supply. Refer to the application note “Using Intersil High Speed A/D Converters” (AN9214) for additional considerations when using high speed converters. Static Performance Definitions Offset Error (VOS) The midscale code transition should occur at a level 1/4 LSB above half-scale. Offset is defined as the deviation of the actual code transition from this point. Full-Scale Error (FSE) The last code transition should occur for an analog input that is 3/ LSB below Positive Full Scale (+FS) with the offset error 4 removed. Full scale error is defined as the deviation of the actual code transition from this point. Differential Linearity Error (DNL) In order to ensure rated performance of the HI5767, the duty cycle of the clock should be held at 50% 5%. It must also have low jitter and operate at standard TTL levels. DNL is the worst case deviation of a code width from the ideal value of 1 LSB. Performance of the HI5767 will only be guaranteed at conversion rates above 1 MSPS. This ensures proper performance of the internal dynamic circuits. Similarly, when power is first applied to the converter, a maximum of 20 cycles at a sample rate above 1 MSPS will have to be performed before valid data is available.A Data Format Select (DFS) pin is provided which will determine the format of the digital data outputs. When at logic low, the data will be output in offset binary format. When at logic high, the data will be output in two’s complement format. Refer to Table 1 for further information. INL is the worst case deviation of a code center from a best fit straight line calculated from the measured data. The output enable pin, OE, when pulled high will three-state the digital outputs to a high impedance state. Set the OE input to logic low for normal operation. OE INPUT DIGITAL DATA OUTPUTS 0 Active 1 High Impedance Supply and Ground Considerations The HI5767 has separate analog and digital supply and ground pins to keep digital noise out of the analog signal path. The digital data outputs also have a separate supply pin, DVCC2 , which can be powered from a 3.0V or 5.0V supply. This allows the outputs to interface with 3.0V logic if so desired. FN4319 Rev 6.00 March 30, 2005 Integral Linearity Error (INL) Power Supply Sensitivity Each of the power supplies are moved plus and minus 5% and the shift in the offset and full scale error (in LSBs) is noted. Dynamic Performance Definitions Fast Fourier Transform (FFT) techniques are used to evaluate the dynamic performance of the HI5767. A low distortion sine wave is applied to the input, it is coherently sampled, and the output is stored in RAM. The data is then transformed into the frequency domain with an FFT and analyzed to evaluate the dynamic performance of the A/D. The sine wave input to the part is typically -0.5dB down from full scale for all these tests. SNR and SINAD are quoted in dB. The distortion numbers are quoted in dBc (decibels with respect to carrier) and DO NOT include any correction factors for normalizing to full scale. The Effective Number of Bits (ENOB) is calculated from the SINAD data by: ENOB = (SINAD - 1.76 + VCORR) / 6.02, where: VCORR = 0.5 dB (Typical). VCORR adjusts the SINAD, and hence the ENOB, for the amount the analog input signal is backed off from full scale. Page 13 of 15 HI5767 Signal To Noise and Distortion Ratio (SINAD) Intermodulation Distortion (IMD) SINAD is the ratio of the measured RMS signal to RMS sum of all the other spectral components below the Nyquist frequency, fS/2, excluding DC. Nonlinearities in the signal path will tend to generate intermodulation products when two tones, f1 and f2 , are present at the inputs. The ratio of the measured signal to the distortion terms is calculated. The terms included in the calculation are (f1+f2), (f1-f2), (2f1), (2f2), (2f1+f2), (2f1-f2), (f1+2f2), (f1-2f2). The ADC is tested with each tone 6dB below full scale. Signal To Noise Ratio (SNR) SNR is the ratio of the measured RMS signal to RMS noise at a specified input and sampling frequency. The noise is the RMS sum of all of the spectral components below fS /2 excluding the fundamental, the first five harmonics and DC. Transient Response THD is the ratio of the RMS sum of the first 5 harmonic components to the RMS value of the fundamental input signal. Transient response is measured by providing a full-scale transition to the analog input of the ADC and measuring the number of cycles it takes for the output code to settle within 10bit accuracy. 2nd and 3rd Harmonic Distortion Over-Voltage Recovery This is the ratio of the RMS value of the applicable harmonic component to the RMS value of the fundamental input signal. Over-Voltage Recovery is measured by providing a full-scale transition to the analog input of the ADC which overdrives the input by 200mV, and measuring the number of cycles it takes for the output code to settle within 10-bit accuracy. Total Harmonic Distortion (THD) Spurious Free Dynamic Range (SFDR) SFDR is the ratio of the fundamental RMS amplitude to the RMS amplitude of the next largest spectral component in the spectrum below fS /2. FN4319 Rev 6.00 March 30, 2005 Full Power Input Bandwidth (FPBW) Full power input bandwidth is the analog input frequency at which the amplitude of the digitally reconstructed output has decreased 3dB below the amplitude of the input sine wave. The input sine wave has an amplitude which swings from -FS to +FS. The bandwidth given is measured at the specified sampling frequency. Page 14 of 15 HI5767 Video Definitions Data Hold Time (tH) Differential Gain and Differential Phase are two commonly found video specifications for characterizing the distortion of a chrominance signal as it is offset through the input voltage range of an ADC. Data hold time is the time to where the previous data (N - 1) is no longer valid. Data Output Delay Time (tOD) Differential Gain (DG) Data output delay time is the time to where the new data (N) is valid. Differential Gain is the peak difference in chrominance amplitude (in percent) relative to the reference burst. Data Latency (tLAT) Differential Phase (DP) Differential Phase is the peak difference in chrominance phase (in degrees) relative to the reference burst. Timing Definitions Refer to Figure 1 and Figure 2 for these definitions. Aperture Delay (tAP) Aperture delay is the time delay between the external sample command (the falling edge of the clock) and the time at which the signal is actually sampled. This delay is due to internal clock path propagation delays. Aperture Jitter (tAJ) Aperture jitter is the RMS variation in the aperture delay due to variation of internal clock path delays. After the analog sample is taken, the digital data representing an analog input sample is output to the digital data bus on the 7th cycle of the clock after the analog sample is taken. This is due to the pipeline nature of the converter where the analog sample has to ripple through the internal subconverter stages. This delay is specified as the data latency. After the data latency time, the digital data representing each succeeding analog sample is output during the following clock cycle. The digital data lags the analog input sample by 7 sample clock cycles. Power-Up Initialization This time is defined as the maximum number of clock cycles that are required to initialize the converter at power-up. The requirement arises from the need to initialize the dynamic circuits within the converter. © Copyright Intersil Americas LLC 2003-2005. All Rights Reserved. All trademarks and registered trademarks are the property of their respective owners. For additional products, see www.intersil.com/en/products.html Intersil products are manufactured, assembled and tested utilizing ISO9001 quality systems as noted in the quality certifications found at www.intersil.com/en/support/qualandreliability.html Intersil products are sold by description only. Intersil may modify the circuit design and/or specifications of products at any time without notice, provided that such modification does not, in Intersil's sole judgment, affect the form, fit or function of the product. Accordingly, the reader is cautioned to verify that datasheets are current before placing orders. Information furnished by Intersil is believed to be accurate and reliable. However, no responsibility is assumed by Intersil or its subsidiaries for its use; nor for any infringements of patents or other rights of third parties which may result from its use. No license is granted by implication or otherwise under any patent or patent rights of Intersil or its subsidiaries. For information regarding Intersil Corporation and its products, see www.intersil.com FN4319 Rev 6.00 March 30, 2005 Page 15 of 15