LB1976

Ordering number : EN6088B Monolithic Digital IC LB1976 Overview For Fan Motor 3-phase Brushless Motor Driver The LB1976 is a 3-phase brushless motor driver IC suited for use in direct PWM driving of DC fan motors for air conditioners, water heaters, and other similar equipment. Since a shunt regulator circuit is built in, single power supply operation sharing the same power supply for the motor is supported. Features • Withstand voltage 60V, output current 2.5A • Direct PWM drive output • 3 built-in output top-side diodes • Built-in current limiter • Built-in FG output circuit Specifications Absolute Maximum Ratings at Ta = 25°C Parameter Supply voltage Symbol VCC max VM max Output current Maximum input current Allowable power dissipation IO max IREG max Pd max1 Pd max2 Operating temperature Storage temperature Topr Tstg VREG pin Independent IC With infinite hear sink Conditions Ratings 7 60 2.5 10 3 20 -20 to +100 -55 to +150 Unit V V A mA W W °C °C Any and all SANYO Semiconductor Co.,Ltd. products described or contained herein are, with regard to "standard application", intended for the use as general electronics equipment (home appliances, AV equipment, communication device, office equipment, industrial equipment etc.). The products mentioned herein shall not be intended for use for any "special application" (medical equipment whose purpose is to sustain life, aerospace instrument, nuclear control device, burning appliances, transportation machine, traffic signal system, safety equipment etc.) that shall require extremely high level of reliability and can directly threaten human lives in case of failure or malfunction of the product or may cause harm to human bodies, nor shall they grant any guarantee thereof. If you should intend to use our products for applications outside the standard applications of our customer who is considering such use and/or outside the scope of our intended standard applications, please consult with us prior to the intended use. If there is no consultation or inquiry before the intended use, our customer shall be solely responsible for the use. Specifications of any and all SANYO Semiconductor Co.,Ltd. products described or contained herein stipulate the performance, characteristics, and functions of the described products in the independent state, and are not guarantees of the performance, characteristics, and functions of the described products as mounted in the customer' s products or equipment. To verify symptoms and states that cannot be evaluated in an independent device, the customer should always evaluate and test devices mounted in the customer' s products or equipment. D2408 MS / 21003AS (OT) / 52199RM (KI) No.6088-1/10 LB1976 Allowable Operating Ranges at Ta = 25°C Parameter Supply voltage range Symbol VCC VM Input current range FG pin applied voltage FG pin output current IREG VFG IFG VREG pin Conditions Ratings 4.5 to 6.7 20 to 56 1 to 5 0 to VCC 0 to 10 Unit V V mA V mA Electrical Characteristics at Ta = 25°C, VCC = 5V, VM = 45V Parameter Supply current Output Block Output saturation voltage VOsat1(L) VOsat1(H) VOsat1 VOsat2(L) VOsat2(H) VOsat2 Output leak current IOLeak(L) IOLeak(H) Upper side diode forward voltage VFH1 VFH2 Hall Amplifier Input bias current Common-mode input voltage range Hall input sensitivity Hysteresis width Input voltage (low to high) Input voltage (high to low) FG Pin (speed pulse output) Output low-level voltage Pull-up resistor value Current Limiter Limiter Thermal Shutdown Thermal shutdown operating temperature Hysteresis width Low-Voltage Protection Operating voltage Non-operating voltage Hysteresis width PWM Oscillator Output high-level voltage Output low-level voltage Amplitude Oscillator frequency Charge current Discharge resistance VREG Pin Pin voltage VREG IREG = 1.5mA 6.6 7.0 7.2 V VOH(OSC) VOL(OSC) VOSC fOSC ICHG RDCHG C = 2200pF 2.95 1.38 1.50 19.6 -110 1.6 3.10 1.45 1.65 23.0 -94 2.1 3.25 1.59 1.71 27.6 -83 2.6 V V Vp-p kHz µA kΩ VLVSD VLVSD(OFF) ∆VLVSD 0.4 3.5 3.8 4.3 0.5 4.1 4.5 0.6 V V V ∆TSD Design target Value (junction temperature) 40 °C TSD Design target Value (junction temperature) 150 180 °C VRF 0.45 0.50 0.55 V VFGL RFG IFG = 5mA 7.5 10 0.5 12.5 V kΩ IHB VICM VHIN ∆VIN(HA) VSLH VSHL -4 1.5 60 23 6 -25 32 16 -16 39 25 -6 -1 VCC-1.5 µA V mVp-p mV mV mV IO = 1.0A IO = 2.0A -100 1.2 2.1 1.6 2.6 IO = 1.0A, VO(sink) IO = 1.0A, VO(source) IO = 1.0A, VO(sink) + VO(source) IO = 2.0A, VO(sink) IO = 2.0A, VO(source) IO = 2.0A, VO(sink) + VO(source) 1.1 0.9 2.0 1.4 1.2 2.6 1.4 1.3 2.6 1.8 1.7 3.4 100 V V V V V V µA µA V V Symbol ICC Conditions min 10 Ratings typ 14 max 18 mA Unit Continued on next page. No.6088-2/10 LB1976 Continued from preceding page. Parameter VCTL Pin Input voltage VCTL1 VCTL2 Input bias current IB1(CTL) IB2(CTL) VCTL Amplifier Reference voltage Output voltage VCREF VCOUT1 VCOUT2 Start/Stop Pin High-level input voltage range Low-level input voltage range Input open voltage Hysteresis width High-level input current Low-level input current Forward/Reverse Pin High-level input voltage range Low-level input voltage range Input open voltage Hysteresis width High-level input current Low-level input current VIH(F/R) VIL(F/R) VIO(F/R) ∆VIN(F/R) IIH(F/R) IIL(F/R) V(F/R) = VCC V(F/R) = 0V VCC-1.5 0 VCC-0.5 0.35 -10 -280 0.50 0 -210 VCC 1.5 VCC 0.65 +10 V V V V µA µA VIH(S/S) VIL(S/S) VIO(S/S) ∆VIN(S/S) IIH(S/S) IIL(S/S) V(S/S) = VCC V(S/S) = 0V VCC-1.5 0 VCC-0.5 0.35 -10 -280 0.50 0 -210 VCC 1.5 VCC 0.65 +10 V V V V µA µA VCTL = 0V VCTL = 5V 2.23 3.90 0.60 2.35 4.20 0.80 2.46 4.40 1.10 V V V Output duty 0% Output duty 100% VCTL = 0V VCTL = 5V 1.1 3.2 -82 92 1.4 3.5 1.7 3.8 V V µA µA Symbol Conditions min Ratings typ max Unit Package Dimensions unit : mm (typ) 3147C 24 Pd max -- Ta With infinite heat sink 28 15 Allowable power dissipation, Pd max -- W 20 12.7 11.2 8.4 R1.7 16 0.4 12 1 20.0 26.75 14 8 4 3 4.0 4.0 Independent IC 0 -20 0 20 40 60 80 100 120 (1.81) 1.78 0.6 1.0 Ambient temperature, Ta -- °C SANYO : DIP28H(500mil) No.6088-3/10 LB1976 Pin Assignment VCOUT VCTL OSC 28 27 26 (NC) VCREF IN1− 25 24 23 IN1+ 22 IN2− IN2+ 21 20 IN3− 19 IN3+ 18 FG1 17 FG2 GND1 16 15 LB1976 1 2 3 S/S 5 F/R 5 6 7 8 9 10 11 12 13 RF 14 VM Top view VCC VREG (NC) OUT1 OUT2 OUT3 (NC) (NC) GND3 GND2 Truth Table Input IN1 1 H IN2 L IN3 H Forward/reverse control F/R L H 2 H L L L H 3 H H L L H 4 L H L L H 5 L H H L H 6 L L H L H Output Source → Sink OUT2 → OUT1 OUT1 → OUT2 OUT3 → OUT1 OUT1 → OUT3 OUT3 → OUT2 OUT2 → OUT3 OUT1 → OUT2 OUT2 → OUT1 OUT1 → OUT3 OUT3 → OUT1 OUT2 → OUT3 OUT3 → OUT2 FG1 L FG output FG2 L L H L L H H H L H H F/R Forward rotation Low Reverse rotation High 0V to 1.5V VCC − 1.5V to VCC FG output FG1 FG2 100 Duty -- VCTL characteristics 80 Duty -- % 60 40 20 0 VCTL1 Control voltage, VCTL -- V VCTL2 No.6088-4/10 LB1976 Block Diagram and Peripheral Circuit VREG VCC S/S F/R FG1 FG2 VCC Reg LVDS TSD Hys.Amp VM H VM IN1 OUT1 H IN2 Logic OUT2 OUT3 H IN3 RF 31kΩ VCTL 40kΩ VCTL Amp Current Limiter PWM OSC 0.5V VCTL VCREF 2.35V VCOUT OSC GND1 GND2 GND3 Pin Functions Pin No. 1 Pin name VCC VREG Pin voltage 4.5V to 6.7V Function Power supply for blocks other than the output block. 2 0.0V to 7.3V Shunt regulator output pin (7V). Equivalent circuit 2 3 S/S 0.0V to VCC Start/stop control pin. Low: start High or Open: stop VCC 20kΩ Typical threshold voltage for VCC = 5V: approx. 2.8V (low to high) approx. 2.3V (high to low) 3.8kΩ 3 Continued on next page. No.6088-5/10 LB1976 Continued from preceding page. Pin No. 4 Pin name F/R Pin voltage 0.0V to VCC Low: forward High or Open: reverse 20kΩ Function Forward/reverse pin. VCC Equivalent circuit Typical threshold voltage for VCC = 5V: approx. 2.8V (low to high) approx. 2.3V (high to low) 3.8kΩ 4 6 7 8 13 OUT1 OUT2 OUT3 RF 0.0V to VCC Output pin 1. Output pin 2. Output pin 3. Output current detect pin. Connect resistor Rf between this pin and ground. Output current is limited to value set with VRF/Rf. (Current limiter operation) VCC 14 6 7 8 0.5V 200Ω 14 11 15 12 17 VM GND3 GND1 GND2 FG1 0.0V to VCC 13 Output block power supply. Output block ground. Ground for blocks other than the output block. Speed pulse output pin 1 with built-in pull-up resistor. 10kΩ VCC 16 17 16 FG2 0.0V to VCC Speed pulse output pin 2 with built-in pull-up resistor. 22 23 20 21 18 19 IN1+ IN1IN2+ IN2IN3+ IN3- 1.5V to VCC − 1.5V Hall input pin. IN+ > IN- : High input IN+ < IN- : Low input VCC 18 20 22 300Ω 300Ω 19 21 23 26 OSC 1.0V to VCC This pin sets the PWM oscillation frequency. Connect a capacitor between this pin and ground. VCC 2V 94µA 200Ω 2.1kΩ 26 Continued on next page. No.6088-6/10 LB1976 Continued from preceding page. Pin No. 27 Pin name VCTL Pin voltage 0.0V to 6.7V • VCTL ≤ VCTL1 Duty cycle 0% • VCTL1 < VCTL < VCTL2 Duty cycle is controlled by VCTL • VCTL ≥ VCTL2 Duty cycle 100% 2.35V 40kΩ Function Output duty cycle control pin. Equivalent circuit 31kΩ VCC 27 24 VCREF 0.0V to VCC − 2.0V VCTL amplifier internal reference voltage pin (2.35V). VCC 100µA 24 200Ω 23.5kΩ 28 VCOUT 0.7V to VCC − 0.7V VCTL amplifier output pin. VCC 28 31kΩ 200Ω No.6088-7/10 LB1976 IC Description 1. Direct PWM Drive The LB1976 employs the direct PWM drive principle. Motor rotation speed is controlled by varying the output duty cycle according to an analog voltage input (VCTL). This eliminates the need to alter the motor power supply voltage. Compared to previous ICs using the PAM principle (such as the Sanyo LB1690), this allows simplification of the power supply circuitry. The VCTL input can be directly supplied by a microcontroller, motor speed can, therefore, be controlled directly from the microcontroller. For PWM, the source-side output transistors are switched on and off so that the ON duty tracks the VCTL input. The output duty cycle can be controlled over the range of 0% to 100% by the VCTL input. 2. PWM Frequency The PWM oscillator frequency fPWM [Hz] is set by the capacitance C [pF] connected between the OSC pin and GND. The following equation applies: fPWM ≈ 1 / (1.97 × C) × 108 Because output transistor on/off switching is subject to a delay, setting the PWM frequency to a very high value will cause the delay to become noticeable. The PWM frequency therefore should normally be kept below 40kHz (typ.), which is achieved with a capacitance C of 1300pF or higher. For reference, the source-side output transistor switching delay time is about 2µs for ON and about 4µs for OFF. 3. Output Diodes Because the PWM switching operation is carried out by the source-side output transistors, Schottky barrier diodes must be connected between the OUT pins and GND (OUT1 to OUT3). Use diodes with an average forward current rating in the range of 1.0 to 2.0A, in accordance with the motor type and current limiting requirements. If no Schottky barrier diodes are connected externally, or if Schottky barrier diodes with high forward voltage (VF) are used, the internal parasitic diode between OUT and GND becomes active. When this happens, the output logic circuit may malfunction, resulting in feed-through current in the output which can destroy the output transistors. To prevent this possibility, Schottky barrier diodes must be used and dimensioned properly. The larger the VF of the externally connected Schottky barrier diodes, or the hotter the IC is, the more likely are the parasitic diodes between OUT and GND to become active and the more likely is malfunction to occur. The VF of the Schottky barrier diodes must be determined so that output malfunction does not occur also when the IC becomes hot. If malfunction occurs, choose a Schottky barrier diode with lower VF. 4. Protection circuits 4-1. Low voltage protection circuit When the VCC voltage falls below a stipulated level (VLVSD), the low voltage protection circuit cuts off the source-side output transistors to prevent VCC related malfunction. 4-2. Thermal shutdown circuit (overheat protection circuit) When the junction temperature rises above a stipulated value (TSD), the thermal shutdown circuit cuts off the sourceside output transistors to prevent IC damage due to overheating. Design the application heat characteristics so that the protection circuit will not be triggered under normal circumstances. 4-3. Current limiter The current limiter cuts off the source-side output transistors when the output current reaches a preset value (limiter value). This interrupts the source current and thereby limits the output current peak value. By connecting the resistance Rf between the RF pin and ground, the output current can be detected as a voltage. When the RF pin voltage reaches 0.5V (typ.), the current limiter is activated. It performs on/off control of the source-side output transistors, thereby limiting the output current to the value determined by 0.5/Rf. 5. Hall Input Circuit The Hall input circuit is a differential amplifier with a hysteresis of 32mV (typ.). The operation DC level must be within the common-mode input voltage range (1.5V to VCC − 1.5V). To prevent noise and other adverse influences, the input level should be at least 3 times the hysteresis (120 to 16mVp-p). If noise at the Hall input is a problem, a noise-canceling capacitor (about 0.01µF) should be connected across the Hall input IN+ and IN− pins. 6. FG Output Circuit The Hall input signal at IN1, IN2, and IN3 is combined and subject to waveform shaping before being output. The signal at FG1 has the same frequency as the FG1 Hall input, and the signal at FG2 has a frequency that is three times higher. No.6088-8/10 LB1976 7. Start/Stop Control Circuit The start/stop control circuit turns the source-side output transistors OFF (motor stop) when a High signal is input at the S/S pin or when the pin is Open. When a Low signal is input at the S/S pin, the source-side output transistors are turned ON, and the normal operation state is established (motor start). 8. Forward/Reverse Switching The LB1976 is designed under the assumption that forward/reverse switching is not carried out while the motor is running. If switching is carried out while the motor is running, reverse torque braking occurs, leading to a high current flow. If the current limiter is triggered, the source-side output transistors are switched off, and the sink-side output transistors go into the short brake condition. However, because the current limiter of this IC cannot control the current flowing in the sink-side output transistors, these may be destroyed by the short brake current. Therefore F/R switching while the motor is running is permissible only if the output current (IO) is limited to a maximum of 2.5A using the motor coil resistance or other suitable means. F/R switching should be carried out only while a High signal is input to the S/S pin or the pin is Open (stop condition), or while the VCTL pin conforms to the following condition: VCTL≤ VCTL1 (duty cycle 0%). In any other condition, F/R switching will result in feed-through current. The F/R pin should therefore be fixed to Low (forward) or High or Open (reverse) during use. 9. VCC, VM Power Supplies When the power supply voltage (VCC, VM) rises very quickly when a power is first applied, a feed-through current may occur at the output. If the current remains below about 0.2A to 0.3A, it does not pose a problem, but such a possibility should still be prevented by slowing down the voltage rise at power-on. Especially if the F/R pin is set to High or Open (reverse), a quick rise in VCC is likely to cause feed-through current. This should be prevented by ensuring that ∆VCC / ∆t = 0.2V/µs or less. Feed-through current can also be prevented by first switching on VCC and then VM during power-on. The sequence at power-down should be as follows. Provide a stop input to the S/S pin or a duty ratio 0% input to the VCTL pin. When the motor has come to a full stop, switch off VM and then VCC. If power is switched off while the motor is still rotating or a current is flowing in the motor coil (including motor restraint or inertia rotation), a counter electromotive current or kickback current may flow on the VM side, depending on the motor type and power-off procedure. If this current cannot be absorbed by the VM power supply or a capacitor, VM voltage may rise and exceed the absolute maximum VM rating for the IC. Ensure that this does not happen through proper design of the VM power supply or through use of a capacitor. Because the LB1976 incorporates a shunt regulator, it can be used on a single power supply. In this case, supply VCC (6.3V typ.) to the VREG pin via an external NPN transistor and resistor. When not using the regulator, leave the VREG pin open. 10. Power Supply Stabilizing Capacitors If the VCC line fluctuates drastically, the low-voltage protection circuit may be activated by mistake, or other malfunctions may occur. The VCC line must therefore be stabilized by connecting a capacitor of at least several µF between VCC and GND. Because a large switching current flows in the VM line, wiring inductance and other factors can lead to VM voltage fluctuations. As the GND line also fluctuates, the VM line must be stabilized by connecting a capacitor of at least several µF between VM and GND, to prevent exceeding VM max or other problems. Especially when long wiring runs (VM, VCC, GND) are used, sufficient capacitance should be provided to ensure power supply stability. 11. VCREF Pin, VCOUT Pin These pins are always used in the Open condition. If chattering occurs in the PWM switching output, connect a capacitor (about 0.1µF) between VCREF and ground or between VCOUT and GND. 12. IC Heat Dissipation Fins A heat sink may be mounted to the heat dissipation fins of this IC, but it may not be connected to GND. The sink should be electrically open. No.6088-9/10 LB1976 13. Sample calculation for internal power dissipation (approximate) The calculation assumes the following parameters: VCC = 5V VM = 30V Source-side output transistor ON duty cycle 80% (PWM control) Output current IO = 1A (RF pin average current) (1) ICC power dissipation P1 P1 = VCC × ICC = 5V × 14mA = 0.07W (2) Output drive current power dissipation P2 P2 = VM × 11mA = 30V × 11mA = 0.33W (3) Source-side output transistor power dissipation P3 P3 = VO(source) × IO × Duty(on) = 0.9V × 1A × 0.8 = 0.72W (4) Sink-side output transistor power dissipation P4 P4 = VO(sink) × IO = 1.1V × 1A = 1.10W (5) Total internal power dissipation P P = P1 + P2 + P3 + P4 = 2.22W 14. IC temperature Rise Measurement Because the chip temperature of the IC cannot be measured directly, measurement according to one of the following procedures should always be carried out. 14-1. Thermocouple measurement A thermocouple element is mounted to the IC heat dissipation fin. This measurement method is easy to implement, but it will be subject to measurement errors if the temperature is not stable. 14-2. Measurement using internal diode characteristics of IC This is the recommended measurement method. It makes use of the parasitic diode incorporated in the IC between FG1 and GND. Set FG1 to High and measure the voltage VF of the parasitic diode to calculate the temperature. (Sanyo data: for IF = −1mA, VF temperature characteristics are about −2mV/°C) 15. NC Pins Because NC pins are electrically open, they may be used for wiring purpose etc. SANYO Semiconductor Co.,Ltd. assumes no responsibility for equipment failures that result from using products at values that exceed, even momentarily, rated values (such as maximum ratings, operating condition ranges, or other parameters) listed in products specifications of any and all SANYO Semiconductor Co.,Ltd. products described or contained herein. SANYO Semiconductor Co.,Ltd. strives to supply high-quality high-reliability products, however, any and all semiconductor products fail or malfunction with some probability. It is possible that these probabilistic failures or malfunction could give rise to accidents or events that could endanger human lives, trouble that could give rise to smoke or fire, or accidents that could cause damage to other property. When designing equipment, adopt safety measures so that these kinds of accidents or events cannot occur. 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Information (including circuit diagrams and circuit parameters) herein is for example only; it is not guaranteed for volume production. Upon using the technical information or products described herein, neither warranty nor license shall be granted with regard to intellectual property rights or any other rights of SANYO Semiconductor Co.,Ltd. or any third party. SANYO Semiconductor Co.,Ltd. shall not be liable for any claim or suits with regard to a third party's intellctual property rights which has resulted from the use of the technical information and products mentioned above. This catalog provides information as of December, 2008. Specifications and information herein are subject to change without notice. PS No.6088-10/10