TS1005IG5T

TS1005 A 0.8V TO 5.5V, 1.3µA, 20kHz RAIL-TO-RAIL SINGLE OP AMP DESCRIPTION FEATURES Single 0.8V to 5.5V Operation Supply current: 1.3μA (typ) Input Bias Current: 2pA (typ) Low TCVOS: 9µV/°C (typ) AVOL Driving 100kΩ Load: 90dB (min) Gain-Bandwidth Product: 20kHz Unity Gain Stable Rail-to-rail Input and Output No Output Phase Reversal 5-pin SC70 or 5-Pin SOT23 Package APPLICATIONS Battery/Solar-Powered Instrumentation Portable Gas Monitors Low-voltage Signal Processing Micropower Active Filters Wireless Remote Sensors Battery-powered Industrial Sensors Active RFID Readers Powerline or Battery Current Sensing Handheld/Portable POS Terminals The TS1005 is a 1.3µA supply current, precision CMOS operational amplifier designed to operate over a supply voltage range from 0.8V to 5.5V with a GBWP of 20kHz. Fully specified at 1.8V, the TS1005 is optimized for ultra-long-life battery-powered applications. The TS1005 is the fifth operational amplifier in the “NanoWatt Analog™” highperformance analog integrated circuits portfolio. The TS1005 exhibits a typical input bias current of 2pA, and has rail-to-rail input and output stages. The TS1005’s combined features make it an excellent choice in applications where very low supply current and low operating supply voltage translate into very long equipment operating time. Applications include: micropower active filters, wireless remote sensors, battery and powerline current sensors, portable gas monitors, and handheld/portable POS terminals. The TS1005 is fully specified over the industrial temperature range (−40°C to +85°C) and is available in a PCB-space saving 5-lead SC70 and SOT23 packaging. TYPICAL APPLICATION CIRCUIT Supply Current Distribution A MicroWatt 2-Pole Sallen Key Low Pass Filter 30% VDD = 1.8V Percent of Units - % 25% 20% 15% 10% 5% 0% 1.15 1.2 1.25 1.3 1.35 Supply Current - µA TS1005 Rev. 1.0 Page 1 TS1005 ABSOLUTE MAXIMUM RATINGS Total Supply Voltage (VDD to VSS) .............................. +6.0V Voltage Inputs (IN+, IN-) ........... (VSS - 0.3V) to (VDD + 0.3V) Differential Input Voltage ............................................ ±6.0 V Input Current (IN+, IN-) .............................................. 20 mA Output Short-Circuit Duration to GND .................... Indefinite Continuous Power Dissipation (TA = +70°C) 5-Pin SC70 (Derate 3.87mW/°C above +70°C) .... 310 mW 5-Pin SOT23(Derate 3.87mW/°C above +70°C) ... 312 mW Operating Temperature Range .................... -40°C to +85°C Junction Temperature .............................................. +150°C Storage Temperature Range ..................... -65°C to +150°C Lead Temperature (soldering, 10s) ............................. +300° Electrical and thermal stresses beyond those listed under “Absolute Maximum Ratings” may cause permanent damage to the device. These are stress ratings only and functional operation of the device at these or any other condition beyond those indicated in the operational sections of the specifications is not implied. Exposure to any absolute maximum rating conditions for extended periods may affect device reliability and lifetime. PACKAGE/ORDERING INFORMATION TAPE & REEL ORDER NUMBER PART PACKAGE MARKING QUANTITY TS1005IJ5 --- TAPE & REEL ORDER NUMBER PART PACKAGE MARKING QUANTITY TS1005IG5 TAJ TS1005IJ5T --TAEB 3000 TS1005IG5T 3000 Lead-free Program: Silicon Labs supplies only lead-free packaging. Consult Silicon Labs for products specified with wider operating temperature ranges. Page 2 TS1005 Rev. 1.0 TS1005 ELECTRICAL CHARACTERISTICS VDD = +1.8V, VSS = 0V, VINCM = VSS; RL = 100kΩ to (VDD-VSS)/2; TA = -40°C to +85°C, unless otherwise noted. Typical values are at TA = +25°C. See Note 1 Parameters Supply Voltage Range Symbol VDD-VSS Conditions Supply Current ISY RL = Open circuit Input Offset Voltage VOS VIN = VSS or VDD Input Offset Voltage Drift Input Bias Current IIN+, IINIOS Input Voltage Range IVR Common-Mode Rejection Ratio CMRR Power Supply Rejection Ratio PSRR Output Voltage Low VOH VOL ISC+ Short-circuit Current ISCOpen-loop Voltage Gain AVOL Gain-Bandwidth Product GBWP Phase Margin Slew Rate Full-power Bandwidth Input Voltage Noise Density Input Current Noise Density φM SR FPBW en in TA = 25°C VIN+, VIN- = (VDD - VSS)/2 -40°C ≤ TA ≤ 85°C TA = 25°C Specified as IIN+ - IINVIN+, VIN- = (VDD - VSS)/2 -40°C ≤ TA ≤ 85°C Guaranteed by Input Offset Voltage Test TA = 25°C Vdd = 5.5V, 0V ≤ VIN(CM) ≤ 5.0V -40°C ≤ TA ≤ 85°C TA = 25°C 0.8V ≤ (VDD - VSS) ≤ 5.5V -40°C ≤ TA ≤ 85°C TA = 25°C Specified as VDD - VOUT, RL = 100kΩ to VSS -40°C ≤ TA ≤ 85°C TA = 25°C Specified as VDD - VOUT, RL = 10kΩ to VSS -40°C ≤ TA ≤ 85°C TA = 25°C Specified as VOUT - VSS, RL = 100kΩ to VDD -40°C ≤ TA ≤ 85°C TA = 25°C Specified as VOUT - VSS, RL = 10kΩ to VDD -40°C ≤ TA ≤ 85°C TA = 25°C VOUT = VSS -40°C ≤ TA ≤ 85°C TA = 25°C VOUT = VDD -40°C ≤ TA ≤ 85°C TA = 25°C VSS+50mV ≤ VOUT ≤ VDD-50mV -40°C ≤ TA ≤ 85°C RL = 100kΩ to VSS, CL = 20pF Unity-gain Crossover, RL = 100kΩ to VSS, CL = 20pF RL = 100kΩ to VSS, AVCL = +1V/V FPBW = SR/(π • VOUT,PP); VOUT,PP = 0.7VPP f = 1kHz f = 1kHz Typ 1.3 TA = 25°C -40°C ≤ TA ≤ 85°C TA = 25°C -40°C ≤ TA ≤ 85°C 0.8 TCVOS Input Offset Current Output Voltage High Min 0.8 Max 5.5 1.6 1.8 3 5 Units V µA mV 9 2 µV/°C pA 100 2 VSS 70 68 70 67 pA 50 VDD V 90 dB 90 dB 3.7 6 mV 30 60 1.5 6 mV 15 30 4 2 mA 15 7 91 84 110 dB 20 kHz 70 degrees 7.5 3400 0.6 10 V/ms Hz µV/√Hz pA/√Hz Note 1: All specifications are 100% tested at TA = +25°C. Specification limits over temperature (TA = TMIN to TMAX) are guaranteed by device characterization, not production tested. TS1005 Rev. 1.0 Page 3 TS1005 TYPICAL PERFORMANCE CHARACTERISTICS Supply Current vs Input Common-Mode Voltage Supply Current vs Supply Voltage 1.5 1.5 +85°C SUPPLY CURENT - µA SUPPLY CURENT - µA TA = +25°C 1.4 +25°C 1.3 -40°C 1.2 1.1 1.6 2.4 3.1 3.9 4.7 1.2 1.1 0 5.5 0.6 1.2 1.8 SUPPLY VOLTAGE - Volt INPUT COMMON-MODE VOLTAGE - Volt Supply Current vs Input Common-Mode Voltage Input Offset Voltage vs Supply Voltage 2.5 1.5 INPUT OFFSET VOLTAGE - mV TA = +25°C SUPPLY CURENT - µA 1.3 1.0 0.8 1.4 1.3 1.2 1.1 1.0 VINCM = 0V 1.25 VINCM = VDD 0 1.25 TA = +25°C -2.5 0 1.1 2.2 3.3 4.4 5.5 0.8 1.6 2.4 3.1 3.9 4.7 5.5 INPUT COMMON-MODE VOLTAGE - Volt SUPPLY VOLTAGE - Volt Input Offset Voltage vs Input Common-Mode Voltage Input Offset Voltage vs Input Common-Mode Voltage 0.9 INPUT OFFSET VOLTAGE - mV 0.7 INPUT OFFSET VOLTAGE - mV 1.4 0.35 0 -0.35 VDD =1.8V TA = +25°C -0.7 0.45 0 -0.45 VDD = 5.5V TA = +25°C -0.9 0 0.6 1.2 1.8 INPUT COMMON-MODE VOLTAGE - Volt TS1005 Rev. 1.0 0 1.1 2.2 3.3 4.4 5.5 INPUT COMMON-MODE VOLTAGE - Volt Page 4 TS1005 TYPICAL PERFORMANCE CHARACTERISTICS Input Bias Current (IIN+, IIN-) vs Input Common-Mode Voltage Input Bias Current (IIN+, IIN-) vs Input Common-Mode Voltage 6 6 VDD = 5.5V INPUT BIAS CURRENT - pA INPUT BIAS CURRENT - pA VDD =1.8V 4 2 TA = +25°C 0 -2 TA = +85°C -4 2 TA = +25°C 0 -2 TA = +85°C -4 -6 -6 0.6 0 1.2 0 1.8 2.2 3.3 4.5 5.5 INPUT COMMON-MODE VOLTAGE - Volt Output Voltage High (VOH) vs Temperature, RLOAD =100kΩ Output Voltage Low (VOL) vs Temperature, RLOAD =100kΩ 11 RL = 100kΩ VDD = 5.5V 8 5 VDD = 1.8V 2 +25 -40 4.75 RL = 100kΩ VDD = 5.5V 3.75 2.75 1.75 VDD = 1.8V 0.75 +85 RL = 10kΩ VDD = 5.5V 80 50 VDD = 1.8V 20 TEMPERATURE - °C TS1005 Rev. 1.0 Output Voltage Low (VOL) vs Temperature, RLOAD =10kΩ OUTPUT SATURATION VOLTAGE - mV 110 +25 +85 TEMPERATURE - °C Output Voltage High (VOH) vs Temperature, RLOAD =10kΩ -40 +25 -40 TEMPERATURE - °C OUTPUT SATURATION VOLTAGE - mV 1.1 INPUT COMMON-MODE VOLTAGE - Volt OUTPUT SATURATION VOLTAGE - mV OUTPUT SATURATION VOLTAGE - mV 4 +85 50 RL = 10kΩ VDD = 5.5V 40 30 20 VDD = 1.8V 10 -40 +25 +85 TEMPERATURE - °C Page 5 TS1005 TYPICAL PERFORMANCE CHARACTERISTICS Output Short Circuit Current, ISC- vs Temperature OUTPUT SHORT-CIRCUIT CURRENT - mA OUTPUT SHORT-CIRCUIT CURRENT - mA Output Short Circuit Current, ISC+ vs Temperature 10 VOUT = 0V 8.5 VDD = 5.5V 7 5.5 VDD = 1.8V 4 -40 +25 +85 VOUT = VDD 23.5 VDD = 5.5V 19 VDD = 1.8V 14.5 10 -40 +85 +25 TEMPERATURE - °C TEMPERATURE - °C 0.1Hz to 10Hz Output Voltage Noise Gain and Phase vs. Frequency 60 100 50 70° 30 GAIN 20 65 10 0 20kHz VOUT(N) - 100µV/DIV 83 PHASE - Degrees PHASE 40 GAIN - dB 28 100µVPP 49 -10 10 100 1k 10k 100k 1 Second/DIV FREQUENCY - Hz Large-Signal Transient Response VDD = 5.5V, VSS = GND, RLOAD = 100kΩ, CLOAD = 15pF OUTPUT OUTPUT INPUT INPUT Small-Signal Transient Response VDD = 5.5V, VSS = GND, RLOAD = 100kΩ, CLOAD = 15pF 200µs/DIV Page 6 2ms/DIV TS1005 Rev. 1.0 TS1005 PIN FUNCTIONS Pin 1 Label OUT 2 VSS 3 4 +IN -IN 5 VDD Function Amplifier Output. Negative Supply or Analog GND. If applying a negative voltage to this pin, connect a 0.1µF capacitor from this pin to analog GND. Amplifier Non-inverting Input. Amplifier Inverting Input. Positive Supply Connection. Connect a 0.1µF bypass capacitor from this pin to analog GND. THEORY OF OPERATION The TS1005 is fully functional for an input signal from the negative supply (VSS or GND) to the positive supply (VDD). The input stage consists of two differential amplifiers, a p-channel CMOS stage and an n-channel CMOS stage that are active over different ranges of the input common mode voltage. The p-channel input pair is active for input common mode voltages, VINCM, between the negative supply to approximately 0.4V below the positive supply. As the common-mode input voltage moves closer towards VDD, an internal current mirror activates the n-channel input pair differential pair. The p-channel input pair becomes inactive for the balance of the input common mode voltage range up to the positive supply. Because both input stages have their own offset voltage (VOS) characteristic, the offset voltage of the TS1005 is a function of the applied input common-mode voltage, VINCM. The VOS has a crossover point at ~0.4V from VDD (Refer to the VOS vs. VCM curve in the Typical Operating Characteristics section). Caution should be taken in applications where the input signal amplitude is comparable to the TS1005’s VOS value and/or the design requires high accuracy. In these situations, it is necessary for the input signal to avoid the crossover point. In addition, amplifier parameters such as PSRR and CMRR which involve the input offset voltage will also be affected by changes in the input common-mode voltage across the differential pair transition region. The second stage is a folded-cascode transistor arrangement that converts the input stage differential signals into a single-ended output. A complementary drive generator supplies current to the output transistors that swing rail to rail. The TS1005 output stages voltage swings within 3.5mV from the rails at 1.8V supply when driving an output load of 100kΩ - which provides the maximum possible dynamic range at the output. This is particularly important when operating on low supply voltages. When driving a stiffer 10kΩ load, the TS1005 swings within 30mV of VDD and within 13mV of VSS (or GND). APPLICATIONS INFORMATION Portable Gas Detection Sensor Amplifier load resistor value or a range of load resistors from which to choose. Gas sensors are used in many different industrial and medical applications. Gas sensors generate a current that is proportional to the percentage of a particular gas concentration sensed in an air sample. This output current flows through a load resistor and the resultant voltage drop is amplified. Depending on the sensed gas and sensitivity of the sensor, the output current can be in the range of tens of microamperes to a few milliamperes. Gas sensor datasheets often specify a recommended There are two main applications for oxygen sensors – applications which sense oxygen when it is abundantly present (that is, in air or near an oxygen tank) and those which detect traces of oxygen in parts-per-million concentration. In medical applications, oxygen sensors are used when air quality or oxygen delivered to a patient needs to be monitored. In fresh air, the concentration of oxygen is 20.9% and air samples containing less than 18% oxygen are considered dangerous. In industrial TS1005 Rev. 1.0 Page 7 TS1005 applications, oxygen sensors are used to detect the absence of oxygen; for example, vacuum-packaging of food products is one example. The circuit in Figure 1 illustrates a typical implementation used to amplify the output of an oxygen detector. The TS1005 makes an excellent choice for this application as it only draws 1.3µA of supply current and operates on supply voltages often required. As shown in Figure 2, the simplest way to achieve this objective is to use an RC filter at the noninverting terminal of the TS1005. If additional attenuation is needed, a two-pole Sallen-Key filter can be used to provide the additional attenuation as shown in Figure 3. For best results, the filter’s cutoff frequency should be 8 to 10 times lower than the TS1005’s crossover frequency. Additional operational amplifier phase margin shift can be avoided if the amplifier bandwidth-to-signal bandwidth ratio is greater than 8. The design equations for the 2-pole Sallen-Key lowpass filter are given below with component values selected to set a 2kHz low-pass filter cutoff frequency: Figure 1: A Micropower, Precision Oxygen Gas Sensor Amplifier. down to 0.8V. With the components shown in the figure, the circuit consumes less than 1.4μA of supply current ensuring that small form-factor singleor button-cell batteries (exhibiting low mAh charge ratings) could last beyond the operating life of the oxygen sensor. The precision specifications of the TS1005, such as its low offset voltage, low TCVOS, low input bias current, high CMRR, and high PSRR are other factors which make the TS1005 an excellent choice for this application. Since oxygen sensors typically exhibit an operating life of one to two years, an oxygen sensor amplifier built around a TS1005 can operate from a conventionally-available single 1.5-V alkaline AA battery for over 145 years! At such low power consumption from a single cell, the oxygen sensor could be replaced over 75 times before the battery requires replacing! R1 = R2 = R = 1MΩ C1 = C2 = C = 80pF Q = Filter Peaking Factor = 1 f–3dB = 1/(2 x π x RC) = 2kHz R3 = R4/(2-1/Q); with Q = 1, R3 = R4. A Single +1.5 V Supply, Instrumentation Amplifier Two Op Amp The TS1005’s ultra-low supply current and ultra-low voltage operation make it ideal for battery-powered applications such as the instrumentation amplifier shown in Figure 4. Figure 4: A Two Op Amp Instrumentation Amplifier. MicroWatt, Buffered Single-pole Low-Pass Filters When receiving low-level signals, limiting the bandwidth of the incoming signals into the system is Figure 2: A Simple, Single-pole Active Low-Pass Filter. Page 8 The circuit utilizes the classic two op amp instrumentation amplifier topology with four resistors Figure 3: A Micropower 2-Pole Sallen-Key Low-Pass Filter. TS1005 Rev. 1.0 TS1005 to set the gain. The equation is simply that of a noninverting amplifier as shown in the figure. The two resistors labeled R1 should be closely matched to each other as well as both resistors labeled R2 to ensure acceptable common-mode rejection performance. Resistor networks ensure the closest matching as well as matched drifts for good temperature stability. Capacitor C1 is included to limit the bandwidth and, therefore, the noise in sensitive applications. The value of this capacitor should be adjusted depending on the desired closed-loop bandwidth of the instrumentation amplifier. The RC combination creates a pole at a frequency equal to 1/(2π×R1C1). If the AC-CMRR is critical, then a matched capacitor to C1 should be included across the second resistor labeled R1. Because the TS1005 accepts rail-to-rail inputs, the input common mode range includes both ground and the positive supply of 1.5V. Furthermore, the rail-to-rail output range ensures the widest signal range possible and maximizes the dynamic range of the system. Also, with its low supply current of 1.3μA, this circuit consumes a quiescent current of only ~2.7μA, yet it still exhibits a 2-kHz bandwidth at a circuit gain of 2. Driving Capacitive Loads While the TS1005’s internal gain-bandwidth product is 20kHz, it is capable of driving capacitive loads up to 50pF in voltage follower configurations without any additional components. In many applications, however, an operational amplifier is required to drive much larger capacitive loads. The amplifier’s output impedance and a large capacitive load create additional phase lag that further reduces the amplifier’s phase margin. If enough phase delay is introduced, the amplifier’s phase margin is reduced. The effect is quite evident when the transient response is observed as there will appear noticeable peaking/ringing in the output transient response. determined empirically was 1.8V. The oscilloscope capture shown in Figure 6 illustrates a typical transient response obtained with a CLOAD = 100pF and an RISO = 120kΩ. Note that as CLOAD is increased a smaller RISO is needed for optimal transient response. Figure 5: Using an External Resistor to Isolate a CLOAD from the TS1005’s Output External Capacitive Load, CLOAD 0-50pF 100pF 500pF 1nF 5nF 10nF External Output Isolation Resistor, RISO Not Required 120kΩ 50kΩ 33kΩ 18kΩ 13kΩ In the event that an external RLOAD in parallel with CLOAD appears in the application, the use of an RISO results in gain accuracy loss because the external series RISO forms a voltage-divider with the external load resistor RLOAD. VIN VOUT If the TS1005 is used in an application that requires driving larger capacitive loads, an isolation resistor between the output and the capacitive load should be used as illustrated in Figure 5. Table 1 illustrates a range of RISO function of the external CLOAD on the TS1005. The power supply voltage TS1005 at which these resistor TS1005 Rev. 1.0 values as a output of the used on the values were Figure 6: TS1003 Transient Response for RISO = 50kΩ and CLOAD = 500pF. Page 9 TS1005 Configuring the TS1005 as Microwatt Analog Comparator design, therefore, was to set the feedback resistor R3: Although optimized for use as an operational amplifier, the TS1005 can also be used as a rail-torail I/O comparator as illustrated in Figure 7. R3 = 10MΩ Calculating a value for R1 is given by the following expression: R1 = R3 x (VHYB/VDD) Substituting VHYB=100mV, VDD=3.0V, and R3=10MΩ into the equation above yields: R1 = 333kΩ Figure 7: A MicroWatt Analog Comparator with UserProgrammable Hysteresis. The following expression was then used to calculate a value for R2: R2 = 1/[VHI/(VREF x R1) – (1/R1) – (1/R3)] External hysteresis can be employed to minimize the risk of output oscillation. The positive feedback circuit causes the input threshold to change when the output voltage changes state. The diagram in Figure 8 illustrates the TS1005’s analog comparator Substituting VHI = 2.1V, VREF = 1.5V, R1 = 333kΩ, and R3 = 10MΩ into the above expression yields: R2 = 909kΩ Printed Circuit Board Layout Considerations Figure 8: Analog Comparator Hysteresis Band and Output Switching Points. hysteresis band and output transfer characteristic. The design of an analog comparator using the TS1005 is straightforward. In this application, a 3.0V power supply (VDD) was used and the resistor divider network formed by RD1 and RD2 generated a convenient reference voltage (VREF) for the circuit at ½ the supply voltage, or 1.5V, while keeping the current drawn by this resistor divider low. Capacitor C1 is used to filter any extraneous noise that could couple into the TS1005’s inverting input. In this application, the desired hysteresis band was set to 100mV (VHYB) with a desired high trip-point (VHI) set at 2.1V and a desired low trip-point (VLO) set at 2.0V. Even though the TS1005 operates from a single 0.8V to 5.5V power supply and consumes very little supply current, it is always good engineering practice to bypass the power supplies with a 0.1μF ceramic capacitor placed in close proximity to the VDD and VSS (or GND) pins. Good pcb layout techniques and analog ground plane management improve the performance of any analog circuit by decreasing the amount of stray capacitance that could be introduced at the op amp's inputs and outputs. Excess stray capacitance can easily couple noise into the input leads of the op amp and excess stray capacitance at the output will add to any external capacitive load. Therefore, PC board trace lengths and external component leads should be kept a short as practical to any of the TS1005’s package pins. Second, it is also good engineering practice to route/remove any analog ground plane from the inputs and the output pins of the TS1005. Since the TS1005 is a low supply current amplifier (1.3µA, typical), it is desired that the design of an analog comparator using the TS1005 should also use as little current as practical. The first step in the Page 10 TS1005 Rev. 1.0 TS1005 Package outline drawing 5-Pin SC70 Package Outline Drawing (N.B., Drawings are not to scale) TS1005 Rev. 1.0 Page 11 TS1005 PACKAGE OUTLINE DRAWING 5-Pin SOT23 Package Outline Drawing (N.B., Drawings are not to scale) Patent Notice Silicon Labs invests in research and development to help our customers differentiate in the market with innovative low-power, small size, analog-intensive mixed-signal solutions. Silicon Labs' extensive patent portfolio is a testament to our unique approach and world-class engineering team. The information in this document is believed to be accurate in all respects at the time of publication but is subject to change without notice. Silicon Laboratories assumes no responsibility for errors and omissions, and disclaims responsibility for any consequences resulting from the use of information included herein. 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