SP6128AEY-L/TR

® SP6128A Low Voltage, Synchronous Step Down PWM Controller Ideal for 2A to 10A, Small Footprint, DC-DC Power Converters ■ ■ ■ ■ ■ ■ ■ ■ ■ ■ ■ ■ ■ ■ Optimized for Single Supply, 3V - 5.5V Applications GL 1 14 BST High Efficiency: Greater Than 95% Possible PVCC 2 13 GH VCC 3 Discontinuous Startup for Precharged Output 12 SWN SP6128A PGND 4 Accurate Fixed 300kHz Frequency Operation 11 ISET 14 pin TSSOP GND 5 10 VFB Fast Transient Response COMP 6 NC 9 Internal Soft Start Circuit NC 7 NC 8 Accurate 0.8V Reference Allows Low Output Voltages Now Available in Lead Free Packaging Resistor Programmable Output Voltage Resistor Programmable Overcurrent Threshold APPLICATIONS Loss-less Current Limit with High Side RDS(ON) ■ DSP Sensing ■ Microprocessor Core Hiccup Mode Current Limit Protection ■ I/O & Logic Dual N-Channel MOSFET Synchronous Driver ■ Industrial Control Quiescent Current: 500µA, 30µA in Shutdown ■ Distributed Power 14 pin TSSOP ■ Low Voltage Power DESCRIPTION The SP6128A is a fixed frequency, voltage mode, synchronous PWM controller designed to work from a single 5V or 3.3V input supply, providing excellent AC and DC regulation for high efficiency power conversion. Requiring only few external components, the SP6128A packaged in an 14-pin TSSOP, is especially suited for low voltage applications where cost, small size and high efficiency are critical. The operating frequency is internally set to 300kHz, allowing small inductor values and minimizing PC board space. The SP6128A drives two N-channel power MOSFETs for improved efficiency and includes an accurate 0.8V reference for low output voltage applications. TYPICAL APPLICATION CIRCUIT 3V to 5.5V C5 10µF D1 MBR0530 R1 5 1 2 3 4 C1 2.2µF 5 6 7 GL BST PVCC SP6128A GH VCC SWN PGND ISET GND VFB COMP NC NC NC 14 13 C4 1µF R3 8k C6 10µF C7 10µF Q1 FDS6690A L1 1.0µH 2.5V/10A 12 11 D2 STPS2L25U 10 9 8 C8 10µF C9 10µF C10 10µF C11 470µF Q2 FDS6690A C12 R4 1.7k 4.7nF C3 R2 Rev. 08/19/05 68pF R5 800 7.87k C2 4.7n SP6128A Low Voltage, Synchronous Step Down PWM Controller 1 © Copyright 2005 Sipex Corporation ABSOLUTE MAXIMUM RATINGS VCC, PVCC ......................................................................................... 7V BST .................................................................. 13.2V BST-SWN .............................................................. 7V SWN ............................................................ -1V to 7V GH ............................................... -0.3V to BST +0.3V GH-SWN ............................................................... 7V All other pins ................................ -0.3V to VCC + 0.3V Peak Output Current < 10µs GH,GL .................................................................. 2A Storage Temperature ........................ -65°C to 150°C Power Dissipation .............................................. 1.3W Junction Temperature, TJ ................................ 125°C Lead Temperature (Soldering, 10 sec) ............ 300°C ESD Rating. ................................................ 2kV HBM Thermal Resistance θJC ............................. 31.7°C/W These are stress ratings only and functional operation of the device at these ratings or any other above those indicated in the operation sections of the specifications below is not implied. Exposure to absolute maximum rating conditions for extended periods of time may affect reliability. ELECTRICAL CHARACTERISTICS Unless otherwise specified: -40°C < TA < 85°C, 3.0V < PVCC = VCC < 5.5V, CCOMP = 22nF, CGH = CGL = 3.3nF, VFB = 0.8V, SWN = GND = 0V, typical value for design guideline only. PARAMETER MIN TYP MAX UNITS CONDITIONS QUIESCENT CURRENT VCC Supply Current 0.5 1.0 mA No Switching PVCC Supply Current 1 20 µA No Switching, GH = Low VCC Supply Current(Disabled) 30 60 µA COMP=0V PVCC Supply Current (Disabled) 1 20 µA COMP=0V ERROR AMPLIFIER Error Amplifier Transconductance 0.6 ms COMP Sink Current 10 35 65 µA VFB = 0.9V, COMP = 0.9V, No Faults COMP Source Current 10 35 65 µA VFB = 0.7V, COMP = 2V COMP Output Impedance 3 VFB Input Bias Current Error Amplifier Reference MΩ 130 nA 0.812 V 330 kHz % Loop in control - 100% DC Possible 0 % Comp=0.7V 150 250 ns PVCC > 4.5V, Ramp up COMP voltage until GH starts switching 12.5 15 µA Temp = 25 °C 0.788 0.8 Trimmed with Error Amp in Unity Gain OSCILLATOR & DELAY PATH Internal Oscillator Frequency 270 Maximum Controlled Duty Cycle 300 90 Minimum Duty Cycle Minimum GH Pulse Width CURRENT LIMIT ISET Pin Sink Current 10 ISET Current Temperature Coefficient Current Limit Time Constant Overcurrent Comparator Threshold Voltage 100 Threshold Voltage Temperature Coefficient Rev. 08/19/05 3400 ppm/°C 15 µs 125 150 3400 mV VISET - VSWN, Temp = 25°C ppm/°C SP6128A Low Voltage, Synchronous Step Down PWM Controller 2 © Copyright 2005 Sipex Corporation ELECTRICAL CHARACTERISTICS Unless otherwise specified: -40°C < TA < 85°C, 3.0V < PVCC = VCC < 5.5V, CCOMP = 22nF, CGH = CGL = 3.3nF, VFB = 0.8V, SWN = GND = 0V, typical value for design guideline only. PARAMETER MIN TYP MAX UNITS CONDITIONS SOFT START, SHUTDOWN, UVLO Internal Soft Start Slew Rate 0.1 COMP Discharge Current 183 COMP Clamp Voltage 0.55 0.65 COMP Clamp Current 10 30 0.29 0.34 0.39 V Measured at COMP Pin 2 5 10 µA COMP = 0.2V, Measured at COMP pin VCC Start Threshold 2.63 2.8 2.95 V VCC Stop Threshold 2.47 2.7 2.9 V Shutdown Threshold Voltage Shutdown Input Pull-up Current 0.3 0.6 V/ms COMP pin, on transition from µA COMP = 0.5V, Fault Initiated 0.75 V VFB = 0.9V 65 µA COMP = 0.5V, VFB = 0.9V shutdown GATE DRIVERS GH Rise Time 60 110 ns PVCC > 4.5V GH Fall Time 60 110 ns PVCC > 4.5V GL Rise Time 60 110 ns PVCC > 4.5V GL Fall Time 60 110 ns PVCC > 4.5V GH to GL Non-Overlap Time 0 100 140 ns PVCC > 4.5V, measured at 2volt threshold GL to GH Non-Overlap Time 0 100 140 ns PVCC > 4.5V, measured at 2volt threshold PIN DESCRIPTION PIN N0. 1 PIN NAME GL 2 PVCC 3 VCC 4 5 6 PGND GND COMP 7, 8, 9 10 NC VFB 11 ISET 12 SWN 13 GH 14 BST Rev. 08/19/05 DESCRIPTION High current driver output for the low side MOSFET switch. It is always low if GH is high. GL swings from PGND to PVCC. Positive input supply for the low side gate driver. It's recommended to tie the PVCC to the VCC pin. Positive input supply for the logic circuitry. Properly bypass this pin to GND with a low ESL/ ESR ceramic capacitor or RC filter. Power ground pin. Signal ground pin. Output of the Error Amplifier. It is internally connected to the inverting input of the PWM comparator. A lead-lag network is typically connected to the COMP pin to compensate the feedback loop in order to optimize the dynamic performance of the voltage mode control loop. Sleep mode can be invoked by pulling the COMP pin below 0.3V with an external open-drain or open-collector transistor. An internal 5µA pull-up ensures start-up. No connect. Feedback Voltage Pin. It is the inverting input of the Error Amplifier and serves as the output voltage feedback point for the Buck converter. The output voltage is sensed and can be adjusted through an external resistor divider. Overcurrent program pin. A resistor programs the overcurrent threshold. The overcurrent comparator sets the fault latch and terminates gate pulses when VISET > VSWN and the high side MOSFET is turned on. This prevents excessive power dissipation in the external power MOSFETs during an overload condition. An internal delay circuit prevents false shutdowns that might otherwise occur during very short, mild overload conditions,due to load transients. Lower supply rail for the GH high-side gate driver. It also connects to the Current Limit comparator. Connect this pin to the switching node at the junction between the two external power MOSFET transistors. This pin monitors the voltage drop across the RDS(ON) of the high side N-channel MOSFET while it is conducting. High current driver output for the high side MOSFET switch. It is always low if GL is high or during a fault. GH swings from SWN to BST. High side driver supply pin. Connect BST to the external boost diode and capacitor as shown in the application schematic on page 1. SP6128A Low Voltage, Synchronous Step Down PWM Controller 3 © Copyright 2005 Sipex Corporation FUNCTIONAL DIAGRAM 1V Reference - 0.8V DRIVER ENABLE + 2 PVCC SHUTDOWN FAULT 0.27V/ms SOFTSTART + GM ERROR AMP 5µA PWM COMP - RESET Dominant PWM Logic R - + VFB 10 14 BST + 350mV 13 GH Synchronous Driver 1 GL Q S COMP 6 12 SWN 4 PGND VCC 3 UVLO 2.8V ON 2.7V OFF 750mV RAMP + Reset Dominant Q 15µA SHUTDOWN + SWN COMP S Over Current GH ISET 11 5 GND F = 300kHz FAULT R - OPERATION General Overview The SP6128A is a constant frequency, voltage mode, synchronous PWM controller designed for low voltage, DC/DC step down converters. It is intended to provide complete control for a high power, high efficiency, precisely regulated output voltage from a highly integrated 14-pin solution. High efficiency is obtained through the use of synchronous rectification. Synchronous regulators replace the catch diode in the standard buck converter with a low R DS(ON) N-channel MOSFET switch allowing for significant efficiency improvements. The SP6128A includes two fast MOSFET drivers with internal non-overlap circuitry and drives a pair of N-channel power transistors. The SP6128A includes an internal 0.27V/ms soft-start circuit that provides controlled ramp up of the output voltage, preventing overshoot and inrush current at power up. The internal free-running oscillator accurately sets the PWM frequency at 300kHz without requiring any external elements and allows the use of physically small, low value external components without compromising performance. A transconductance amplifier is used for the error amplifier, which compares an attenuated sample of the output voltage with a precision, 0.8V reference voltage. The output of the error amplifier (COMP), is compared to a 0.75V peak-topeak ramp waveform to provide PWM control. The COMP pin provides access to the output of the error amplifier and allows the use of external components to stabilize the voltage loop. Rev. 08/19/05 Current limiting is implemented by monitoring the voltage drop across the RDS(ON) of the high side N-channel MOSFET while it is conducting, thereby eliminating the need for an external sense resistor. The overcurrent threshold can be programmed by a single resistor. SP6128A Low Voltage, Synchronous Step Down PWM Controller 4 © Copyright 2005 Sipex Corporation OPERATION: continued When the overcurrent threshold is exceeded, the overcurrent comparator sets the fault latch and terminates the output pulses. The controller stops switching and goes through a hiccup sequence. This prevents excessive power dissipation in the external power MOSFETs during an overload condition. An internal delay circuit prevents that very short and mild overload conditions, that could occur during a load transient, activate the current limit circuit. UVLO Assuming that there is not shutdown condition present, then the voltage on the VCC pin determines operation of the SP6128A. As VCC rises, the UVLO block monitors VCC and keeps the high side and low side MOSFETS off and the internal SS voltage low until VCC reaches 2.8V. If no faults are present, the SP6128A will initiate a soft start when VCC exceeds 2.8 V. Hysteresis (about 100mV) in the UVLO comparator provides noise immunity at start-up. A low power sleep mode can be invoked in the SP6128A by externally forcing the COMP pin below 0.3V. Quiescent supply current in sleep mode is typically less than 30µA. An internal 5µA pull-up current at the COMP pin brings the SP6128A out of shutdown mode. Soft Start Soft start is required on step-down controllers to prevent excess inrush current through the power train during start-up. Typically this is managed by sourcing a controlled current into a timing capacitor and then using the voltage across this capacitor to slowly ramp up either the error amp reference or the error amp output (COMP). The control loop creates narrow width driver pulses while the output voltage is low and allows these pulses to increase to their steady-state duty cycle as the output voltage increases to its regulated value. As a result of controlling the inductor volt*second product during startup, inrush current is also controlled. An internal 0.8V 1.5% reference allows output voltage adjustment for low voltage applications. The SP6128A also includes an accurate undervoltage lockout that shuts down the controller when the input voltage falls below 2.7V. Output overvoltage protection is achieved by turning off the high side switch and turning on the low side N-channel MOSFET 100% of the time. Enable Low quiescent mode or “Sleep Mode” is initiated by pulling the COMP pin below 0.3V with an external open-drain or open-collector transistor. Supply current is reduced to 30µA (typical) in shutdown. On power-up, assuming that VCC has exceeded the UVLO start threshold (2.8V), an internal 5µA pull-up current at the COMP pin brings the SP6128A out of shutdown mode and ensures start-up. During normal operating conditions and in absence of a fault, an internal clamp prevents the COMP pin from swinging below 0.6V. This guarantees that during mild transient conditions, due either to line or load variations, the SP6128A does not enter shutdown unless it is externally activated. In the SP6128A the duration of the soft-start is controlled by an internal timing circuit that provides a 0.3V/mS slew-rate, which is used during startup and overcurrent to set the hiccup time. The SP6128A implements soft-start by ramping up the error amplifier reference voltage providing a controlled slew-rate of the output voltage, thereby preventing overshoot and inrush current at power up. The presence of the output capacitor creates extra current draw during startup. Simply stated, dVOUT/ dt requires an average sustained current in the output capacitor and this current must be considered while calculating peak inrush current and over current thresholds. An approximate expression to determine the excess inrush current due to the dVOUT/dt of the output capacitor COUT is: During Sleep Mode, the high side and low side MOSFETS are turned off and the internal soft start voltage is held low. Rev. 08/19/05 VOUT Iinrush = COUT x (0.27 V/ms) x 0.8V SP6128A Low Voltage, Synchronous Step Down PWM Controller 5 © Copyright 2005 Sipex Corporation OPERATION: continued As the figure shows, the SS voltage controls a variety of signals. First, provided all the external fault conditions are removed, an internal 5µA pull-up at the COMP pin brings the SP6128A out of shutdown mode. The internal timing circuit is then activated and controls the ramp-up of the error amp reference voltage. The COMP pin is pulled to 0.7V by the internal clamp and then gradually charges preventing the error amplifier from forcing the loop to maximum duty cycle. As the COMP voltage crosses about 1V (valley voltage of the PWM ramp), the driver begins to switch the high side MOSFET with narrow pulses in an effort to keep the converter output regulated . The SP6128A operates at low duty cycle as the COMP voltage increases above 1V. As the error amp reference ramps upward, the driver pulses widen until a steady state value is reached and the output voltage is regulated to the final value ending the soft start charge cycle. COMP 1V 0.7 V 0.3 V 0V Internal SS Voltage Error Amp Reference Voltage 0.8 V 0V Hiccup Mode I(L) When the converter enters a fault mode, the SP6128A holds the high side and low side MOSFETs off for a finite period of time. Provided that the SP6128A is enabled, this time is set by the internal charge of the soft-start capacitor. In the event of an overcurrent condition, the current sense comparator sets the fault latch, which in turn discharge the internal SS capacitor, the COMP pin and holds the output drivers off. During this condition, the SP6128A stays off for the time it takes to discharge the COMP pin down to the 0.29V shutdown threshold. At this point, the fault latch is reset, but before the SP6128A is allowed to attempt restart, the COMP pin has to charge back to 1V before any output switching can be initiated. Then, the regulator attempts to restart normally by delivering short gate pulses and if the overcurrent condition is still present, the cycle will repeat itself. However, if upon restart, the overcurrent condition is still present, the SP6128A will detect the fault and remain in a fault state until the internal soft start voltage reaches about VCC-1V thereby increasing the MOSFET off-time. This protection scheme minimizes thermal stress to the regulator components as the overcurrent condition persists. Rev. 08/19/05 Inductor Current 0A V(VCC) FAULT 0V V(VCC) SWN Voltage 0V TIME SP6128A Low Voltage, Synchronous Step Down PWM Controller 6 © Copyright 2005 Sipex Corporation OPERATION: continued A more detailed description of the waveform is shown below. SP6128A OVER CURRENT (HICCUP MODE) Test Conditions BST = 5.0V SWN - tied to GND through 1k Resistor COMP – released from GND VFB = 0.7V VCC = PVCC = 5.0V Overcurrent Detected GH Turns Off Fault Mode Enabled Internal SSTART rises until ~ VCC-1V, then gives command to attempt RESTART GH COMP Clamps ~ 3V COMP After pop, COMP retains internal SSTART slope ENABLE Part Attempt RESTART 5µA PULLUP slope to 0.3V; 35µA PULLUP to 0.7V Internal SSTART passes V(VFB), COMP pops to ~ internal SSTART voltage +0.7V Over Current Protection current condition upon reaching a CMOS inverter threshold. There are many advantages to this approach. First, the filtering action of the gated scheme protects against false and undesirable triggering that could occur during a minor transient overload condition or supply line noise. Furthermore, the total amount of time to trigger the fault depends on the on-time of the high side NMOS switch. Fifteen, 1µs pulses are equivalent to thirty, 500ns pulses or one, 15µs pulse, however, depending on the period, each scenario takes a different amount of total time to trigger a fault. Therefore, the fault becomes an indicator of average power in the high side Over current protection on the SP6128A is implemented through detection of an excess voltage condition across the high side NMOS switch during conduction. This is typically referred to as high side RDS(ON) detection and eliminates the need of an external sense resistor. The over current comparator charges an internal sampling capacitor each time VSWN is lower than (VISET - 140mV) and the GH voltage is high. The discharge/charge current ratio on the sampling capacitor is about 2%. Therefore, provided that the over current condition persists, the capacitor voltage will be pumped up during each time GH switches high. This voltage will trigger an over Rev. 08/19/05 SP6128A Low Voltage, Synchronous Step Down PWM Controller 7 © Copyright 2005 Sipex Corporation OPERATION: continued consists of one high side NMOS, 4Ω driver, GH, and one low side, 4 Ω, NMOS driver, GL, optimized for driving external power MOSFET’s in a synchronous buck topology. The output drivers also provide gate drive non-overlap mechanism that provides a dead time between GH and GL transitions to avoid potential shootthrough problems in the external MOSFETs. switch. The ISET current has a temperature coefficient in an effort to first order match the thermal characteristics of the RDS(ON) of the high side NMOS switch. It assumed that the SP6128A will be used in compact designs where there is a high amount of thermal coupling between the high side switch and the controller. Discontinuous Start Up The following figure shows typical waveforms for the output drivers. Today’s distributed power systems require multiple supply voltages, such as core and I/O voltages. In many applications, there’s requirement on the maximum voltage difference allowed between these supplies at any time. This requirement can be potentially violated during power start up when individual power supply ramps up in sequence or in different slew rates. As a solution, system designers often pre-charge power supplies through an external circuit prior to start up. Unfortunately, under this condition many existing synchronous controllers turn on the low side MOSFET during soft start for a long period of time, thereby, discharging the output capacitors. The discharge period creates a number of problems. One is the obvious problem of losing the intended pre-charged output voltage. Another problem is a build up of excessive and unchecked current in the low side MOSFET and inductor. Lastly, this uncontrolled discharge current creates conditions that could damage either the distributed power supplies or the rather expensive “load” ICs. As with all synchronous designs, care must be taken to ensure that the MOSFETs are properly chosen for non-overlap time, enhancement gate drive voltage, “on” resistance RDS(ON), reverse transfer capacitance Crss, input voltage and maximum output current. GATE DRIVER TEST CONDITIONS 5V FALL TIME GH(GL) 2V 10 % 5V 90 % GL(GH) RISE TIME 2V 10 % NON-OVERLAP V(BST) GH Voltage To prevent soft start from discharging the precharged output, SP6128A has built-in discontinuous start up. This operation disables the low side MOSFET driver GL during start up until either there is GH pulse or the internal SSTART reaches Vcc-1V. This feature eliminates the output discharging path during start up. During the steady state operation, the GL is fully engaged, and the operation is identical to regular synchronous buck converters. 0V V(VCC) GL Voltage 0V V(VCC=VIN) SWN Voltage ~0V - V(Diode) V Output Drivers ~ 2*V(VIN) The SP6128A, unlike some other bipolar controller IC’s, incorporates gate drivers with railto-rail swing that help prevent spurious turn on due to capacitive coupling. The driver stage Rev. 08/19/05 90 % BST Voltage ~ V(VIN) TIME SP6128A Low Voltage, Synchronous Step Down PWM Controller 8 © Copyright 2005 Sipex Corporation PACKAGE: TSSOP PLASTIC THIN SMALL OUTLINE (TSSOP) DIMENSIONS in inches (mm) Minimum/Maximum Symbol D 14 Lead 0.193/0.201 (4.90/5.10) e 0.026 BSC (0.65 BSC) e 0.126 BSC (3.2 BSC) 0.252 BSC (6.4 BSC) 1.0 OIA 0.169 (4.30) 0.177 (4.50) 0.039 (1.0) 0’-8’ 12’REF e/2 0.039 (1.0) 0.043 (1.10) Max D 0.033 (0.85) 0.037 (0.95) 0.007 (0.19) 0.012 (0.30) 0.002 (0.05) 0.006 (0.15) (θ2) 0.008 (0.20) 0.004 (0.09) Min 0.004 (0.09) Min Gage Plane 0.010 (0.25) (θ3) 0.020 (0.50) 0.026 (0.75) (θ1) 1.0 REF Rev. 08/19/05 SP6128A Low Voltage, Synchronous Step Down PWM Controller 9 © Copyright 2005 Sipex Corporation ORDERING INFORMATION Part Number Operating Temperature Range Package Type SP6128AEY ............................................ -40˚C to +85˚C ...................................... 14-Pin TSSOP SP6128AEY/TR ...................................... -40˚C to +85˚C ...................................... 14-Pin TSSOP SP6128AHY ........................................... -40˚C to +105˚C ..................................... 14-Pin TSSOP SP6128AHY/TR ..................................... -40˚C to +105˚C ..................................... 14-Pin TSSOP SP6128ACY .............................................. 0˚C to +70˚C ....................................... 14-Pin TSSOP SP6128ACY/TR ........................................ 0˚C to +70˚C ....................................... 14-Pin TSSOP Available in lead free packaging. To order add "-L" suffix to part number. Example: SP6128AEY/TR = standard; SP6128AEY-L/TR = lead free /TR = Tape and Reel Pack quantity is 2,500 for TSSOP. Corporation ANALOG EXCELLENCE Sipex Corporation Headquarters and Sales Office 233 South Hillview Drive Milpitas, CA 95035 TEL: (408) 934-7500 FAX: (408) 935-7600 Sipex Corporation reserves the right to make changes to any products described herein. Sipex does not assume any liability arising out of the application or use of any product or circuit described herein; neither does it convey any license under its patent rights nor the rights of others. Rev. 08/19/05 SP6128A Low Voltage, Synchronous Step Down PWM Controller 10 © Copyright 2005 Sipex Corporation