TS613
DUAL WIDE BAND OPERATIONAL AMPLIFIER
WITH HIGH OUTPUT CURRENT
■ LOW NOISE : 3nV/√Hz, 1.2pA/√Hz
■ HIGH OUTPUT CURRENT : 200mA
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■ VERY LOW HARMONIC AND INTERMODULATION DISTORTION
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SO8
(Plastic Micropackage)
■ HIGH SLEW RATE : 40V/µs
■ SPECIFIED FOR 25Ω LOAD
DESCRIPTION
The TS613 is a dual operational amplifier featuring a high output current (200mA min.), large
gain-bandwidth product (130MHz) and capable of
driving a 25Ω load with a 160mA output current at
±6V power supply.
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This device is particularly intended for applications
where multiple carriers must be amplified simultaneously with very low intermodulation products.
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DW
SO8 Exposed-Pad
(Plastic Micropackage)
PIN CONNECTIONS (top view)
The TS613 is housed in a SO8 plastic package
and a SO8 Exposed-Pad plastic package.
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APPLICATION
let
■ UPSTREAM line driver for Asymmetric Digital
Subscriber Line (ADSL) (NT).
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ORDER CODE
Output1 1
Inverting Input1 2
_
Non Inverting Input1 3
+
VCC - 4
Part
Number
Temperature
Range
TS613ID
TS613IDW
-40, +85°C
-40, +85°C
8 VCC +
7 Output2
_
6 Inverting Input2
+
5 Non Inverting Input2
Package
D
DW
•
•
Cross Section View Showing Exposed-Pad
This pad can be connected to a (-Vcc) copper area on the PCB
D = Small Outline Package (SO) - also available in Tape & Reel (DT)
DW = Small Outline Package inExposed-Pad (SO) - also available in
Tape & Reel (DWT)
December 2002
1/10
TS613
ABSOLUTE MAXIMUM RATINGS
Symbol
VCC
Vid
Vin
Parameter
Supply voltage
Unit
±7
V
Differential Input Voltage
±2
V
±6
Input Voltage Range
V
2)
3)
Toper
Operating Free Air Temperature Range
-40 to + 85
°C
Tstd
Storage Temperature
-65 to +150
°C
150
°C
Tj
SO8
Rthjc
Rthja
Maximum Junction Temperature
Output Short Circuit Duration
4)
Thermal Resistance Junction to Case
28
Thermal Resistance Junction to Ambient Area
715
Thermal Resistance Junction to Ambient Area
Pmax.
Maximum Power Dissipation (@25°C)
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Maximum Power Dissipation (@25°C)
SO8 Exposed-Pad
Rthjc
Thermal Resistance Junction to Case
Rthja
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°C/W
175
Pmax.
1.
2.
3.
4.
Value
1)
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°C/W
mW
16
°C/W
60
°C/W
2000
mW
Value
Unit
All voltages values, except differential voltage are with respect to network terminal.
Differential voltages are non-inverting input terminal with respect to the inverting input terminal.
The magnitude of input and output voltages must never exceed VCC +0.3V.
An output current limitation protects the circuit from transient currents. Short-circuits can cause excessive heating.
Destructive dissipation can result from short circuit on amplifiers.
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OPERATING CONDITIONS
Symbol
VCC
Vicm
2/10
ct
Supply Voltage
du
Common Mode Input Voltage
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(s)
Parameter
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±2.5 to ±6
(VCC) +2 to (VCC
V
+)
-1
V
TS613
ELECTRICAL CHARACTERISTICS
Symbol
VCC = ±6V, Tamb = 25°C (unless otherwise specified).
Parameter
Test Condition
Min.
Typ.
Max
Unit
-6
-1
6
10
mV
DC PERFORMANCE
Vio
∆Vio
Differential Input Offset Voltage
Iio
Input Offset Current
Iib
Input Bias Current
CMR
Common Mode Rejection Ratio
SVR
Supply Voltage Rejection Ratio
ICC
Tamb
Tmin. < Tamb < Tmax.
Tamb = 25°C
Tamb
Input Offset Voltage
0.2
Tmin. < Tamb < Tmax.
Tamb
Tmin. < Tamb < Tmax.
Vic = ±2V, Tamb
Tmin. < Tamb < Tmax.
Vic = ±6V to ±4V, Tamb
Tmin. < Tamb < Tmax.
No load, Vout = 0
Total Supply Current per Operator
High Level Output Voltage
Low Level Output Voltage
AVD
Large Signal Voltage Gain
GBP
SR
Isink
Isource
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Output Short Circuit Current
uc
Phase Margin at AVCL = 14dB
ΦM6
Phase Margin at AVCL = 6dB
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NOISE AND DISTORTION
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Equivalent Input Noise Voltage
Equivalent Input Noise Current
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THD
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)-
Slew Rate
ΦM14
Iout = 160mA, RL to GND
Iout = 160mA, RL to GND
Vout = 7V peak
RL = 25Ω, Tamb
Tmin. < Tamb < Tmax.
AVCL = +11, f = 20MHz
RL = 100Ω
AVCL = +7, RL = 50Ω
Vid = ±1V, Tamb
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Gain Bandwidth Product
Total Harmonic Distortion
HD2-10
2nd Harmonic Distortion
HD2+2
2nd Harmonic Distortion
HD3-10
3rd Harmonic Distortion
HD3+2
3rd Harmonic Distortion
IM2-10
2nd Order Intermodulation Product
IM3-10
3rd Order Intermodulation Product
90
70
108
70
50
88
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Tmin. < Tamb < Tmax.
RL = 25Ω//15pF
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4
6500
4.5
-4.5
mV
µA
µA
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DYNAMIC PERFORMANCE and OUTPUT CHARACTERISTICS
VOH
VOL
5
6
3
5
15
30
-4
dB
dB
mA
V
V
11000
V/V
80
130
MHz
23
±200
±180
40
±320
V/µs
5000
mA
60
°
RL = 25Ω//15pF
40
°
f = 100kHz
f = 100kHz
Vout = 4Vpp, f = 100kHz
AVCL = -10
RL = 25Ω//15pF
3
1.2
nV/√Hz
pA/√Hz
-69
dB
-70
dBc
-74
dBc
-80
dBc
-79
dBc
-77
dBc
-77
dBc
Vout = 4Vpp, f = 100kHz
AVCL = -10
Load =25Ω//15pF
Vout = 4Vpp, f = 100kHz
AVCL = +2
Load =25Ω//15pF
Vout = 4Vpp, f = 100kHz
AVCL = -10
Load =25Ω//15pF
Vout = 4Vpp, f = 100kHz
AVCL = +2
Load =25Ω//15pF
F1 = 80kHz, F2 = 70kHz
Vout = 8Vpp, AVCL = -10
Load = 25Ω//15pF
F1 = 80kHz, F2 = 70kHz
Vout = 8Vpp, AVCL = -10
Load = 25Ω//15pF
3/10
TS613
The TS613 is housed in an Exposed-Pad plastic
package. As described on the figures below, this
package uses a leadframe upon which the dice is
mounted. This leadframe is exposed as a thermal
pad on the underside of the package. The thermal
contact is direct with the dice. This thermal path
provide an excellent thermal performance.
3rd ORDER INTERMODULATION
Gain=15dB, Vcc=±6V, RL=25Ω, 2 tones 70kHz/
80kHz
0
-10
-20
-30
IM3 (dBc)
THERMAL INFORMATION
The thermal pad is electrically isolated from all
pins in the package. It can also be soldered to a
copper area of the PCB underneath the package.
Through these thermal paths within this copper area, heat can be conducted away from the package. In this case, the copper area must be connected to (-Vcc)
-40
90kHz
-50
230kHz
-60
-70
)
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-80
60kHz
-90
220kHz
-100
1
1,5
2
uc
2,5
3
3,5
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4,5
Vout peak (V)
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2nd ORDER INTERMODULATION
Gain=15dB, Vcc=±6V, RL=25Ω, 2 tones 180kHz/
280kHz, Spurious measurement @100kHz
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Bottom View
Side View
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-55
IM2 (dBc)
DICE
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-60
-65
DICE
Cross Section View
-70
1,5
2
2,5
3
3,5
4
4,5
Vout peak (V)
INTERMODULATION DISTORTION
4/10
3rd ORDER INTERMODULATION
Gain=15dB, Vcc=±6V, RL=25Ω, 2 tones 180kHz/
280kHz
0
-10
-20
-30
IM3 (dBc)
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The curves shown below are the measurements
results of a single operator wired as an adder with
a gain of 15dB.
The operational amplifier is supplied by a symmetric ±6V and is loaded with 25Ω.
Two synthesizers (Rhode & Schwartz SME) generate two frequencies (tones) (70 & 80kHz ; 180 &
280kHz).
An HP3585 spectrum analyzer measures the spurious level at different frequencies.
The curves are traced for different output levels
(the value in the X ax is the value of each tone).
The output levels of the two tones are the same.
The generators and spectrum analyzer are phase
locked to enhance measurement precision.
-40
-50
80kHz
-60
380kHz
-70
-80
640kHz
-90
740kHz
-100
1
1,5
2
2,5
3
Vout peak (V)
3,5
4
4,5
TS613
Closed Loop Gain and Phase vs. Frequency
Gain=+6, Vcc=±6V, RL=25Ω
Closed Loop Gain and Phase vs. Frequency
Gain=+2, Vcc=±6V, RL=25Ω
10
200
200
20
Gain
Gain
15
0
-20
-100
Gain (dB)
Phase
-10
100
10
5
Phase
0
0
-5
-10
)
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-15
-30
-200
10kHz
100kHz
1MHz
10MHz
-20
100MHz
10kHz
100kHz
Frequency
O
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Gain (dB)
10
Phase
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-30
10kHz
100kHz
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1MHz
10MHz
Frequency
0
Phase (degrees)
100
20
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+
_
15
10k
100
10
-100
5
-200
0
100Hz
100MHz
1kHz
10kHz
100kHz
1MHz
Frequency
Maximum Output Swing
Vcc=±6V, RL=25Ω
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-200
100MHz
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200
Gain
20
-100
Equivalent Input Voltage Noise
Gain=+100, Vcc=±6V, no load
en (nV/VHz)
30
-20
10MHz
Frequency
Closed Loop Gain and Phase vs. Frequency
Gain=+11, Vcc=±6V, RL=25Ω
-10
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1MHz
Phase (degrees)
100
Phase (degrees)
Gain (dB)
0
Channel Separation (Xtalk) vs. Frequency
XTalk=20Log(V2/V1), Vcc=±6V, RL=25Ω
-20
5
VIN
4
output
3
-40
Xtalk (dB)
swing (V)
2
input
1
+
49.9Ω
_
-30
0
100Ω
+
49.9Ω
_
-50
-1
-60
-2
V1
1kΩ
100Ω
25Ω
V2
1kΩ
25Ω
-3
-70
-4
-5
0
2
4
6
Time (µs)
8
10
-80
10kHz
100kHz
1MHz
10MHz
Frequency
5/10
TYPICAL APPLICATION : TS613 AS DRIVER
FOR ADSL LINE INTERFACES
A SINGLE SUPPLY IMPLEMENTATION WITH PASSIVE
OR ACTIVE IMPEDANCE MATCHING
by C. PRUGNE
The TS613 is used as a dual line driver for the upstream signal.
For the remote terminal it is required to create an
ADSL modem easy to plug in a PC. In such an application, the driver should be implemented with a
+12 volts single power supply. This +12V supply is
available on PCI connector of purchase.
The figure 2 shows a single +12V supply circuit
that uses the TS613 as a remote terminal transmitter in differential mode.
ADSL CONCEPT
Asymmetric Digital Subscriber Line (ADSL), is a
new modem technology, which converts the existing twisted-pair telephone lines into access paths
for multimedia and high speed data communications.
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ADSL transmits more than 8 Mbps to a subscriber,
and can reach 1Mbps from the subscriber to the
central office. ADSL can literally transform the actual public information network by bringing movies, television, video catalogs, remote CD-ROMs,
LANs, and the Internet into homes.
An ADSL modem is connected to a twisted-pair
telephone line, creating three information channels: a high speed downstream channel (up to
1.1MHz) depending on the implementation of the
ADSL architecture, a medium speed upstream
channel (up to 130kHz) and a POTS (Plain Old
Telephone Service), split off from the modem by
filters.
Figure 2 : TS613 as a differential line driver with
a +12V single supply
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Figure 1 : Typical ADSL Line Interface
high output
current
upstream
digital
treatment
TS613
Line Driver
impedance
matching
HYBRID
CIRCUIT
analog to
digital
6/10
reception
(analog)
reception
circuits
twisted-pair
telephone
line
downstream
_
1k
+12V
10n
12.5
GND
R2
1:2
Vi
47k
Vo
1/2 R1
Vcc/2
1/2
10µ
Vi
25Ω
100Ω
R1
47k 100n
GND
Hybrid
&
Transformer
Vo
+
R3
+12V
12.5
GND
100n
The Figure1 shows a typical analog line interface
used for ADSL. The upstream and downstream
signals are separated from the telephone line by
using an hybrid circuit and a line transformer. On
this note, the accent will be made on the emission
path.
digital to emission LP filter
analog
(analog)
+
+12V
_
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1µ
100n
1k
THE LINE INTERFACE - ADSL Remote
Terminal (RT):
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The driver is biased with a mid supply (nominaly
+6V), in order to maintain the DC component of
the signal at +6V. This allows the maximum dynamic range between 0 and +12 V. Several options are possible to provide this bias supply (such
as a virtual ground using an operational amplifier),
such as a two-resistance divider which is the
cheapest solution. A high resistance value is required to limit the current consumption. On the
other hand, the current must be high enough to
bias the inverting input of the TS613. If we consider this bias current (5µA) as the 1% of the current
through the resistance divider (500µA) to keep a
stable mid supply, two 47kΩ resistances can be
used.
The input provides two high pass filters with a
break frequency of about 1.6kHz which is necessary to remove the DC component of the input signal. To avoid DC current flowing in the primary of
the transformer, an output capacitor is used. The
TS613
1µF capacitance provides a path for low frequencies, the 10nF capacitance provides a path for
high end of the spectrum.
Component calculation:
Let us consider the equivalent circuit for a single
ended configuration, figure4.
In differential mode the TS613 is able to deliver a
typical amplitude signal of 18V peak to peak.
Figure 4 : Single ended equivalent circuit
The dynamic line impedance is 100Ω. The typical
value of the amplitude signal required on the line
is up to 12.4V peak to peak. By using a 1:2 transformer ratio the reflected impedance back to the
primary will be a quarter (25Ω) and therefore the
amplitude of the signal required with this impedance will be the half (6.2 V peak to peak). Assuming the 25Ω series resistance (12.5Ω for both outputs) necessary for impedance matching, the output signal amplitude required is 12.4 V peak to
peak. This value is acceptable for the TS613. In
this case the load impedance is 25Ω for each driver.
For the ADSL upstream path, a lowpass filter is
absolutely necessary to cutoff the higher frequencies from the DAC analog output. In this simple
non-inverting amplification configuration, it will be
easy to implement a Sallen-Key lowpass filter by
using the TS613. For ADSL over POTS, a maximum frequency of 135kHz is reached. For ADSL
over ISDN, the maximum frequency will be
276kHz.
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With passive matching, the output signal amplitude of the driver must be twice the amplitude on
the load. To go beyond this limitation an active
maching impedance can be used. With this technique it is possible to keep good impedance
matching with an amplitude on the load higher
than the half of the ouput driver amplitude. This
concept is shown in figure3 for a differential line.
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Figure 3 : TS613 as a differential line driver with
an active impedance matching
Vcc+
_
1k
10n
GND
R2
Vi
Rs1
_
Vi
Vo°
Vo
R2
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-1
R3
1/2R1
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1/2RL
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Let us consider the unloaded system. Assuming
the currents through R1, R2 and R3
as respectively:
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2Vi Vi – Vo° )
Vi + Vo )---------, (------------------------- and (----------------------R2
R3
R1
As Vo° equals Vo without load, the gain in this
case becomes :
2R2 R2
1 + ----------- + ------Vo ( noload )
R1 R3
G = ------------------------------- = ----------------------------------Vi
R2
1 – ------R3
The gain, for the loaded system will be (1):
2R2 R2
1 + ----------- + ------1
R1 R3
Vo
(
withload
)
GL = ------------------------------------ = --- ----------------------------------- ,( 1 )
2
R2
Vi
1 – ------R3
As shown in figure5, this system is an ideal generator with a synthesized impedance as the internal
impedance of the system. From this, the output
voltage becomes:
Vo = ( ViG ) – ( RoIout ) ,( 2 )
with Ro the synthesized impedance and Iout the
output current. On the other hand Vo can be expressed as:
2R2 R2
Vi 1 + ----------- + -------
R1 R3 Rs1Iout
Vo = ----------------------------------------------- – --------------------- ,( 3 )
R2
R2
1 – ------1 – ------R3
R3
1µ
100n
+
Rs1
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INCREASING THE LINE LEVEL BY USING AN
ACTIVE IMPEDANCE MATCHING
Vcc+
+
Vo°
1:n
Vo
1/2 R1
R3
RL
Vcc/2
1/2 R1
10µ
Vi
1k
GND
_
100Ω
R5
100n
+
Hybrid
&
Transformer
R4
Vcc+
Vo°
Vo
Rs2
GND
100n
7/10
TS613
By identification of both equations (2) and (3), the
synthesized impedance is, with Rs1=Rs2=Rs:
Rs
Ro = ----------------- ,( 4 )
R2
1 – ------R3
GL (gain for the
loaded system)
R1
2R2/[2(1-R2/R3)GL-1-R2/R3]
R2 (=R4)
Abritrary fixed
R3 (=R5)
Figure 5 : Equivalent schematic. Ro is the synthesized impedance
GL is fixed for the application requirements
GL=Vo/Vi=0.5(1+2R2/R1+R2/R3)/(1-R2/R3)
R2/(1-Rs/0.5RL)
Rs
0.5RL(k-1)
CAPABILITIES
Iout
Ro
Vi.Gi
The table below shows the calculated components for different values of k. In this case
R2=1000Ω and the gain=16dB. The last column
displays the maximum amplitude level on the line
regarding the TS613 maximum output capabilities
(18Vpp diff.) and a 1:2 line transformer ratio.
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1/2RL
Unlike the level Vo° required for a passive impedance, Vo° will be smaller than 2Vo in our case. Let
us write Vo°=kVo with k the matching factor varying between 1 and 2. Assuming that the current
through R3 is negligeable, it comes the following
resistance divider:
kVoRL
Ro = --------------------------RL + 2Rs1
After choosing the k factor, Rs will equal to
1/2RL(k-1).
A good impedance matching assumes:
1
R o = --- RL ,( 5 )
2
)
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2Rs
R2
------- = 1 – ---------- ,( 6 )
RL
R3
By fixing an arbitrary value for R2, (6) gives:
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R2
R3 = ------------------2Rs
1 – ---------RL
Finally, the values of R2 and R3 allow us to extract
R1 from (1), and it comes:
2R2
R1 = --------------------------------------------------------- ,( 7 )
R2
R2
2 1 – ------- GL – 1 – ------
R3
R3
with GL the required gain.
8/10
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Active matching
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R1
(Ω)
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From (4) and (5) it becomes:
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1.3
1.4
1.5
1.6
1.7
820
490
360
270
240
Passive
R3
(Ω)
Rs
(Ω)
1500 3.9
1600 5.1
2200 6.2
2400 7.5
3300 9.1
matching
TS613 Output
Level to get
12.4Vpp on
the line
(Vpp diff)
8
8.7
9.3
9.9
10.5
12.4
Maximum
Line level
(Vpp diff)
27.5
25.7
25.3
23.7
22.3
18
MEASUREMENT OF THE POWER
CONSUMPTION IN THE ADSL APPLICATION
Conditions:
Passive impedance matching
Transformer turns ratio: 2
Power Supply: 12V
Maximun level required on the line: 12.4Vpp
Maximum output level of the driver: 12.4Vpp
Crest factor: 5.3 (Vp/Vrms)
The TS613 power consumption during emission
on 900 and 4550 meter twisted pair telephone
lines: 360mW
TS613
PACKAGE MECHANICAL DATA
8 PINS - PLASTIC MICROPACKAGE (SO)
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Millimeters
Dim.
Min.
A
a1
a2
a3
b
b1
C
c1
D
E
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F
L
M
S
Max.
0.1
0.65
0.35
0.19
0.25
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3.8
0.4
o
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1.75
0.25
1.65
0.85
0.48
0.25
0.5
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4.8
5.8
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Typ.
Min.
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Inches
Typ.
Max.
0.026
0.014
0.007
0.010
0.069
0.010
0.065
0.033
0.019
0.010
0.020
0.189
0.228
0.197
0.244
0.004
45° (typ.)
5.0
6.2
1.27
3.81
0.050
0.150
4.0
1.27
0.6
0.150
0.016
0.157
0.050
0.024
8° (max.)
9/10
TS613
PACKAGE MECHANICAL DATA
8 PINS - PLASTIC MICROPACKAGE (SO Exposed-Pad)
)
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Millimeters
Dim.
Min.
A
A1
A2
B
C
D
D1
E
E1
e
H
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L
k
ddd
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1.350
0.000
1.100
0.330
0.190
4.800
Typ.
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Pr
Max.
Min.
1.750
0.250
1.650
0.510
0.250
5.000
0.053
0.001
0.043
0.013
0.007
0.189
4.000
0.150
3.10
3.800
5.800
0.250
0.400
0d
-O
o
r
P
Inches
Typ.
Max.
0.069
0.010
0.065
0.020
0.010
0.197
0.122
2.41
1.270
0.157
0.095
0.050
6.200
0.500
1.270
8d
0.100
0.228
0.010
0.016
0d
0.244
0.020
0.050
8d
0.004
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consequences of use of such information nor for any infringement of patents or other rights of third parties which may result from
its use. No license is granted by implication or otherwise under any patent or patent rights of STMicroelectronics. Specifications
mentioned in this publication are subject to change without notice. This publication supersedes and replaces all information
previously supplied. STMicroelectronics products are not authorized for use as critical components in life support devices or
systems without express written approval of STMicroelectronics.
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