TK83361M

TK83361M NARROW BAND FM IF IC FEATURES n Wide Operating Voltage Range 2.0 to 8.0V n RF Input Frequency up to 220 MHz n Low Supply Current (2.8mA, squelch off, 3.8mA, n n squelch on) Low External Component Count Excellent Limiting Sensitivity (-3dB = 8dBµ ) APPLICATIONS n n n n n Amateur Radio Transceivers Cordless Phones Remote Controls Wireless Data Transceivers Battery Powered Devices DESCRIPTION The TK83361M is a narrow band FM IF IC designed for cordless phones, radio transceivers, remote controls, wireless data transceivers, and other communication equipment. It integrates the mixer, oscillator, limiting amplifier, FM demodulator, filter amplifier and squelch circuit into a single surface mount SOP-16 package. The low operating current combined with a minimum operating voltage of only 2 V makes this device ideal for battery powered devices. The TK83361M offers improved performance over the MC3361C. The operating frequency has been increased to 220MHz (vs. 60MHz) while reducing the supply current from 5.2 mA to 3.8mA (squelch on). Offered in the SOP-16 surface mount package, the TK83361M is a drop-in replacement for the MC3361C. TK83361M OSC (B) 1 16 RF INPUT OSC (E) 2 15 GND MIXER OUT 3 14 SCAN CONTROL VCC 4 13 SCAN CONTROL IF INPUT 5 12 SQUELCH INPUT 11 FILTER AMP OUTPUT 10 FILTER AMP INPUT 9 AF OUTPUT DECOUPLE 6 DECOUPLE 7 QUAD COIL 8 BLOCK DIAGRAM ORDERING INFORMATION OSC (B) 1 OSC MIXER 16 RF INPUT TK83361M Tape/Reel Code OSC (E) 2 GND 15 GND MIXER OUT 3 SQUELCH 14 SCAN CONTROL VCC 4 VCC 13 SCAN CONTROL TAPE/REEL CODE TL: Tape Left IF INPUT 5 12 SQUELCH INPUT 11 FILTER AMP OUTPUT 10 FILTER AMP INPUT 10pF QUAL DET DECOUPLE 6 LIMIT AMP FILTER AMP DECOUPLE 7 QUAD COIL 8 9 AF OUTPUT December 2000 TOKO, Inc. Page 1 TK83361M ABSOLUTE MAXIMUM RATINGS Supply Voltage ........................................................ 10 V Operating Voltage ......................................... 2.0 to 8.0 V Power Dissipation (Note 1) ................................ 600 mW Storage Temperature Range ................... -55 to +150 °C Operating Temperature Range .................. -30 to +70 °C Input Frequency ............................................... 220 MHz TK83361M ELECTRICAL CHARACTERISTICS Test Conditions: VCC = 4.0 V, fRF = 10.7 MHz, VRF = +80dBµ, fm = 1kHz, fdev = ±3kHz, fOSC = 10.245MHz, Ta = 25°C, unless otherwise specified. SYMBOL ICC1 ICC2 Limit VO ZO THD GM RIM Gf fOC SH SL SH SL HYS PARAMETER Supply Current 1 Supply Current 2 -3dB Limiting Sensitivity Output Voltage Output Impedance Total Harmonic Distortion Mixer Conversion Gain Mixer Input Impedance Filter Amplifier Gain Filter Amplifier Output Terminal Voltage Scan Control High Level Scan Control Low Level Scan Control High Level Scan Control Low Level Squelch Hysteresis TEST CONDITIONS No Signal, Squelch off No Signal, Squelch on -3dB pt.(1kHz) VRF = +80dBµ, fdev = ±3kHz VRF = +80dBµ, fdev = ±3kHz VRF = +80dBµ, fdev = ±3kHz Pin 3: terminated DC Measurement fin = 10kHz, Vin = 0.3mV No Signal Squelch Input VSQ = 0.0V Squelch Input VSQ = 2.5V Squelch Input VSQ = 2.5V Squelch Input VSQ = 0.0V MIN TYP 2.8 3.8 8 MAX 3.5 4.9 15 UNITS mA mA dBµ mVrms Ω 130 170 450 0.86 2.5 % dB kΩ dB 21 28 3.3 40 0.5 3.0 50 0.7 3.9 0.0 0.4 0.9 V V V V 3.0 3.9 0.0 45 0.4 100 V mV Note 1: Power dissipation must be decreased at a rate of 4.8 mW/°C for operation above 25°C. Page 2 December 2000 TOKO, Inc. TK83361M TEST CIRCUIT 10.245MHz 1 33pF 10µF + 0.1µF CF VCC 0.01µF MIXER OSC 2 GND 15 16 50Ω 100k Ω VCC 120pF 3 SQUELCH 4 VCC 13 14 10k Ω 5 0.1µF 6 0.1µF 7 LIMIT AMP FILTER AMP 12 1µF + 11 470k Ω 1µF + 510Ω 10 10pF CF = BLFC455D (TOKO) CFU455D2 (MURATA) QUAD COIL = 7MCS-13546Z 20k Ω 8 QUAD COIL 9 QUAD DET 8.2k Ω 0.01µF TYPICAL PERFORMANCE CHARACTERISTICS 9 - 1. Mixer + IF Section VO(DET), AMR, N, THD vs. VO(DET), OUTPUT LEVEL, AMR, AM REJECTION AND N, NOISE (dBV) VO(DET), AMR, N, THD vs. VO(DET), Output Level, AMR, AM REJECTION AND N, NOISE (dBV) -10 -20 -30 -40 -50 -60 -70 RF INPUT SIGNAL LEVEL VO(DET) V =4.0V cc f =10.7MHz RF f =1kHz, f =±3kHz m dev fOSC=10.245MHz AMR(mod=30%) 7.0 6.0 5.0 4.0 3.0 2.0 1.0 THD, TOTAL HARMONIC DISTORTION(%) -10 -20 -30 -40 -50 -60 -70 RF INPUT SIGNAL LEVEL VO(DET) V =4.0V cc f =455kHz IF f =1kHz, f =±3kHz m dev 7.0 6.0 5.0 4.0 3.0 2.0 N THD, TOTAL HARMONIC DISTORTION(%) AMR (MOD.=30%) THD N THD 1.0 -80 0.0 -20 ±0 +20 +40 +60 +80 +100 +120 VRF, RF INPUT SIGNAL LEVEL (dB µ) TRANSIENT RESPONSE -80 0.0 -20 ±0 +20 +40 +60 +80 +100 +120 VIF, IF INPUT SIGNAL LEVEL (dB µ) 20dB NQS vs. RF INPUT FREQUENCY 4.0 SUPPLY VOLTAGE, OUTPUT LEVEL (V) VCC 1kHz±3kHz Non-mod RELATIVE 20dB NQ SENSITIVITY(dB) 3.5 3.0 2.5 2.0 1.5 1.0 0.5 fRF = 10.7MHz f m = 1kHz fdev = ±3kHz fOSC = 10.245MHz VOSC = ±0dBm 0 -20 -40 -60 0 -20 -40 -60 -20 -15 -10 -5 ±0 +5 +10 +15 +20 fRF±∆f RF, RF INPUT FREQUENCY(kHz) 20dB NQS = 18.0dB µ fRF = 58MHz fOSC = 58.545MHz 20dB NQS = 17.5dB µ fRF = 10.7MHz fOSC = 10.245MHz 0.0 -0.5 0.0 0.5 1.0 1.5 2.0 2.5 3.0 3.5 4.0 τR, RISE TIME (msec) December 2000 TOKO, Inc. Page 3 TK83361M TYPICAL PERFORMANCE CHARACTERISTICS (CONT.) 9 - 2. Mixer Section 32 GM, MIXER CONVERSION GAIN (dB) MIXER INPUT FREQUENCY RESPONSE 30 28 VOMR, RELATIVE MIXER OUTPUT LEVEL (dB) 0 -2 -4 -6 -8 -10 -12 -14 -16 -18 -20 MIXER OUTPUT FREQUENCY RESPONSE 26 VCC = 4.0V fRF VARIABLE VRF = +60dB µ fOM = 455kHz VOSC = ±0dBm VCC = 4.0V fRF = 10.7MHz VRF = +60dB µ fOSC VARIABLE VOSC = ±0dBm 24 22 1M 10M 100M 1G fRF, RF INPUT FREQUENCY (Hz) THE 3rd ORDER INTERCEPT POINT 100k 1M 10M fOM, MIXER OUTPUT FREQUENCY (Hz) SINAD, GM S/N vs. LOCAL OSC INPUT SIGNAL LEVEL VOM, MIXER OUTPUT LEVEL (dB µ) IIP3 = 107dB µ SINAD, 12dB SINAD SENSITIVITY (dB µ) S/N, signal to noise ratio (dB) 140 120 100 80 60 60 SINAD 35 GM 1st ORDER DESIRED fRF = 10.7MHz 50 40 30 S/N 30 25 20 fRF = 10.7MHz 21MHz 58MHz 83MHz GM, MIXER CONVERSION GAIN(dB) 40 20 3rd ORDER INTERMOD fRF1 = 10.7125MHz fRF2 = 10.725MHz 20 10 15 10 20 40 60 80 100 120 VRF, RF INPUT SIGNAL LEVEL (dB µ) 9 - 3. IF Section OUTPUT LEVEL, TOTAL HARMONIC DISTORTION vs. IF INPUT FREQUENCY 10.0 -10 V O(DET) 0 -70 -60 -50 -40 -30 -20 -10 0 10 20 0 VOSC, LOCAL OSC INPUT SIGNAL LEVEL (dB µ) OUTPUT DC VOLTAGE vs. IF INPUT FREQUENCY VO(DC), OUTPUT DC VOLTAGE (V) 4.0 3.5 3.0 2.5 2.0 1.5 1.0 RD VO(DET), OUTPUT LEVEL(dBV) -20 -30 -40 -50 VCC = 4.0V VIF = ±80dB µ f m = 1kHz fdev =±3kHz 8.0 6.0 VCC = 4.0V VIF = +80dB µ THD, TOTAL HARMONIC DISTORTION(%) 4.0 2.0 THD VCC RD = 5k Ω QUAD COIL RD = 10k Ω RD = 20k Ω .5 8 -60 0.0 -40 -30 -20 -10 ±0 +10 +20 +30 +40 455±∆f IF, IF INPUT FREQUENCY (kHz) 0 -80 -60 -40 -20 ±0 +20 +40 +60 +80 455±∆f IF, IF INPUT FREQUENCY (kHz) Page 4 December 2000 TOKO, Inc. TK83361M TYPICAL PERFORMANCE CHARACTERISTICS (CONT.) OUTPUT LEVEL, TOTAL HARMONIC DISTORTION vs. IF DEVIATION FREQUENCY OUTPUT LEVEL vs. IF MODULATION FREQUENCY 6.0 VO(DET)R, RELATIVE OUTPUT LEVEL (dB) VO(DET), OUTPUT LEVEL(mVrms) 600 500 400 300 200 VO(DET) VCC =4.0V fIF = 455kHz VIF = +80dB µ f m = 1kHz ±0 RD = 20k Ω 10k Ω 5.0 4.0 3.0 2.0 1.0 THD THD, TOTAL HARMONIC DISTORTION(%) -10 5k Ω -20 VCC -30 -40 100 0 VCC =4.0V fIF = 455kHz VIF = +80dB µ fdev = ±3kHz Pin 9: open RD QUAD COIL 8 0 1 2 3 4 5 6 7 8 9 10 fdev., IF DEVIATION FREQUENCY (kHz) 0.0 100 1k 10k 100k 1M f m , IF MODULATION FREQUENCY (HZ) INPUT LEVEL RESPONSE 10 Vout , OUTPUT LEVEL(Vrms) 9 - 4. Filter Amplifer Section GAIN vs. INPUT FREQUENCY Gf , FILTER AMPLIFIER GAIN (dB) 70 60 50 40 30 20 10 0 1k 10k 100k 1M fin , FILTER AMPLIFIER INPUT FREQUENCY (Hz) 11 Rf 100 THD VCC = 4.0V Vin = 0.3mV R1 = 510Ω Rf = 470k Ω THD, TOTAL HARMONIC DISTORTION(%) 1 VOUT 10.0 1µF + 100m 1µF + 10 R1 VCC = 4.0V Fin = 10kHz R1 = 510Ω Rf = 470k Ω 1.0 10m 0.1 1 10 0.1 100 Vin , INPUT LEVEL(mVrms) 9 - 5. Squelch Section SCAN CONTROL vs. SQUELCH INPUT VOLTAGE 4.0 SC SC SC, SC, SCAN CONTROL(V) 3.5 3.0 2.5 2.0 1.5 1.0 VCC = 4.0V 0 .60 .65 .70 .75 .80 VSQ, SQUELCH INPUT VOLTAGE(V) December 2000 TOKO, Inc. Page 5 TK83361M TYPICAL PERFORMANCE CHARACTERISTICS (CONT.) 9 - 6. Versus Supply Voltage Characteristics SUPPLY CURRENT, 12dB SINAD SENSITIVITY, MIXER CONVERSION GAIN vs. SUPPLY VOLTAGE 9.0 ICC, SUPPLY CURRENT(mA) 8.0 7.0 6.0 5.0 4.0 3.0 2.0 1.0 0.0 1 2 34 5 67 8 VCC, SUPPLY VOLTAGE(V) 9 SINAD ICC1: sq on ICC2: sq off GM 18 16 14 12 10 8 6 4 2 0 36 0 OUTPUT LEVEL, TOTAL HARMONIC DISTORTION, SIGNAL TO NOISE RATIO, OUTPUT DC VOLTAGE vs. SUPPLY VOLTAGE S/N SINAD, 12dB SINAD SENSITIVITY(dB µ) 7 6 70 60 32 28 24 20 16 12 8 4 0 GM, MIXER CONVERSION GAIN(dB) S/N, SIGNAL TO NOISE RATIO (dB) VO(DET), OUTPUT LEVEL(dBV) -5 -10 -15 -20 -25 VO(DET) THD(%),VO(DC)(V) 5 4 VO(DC) 50 40 30 20 10 0 3 2 THD -30 -35 1 2 34 5 67 8 VCC, SUPPLY VOLTAGE(V) 9 1 0 MIXER OUTPUT LEVEL vs. SUPPLY VOLTAGE VTH, VTL , THRESHGf , FILTER OLD VOLTAGE(V) AMP. GAIN(dB) VOM, MIXER OUTPUT LEVEL(dB µ) 140 120 100 80 60 40 20 20 40 60 80 100 VRF, RF INPUT SIGNAL LEVEL(dB µ) 120 VCC = 8.5V 4.0V 2.0V FILT. AMP. GAIN, FILT. AMP. OUTPUT DC VOLTAGE, THRESHOLD VOLTAGE, HYSTERESIS vs. SUPPLY VOLTAGE 70 1.0 60 50 40 0.8 0.6 0.4 0.2 0.0 1 2 34 5 6 7 8 VCC, SUPPLY VOLTAGE(V) 9 VTH VTL HYS Gf fOC fOC, OUTPUT DC VOLTAGE HYS, SQUELCH HYSTERESIS(mV) 0.8 0.6 0.4 120 90 60 30 0 Page 6 December 2000 TOKO, Inc. TK83361M TYPICAL PERFORMANCE CHARACTERISTICS (CONT.) 9 - 7. Versus Ambient Temperature Characteristics SUPPLY CURRENT, 12dB SINAD SENSITIVITY, MIXER CONVERSION GAIN vs. AMBIENT TEMPERATURE 9 18 GM OUTPUT LEVEL, TOTAL HARMONIC DISTORTION, SIGNAL TO NOISE RATIO, OUTPUT DC VOLTAGE vs. AMBIENT TEMPERATURE SINAD, 12dB SINAD SENSITIVITY(dB µ) 36 32 28 24 20 16 12 8 4 0 0 7 6 S/N 70 60 50 40 30 20 10 0 GM, MIXER CONVERSION GAIN(dB) S/N, SIGNAL TO NOISE RATIO (dB) ICC, SUPPLY CURRENT(mA) 8 7 6 5 4 3 2 1 16 14 12 VO(DET), OUTPUT LEVEL(dBV) -5 -10 -15 -20 -25 -30 -35 VO(DC) VO(DET) 5 4 3 2 1 THD(%),VO(DC)(V) SINAD ICC2: sq off 10 8 6 ICC1: sq on 4 2 THD 0 0 -40 -20 0 20 40 60 80 100 Ta, AMBIENT TEMPERATURE (°C) 0 -40 -20 0 20 40 60 80 100 Ta, AMBIENT TEMPERATURE(°C) MIXER OUTPUT LEVEL vs. AMBIENT TEMPERATURE VOM, MIXER OUTPUT LEVEL(dB µ) 140 Gf , FILTER AMP. GAIN(dB) 120 100 80 60 40 20 20 40 60 80 100 VRF, RF INPUT SIGNAL LEVEL(dB µ) 120 Ta = +25°C +85°C -40°C 70 60 50 40 0.8 0.6 0.4 0.2 0.0 FILT. AMP. GAIN, FILT. AMP. OUTPUT DC VOLTAGE, THRESHOLD VOLTAGE, HYSTERESIS vs. AMBIENT TEMP. Gf 1.0 0.8 0.6 fOC, OUTPUT DC HYS, SQUELCH VOLTAGE(V) HYSTERESIS(mV) VTH fOC 0.5 120 VTH, VTL , THRESHOLD VOLTAGE(V) VTL 90 60 HYS 30 0 -40 -20 0 20 40 60 80 100 Ta, AMBIENT TEMPERATURE(°C) December 2000 TOKO, Inc. Page 7 TK83361M PIN FUNCTION DESCRIPTION PIN SYMBOL TERMINAL VOLTAGE (V) INTERNAL EQUIVALENT CIRCUIT DESCRIPTION 1 OSC(B) VCC The base of the Colpitts oscillator. The Colpitts oscillator is composed of Pin 1 and Pin 2. The emitter of the Colpitts oscillator. Using an external OSC source, local level must be injected into Pin 1, and Pin 2 must be opened. Output of the Mixer. VCC 4 1 2 OSC(E) 2 3 4 MIXER OUT VCC Supply Voltage. 3 5 IF INPUT VCC Input to the IF limiter amplifier. This pin is terminated by internal 1.8kW resistor. 1.8k 51.8K 50K 5 6 7 DECOUPLE DECOUPLE IF Decoupling. IF Decoupling 6 7 8 QUAD COIL 10p VCC Phase Shifter. 8 9 AF OUTPUT VCC Recovered Audio Output 10p 9 Page 8 December 2000 TOKO, Inc. TK83361M PIN FUNCTION DESCRIPTION (CONT.) PIN SYMBOL TERMINAL VOLTAGE (V) INTERNAL EQUIVALENT CIRCUIT DESCRIPTION Filter Amplifier Input. 10 FILTER AMPLIFIER INPUT 10 VCC 11 FILTER AMPLIFIER OUTPUT Filter Amplifier Output. VCC 11 12 SQUELCH INPUT Squelch Input. VCC 13 SCAN CONTROL 12 20k 13 Scan Control. 14 14 SCAN CONTROL Scan Control. 15 16 GND VCC 3.3K Ground Mixer Input. 3.3K 16 RF INPUT 15 December 2000 TOKO, Inc. Page 9 TK83361M TEST BOARD Figure 1: Solder Side View (Circuit Side View) Figure 2: Component Placement View NOTES: 1. Above test board is laid out for the TEST CIRCUIT (page 3). 2. Scale 1:1 (60mmx60mm) 3. 10.245MHz Fundamental mode crystal, about 30pF load. 4. 455kHz CF, TOKO Type BLFC455D or MURATA Type CFU455D2 or equivalent. 5. COIL, TOKO Type 7MCS-13546Z or 7MC-8128Z or equivalent. APPLICATIONS INFORMATION 12-1. Mixer Section The mixer consists of a Gilbert cell and a local oscillator. The mixer conversion gain, when Pin 4 is terminated, is 28dB. The RF input is unbalanced. 12-1-1. A Local OSC The oscillator included is a general Colpitts type OSC. The drive current of OSC is 200µA. Examples of components are shown in Fig. 3. The examples are explained in the next paragraph. Figure 3: Oscillator Components i) Under Crystal Control VCC ii) Parallel LC Components VCC 1 1 2 2 Page 10 December 2000 TOKO, Inc. TK83361M APPLICATIONS INFORMATION (CONT.) (1) Using an External Oscillator Source The circuit composition using an external OSC source is shown in Fig. 4. When using an external OSC source instead of the internal OSC, the local level must be injected into Pin 1 by capacitor coupling. In this case, Pin 2 must be open. The local OSC operates as an emitter follower for a multiplier by opening Pin 2 and injecting into Pin 1. Figure 4: External Injection VCC tor. It is easy to increase the drive current by connecting resistor Re between Pin 2 and GND. Being short of drive current, it makes gm increase to increase the drive current by connecting external resistor Re. In that case, the amount of drive current increase, Ie, is shown in Eq.(1). V VBE V 0.7 Ie = CC = CC Re Re (1) 50Ω ~ 0.01µ 1 50Ω open RF IF 2 (2) For 3rd Overtone mode In general, a crystal oscillator can oscillate in the fundamental mode and overtone mode. For example, it is easy for a 30MHz-overtone crystal to oscillate at 10MHz, fundamental mode. The reason is because the impedance of the fundamental mode is the same as the impedance of the overtone. Therefore, it is necessary for the circuit to select the overtone frequency by using a tuning coil. How to oscillate a general 3rd overtone oscillator is explained. In the case of an overtone mode of 30MHz and higher, using a crystal oscillator, we recommend the circuit in Fig. 5 to suppress the fundamental mode oscillation. Figure 5: Overtone Mode Circuit VCC In order to oscillate at the 3rd overtone frequency, the values of C2, C3 and L (Fig.5) are selected. Fig.6 shows a 2-port impedance response of the C2~C3~L loop network. Regarding the condition of oscillation, the impedance characteristic is capacitive at the vacinity of the overtone frequency. It is reactive at the vicinity of the fundamental frequency. The condition of oscillation is as follows: fOSC is between fa and fb, 3 x fOSC is fb and higher. Please see Fig.6 Figure 6: 2-port Impedance Response of Resonance Network +j fOSC fa fb 3 X f OSC -j Where: fa: series resonant freq. fb: parallel resonant freq. fOSC: fundamental mode freq. 3 x fOSC: 3rd order overtone freq. Equations of 3rd order overtone oscillation are shown below. Reactance fa = 1 , 2π L xC2 fb = fa C 1+ 2 C3 (2) The series value of the equivalent capacitance at the 3rd 1 order overtone freq. of this network, which is decided in the above -mentioned, and the capacitance of C1 must be equal C1 C2 L 2 to load capacitance CL. C3 Being short of negative resistance of the circuit, increase the transistor’s bias current by decreasing Re. It is able to Re decide the OSC level for minute adjusting Re. Please refer the most suitable OSC level range to 12dB SINAD sensitivity versus local OSC input signal level in TYPICAL PERThe following explains how to decide the circuit constants of FORMANCE CHARACTERISTICS. The saturating range the overtone-crystal-oscillation fundamental circuit. is the most suitable OSC level range. It is comparatively As the operating frequency increases the oscillation ampli- easy to decide the circuit constant by examining it with a tude decreases because of a shortage of gm of the oscilla- network analyzer. X’tal December 2000 TOKO, Inc. Page 11 TK83361M APPLICATIONS INFORMATION (CONT.) 12-2. IF Section The IF section includes a 6 stage differential amplifier. The fixed internal input matching resistor is 1.8kΩ. The total gain of the limiting amplifier section is approximately 77dB. The decoupling capacitors of Pin 6~7 must be connected as near as possible to the GND pin of the IC . And, make the impedance of the connecting-to-GND line to be as small as possible. If the impedance is not small enough, the sensitivities may worsen. Figure 7: IF Limiter Amplifier Input Block 12-3-2. Phase Shifter The IF signal from the limiter amplifier is provided with 90° phase shift and drives the quadrature detector. The parallel RCL resonance circuit is capable of using the internal 10pF phase shift capacitor. 12-3-3. Audio Output After quadrature detection, the audio signal is pulled out through Pin 9. The required signal is pulled out through the LPF. 12-3-4. For Stable Operation To prevent worsening the distortion, observe the following notes: (1) Demodulated Output Voltage Too large of a demodulated output voltage will worsen the distortion due to the dynamic range of the demodulator. (2) The Signal Level in Phase Shifter (Pin 8) If the phase shifter signal level is too small, the noise level grows worse. This will cause the distortion to grow worse. (3) Band Width of Phase Shifter (Pin 8) If the bandwidth of the phase shifter is narrower than IF bandwidth, including the demodulated element, the distortion will grow worse. 12-4. Filter Amplifier Section An inverting op amp has an output at Pin 11 and the inverting input at Pin 10. The op amp, which has a wide stable operating temperature range, may be used as an active noise filter. 12-4-1. Active BPF Application An active BPF application is shown in Fig. 9, and its Response is shown in Fig. 10. Note at this point to add the bias voltage at Pin 8 from external source. The signal from the phase shifter is put into the multiplier cell through the emitter follower of transistor Q1. Pin 8 is singleconnected with the base terminal. And, it is necessary for Pin 8 to add the same voltage, as the base terminal of Q2 of the opposite side of Q1 through the multiplier is connected with the supply voltage. If the base voltages differ between transistors Q1 and Q2, it alters the DC zero point or worsens the distortion of the demodulation output. 50K 5 1.8k 51.8K 6 7 12-3. FM Demodulator A quadrature FM demodulator using a Gilbert cell is included. 12-3-1. Internal Equivalent Circuit The internal equivalent circuit is shown in Fig. 8. Figure 8: Internal Equivalent Circuit of Demodulator VCC QUAD COIL RD 8 VCC Active Load VCC Q1 Q2 from IF LIM AMP 10pF Multiplier Cell Page 12 December 2000 TOKO, Inc. TK83361M APPLICATIONS INFORMATION (CONT.) Figure 9. Active BPF VTH indicates the Hi threshold voltage, VTL indicates the Lo threshold voltage in Fig. 11. 12-6. Application Example R1 VIN ~ R2 C R3 XTAL NETWORK Figure 10. Frequency Response 20 GAIN (dB) 15 10 5 0 NARROW BAND BPF VCC = 4.0V Vin = 50mV R1 = 18k Ω R2 = 750Ω R3 = 390k Ω C = 0.001µF 1k 10k 100k fin , FILTER AMPLIFIER INPUT FREQUENCY (Hz) VCC PHASE SHIFTER Eq. (3) is formularized, where G0 is the gain at center frequency f0, and 3dB bandwidth Q=f0/BW. R3 R1R3 Q , R2 = , R3 = πf 0C 2G0 4Q2R1-R3 R1 = 12-5. Squelch Section The output, which is controlled in accordance with the noise level from the rectifier, is injected into the squelch input pin. There is about 45mV of hysteresis at the Squelch Input to prevent jitter. Figure 11. Squelch Output versus Squelch Input i) Pin 13 Output Scan Control(V) ii) Pin 14 Output Scan Control(V) VTL VTH VSQ(V) December 2000 TOKO, Inc. + VTL VTH VSQ(V) C VOUT Figure 12: Application Example Block Digram RF INPUT 1 OSC 2 MIXER 16 GND 15 MUTE 3 SQUELCH 4 VCC 14 SCAN CONTROL to PLL 13 RECTIFIER 5 0.1µF 6 LIMIT AMP 12 0.1µF 7 FILTER AMP NETWORK 11 10 10pF 8 QUAD DET 9 LPF (3) AF OUTPUT 12-7. Attentions to Layout Design As this product is considered for stable operation, the mixer block and the other block that includes IF stage, OP amp and squelch are independent from each other. However in order to realize stable operation, please pay attention to the following, because of high frequency operation. (1) Bypass Capacitor A bypass capacitor must be connected with minimum distance between the VCC pin and the GND pin. (2) VCC/GND Pattern In order to make low impedance VCC/GND lines, please keep the pattern as wide as possible. (3) Pattern near Demodulator Pattern layout around the phase shifter for demodulator: please keep as short as possible. Page 13 TK83361M NOTES WARNING - Life support applications policy. TOKO, Inc. products shall not be used within any life support systems without the specific written consent of TOKO, Inc. A life support system is a product or system intended to support or sustain life which, if it fails, can be reasonably expected to result in a significant personal injury or death. The contents of this application as of December 2000. The contents of this datasheet are subject to change without notice or stop manufacture. The circuits shown in this specification are intended to explain typical applications of the products concerned. Accordingly, TOKO, Inc. is not responsible for any circuit problems, or for any infringement of third party patents or any other intellectual property rights that may arise from the use of these circuits. Moreover, this specification dose not signify that TOKO, Inc. agrees implicitly or explicitly to license any patent rights or other intellectual property rights which it holds. No Ozone Depleting Substances (ODS) were used in the manufacture of these parts. Examples of characteristics given here are typical for each product and being technical data, these do not constitute a guarantee of characteristics or conditions of use. Page 14 December 2000 TOKO, Inc. TK83361M PACKAGE OUTLINE Marking Information Marking 0.76 TOKO Mark 16 Mark 9 SOP-16 TK83361M 83361 1.27 YYY 1 8 Lot No. 3.9±0.2 1.27 Recommended Mount Pad 9.9±0.2 ±0.2 0 ~ 0.25 1.45 1.75 max 0.5±0.2 0.4 -0.05 +0.15 0.1 1.27 0 ~ 10 0.12 M Dimensions are shown in millimeters Tolerance: x.x = ± 0.2 mm (unless otherwise specified) 6.0±0.3 Toko America, Inc. Headquarters 1250 Feehanville Drive, Mount Prospect, Illinois 60056 Tel: (847) 297-0070 Fax: (847) 699-7864 TOKO AMERICA REGIONAL OFFICES Midwest Regional Office Toko America, Inc. 1250 Feehanville Drive Mount Prospect, IL 60056 Tel: (847) 297-0070 Fax: (847) 699-7864 Western Regional Office Toko America, Inc. 2480 North First Street , Suite 260 San Jose, CA 95131 Tel: (408) 432-8281 Fax: (408) 943-9790 Semiconductor Technical Support Toko Design Center 4755 Forge Road Colorado Springs, CO 80907 Tel: (719) 528-2200 Fax: (719) 528-2375 Visit our Internet site at http://www.tokoam.com The information furnished by TOKO, Inc. is believed to be accurate and reliable. However, TOKO reserves the right to make changes or improvements in the design, specification or manufacture of its products without further notice. TOKO does not assume any liability arising from the application or use of any product or circuit described herein, nor for any infringements of patents or other rights of third parties which may result from the use of its products. No license is granted by implication or otherwise under any patent or patent rights of TOKO, Inc. December 2000 TOKO, Inc. © 2000 Toko, Inc. All Rights Reserved IC-231-TK11031 0798O0.0K 0.2 -0.05 +0.15 5.4 Page 15 Printed in the USA