AD706ARZ-REEL7

Dual Picoampere Input Current Bipolar Op Amp AD706 Data Sheet CONNECTION DIAGRAM FEATURES High DC Precision 100
V Max Offset Voltage 1.5
V/C Max Offset Drift 200 pA Max Input Bias Current 0.5
V p-p Voltage Noise, 0.1 Hz to 10 Hz 750
A Supply Current Available in 8-Lead PDlP and Surface-Mount (SOIC) Packages Available in Tape and Reel in Accordance with EIA-481A Standard Quad Version: AD704 PDIP (N) and Plastic SOIC (R) Packages AMPLIFIER 1 AMPLIFIER 2 AD706 OUTPUT 1 8 V –IN 2 7 OUTPUT IN 3 6 –IN V– 5 IN 4 TOP VIEW APPLICATIONS Low Frequency Active Filters Precision Instrumentation Precision Integrators GENERAL DESCRIPTION PRODUCT HIGHLIGHTS The AD706 is a dual, low power, bipolar op amp that has the low input bias current of a JFET amplifier, but which offers a significantly lower IB drift over temperature. It utilizes superbeta bipolar input transistors to achieve picoampere input bias current levels (similar to FET input amplifiers at room temperature), while its IB typically only increases by 5⫻ at 125°C (unlike a JFET amp, for which IB doubles every 10°C for a 1000⫻ increase at 125°C). The AD706 also achieves the microvolt offset voltage and low noise characteristics of a precision bipolar input amplifier. 1. The AD706 is a dual low drift op amp that offers JFET level input bias currents, yet has the low IB drift of a bipolar amplifier. It may be used in circuits using dual op amps such as the LT1024. The AD706 is an excellent choice for use in low frequency active filters in 12-bit and 14-bit data acquisition systems, in precision instrumentation, and as a high quality integrator. The AD706 is internally compensated for unity gain and is available in five performance grades. The AD706J is rated over the commercial temperature range of 0°C to +70°C. The AD706A is rated for the extended industrial temperature range of –40°C to +85°C. The AD706 is offered in two varieties of an 8-lead package: PDIP and surface-mount (SOIC). Rev. G Document Feedback One Technology Way, P.O. Box 9106, Norwood, MA 02062-9106, U.S.A. Tel: 781.329.4700 ©2002–2017 Analog Devices, Inc. All rights reserved. Technical Support www.analog.com 2. The AD706 provides both low drift and high dc precision. 3. The AD706 can be used in applications where a chopper amplifier would normally be required but without the chopper’s inherent noise. 100 10 TYPICAL IB – nA Since it has < 200 pA of bias current, the AD706 does not require the commonly used “balancing” resistor. Furthermore, the current noise is only 50 fA/√Hz, which makes this amplifier usable with very high source impedances. At 600 ␮A max supply current (per amplifier), the AD706 is well suited for today’s high density boards. Dual Picoampere Input Current Bipolar Op Amp AD706 Data Sheet Rev. F Information furnished by Analog Devices is believed to be accurate and reliable. However, no responsibility is assumed by Analog Devices for its use, nor for any infringements of patents or other rights of third parties that may result from its use. Specifications subject to change without notice. No license is granted by implication or otherwise under any patent or patent rights of Analog Devices. Trademarks and registered trademarks are the property of their respective owners. TYPICAL JFET AMP 1 0.1 AD706 0.01 –55 +25 +110 TEMPERATURE – C +125 Figure 1. Input Bias Current vs. Temperature Document Feedback Information furnished by Analog Devices is believed to be accurate and reliable. However, no responsibility is assumed by Analog Devices for its use, nor for any infringements of patents or other rights of third parties that may result from its use. Specifications subject to change without notice. No license is granted by implication or otherwise under any patent or patent rights of Analog Devices. Trademarks and registered trademarks are the property of their respective owners. One Technology Way, P.O. Box 9106, Norwood, MA 02062-9106, U.S.A. Tel: 781.329.4700 ©2002–2018 Analog Devices, Inc. All rights reserved. Technical Support www.analog.com AD706–SPECIFICATIONS (@ T = +25C, V A Parameter INPUT OFFSET VOLTAGE Initial Offset Offset vs. Temperature, Average TC vs. Supply (PSRR) TMIN to TMAX Long Term Stability INPUT BIAS CURRENT1 vs. Temperature, Average TC TMIN to TMAX TMIN to TMAX INPUT OFFSET CURRENT vs. Temperature, Average TC TMIN to TMAX TMIN to TMAX CM = 0 V and 15 V dc, unless otherwise noted.) Conditions Min TMIN to TMAX VS = ± 2 V to ± 18 V VS = ± 2.5 V to ± 18 V 110 106 VCM = 0 V VCM = ± 13.5 V AD706J/A Typ Max Unit 30 40 0.2 132 126 0.3 100 150 1.5 µV µV µV/°C dB dB µV/Month 50 200 250 pA pA pA/°C pA pA 0.3 VCM = 0 V VCM = ± 13.5 V 300 400 VCM = 0 V VCM = ± 13.5 V 30 0.6 80 80 VCM = 0 V VCM = ± 13.5 V MATCHING CHARACTERISTICS Offset Voltage Input Bias Current2 TMIN to TMAX 106 106 106 104 TMIN to TMAX Power Supply Rejection FREQUENCY RESPONSE Unity Gain Crossover Frequency Slew Rate TMIN to TMAX @ f = 10 Hz RL = 2 kΩ G = –1 TMIN to TMAX INPUT IMPEDANCE Differential Common Mode INPUT VOLTAGE RANGE Common-Mode Voltage Common-Mode Rejection Ratio 250 350 150 250 300 500 TMIN to TMAX Common-Mode Rejection Crosstalk (Figure 2a) 150 250 VCM = ± 13.5 V TMIN to TMAX ± 13.5 110 108 pA pA pA/°C pA pA µV µV pA pA dB dB dB dB 150 dB 0.8 0.15 0.15 MHz V/µs V/µs 40||2 300||2 MΩ||pF GΩ||pF ± 14 132 128 V dB dB INPUT CURRENT NOISE 0.1 Hz to 10 Hz f = 10 Hz 3 50 pA p-p fA/√Hz INPUT VOLTAGE NOISE 0.1 Hz to 10 Hz f = 10 Hz f = 1 kHz 0.5 17 15 µV p-p nV/√Hz nV/√Hz OPEN-LOOP GAIN OUTPUT CHARACTERISTICS Voltage Swing Current Capacitive Load Drive Capability VO = ± 12 V RLOAD = 10 kΩ TMIN to TMAX VO = ± 10 V RLOAD = 2 kΩ TMIN to TMAX RLOAD = 10 kΩ TMIN to TMAX Short Circuit Gain = +1 –2– 22 200 150 2000 1500 V/mV V/mV 200 150 1000 1000 V/mV V/mV ± 13 ± 13 ± 14 ± 14 ± 15 10,000 V V mA pF REV. G AD706 SPECIFICATIONS (continued) Parameter Conditions AD706J/A Typ Min POWER SUPPLY Rated Performance Operating Range Quiescent Current, Total ± 15 ± 2.0 TRANSISTOR COUNT TMIN to TMAX 0.75 0.8 Number of Transistors 90 Max Unit ± 18 1.2 1.4 V V mA mA NOTES 1 Bias current specifications are guaranteed maximum at either input. 2 Input bias current match is the difference between corresponding inputs (I B of –IN of Amplifier 1 minus I B of –IN of Amplifier 2). CMRR match is the difference between PSRR match is the difference between ∆VOS1 ∆VCM for Amplifier 1 and ∆VOS1 ∆VSUPPLY ∆VOS2 ∆VCM for Amplifier 1 and for Amplifier 2, expressed in dB. ∆VOS2 ∆VSUPPLY for Amplifier 2, expressed in dB. All min and max specifications are guaranteed. Specifications subject to change without notice. ESD CAUTION ABSOLUTE MAXIMUM RATINGS 1 Supply Voltage . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . ± 18 V Internal Power Dissipation (Total: Both Amplifiers)2 . . . . . . . . . . . . . . . . . . . . 650 mW Input Voltage . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . ± VS Differential Input Voltage3 . . . . . . . . . . . . . . . . . . . . . . +0.7 V Output Short Circuit Duration . . . . . . . . . . . . . . . . Indefinite Storage Temperature Range (N, R) . . . . . . . –65°C to +125°C Operating Temperature Range AD706J . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 0°C to +70°C AD706A . . . . . . . . . . . . . . . . . . . . . . . . . . . . –40°C to +85°C Lead Temperature (Soldering 10 secs) . . . . . . . . . . . . . 300°C METALIZATION PHOTOGRAPH NOTES 1 Stresses above those listed under Absolute Maximum Ratings may cause permanent damage to the device. This is a stress rating only; functional operation of the device at these or any other conditions above those indicated in the operational section of this specification is not implied. Exposure to absolute maximum rating conditions for extended periods may affect device reliability. 2 Specification is for device in free air: 8-Lead PDIP Package: θJA = 100°C/W 8-Lead Small Outline Package: θJA = 155°C/W 3 The input pins of this amplifier are protected by back-to-back diodes. If the differential voltage exceeds ± 0.7 V, external series protection resistors should be added to limit the input current to less than 25 mA. Dimensions shown in inches and (mm). Contact factory for latest dimensions. OUTPUT A 1 0.118 (3.00) –INPUT A 2 7 +INPUT A 3 –VS 4 6 5 0.074 (1.88) REV. G +VS 8 –3– OUTPUT B –INPUT B +INPUT B AD706–Typical Performance Characteristics (Default Conditions: 5 V, CL = 5 pF, G = 2, Rg = Rf = 1 kΩ, RL = 2 kΩ, VO = 2 V p-p, Frequency = 1 MHz, TA = 25C) 1000 1000 SAMPLE SIZE: 3000 400 800 NUMBER OF UNITS 600 600 400 200 200 –80 TPC 1. Typical Distribution of Input Offset Voltage –80 0 80 160 INPUT BIAS CURRENT – pA –120 TPC 2. Typical Distribution of Input Bias Current VS –1.5 1.5 1.0 0.5 –VS 5 10 15 SUPPLY VOLTAGE – Volts 30 25 20 15 10 5 0 1k 20 TPC 4. Input Common-Mode Voltage Range vs. Supply Voltage 100 OFFSET VOLTAGE DRIFT –
V/C OUTPUT VOLTAGE – Volts p-p –1.0 10k 100k FREQUENCY – Hz 80 40 3 2 1 0 0 –0.8 –0.4 0 0.4 0.8 OFFSET VOLTAGE DRIFT –
V/C TPC 7. Typical Distribution of Offset Voltage Drift FOR INDUSTRIAL TEMPERATURE RANGE 1.0 10k 100k 1M 10M SOURCE RESISTANCE –  100M 60 INPUT BIAS CURRENT – pA 120 CHANGE IN OFFSET VOLTAGE –
V 160 10 TPC 6. Offset Voltage Drift vs. Source Resistance 4 SAMPLE SIZE: 375 –55C TO 125C SOURCE RESISTANCE MAY BE EITHER BALANCED OR UNBALANCED 0.1 1k 1M TPC 5. Large Signal Frequency Response 200 –60 0 60 120 INPUT OFFSET CURRENT – pA TPC 3. Typical Distribution of Input Offset Current 35 –0.5 0 400 0 –160 –40 0 40 80 INPUT OFFSET VOLTAGE –
V 600 200 0 0 INPUT COMMON-MODE VOLTAGE LIMIT – Volts (REFERRED TO SUPPLY VOLTAGES) SAMPLE SIZE: 2400 800 NUMBER OF UNITS NUMBER OF UNITS 800 NUMBER OF UNITS 1000 SAMPLE SIZE: 5100 0 1 2 3 4 WARM-UP TIME – Minutes TPC 8. Change in Input Offset Voltage vs. Warm-Up Time –4– 5 40 20 POSITIVE IB 0 –20 –40 –60 –15 NEGATIVE IB –10 –5 0 5 10 15 COMMON-MODE VOLTAGE – Volts TPC 9. Input Bias Current vs. Common-Mode Voltage REV. G AD706 1000 CURRENT NOISE – fA/冪Hz 10 100 10 FREQUENCY – Hz 100 20M 10 VOUT 1 1000 CMRR – dB QUIESCENT CURRENT –
A 900 160 180 160 120 140 100 120 –55C 600 5 10 15 SUPPLY VOLTAGE –  Volts OPEN-LOOP VOLTAGE GAIN – dB OPEN-LOOP VOLTAGE GAIN –55C +25C +125C 1M 2 4 6 8 10 LOAD RESISTANCE – k 100 TPC 16. Open-Loop Gain vs. Load Resistance vs. Load Resistance REV. G – PSRR 80 60 20 40 1 10 20 0.1 100 1k 10k 100k 1M FREQUENCY – Hz TPC 14. Common-Mode Rejection Ratio vs. Frequency 10M 1 100 40 0 0.1 20 TPC 13. Quiescent Supply Current vs. Supply Voltage 100k 80 60 + PSRR 700 0 10 TPC 12. 0.1 Hz to 10 Hz Noise Voltage 140 +25C 5 TIME – Seconds 0 1000 TPC 11. Input Noise Current Spectral Density 1000 +125C 100 10 FREQUENCY – Hz 1 TPC 10. Input Noise Voltage Spectral Density 800 10k 140 0 +VS 120 30 –0.5 100 60 PHASE 80 90 60 120 150 40 GAIN 20 180 0 210 –20 0.01 0.1 1 240 10 100 1k 10k 100k 1M 10M FREQUENCY – Hz TPC 17. Open-Loop Gain and Phase Shift vs. Frequency –5– 1 10 100 1k 10k 100k 1M FREQUENCY – Hz TPC 15. Power Supply Rejection Ratio vs. Frequency (REFERRED TO SUPPLY VOLTAGES) 1 0.5
V OUTPUT VOLTAGE SWING – Volts 1 100 PSRR – dB 100 PHASE SHIFT – Degrees VOLTAGE NOISE – nV/冪Hz 1000 –1.0 –1.5 +1.5 +1.0 +0.5 –VS 0 5 10 15 SUPPLY VOLTAGE –  Volts 20 TPC 18. Output Voltage Swing vs. Supply Voltage AD706 1000 CLOSED-LOOP OUTPUT IMPEDANCE –  –80 CROSSTALK – dB –100 –120 –140 100 10 AV = –1000 1 AV = + 1 0.1 0.01 IOUT = +1mA 0.001 –160 10 100 1k FREQUENCY – Hz 10k 100k 1 Figure 2a. Crosstalk vs. Frequency 10 100 1k FREQUENCY – Hz 10k 100k Figure 3. Magnitude of Closed-Loop Output Impedance vs. Frequency +VS 0.1
F 2 1/2 AD706 3 4 RF VOUT1 1 20V p-p +VS 0.1
F RL 2k SINE WAVE GENERATOR 0.1
F 8 –VS VOUT 1/2 AD706 VIN 4 RL 2k 20k +VS 0.1
F 1
F 2.21k 6 CL SQUARE WAVE INPUT 0.1
F –VS 8 1/2 AD706 Figure 4a. Unity Gain Follower (For large signal applications, resistor RF limits the current through the input protection diodes.) VOUT2 7 5 CROSSTALK = 20 LOG10 VOUT2 VOUT1 –20dB Figure 2b. Crosstalk Test Circuit Figure 4b. Unity Gain Follower Large Signal Pulse Response, RF = 10 kΩ, CL = 1,000 pF Figure 4c. Unity Gain Follower Small Signal Pulse Response, RF = 0 Ω, CL = 100 pF –6– Figure 4d. Unity Gain Follower Small Signal Pulse Response, RF = 0 Ω, CL = 1000 pF REV. G AD706 10k +VS + 0.1
F 10k – VIN 8 VOUT 1/2 AD706 SQUARE WAVE INPUT RL 2.5k 4 + CL 0.1µF –VS Figure 5a. Unity Gain Inverter Connection Figure 5b. Unity Gain Inverter Large Signal Pulse Response, CL = 1,000 pF Figure 5c. Unity Gain Inverter Small Signal Pulse Response, CL = 100 pF CMR is still dependent upon the ratio matching of Resistors R1 through R4. Resistor values for this circuit, using the optional gain resistor, RG, can be calculated using Figure 6 shows an in-amp circuit that has the obvious advantage of requiring only one AD706, rather than three op amps, with subsequent savings in cost and power consumption. The transfer function of this circuit (without RG) is VOUT = (VIN1 Figure 5d. Unity Gain Inverter Small Signal Pulse Response, CL = 1000 pF R1= R4 = 49.9 kΩ 49.9 kΩ R2 = R3 = 0.9 G −1 99.8 kΩ RG = 0.06 G R4   − VIN2 )  1 +   R3 for R1 = R4 and R2 = R3. Input resistance is high, thus permitting the signal source to have an unbalanced output impedance. where G = The desired circuit gain. Table I provides practical 1% resistance values. Note that without resistor RG, R2 and R3 = 49.9 kΩ/G–1. R RG (OPTIONAL) G (OPTIONAL) R1 R1 R2 R2 49.9k 49.9k R3 R3 R4 R4 0.1 F 0.1
F 22 V VIN1 IN1 V VIN2 IN2 R RPP** 1k 1k R RPP** 1k 1k 33 –– + + Table I. Operating Gains of Amplifiers A1 and A2 and Practical 1% Resistor Values for the Circuit of Figure 6 49.9k 49.9k +V +VSS 1/2 1/2 88 A1 A1 1/2 1/2 11 AD706 AD706 55 +– 66 –+ R4 2R4 V VOUT = (V (VIN1 –V VIN2 (1+ R4 )) ++ (( 2R4 )) OUT = IN1 – IN2)) (1+ R3 R R3 RG G FOR FOR R1 R1 = = R4, R4, R2 R2 == R3 R3 AD706 AD706 A2 A2 –V –VSS 44 77 OUTPUT OUTPUT 0.1 F 0.1
F * OPTIONAL INPUT PROTECTION RESISTOR FOR GAINS GREATER *OPTIONAL INPUT PROTECTION RESISTOR FOR GAINS GREATER THAN 100 100 OR INPUT VOLTAGES EXCEEDING THE SUPPLY THAN OR INPUT VOLTAGES EXCEEDING THE SUPPLYVOLTAGE. VOLTAGE. Gain of A1 Gain of A2 R2, R3 R1, R4 1.10 1.33 1.50 2.00 10.1 101.0 1001 11.00 4.01 3.00 2.00 1.11 1.01 1.001 49.9 kΩ 49.9 kΩ 49.9 kΩ 49.9 kΩ 49.9 kΩ 49.9 kΩ 49.9 kΩ 1.10 1.33 1.50 2.00 10.10 101.0 1001 499 kΩ 150 kΩ 100 kΩ 49.9 kΩ 5.49 kΩ 499 Ω 49.9 Ω For a much more comprehensive discussion of in-amp applications, refer to the Instrumentation Amplifier Applications Guide— available free from Analog Devices, Inc. Figure 6. Two Op Amp Instrumentation Amplifier Furthermore, the circuit gain may be fine trimmed using an optional trim resistor, RG. Like the three op amp circuit, CMR increases with gain, once initial trimming is accomplished—but REV. G Circuit Gain –7– AD706 R1 1M C1 R2 1M + 3 INPUT 1/2 C2 AD706 2 *WITHOUT THE NETWORK, PINS 1 AND 2, AND 6 AND 7 OF THE AD706 ARE TIED TOGETHER. CAPACITORS C1 AND C2 ARE SOUTHERN ELECTRONICS MPCC, POLYCARB 5%, 50V – +VS C3 R3 1M 1 0.1
F R4 1M 5 + C4 4 8 1/2 7 AD706 6 0.1
F OUTPUT – –VS R5 2M R6 2M C5 0.01
F C6 0.01
F OPTIONAL BALANCE RESISTOR NETWORKS* OFFSET VOLTAGE OF FILTER CIRCUIT (RTI) –
V Figure 7. 1 Hz, 4-Pole Active Filter 1 Hz, 4-Pole, Active Filter Figure 7 shows the AD706 in an active filter application. An important characteristic of the AD706 is that both the input bias current, input offset current, and their drift remain low over most of the op amp’s rated temperature range. Therefore, for most applications, there is no need to use the normal balancing resistor. Adding the balancing resistor enhances performance at high temperatures, as shown by Figure 8. 180 WITHOUT OPTIONAL BALANCE RESISTOR, R3 120 60 0 WITH OPTIONAL BALANCE RESISTOR, R3 –60 –120 –180 –40 0 40 80 TEMPERATURE – C 120 Figure 8. VOS vs. Temperature Performance of the 1 Hz Filter Table II. 1 Hz, 4-Pole, Low Pass Filter Recommended Component Values Desired Low Pass Response Section 1 Frequency (Hz) Bessel Butterworth 0.1 dB Chebychev 0.2 dB Chebychev 0.5 dB Chebychev 1.0 dB Chebychev 1.43 1.00 0.648 0.603 0.540 0.492 Q Section 2 Frequency (Hz) Q C1 (
F) C2 (
F) C3 (
F) C4 (
F) 0.522 0.541 0.619 0.646 0.705 0.785 1.60 1.00 0.948 0.941 0.932 0.925 0.806 1.31 2.18 2.44 2.94 3.56 0.116 0.172 0.304 0.341 0.416 0.508 0.107 0.147 0.198 0.204 0.209 0.206 0.160 0.416 0.733 0.823 1.00 1.23 0.0616 0.0609 0.0385 0.0347 0.0290 0.0242 NOTE Specified Values are for a –3 dB point of 1.0 Hz. For other frequencies simply scale capacitors C1 through C4 directly, i.e. for 3 Hz Bessel response, C1 = 0.0387 µF, C2 = 0.0357 µF, C3 = 0.0533 µF, C4 = 0.0205 µF. –8– REV. G AD706 Data Sheet OUTLINE DIMENSIONS 0.400 (10.16) 0.365 (9.27) 0.355 (9.02) 8 5 1 4 0.280 (7.11) 0.250 (6.35) 0.240 (6.10) 0.100 (2.54) BSC 0.325 (8.26) 0.310 (7.87) 0.300 (7.62) 0.060 (1.52) MAX 0.210 (5.33) MAX 0.015 (0.38) MIN 0.150 (3.81) 0.130 (3.30) 0.115 (2.92) SEATING PLANE 0.022 (0.56) 0.018 (0.46) 0.014 (0.36) 0.195 (4.95) 0.130 (3.30) 0.115 (2.92) 0.015 (0.38) GAUGE PLANE 0.014 (0.36) 0.010 (0.25) 0.008 (0.20) 0.430 (10.92) MAX 0.005 (0.13) MIN 0.070 (1.78) 0.060 (1.52) 0.045 (1.14) 070606-A COMPLIANT TO JEDEC STANDARDS MS-001 CONTROLLING DIMENSIONS ARE IN INCHES; MILLIMETER DIMENSIONS (IN PARENTHESES) ARE ROUNDED-OFF INCH EQUIVALENTS FOR REFERENCE ONLY AND ARE NOT APPROPRIATE FOR USE IN DESIGN. CORNER LEADS MAY BE CONFIGURED AS WHOLE OR HALF LEADS. Figure 9. 8-Lead Plastic Dual-in-line Package [PDIP] Narrow Body (N-8) Dimensions shown in inches and (millimeters) 5.00 (0.1968) 4.80 (0.1890) 1 5 6.20 (0.2441) 5.80 (0.2284) 4 1.27 (0.0500) BSC 0.25 (0.0098) 0.10 (0.0040) COPLANARITY 0.10 SEATING PLANE 1.75 (0.0688) 1.35 (0.0532) 0.51 (0.0201) 0.31 (0.0122) 0.50 (0.0196) 45° 0.25 (0.0099) 8° 0° 0.25 (0.0098) 0.17 (0.0067) 1.27 (0.0500) 0.40 (0.0157) COMPLIANT TO JEDEC STANDARDS MS-012-AA CONTROLLING DIMENSIONS ARE IN MILLIMETERS; INCH DIMENSIONS (IN PARENTHESES) ARE ROUNDED-OFF MILLIMETER EQUIVALENTS FOR REFERENCE ONLY AND ARE NOT APPROPRIATE FOR USE IN DESIGN. 012407-A 8 4.00 (0.1574) 3.80 (0.1497) Figure 10. 8-Lead Standard Small Outline Package [SOIC_N] Narrow Body (R-8) Dimensions shown in millimeters and (inches) ORDERING GUIDE Model AD706AR AD706ARZ AD706ARZ-REEL AD706ARZ-REEL7 AD706JNZ AD706JRZ AD706JRZ-REEL AD706JRZ-REEL7 REV. G Temperature Range −40°C to +85°C −40°C to +85°C −40°C to +85°C −40°C to +85°C 0°C to + 70°C 0°C to + 70°C 0°C to + 70°C 0°C to + 70°C Package Description 8-Lead SOIC_N 8-Lead SOIC_N 8-Lead SOIC_N, 13” Tape and Reel 8-Lead SOIC_N, 7” Tape and Reel 8-Lead PDIP 8-Lead SOIC_N 8-Lead SOIC_N, 13”Tape and Reel 8-Lead SOIC_N, 7” Tape and Reel – 9– Package Option R-8 R-8 R-8 R-8 N-8 R-8 R-8 R-8 Data Sheet AD706 REVISION HISTORY 7/2018—Rev. F to Rev. G Changed Plastic Mini-DIP to PDIP ................................. Universal Updated Outline Dimensions ........................................................10 8/2017—Rev. E to Rev. F Changes to Figure 6........................................................................... 6 Updated Outline Dimensions ........................................................10 Changes to Ordering Guide ...........................................................10 10/2003—Rev. D to Rev. E Removed K Version ........................................................... Universal Changes to Features and Product Description .............................. 1 Renumbered TPC’s ........................................................................... 4 Renumbered Figured ........................................................................ 6 Updated Outline Dimensions .......................................................... 9 10/2002—Rev. C to Rev. D Deleted 8-Lead CERDIP (Q-8) Package ......................... Universal Changes to Features and Product Description .............................. 1 Changes to Specifications Section................................................... 2 Changes to Absolute Maximum Ratings Section.......................... 3 Changes to Ordering Guide ............................................................. 3 Updated Outline Dimensions ........................................................15 ©2018 Analog Devices, Inc. All rights reserved. Trademarks and registered trademarks are the property of their respective owners. D00820-0-7/18(G) Rev. G | Page 10 of 10