ADC3643IRSBT

ADC3643 ADC3643 SBAS886 – OCTOBER 2020 SBAS886 – OCTOBER 2020 www.ti.com ADC364x 14-bit, 10-MSPS to 65-MSPS, Low-Noise, Low Power Dual Channel ADC 1 Features 3 Description • • • • The ADC364x family of devices are low-noise, ultralow power, 14-bit, 10-MSPS to 65-MSPS dualchannel, high-speed analog-to-digital converters (ADCs). Designed for low power consumption, these devices deliver a noise spectral density of –155 dBFS/Hz, combined with excellent linearity and dynamic range. The ADC364x offers very good dc precision, together with IF sampling support, which make the device an excellent choice for a wide range of applications. High-speed control loops benefit from the short latency of only one clock cycle. The ADC consumes only 72 mW/ch at 65 MSPS, and power consumption scales well with lower sampling rates. • • • • • • • • • • • Dual channel 14-bit 10/25/65 MSPS ADC Noise floor: –155 dBFS/Hz Ultra-low power with optimized power scaling: 29 mW/ch (10 MSPS) to 72 mW/ch (65 MSPS) Latency: 1 clock cycle 14-Bit, no missing codes INL: ±0.6 LSB; DNL: ±0.2 LSB Reference: external or internal Industrial temperature range: –40°C to +105°C On-chip digital filter (optional) – Decimation by 2, 4, 8, 16, 32 – 32-bit NCO DDR and Serial CMOS interface Small footprint: 40-VQFN (5 mm × 5 mm) package Single 1.8-V supply Spectral performance (fIN = 5 MHz): – SNR: 79.0 dBFS – SFDR: 93-dBc HD2, HD3 – SFDR: 101-dBFS worst spur Spectral performance (fIN = 64 MHz): – SNR: 74.0 dBFS – SFDR: 84-dBc HD2, HD3 – SFDR: 90-dBFS worst spur The ADC364x use a DDR or serial CMOS interface to output the data offering lowest power digital interface, together with flexibility to minimize the number of digital interconnects. These devices are a pin-to-pin compatible family with different speed grades. These devices support the extended industrial temperature range of –40 to +105⁰C. Device Information ADC364x (1) VQFN (40) High-speed data acquisition Industrial monitoring Thermal imaging Imaging and sonar Software defined radio Power quality Communications infrastructure High-speed control loops Instrumentation Smart grids Spectroscopy Radar Source measurement unit (SMU) GPS receiver Sonar Substation automation BODY SIZE (NOM) 5.00 × 5.00 mm For all available packages, see the package option addendum at the end of the data sheet. 2 Applications • • • • • • • • • • • • • • • • PACKAGE(1) PART NUMBER Device Comparison PART NUMBER RESOLUTION SAMPLING RATE ADC3643 14 BIT 65 MSPS ADC3642(1) 14 BIT 25 MSPS ADC3641(1) 14 BIT 10 MSPS (1) Product Preview REFBUF 1.2V REF Digital Downconverter VREF Crosspoint Switch NCO ADC 14bit AIN N DCLK VCM 0.95V Dig I/F CMOS NCO DA0..6 DB0..6 BIN ADC 14bit N CLK ADC364x Block Diagram An IMPORTANT NOTICE at the end of this data sheet addresses availability, warranty, changes, use in safety-critical applications, Copyright © 2020 Texas Instruments Incorporated Submit contains Document Feedback intellectual property matters and other important disclaimers. UNLESS OTHERWISE NOTED, this document PRODUCTION DATA. Product Folder Links: ADC3643 1 ADC3643 www.ti.com SBAS886 – OCTOBER 2020 Table of Contents 1 Features............................................................................1 2 Applications..................................................................... 1 3 Description.......................................................................1 4 Revision History.............................................................. 2 5 Pin Configuration and Functions...................................3 6 Specifications.................................................................. 5 6.1 Absolute Maximum Ratings ....................................... 5 6.2 ESD Ratings .............................................................. 5 6.3 Recommended Operating Conditions ........................5 6.4 Thermal Information ...................................................5 6.5 Electrical Characteristics - Power Consumption ........ 6 6.6 Electrical Characteristics - DC Specifications ............ 7 6.7 Electrical Characteristics - AC Specifications ADC3641 ......................................................................9 6.8 Electrical Characteristics - AC Specifications ADC3642 ....................................................................10 6.9 Electrical Characteristics - AC Specifications ADC3643 .................................................................... 11 6.10 Timing Requirements ............................................. 12 6.11 Typical Characteristics - ADC3643......................... 14 7 Parameter Measurement Information.......................... 19 8 Detailed Description......................................................21 8.1 Overview................................................................... 21 8.2 Functional Block Diagram......................................... 21 8.3 Feature Description...................................................22 8.4 Device Functional Modes..........................................42 8.5 Programming............................................................ 43 8.6 Register Maps...........................................................45 9 Application and Implementation.................................. 61 9.1 Typical Application.................................................... 61 10 Initialization Set Up..................................................... 64 10.1 Register Initialization During Operation.................. 64 11 Power Supply Recommendations..............................65 12 Layout...........................................................................67 12.1 Layout Guidelines................................................... 67 12.2 Layout Example...................................................... 67 13 Device and Documentation Support..........................68 13.1 Receiving Notification of Documentation Updates..68 13.2 Support Resources................................................. 68 13.3 Trademarks............................................................. 68 13.4 Electrostatic Discharge Caution..............................68 13.5 Glossary..................................................................68 14 Mechanical, Packaging, and Orderable Information.................................................................... 68 4 Revision History NOTE: Page numbers for previous revisions may differ from page numbers in the current version. 2 DATE REVISION NOTES October 2020 * Initial release. Submit Document Feedback Copyright © 2020 Texas Instruments Incorporated Product Folder Links: ADC3643 ADC3643 www.ti.com SBAS886 – OCTOBER 2020 GND BINP BINM GND AVDD SCLK DB0 DB1 DB2 DB3 5 Pin Configuration and Functions 40 39 38 37 36 35 34 33 32 31 PDN/SYNC 1 30 IOVDD VREF 2 29 DB4 REFGND 3 28 DB5 REFBUF 4 27 DB6 AVDD 5 26 IOGND CLKP 6 25 DCLK CLKM 7 24 DA6 VCM 8 23 DA5 RESET 9 22 DA4 21 IOVDD GND PAD (backside) 13 14 15 16 17 18 AINM GND AVDD SEN DA0 DA1 19 20 DA3 12 DA2 11 AINP 10 GND SDIO Figure 5-1. RSB Package, 40-Pin WQFN, Top View Table 5-1. Pin Functions PIN NAME NO. I/O DESCRIPTION INPUT/REFERENCE AINM 13 I Negative analog input, channel A AINP 12 I Positive analog input, channel A BINP 39 I Positive analog input, channel B BINM 38 I Negative analog input, channel B REFBUF 4 I 1.2V external voltage reference input for use with internal reference buffer. Internal 100 kΩ pull-up resistor to AVDD. This pin is also used to configure default operating conditions. REFGND 3 I Reference ground input VCM 8 O Common-mode voltage output for the analog inputs, 0.95V VREF 2 I External voltage reference input CLKM 7 I Negative differential sampling clock input for the ADC CLKP 6 I Positive differential sampling clock input for the ADC PDN/SYNC 1 I Power down/Synchronization input. This pin can be configured via the SPI interface. Active high. This pin has an internal 21 kΩ pull-down resistor. RESET 9 I Hardware reset. Active high. This pin has an internal 21 kΩ pull-down resistor. CLOCK CONFIGURATION Submit Document Feedback Copyright © 2020 Texas Instruments Incorporated Product Folder Links: ADC3643 3 ADC3643 www.ti.com SBAS886 – OCTOBER 2020 Table 5-1. Pin Functions (continued) PIN NAME NO. I/O DESCRIPTION SCLK 35 I Serial interface clock input. This pin has an internal 21 kΩ pull-down resistor. SDIO 10 I Serial interface data input and output. This pin has an internal 21 kΩ pull-down resistor. SEN 16 I Serial interface enable. Active low. This pin has an internal 21 kΩ pull-up resistor to AVDD. DIGITAL INTERFACE DA0 17 O CMOS digital data output. DA1 18 I/O CMOS digital data output. Used as FCLK frame clock output for serialized CMOS output modes. Configured using SPI. DA2 19 O CMOS digital data output. DA3 20 O CMOS digital data output. DA4 22 O CMOS digital data output. DA5 23 O CMOS digital data output. DA6 24 O CMOS digital data output. DB0 34 O CMOS digital data output. DB1 33 I/O CMOS digital data output. Used as DCLKIN bit clock input for serialized CMOS output modes. Configured using SPI. DB2 32 O CMOS digital data output. DB3 31 O CMOS digital data output. DB4 29 O CMOS digital data output. DB5 28 O CMOS digital data output. DB6 27 O CMOS digital data output. DCLK 25 O CMOS output for data bit clock. AVDD 5,15,36 I Analog 1.8-V power supply GND 11,14,37,40, PowerPAD I Ground, 0 V IOGND 26 I Ground, 0 V for digital interface IOVDD 21,30 I 1.8-V power supply for digital interface POWER SUPPLY 4 Submit Document Feedback Copyright © 2020 Texas Instruments Incorporated Product Folder Links: ADC3643 ADC3643 www.ti.com SBAS886 – OCTOBER 2020 6 Specifications 6.1 Absolute Maximum Ratings over operating free-air temperature range (unless otherwise noted)(1) PARAMETER TEST CONDITIONS MIN MAX UNIT Supply voltage range, AVDD, IOVDD –0.3 2.1 V Supply voltage range, GND, IOGND, REFGND –0.3 0.3 V AINP/M, BINP/M, CLKP/M, DB1 (DCLKIN) Voltage applied to VREF, REFBUF input pins PDN, RESET, SCLK, SEN, SDIO –0.3 2.1 –0.3 2.1 –0.3 2.1 Junction temperature, TJ Storage temperature, Tstg (1) V –65 105 °C 150 °C Stresses beyond those listed under Absolute Maximum Ratings may cause permanent damage to the device. These are stress ratings only, which do not imply functional operation of the device at these or any other conditions beyond those indicated under Recommended Operating Conditions. Exposure to absolute-maximum-rated conditions for extended periods may affect device reliability. 6.2 ESD Ratings VALUE V(ESD) (1) (2) Electrostatic discharge Human body model (HBM), per ANSI/ESDA/JEDEC JS-001, all pins(1) 2500 Charged device model (CDM), per JEDEC specification JESD22-C101, all pins(2) 1000 UNIT V JEDEC document JEP155 states that 500-V HBM allows safe manufacturing with a standard ESD control process. JEDEC document JEP157 states that 250-V CDM allows safe manufacturing with a standard ESD control process. 6.3 Recommended Operating Conditions over operating free-air temperature range (unless otherwise noted) Supply voltage range TA Operating free-air temperature TJ Operating junction temperature (1) (2) MIN NOM MAX UNIT AVDD(1) 1.75 1.8 1.85 V IOVDD(1) 1.75 1.8 1.85 V –40 105 °C 105(2) °C Measured to GND. Prolonged use above this junction temperature may increase the device failure-in-time (FIT) rate. 6.4 Thermal Information ADC364x THERMAL METRIC RSB (QFN) UNIT 40 Pins RΘJA Junction-to-ambient thermal resistance 30.7 °C/W RΘJC(top) Junction-to-case (top) thermal resistance 16.4 °C/W RΘJB Junction-to-board thermal resistance 10.5 °C/W ΨJT Junction-to-top characterization parameter 0.2 °C/W ΨJB Junction-to-board characterization parameter 10.5 °C/W RΘJC(bot) Junction-to-case (bottom) thermal resistance 2.0 °C/W Submit Document Feedback Copyright © 2020 Texas Instruments Incorporated Product Folder Links: ADC3643 5 ADC3643 www.ti.com SBAS886 – OCTOBER 2020 6.5 Electrical Characteristics - Power Consumption Typical values are over the operating free-air temperature range, at TA = 25°C, full temperature range is TMIN = –40°C to T = 105°C, ADC sampling rate = 65 MSPS, 50% clock duty cycle, AVDD, IOVDD = 1.8 V, external 1.6V reference, 5 pF output load, and –1-dBFS differential input, unless otherwise noted MAX PARAMETER TEST CONDITIONS MIN TYP MAX UNIT ADC3641 - 10 MSPS IAVDD Analog supply current current(1) IIOVDD I/O supply PDIS Power dissipation(1) IIOVDD I/O supply current(1) External reference DDR CMOS External reference, DDR CMOS 27 mA 5 58 Serial CMOS 2-wire TBD Serial CMOS 1-wire TBD 4x complex decimation, Serial CMOS 2-wire TBD mW mA ADC3642 - 25 MSPS IAVDD Analog supply current current(1) IIOVDD I/O supply PDIS Power dissipation(1) IIOVDD I/O supply current(1) External reference DDR CMOS External reference, DDR CMOS 31 mA 8 70 Serial CMOS 2-wire TBD 4x complex decimation, Serial CMOS 2-wire TBD mW mA ADC3643 - 65 MSPS IAVDD Analog supply current current(1) IIOVDD I/O supply PDIS Power dissipation(1) External reference 64 78 DDR CMOS 16 20 144 176 External reference, DDR CMOS 8x complex decimation, Serial CMOS 2-wire 19 16x complex decimation, Serial CMOS 1-wire 17 IIOVDD 32x complex decimation, Serial CMOS 1-wire 15 IIOVDD 32x complex decimation, Serial CMOS 1/2-wire 16 IIOVDD IIOVDD I/O supply current(1) mA mW mA MISCELLANEOUS Internal reference, additional analog supply current IAVDD External 1.2V reference (REFBUF), additional analog supply current Single ended clock input, reduces analog supply current by PDIS (1) 6 Power consumption in global power down mode FS = 10 MSPS 1 FS = 25 MSPS 1.5 FS = 65 MSPS 3 mA 0.3 Enabled via SPI 0.7 Default power down mask, internal reference 5 Default power down mask, external reference 9 mW Measured with a 2 MHz input frequency full-scale sine wave at specified sample rate, with ~ 5 pF loading on each CMOS output pin. Submit Document Feedback Copyright © 2020 Texas Instruments Incorporated Product Folder Links: ADC3643 ADC3643 www.ti.com SBAS886 – OCTOBER 2020 6.6 Electrical Characteristics - DC Specifications Typical values are over the operating free-air temperature range, at TA = 25°C, full temperature range is TMIN = –40°C to T MAX = 105°C, ADC sampling rate = 65 MSPS, 50% clock duty cycle, AVDD, IOVDD = 1.8 V, external 1.6V reference, 5 pF output load, and –1-dBFS differential input, unless otherwise noted PARAMETER TEST CONDITIONS MIN TYP MAX UNIT DC ACCURACY No missing codes PSRR 14 FIN = 1 MHz bits 50 dB ADC3641 - 10 MSPS: DC ACCURACY DNL Differential nonlinearity FIN = 5 MHz TBD ± 0.1 ± 0.25 LSB INL Integral nonlinearity FIN = 5 MHz TBD ± 0.6 ± 0.8 LSB VOS_ERR Offset error TBD 8 TBD VOS_DRIFT Offset drift over temperature TBD TBD 0.1 LSB LSB/ºC GAINERR Gain error External 1.6 V reference TBD 0.05 TBD %FSR GAINDRIFT Gain drift over temperature External 1.6 V reference TBD TBD 10 ppm/ºC GAINERR Gain error Internal reference TBD TBD TBD %FSR GAINDRIFT Gain drift over temperature Internal reference TBD TBD TBD dB Transition Noise 0.6 LSBRMS ADC3642 - 25 MSPS: DC ACCURACY DNL Differential nonlinearity FIN = 5 MHz TBD ± 0.1 ± 0.25 LSB INL Integral nonlinearity FIN = 5 MHz TBD ± 0.6 ± 0.8 LSB VOS_ERR Offset error TBD 8 TBD VOS_DRIFT Offset drift over temperature TBD TBD 0.1 LSB LSB/ºC GAINERR Gain error External 1.6 V reference TBD 0.05 TBD %FSR GAINDRIFT Gain drift over temperature External 1.6 V reference TBD TBD 10 ppm/ºC GAINERR Gain error Internal reference TBD TBD TBD %FSR GAINDRIFT Gain drift over temperature Internal reference TBD TBD TBD Transition Noise 0.6 dB LSBRMS ADC3643 - 65 MSPS: DC ACCURACY DNL Differential nonlinearity FIN = 5 MHz -0.35 ± 0.2 0.35 LSB INL Integral nonlinearity FIN = 5 MHz -1.25 ± 0.6 1.25 LSB VOS_ERR Offset error 35 0 35 LSB VOS_DRIFT Offset drift over temperature GAINERR Gain error External 1.6 V reference GAINDRIFT Gain drift over temperature External 1.6 V reference GAINERR Gain error Internal reference GAINDRIFT Gain drift over temperature Internal reference 131 ppm/ºC 0.6 LSBRMS 2.25 Vpp Transition Noise -1 LSB/ºC 0.6 %FSR -5 ppm/ºC 0.8 %FSR ADC ANALOG INPUT (AINP/M, BINP/M) FS Input full scale Default, differential VCM Input common mode voltage RIN Differential input resistance FIN = 100 kHz CIN Differential input capacitance FIN = 100 kHz VOCM Output common mode voltage BW Analog input bandwidth (-3dB) 900 MHz 0.9 0.95 1.0 V 8 Ω 7 pF 0.95 V Submit Document Feedback Copyright © 2020 Texas Instruments Incorporated Product Folder Links: ADC3643 7 ADC3643 www.ti.com SBAS886 – OCTOBER 2020 6.6 Electrical Characteristics - DC Specifications (continued) Typical values are over the operating free-air temperature range, at TA = 25°C, full temperature range is TMIN = –40°C to T MAX = 105°C, ADC sampling rate = 65 MSPS, 50% clock duty cycle, AVDD, IOVDD = 1.8 V, external 1.6V reference, 5 pF output load, and –1-dBFS differential input, unless otherwise noted PARAMETER TEST CONDITIONS MIN TYP MAX UNIT Internal Voltage Reference VREF Internal reference voltage VREF Output Impedance 1.6 V 8 Ω 1.2 V Reference Input Buffer (REFBUF) External reference voltage External voltage reference (VREF) 1.6 V Input Current VREF External voltage reference 0.3 mA Input impedance 5.3 kΩ Clock Input (CLKP/M) Input clock frequency 0.5 VID Differential input voltage 1 VCM Input common mode voltage RIN Single ended input resistance to common mode CIN Single ended input capacitance 65 MHz 3.6 Vpp 0.9 V 5 kΩ 1.5 Clock duty cycle 40 50 pF 60 % Digital Inputs (RESET, PDN, SCLK, SEN, SDIO) VIH High level input voltage VIL Low level input voltage IIH High level input current IIL Low level input current CI Input capacitance 1.4 0.4 90 -150 150 90 1.5 V uA pF Digital Output (SDOUT) VOH High level output voltage ILOAD = -400 uA VOL Low level output voltage ILOAD = 400 uA IOVDD – 0.1 IOVDD V 0.1 CMOS Interface (DA0:DA6, DB0:DB6) Output data rate 8 per CMOS output pin VOH High level output voltage ILOAD = -400 uA VOL Low level output voltage ILOAD = 400 uA VIH High level input voltage VIL Low level input voltage Input clock (Serial CMOS) 250 IOVDD – 0.1 IOVDD MHz V 0.1 IOVDD – 0.1 IOVDD V 0.1 Submit Document Feedback Copyright © 2020 Texas Instruments Incorporated Product Folder Links: ADC3643 ADC3643 www.ti.com SBAS886 – OCTOBER 2020 6.7 Electrical Characteristics - AC Specifications ADC3641 Typical values are over the operating free-air temperature range, at TA = 25°C, full temperature range is TMIN = –40°C to T MAX = 105°C, ADC sampling rate = 10 MSPS, external reference, 50% clock duty cycle, AVDD, IOVDD = 1.8 V, external 1.6V reference, 5 pF output load, and –1-dBFS differential input, unless otherwise noted PARAMETER TEST CONDITIONS MIN TYP MAX UNIT ADC3641: 10 MSPS NSD Noise Spectral Density SNR Signal to noise ratio fIN = 1.1 MHz, AIN = -20 dBFS -146.0 fIN = 1.1 MHz SINAD Signal to noise and distortion ratio fIN = 4.9 MHz 79.0 TBD 78.0 fIN = 1.1 MHz TBD TBD fIN = 9.9 MHz THD Effective number of bits Total Harmonic Distortion (First five harmonics) fIN = 4.9 MHz Non HD2,3 Spur free dynamic range including second and third harmonic distortion Spur free dynamic range (excluding HD2 and HD3) 12.6 fIN = 1.1 MHz TBD TBD fIN = 4.9 MHz Two tone inter-modulation distortion TBD 90 90 fIN = 1.1 MHz 95 f1 = 1 MHz, f2 = 2 MHz, AIN = -7 dBFS/ tone dBc 90 TBD fIN = 9.9 MHz fIN = 4.9 MHz bit TBD fIN = 1.1 MHz fIN = 9.9 MHz IMD3 12.8 fIN = 9.9 MHz fIN = 4.9 MHz dBFS 12.8 TBD fIN = 9.9 MHz SFDR TBD dBFS TBD fIN = 1.1 MHz ENOB 79.0 fIN = 9.9 MHz fIN = 4.9 MHz dBFS/Hz TBD 95 dBc dBFS 95 TBD dBc Submit Document Feedback Copyright © 2020 Texas Instruments Incorporated Product Folder Links: ADC3643 9 ADC3643 www.ti.com SBAS886 – OCTOBER 2020 6.8 Electrical Characteristics - AC Specifications ADC3642 Typical values are over the operating free-air temperature range, at TA = 25°C, full temperature range is TMIN = –40°C to T MAX = 105°C, ADC sampling rate = 25 MSPS, external reference, 50% clock duty cycle, AVDD, IOVDD = 1.8 V, external 1.6V reference, 5 pF output load, and –1-dBFS differential input, unless otherwise noted PARAMETER TEST CONDITIONS MIN TYP MAX UNIT ADC3642: 25 MSPS NSD Noise Spectral Density fIN = 1.1 MHz, AIN = -20 dBFS -151.0 fIN = 1.1 MHz fIN = 5 MHz SNR Signal to noise ratio Signal to noise and distortion ratio 79.0 TBD 78.4 fIN = 20 MHz 77.0 fIN = 40 MHz 76.0 fIN = 1.1 MHz TBD TBD TBD fIN = 20 MHz TBD fIN = 40 MHz TBD fIN = 5 MHz Effective number of bits Total Harmonic Distortion (First five harmonics) THD SFDR Spur free dynamic range including second and third harmonic distortion 12.7 12.5 fIN = 40 MHz 12.3 fIN = 1.1 MHz TBD TBD TBD fIN = 20 MHz TBD fIN = 40 MHz TBD fIN = 1.1 MHz 90 TBD Non HD2,3 IMD3 10 Two tone inter-modulation distortion 90 fIN = 20 MHz 88 fIN = 40 MHz 85 dBc 95 TBD 95 fIN = 10 MHz 95 fIN = 20 MHz 95 fIN = 40 MHz 95 f1 = 1 MHz, f2 = 2 MHz, AIN = -7 dBFS/ tone TBD f1 = 10 MHz, f2 = 12 MHz, AIN = -7 dBFS/tone TBD Submit Document Feedback dBc 90 fIN = 10 MHz fIN = 5 MHz bit TBD fIN = 10 MHz fIN = 1.1 MHz Spur free dynamic range (excluding HD2 and HD3) 12.8 fIN = 20 MHz fIN = 5 MHz dBFS 12.8 TBD fIN = 10 MHz fIN = 5 MHz dBFS TBD fIN = 10 MHz fIN = 1.1 MHz ENOB 79.0 fIN = 10 MHz fIN = 5 MHz SINAD dBFS/Hz dBFS dBc Copyright © 2020 Texas Instruments Incorporated Product Folder Links: ADC3643 ADC3643 www.ti.com SBAS886 – OCTOBER 2020 6.9 Electrical Characteristics - AC Specifications ADC3643 Typical values are over the operating free-air temperature range, at TA = 25°C, full temperature range is TMIN = –40°C to T MAX = 105°C, ADC sampling rate = 65 MSPS, external reference, 50% clock duty cycle, AVDD, IOVDD = 1.8 V, external 1.6V reference, 5 pF output load, and –1-dBFS differential input, unless otherwise noted PARAMETER TEST CONDITIONS MIN TYP MAX UNIT ADC3643: 65 MSPS NSD Noise Spectral Density fIN = 1.1 MHz, AIN = -20 dBFS -155.0 fIN = 1.1 MHz fIN = 5 MHz SNR Signal to noise ratio 79.0 77.0 79.0 fIN = 20 MHz 78.8 fIN = 40 MHz 77.0 fIN = 64 MHz 74.0 fIN = 1.1 MHz SINAD Signal to noise and distortion ratio Effective number of bits 78.9 fIN = 20 MHz 78.0 fIN = 40 MHz 76.0 fIN = 64 MHz 73.4 Total Harmonic Distortion (First five harmonics) 12.8 fIN = 20 MHz 12.8 fIN = 40 MHz 12.5 fIN = 64 MHz 12.0 Spur free dynamic range including second and third harmonic distortion Non HD2,3 IMD3 Spur free dynamic range (excluding HD2 and HD3) Two tone inter-modulation distortion 91 91 fIN = 20 MHz 85 fIN = 40 MHz 82 fIN = 64 MHz 81 fIN = 1.1 MHz 90 88 95 fIN = 20 MHz 88 fIN = 40 MHz 83 fIN = 64 MHz 84 fIN = 1.1 MHz 100 93 dBc 93 fIN = 10 MHz fIN = 5 MHz bit 88 84 fIN = 10 MHz fIN = 5 MHz SFDR 12.8 fIN = 10 MHz fIN = 5 MHz dBFS 12.8 12.4 fIN = 1.1 MHz THD 79.0 fIN = 10 MHz fIN = 5 MHz dBFS 79.0 76.2 fIN = 1.1 MHz ENOB 79.0 fIN = 10 MHz fIN = 5 MHz dBFS/Hz dBc 101 fIN = 10 MHz 98 fIN = 20 MHz 95 fIN = 40 MHz 94 fIN = 64 MHz 90 f1 = 10 MHz, f2 = 12 MHz, AIN = -7 dBFS/tone 92 dBFS dBc Submit Document Feedback Copyright © 2020 Texas Instruments Incorporated Product Folder Links: ADC3643 11 ADC3643 www.ti.com SBAS886 – OCTOBER 2020 6.10 Timing Requirements Typical values are over the operating free-air temperature range, at TA = 25°C, full temperature range is TMIN = –40°C to T MAX = 105°C, ADC sampling rate = 65 MSPS, 50% clock duty cycle, AVDD, IOVDD = 1.8 V, and –1-dBFS differential input, unless otherwise noted PARAMETER TEST CONDITIONS MIN NOM MAX UNIT ADC Timing Specifications tAD Aperture delay 0.85 tA Aperture jitter Square wave clock with fast edges tJ Jitter on DCLKIN Serial CMOS output mode Recory time from +6 dB overload condition Signal conversion period, referenced to sampling clock falling edge tCONV Time to valid data after coming out of power down. Internal reference. Wake up time Time to valid data after coming out of power down. External 1.6V reference. tS,SYNC Setup time for SYNC input signal tH,SYNC Hold time for SYNC input signal ADC Latency 180 FS = 10 Msps -TS/2 FS = 25 Msps -TS/2 FS = 65 Msps -TS/4 FS = 10 Msps +TS × 1/5 FS = 25 Msps +TS × 3/8 FS = 65 Msps +TS × 5/8 Bandgap reference enabled, single ended clock 14.6 Bandgap reference enabled, differential clock 14.0 Bandgap reference disabled, single ended clock 1.7 Bandgap reference disabled, differential clock 2.1 Bandgap reference enabled, single ended clock 14.6 Bandgap reference enabled, differential clock 14.0 Bandgap reference disabled, single ended clock 1.8 Bandgap reference disabled, differential clock 1.7 Add. Latency Sampling Clock Period Sampling Clock Period us ms us ms 500 ps 600 DDR CMOS 1 Serialized CMOS: 2-wire 2 Serialized CMOS: 1-wire 1 Serialized CMOS: 1/2-wire ps Clock cycle 1 Referenced to sampling clock rising edge Signal input to data output fs ± 50 SNR within 1 dB of expected value Signal acquisition period, referenced to sampling clock falling edge tACQ ns Clock cycles 1 Real decimation by 2 21 Complex decimation by 2 22 Real or complex decimation by 4, 8, 16, 32 23 Output clock cycles INTERFACE TIMING - PARALLEL DDR CMOS tPD Propagation delay: sampling clock falling edge to DCLK rising edge tCD DCLK rising edge to output data delay tDV Data valid, DDR CMOS 3 5 Fout = 10 MSPS -0.70 -0.32 Fout = 25 MSPS -0.68 -0.30 -0.31 Fout = 65 MSPS -0.73 Fout = 10 MSPS 49.35 49.93 Fout = 25 MSPS 19.66 19.77 Fout = 65 MSPS 12 Submit Document Feedback 7.42 7 ns ns ns 7.51 Copyright © 2020 Texas Instruments Incorporated Product Folder Links: ADC3643 ADC3643 www.ti.com SBAS886 – OCTOBER 2020 6.10 Timing Requirements (continued) Typical values are over the operating free-air temperature range, at TA = 25°C, full temperature range is TMIN = –40°C to T = 105°C, ADC sampling rate = 65 MSPS, 50% clock duty cycle, AVDD, IOVDD = 1.8 V, and –1-dBFS differential input, unless otherwise noted MAX PARAMETER TEST CONDITIONS MIN NOM MAX UNIT INTERFACE TIMING - SERIAL CMOS tPD Delay between sampling clock falling edge to DCLKIN falling edge < 2.5ns. 2+T 3+T 4+T TDCLK = DCLK period DCLK + DCLK + DCLK + tCDCLK = Sampling clock falling edge to tCDCLK tCDCLK tCDCLK DCLKIN falling edge Propagation delay: sampling clock falling edge to DCLK rising edge Delay between sampling clock falling edge to DCLKIN falling edge >= 2.5ns. TDCLK = DCLK period tCDCLK = Sampling clock falling edge to DCLKIN falling edge DCLK rising edge to output data delay, 2-wire serial CMOS tCD DCLK rising edge to output data delay, 1-wire series CMOS DCLK rising edge to output data delay, 1/2wire serial CMOS Data valid, 2-wire serial CMOS tDV 2+t 3+t 4+t CDCLK CDCLK CDCLK Fout = 10 MSPS, DA/B5,6 = 80 MBPS -0.24 0.10 Fout = 20 MSPS, DA/B5,6 = 160 MBPS -0.29 0.10 Fout = 30 MSPS, DA/B5,6 = 240 MBPS -0.28 0.09 Fout = 5 MSPS, DA/B6 = 80 MBPS -0.22 0.11 Fout = 10 MSPS, DA/B6 = 160 MBPS -0.27 0.11 Fout = 15 MSPS, DA/B6 = 240 MBPS -0.52 0.08 Fout = 5 MSPS, DA6 = 160 MBPS -0.24 0.10 Fout = 10 MSPS, DA/B5,6 = 80 MBPS 12.19 12.36 Fout = 20 MSPS, DA/B5,6 = 160 MBPS 5.93 6.1 Fout = 30 MSPS, DA/B5,6 = 240 MBPS 3.91 4.07 Fout = 5 MSPS, DA/B6 = 80 MBPS ns ns 12.21 12.39 Data valid, 1-wire serial CMOS Fout = 10 MSPS, DA/B6 = 160 MBPS 5.95 Fout = 15 MSPS, DA/B6 = 240 MBPS 3.83 4.08 Data valid, 1/2-wire serial CMOS Fout = 5 MSPS, DA6 = 160 MBPS 5.36 6.13 ns 6.1 SERIAL PROGRAMMING INTERFACE (SCLK, SEN, SDIO) - Input fCLK(SCLK) Serial clock frequency tSU(SEN) SEN to rising edge of SCLK tH(SEN) SEN from rising edge of SCLK tSU(SDIO) SDIO to rising edge of SCLK tH(SDIO) SDIO from rising edge of SCLK 20 MHz 10 9 ns 17 9 SERIAL PROGRAMMING INTERFACE (SDIO) - Output t(OZD) SDIO tri-state to driven 3.9 10.8 t(ODZ) SDIO data to tri-state 3.4 14 t(OD) SDIO valid from falling edge of SCLK 3.9 10.8 ns Submit Document Feedback Copyright © 2020 Texas Instruments Incorporated Product Folder Links: ADC3643 13 ADC3643 www.ti.com SBAS886 – OCTOBER 2020 6.11 Typical Characteristics - ADC3643 0 0 -20 -20 -40 -40 Amplitude (dBFS) Amplitude (dBFS) Typical values at T A = 25 °C, ADC sampling rate F S = 65 MSPS, AIN = –1 dBFS differential input, AVDD = IOVDD = 1.8 V, 65k FFT, external 1.6 V reference, 5 pF output load, unless otherwise noted. -60 -80 -60 -80 -100 -100 -120 -120 -140 -140 0 10 20 Input Frequency (MHz) 0 30 10 20 Input Frequency (MHz) 30 D002 D001 Figure 6-2. Single Tone FFT at FIN = 10 MHz 0 0 -20 -20 -40 -40 Amplitude (dBFS) Amplitude (dBFS) Figure 6-1. Single Tone FFT at FIN = 1.1 MHz -60 -80 -60 -80 -100 -100 -120 -120 -140 -140 0 10 20 Input Frequency (MHz) 0 30 10 20 Input Frequency (MHz) 30 D004 D003 Figure 6-4. Single Tone FFT at FIN = 40 MHz AIN = -20 dBFS 0 0 -20 -20 -40 -40 Amplitude (dBFS) Amplitude (dBFS) Figure 6-3. Single Tone FFT at FIN = 10 MHz -60 -80 -60 -80 -100 -100 -120 -120 -140 -140 0 10 20 Input Frequency (MHz) 30 0 10 20 Input Frequency (MHz) 30 D005 Figure 6-5. Single Tone FFT at FIN = 64 MHz 14 D006 Figure 6-6. Single Tone FFT at FIN = 90 MHz Submit Document Feedback Copyright © 2020 Texas Instruments Incorporated Product Folder Links: ADC3643 ADC3643 SBAS886 – OCTOBER 2020 0 0 -20 -20 -40 -40 Amplitude (dBFS) Amplitude (dBFS) www.ti.com -60 -80 -60 -80 -100 -100 -120 -120 -140 -140 0 10 20 Input Frequency (MHz) 30 0 10 20 Input Frequency (MHz) 30 D008 D009 AIN = -7 dBFS/tone AIN = -20 dBFS/tone Figure 6-7. Two Tone FFT at FIN = 10/12 MHz 85 13 Ext REF Int REF SNR, int REF SFDR, int REF Non HD23, int REF 12.8 105 SFDR, Non HD23 (dBc) SNR, ext REF SFDR, ext REF Non HD23, ext REF 83 12.6 81 100 79 95 77 90 75 85 12 80 70 11.8 73 0 10 20 30 40 50 Input Frequency (MHz) 60 ENOB (bit) SNR (dBFS) Figure 6-8. Two Tone FFT at FIN = 10/12 MHz 110 12.4 12.2 0 10 20 30 40 50 Input Frequency (MHz) 60 70 D021 D020 Figure 6-10. ENOB vs Input Frequency Figure 6-9. AC Performance vs Input Frequency 81.5 105 SNR SFDR SFDR Non HD23 80 110 79.5 105 79 100 75 80 60 79.5 45 30 -70 -60 -50 -40 -30 -20 Input Amplitude (dBFS) -10 0 78.5 95 78 90 77.5 85 77 10 15 20 25 30 35 40 45 50 ADC Sampling Rate (MSPS) D026 55 60 SFDR, Non HD23 (dBc) 80.5 SNR (dBFS) 90 SFDR, Non HD23 (dBc) SNR (dBFS) 115 SNR 81 79 -80 80.5 Non HD23 80 65 D029 FIN = 5 MHz FIN = 5 MHz Figure 6-11. AC Performance vs Input Amplitude Figure 6-12. AC Performance vs Sampling Rate Submit Document Feedback Copyright © 2020 Texas Instruments Incorporated Product Folder Links: ADC3643 15 ADC3643 www.ti.com SBAS886 – OCTOBER 2020 120 110 78.5 105 78 100 77.5 95 77 90 76.5 85 0.5 1 1.5 2 Clock Amplitude (Vpp) 2.5 100 SNR (dBFS) SINAD (dBFS) SFDR (dBc) 115 79 0 80 79.5 95 79 90 78.5 85 SNR/SINAD (dBFS) SNR (dBFS) 79.5 SNR, FIN = 10 MHz SFDR, FIN = 10 MHz SFDR (dBc) SNR, FIN = 5 MHz SFDR, FIN = 5 MHz 78 1.7 1.75 3 1.8 AVDD (V) SFDR (dBc) 80 80 1.9 1.85 D041 FIN = 5 MHz D030 Figure 6-13. AC Performance vs Clock Amplitude Figure 6-14. AC Performance vs AVDD 80.5 110 95 78.5 90 85 0.975 79.5 95 79 90 78.5 85 78 35 1 40 45 50 55 60 Clock Duty Cycle (%) D048 65 SFDR (dBc) 79 0.95 VCM (V) SFDR 105 100 0.925 100 SNR 79.5 78 0.9 80 SNR (dBFS) SNR (dBFS) 80 SFDR, -40qC SFDR, 25qC SFDR, 105qC SFDR (dBc) SNR, -40qC SNR, 25qC SNR, 105qC 80 70 D051 FIN = 5 MHz FIN = 5 MHz Figure 6-15. AC Performance vs VCM vs Temperature Figure 6-16. AC Performance vs Clock Duty Cycle 1 110 ChA Victim ChB Victim Ext REF INT REF Integral Nonlinearity (LSB) Isolation (dBc) 105 100 95 90 0.5 0 -0.5 85 80 0 10 20 30 40 50 60 70 80 Input Frequency (MHz) 90 -1 100 110 120 0 2048 D053 4096 6144 8192 Code 10240 12288 14336 16384 D054 Figure 6-17. Isolation vs Input Frequency FIN = 5 MHz Figure 6-18. INL vs Code 16 Submit Document Feedback Copyright © 2020 Texas Instruments Incorporated Product Folder Links: ADC3643 ADC3643 www.ti.com SBAS886 – OCTOBER 2020 0.5 100 Ext REF Int REF 90 0.3 80 0.2 70 Code Occurance (%) Differential Nonlinearity (LSB) 0.4 0.1 0 -0.1 -0.2 60 50 40 30 20 -0.3 10 -0.4 0 -0.5 0 2048 4096 6144 8192 Code 8195 10240 12288 14336 16384 8196 8197 8198 Output Code 8199 8200 D061 D066 Figure 6-20. DC Histogram FIN = 5 MHz Figure 6-19. DNL vs Code 80 24 IAVDD, ADC3641/42 IAVDD, ADC3643 IIOVDD, DDR 75 70 IIOVDD, 2-w IIOVDD, 1-w IIOVDD, 1/2-w 22 20 65 12288 18 IAVDD (mA) Output Code 60 8192 4096 16 ADC3643 55 14 50 12 45 10 40 8 35 6 30 4 ADC3641/42 25 2 20 0 0 10000 20000 30000 40000 Samples 50000 60000 70000 IIOVDD (mA) 16384 5 10 15 20 25 30 35 40 45 Sampling Rate (MSPS) 50 55 60 0 65 D065 D064 FIN = 1 MHz Pulse input = 1 MHz Figure 6-21. Pulse Response Figure 6-22. Current vs Sampling Rate Submit Document Feedback Copyright © 2020 Texas Instruments Incorporated Product Folder Links: ADC3643 17 ADC3643 www.ti.com SBAS886 – OCTOBER 2020 27.5 35 Bypass (DDR) /4 Real (2-w) /8 Real (2-w) /32 Real (2-w) 25 22.5 /2 Real (2-w) /4 Complex (2-w) /8 Complex (2-w) /32 Complex (2-w) 25 20 17.5 IIOVDD (mA) IIOVDD (mA) CL = 5 pF CL = 10 pF CL = 15 pF CL = 22 pF 30 15 12.5 10 20 15 10 7.5 5 5 0 2.5 5 10 15 20 25 30 35 40 45 Sampling Rate (MSPS) 50 55 60 65 5 10 D066 20 25 30 35 40 45 Sampling Rate (MSPS) 50 55 60 65 D067 FIN = 1 MHz FIN = 1 MHz Figure 6-23. IIOVDD Current vs Decimation 18 15 Figure 6-24. IIOVDD Current vs Load Capacitance Submit Document Feedback Copyright © 2020 Texas Instruments Incorporated Product Folder Links: ADC3643 ADC3643 www.ti.com SBAS886 – OCTOBER 2020 7 Parameter Measurement Information Sample N Input Signal Sample N+1 tAD tPD Sampling Clock tACQ tCONV tCD TDCLK DCLK tDV D13 D6 D13 D6 D13 DA0 D7 D0 D7 D0 D7 DB6 D13 D6 D13 D6 D13 D7 D0 D7 D0 D7 ... ... DA6 DB0 Sample N-2 Sample N-1 Sample N Figure 7-1. Timing diagram: DDR CMOS Sample N Input Signal Sample N+1 tAD tPD Sampling Clock tACQ tCONV tCDCLK DCLKIN DCLK tCD TDCLK FCLK tDV DA6 D13 D11 D9 D7 D5 D3 D1 D13 D11 D9 D7 D5 D3 D1 DA5 D12 D10 D8 D6 D4 D2 D0 D12 D10 D8 D6 D4 D2 D0 DB6 D13 D11 D9 D7 D5 D3 D1 D13 D11 D9 D7 D5 D3 D1 DB5 D12 D10 D8 D6 D4 D2 D0 D12 D10 D8 D6 D4 D2 D0 Sample N-2 Sample N-1 Figure 7-2. Timing diagram: 2-wire serial CMOS Submit Document Feedback Copyright © 2020 Texas Instruments Incorporated Product Folder Links: ADC3643 19 ADC3643 www.ti.com SBAS886 – OCTOBER 2020 Sample N Input Signal Sample N+1 tAD tPD Sampling Clock tACQ tCONV tCDCLK DCLKIN DCLK tCD TDCLK FCLK tDV DA6 D2 D1 D0 D13 D12 D11 D10 D9 D8 D7 D6 D5 D4 D3 D2 D1 D0 DB6 D2 D1 D0 D13 D12 D11 D10 D9 D8 D7 D6 D5 D4 D3 D2 D1 D0 Sample N-2 Sample N-1 Figure 7-3. Timing diagram: 1-wire serial CMOS Sample N Input Signal Sample N+1 tAD tPD Sampling Clock tACQ tCONV tCDCLK DCLKIN (DB1) TDCLK DCLK tCD FCLK (DA1) tDV Channel A DA6 Channel B D D D D D D D D D D D D D D D D D D D D D D D D D D D D D D D D D D 5 4 3 2 1 0 13 12 11 10 9 8 7 6 5 4 3 2 1 0 13 12 11 10 9 8 7 6 5 4 3 2 1 0 Sample N-2 Sample N-1 Figure 7-4. Timing diagram: 1/2-wire serial CMOS 20 Submit Document Feedback Copyright © 2020 Texas Instruments Incorporated Product Folder Links: ADC3643 ADC3643 www.ti.com SBAS886 – OCTOBER 2020 8 Detailed Description 8.1 Overview The ADC364x is a low noise, ultra-low power 14-bit high-speed dual channel ADC family supporting sampling rates from 10 to 65 Msps. It offers very good DC precision together with IF sampling support which makes it ideally suited for a wide range of applications. The ADC364x is equipped with an on-chip internal reference option but it also supports the use of an external, high precision 1.6 V voltage reference or an external 1.2 V reference which is buffered and gained up internally. Because of the inherent low latency architecture, the digital output result is available after only one clock cycle. Single ended as well as differential input signaling is supported. An optional programmable digital down converter enables external anti-alias filter relaxation as well as output data rate reduction. The digital filter provides a 32-bit programmable NCO and supports both real or complex decimation. The ADC364x family uses a parallel DDR CMOS as well as a 2-wire, 1-wire and 1/2-wire serial CMOS interface to output the data offering lowest power digital interface together with the flexibility to minimize the number of digital interconnects. The ADC364x includes a digital output formatter which supports output resolutions from 14 to 20-bit. The device is a pin-to-pin compatible family with different speed grades. The device features and control options can be set up either through pin configurations or via SPI register writes. 8.2 Functional Block Diagram REFBUF 1.2 V REF Digital Downconverter VREF Crosspoint Switch NCO ADC 14 bit AIN N DCLK VCM 0.95 V Dig I/F CMOS NCO BIN DA0..6 DB0..6 ADC 14 bit N CLK SDIO SCLK SEN RESET PDN/SYNC Control Submit Document Feedback Copyright © 2020 Texas Instruments Incorporated Product Folder Links: ADC3643 21 ADC3643 www.ti.com SBAS886 – OCTOBER 2020 8.3 Feature Description 8.3.1 Analog Input The analog inputs of ADC364x are intended to be driven differentially. Both AC coupling and DC coupling of the analog inputs is supported. The analog inputs are designed for an input common mode voltage of 0.95 V which must be provided externally on each input pin. DC-coupled input signals must have a common mode voltage that meets the device input common mode voltage range. The equivalent input network diagram is shown in Figure 8-1. All four sampling switches, on-resistance shown in red, are in same position (open or closed) simultaneously. AVDD Sampling Switch xINP/ xINM 1 2 nH 0.32 pF 125 24 1.4 pF 0.15 pF 0.6 pF 0.6 pF GND GND GND 6.4 pF 7 GND GND GND 5 0.7 pF GND 1.6 pF GND GND Figure 8-1. Equivalent Input Network 8.3.1.1 Analog Input Bandwidth Figure 8-2 shows the analog full power input bandwidth of the ADC364x with a 50 Ω. The -3 dB bandwidth is approximately 900 MHz and the useful input bandwidth with good AC performance is approximately 120 MHz. The equivalent input resistance RIN and input capacitance CIN vs frequency are shown in Figure 8-3. 13 -2 -3 -4 -5 -6 10 100 Input Frequency (MHz) 1000 22 12 11 10 10 8 9 6 8 4 7 2 6 0.1 ADC3 Figure 8-2. ADC Analog Input bandwidth response 14 RIN CIN 1 10 Input Frequency (MHz) 100 Differential CIN (pF) 12 -1 Differential RIN (k:) Normalized Gain Response (dB) 0 0 1000 ADC3 Figure 8-3. Equivalent RIN/CIN vs Input Frequency Submit Document Feedback Copyright © 2020 Texas Instruments Incorporated Product Folder Links: ADC3643 ADC3643 www.ti.com SBAS886 – OCTOBER 2020 8.3.1.2 Analog Front End Design The ADC364x is an unbuffered ADC and thus a passive kick-back filter is recommended to absorb the glitch from the sampling operation. Depending on if the input is driven by a balun or a differential amplifier with low output impedance, a termination network may be needed. Additionally a passive DC bias circuit is required in AC-coupled applications which can be combined with the termination network. 8.3.1.2.1 Sampling Glitch Filter Design The front end sampling glitch filter is designed to optimize the SNR and HD3 performance of the ADC. The filter performance is dependent on input frequency and therefore the following filter designs are recommended for different input frequency ranges as shown in Figure 8-4 and Figure 8-5 (assuming 50 Ω source impedance). 33 10 180nH 100 pF Termination 33 180nH 10 Figure 8-4. Sampling glitch filter example for input frequencies from DC to 30 MHz 33 10 120nH 150nH 100pF 82 pF Termination 33 10 120nH 100pF Figure 8-5. Sampling glitch filter example for input frequencies from 30 to 70 MHz 8.3.1.2.2 Single Ended Input The ADC can be configured to operate with single ended input instead of differential using just the positive signal input. This operating mode must be enabled via SPI register write (address 0x11). The single ended signal is connected to the negative ADC input and both the positive and negative input need to be biased to VCM as shown in Figure 8-6. 0.56V 0V -0.56V C INM 0.56V VCM -0.56V INM R VCM VCM INP C VCM INP C Figure 8-6. Single ended analog input: AC coupled (left) and DC coupled (right) The signal swing is now reduced by 6-dB (single ended input with 1.125 Vpp vs differential 2.25 Vpp), and the resulting SNR is reduced by 3-dB. Submit Document Feedback Copyright © 2020 Texas Instruments Incorporated Product Folder Links: ADC3643 23 ADC3643 www.ti.com SBAS886 – OCTOBER 2020 8.3.1.2.3 Analog Input Termination and DC Bias Depending on the input drive circuitry, a termination network and/or DC biasing needs to be provided. 8.3.1.2.3.1 AC-Coupling The ADC364x requires external DC bias using the common mode output voltage (VCM) of the ADC together with the termination network as shown in Figure 8-7. The termination is located within the glitch filter network. When using a balun on the input, the termination impedance has to be adjusted to account for the turns ratio of the transformer. When using an amplifier, the termination impedance can be adjusted to optimize the amplifier performance. Glitch Filter Termination 33 1 uF 10 180nH 25 100 pF VCM 0.1 …F 33 25 1 uF VCM 180nH 10 Figure 8-7. AC-Coupling: termination network provides DC bias (glitch filter example for DC - 30 MHz) 8.3.1.2.3.2 DC-Coupling In DC coupled applications the DC bias needs to be provided from the fully differential amplifier (FDA) using VCM output of the ADC as shown in Figure 8-8. The glitch filter in this case is located between the anti-alias filter and the ADC. No termination may be needed if amplifier is located close to the ADC or if the termination is part of the anti-alias filter. Glitch Filter 33 10 180nH AAF (Anti Alias Filter) 100 pF 33 VCM 180nH 10 Figure 8-8. DC-Coupling: DC bias provided by FDA (glitch filter example for DC - 30 MHz) 24 Submit Document Feedback Copyright © 2020 Texas Instruments Incorporated Product Folder Links: ADC3643 ADC3643 www.ti.com SBAS886 – OCTOBER 2020 8.3.1.3 Auto-Zero Feature The ADC364x includes an internal auto-zero front end amplifier circuit which improves the 1/f flicker noise. This auto-zero feature is enabled by default for the ADC3641/2 and can be enabled using SPI register writes for the ADC3643 (register 0x11, D0). 0 -80 Auto-zero DIS Auto-zero EN -20 -90 -40 -100 Amplitude (dBFS) Amplitude (dBFS) Auto-zero DIS Auto-zero EN -60 -80 -100 -120 -130 -120 -140 -140 -150 -160 0 2.5 5 7.5 10 -160 0.01 12.5 Frequency (MHz) 0.1 1 10 100 Frequency (kHz) adc3 Figure 8-9. FFT at 25 MSPS with input frequency of 3 MHz (auto-zero feature enable vs disable, 4M point FFT) 1000 adc3 Figure 8-10. FFT at 25 MSPS with input frequency of 3 MHz (auto-zero feature enable vs disable, 4M point FFT) -80 0 AZ DIS AZ EN -20 Auto-zero DIS Auto-zero EN -100 Amplitude (dBFS) -40 Amplitude (dBFS) -110 -60 -80 -120 -100 -140 -120 -140 0 10 20 Input Frequency (MHz) -160 0.01 30 adc3 Figure 8-11. ADC3643: FFT at 65 MSPS with input frequency of 5 MHz (auto-zero feature enable vs disable, 4M point FFT) 0.1 1 10 Input Frequency (MHz) 100 1000 adc3 Figure 8-12. ADC3643: FFT at 65 MSPS with input frequency of 5 MHz (auto-zero feature enabled vs disabled, 4M point FFT) Submit Document Feedback Copyright © 2020 Texas Instruments Incorporated Product Folder Links: ADC3643 25 ADC3643 www.ti.com SBAS886 – OCTOBER 2020 8.3.2 Clock Input In order to maximize the ADC SNR performance, the external sampling clock should be low jitter and differential signaling with a high slew rate. This is especially important in IF sampling applications. For less jitter sensitive applications, the ADC364x provides the option to operate with single ended signaling which saves additional power consumption. 8.3.2.1 Single Ended vs Differential Clock Input The ADC364x can be operated using a differential or a single ended clock input where the single ended clock consumes less power consumption. However clock amplitude impacts the ADC aperture jitter and consequently the SNR. For maximum SNR performance, a large clock signal with fast slew rates needs to be provided. • • Differential Clock Input: The clock input can be AC coupled externally. The ADC364x provides internal biasing for that use case. Single Ended Clock Input: This mode needs to be configured using SPI register TBD. In this mode there is no internal clock biasing and thus the clock input needs to be DC coupled around a 0.9V center. The unused input needs to be AC coupled to ground. 1.8V CLKP CLKP + 0.9V 5kO 0V VCM 0.9V 5kO CLKM CLKM - Figure 8-13. External and internal connection using differential (left) and single ended (right) clock input 8.3.2.2 Signal Acquisition Time Adjust The ADC364x includes a register (DLL PDN (0x11, D2) which increases the signal acquisition time window for clock rates below 40 MSPS from 25% to 50% of the clock period. Increasing the sampling time provides a longer time for the driving amplifier to settle out the signal which can improve the SNR performance of the system. Note This register needs to be set for the 65 MSPS speed grade (ADC3643) when operating at sampling rates below 40 MSPS. For the 10 and 25 MSPS device speed grades the sampling time is already set to TS/2. When powering down the DLL, the acquisition time tracks the clock duty cycle (50% is recommended). Table 8-1. Acquisition time vs DLL PDN setting SAMPLING CLOCK FS (MSPS) DLL PDN (0x11, D2) ACQUISITION TIME (tACQ) 65 0 TS / 4 ≤ 40 1 TS / 2 TS: Sampling clock period 26 Submit Document Feedback Copyright © 2020 Texas Instruments Incorporated Product Folder Links: ADC3643 ADC3643 www.ti.com SBAS886 – OCTOBER 2020 8.3.3 Voltage Reference The ADC364x provides three different options for supplying the voltage reference to the ADC. An external 1.6 V reference can be directly connected to the VREF input; a voltage 1.2 V reference can be connected to the REFBUF input using the internal gain buffer or the internal 1.2 V reference can be enabled to generate a 1.6 V reference voltage. For best performance, the reference noise should be filtered by connecting a 10 μF and a 0.1 μF ceramic bypass capacitor to the VREF pin. The internal reference circuitry of the ADC364x is shown in Figure 8-14. Note The voltage reference mode can be selected using SPI writes or by using the REFBUF pin (default) as a control pin (Section 8.5.1). If the REFBUF pin is not used for configuration, the REFBUF pin should be connected to AVDD (even though the REFBUF pin has a weak internal pullup to AVDD) and the voltage reference option has to be selected using the SPI interface. xINP xINM 0.95V VCM VREF (1.6V) x1.33 REFBUF (1.2V) VREF1.2 REFGND Figure 8-14. Different voltage reference options for ADC364x 8.3.3.1 Internal voltage reference The 1.6 V reference for the ADC can be generated internal using the on-chip 1.2 V reference along with the internal gain buffer. A 10 μF and a 0.1 μF ceramic bypass capacitor (C VREF) should connected between the VREF and REFGND pins as close to the pins as possible. xINP xINM VCM 0.95V VREF (1.6V) X1.33 CVREF REFBUF (1.2V) VREF1.2 REFGND Figure 8-15. Internal reference Submit Document Feedback Copyright © 2020 Texas Instruments Incorporated Product Folder Links: ADC3643 27 ADC3643 www.ti.com SBAS886 – OCTOBER 2020 8.3.3.2 External voltage reference (VREF) For highest accuracy and lowest temperature drift, the VREF input can be directly connected to an external 1.6 V reference. A 10 μF and a 0.1 μF ceramic bypass capacitor (CVREF) connected between the VREF and REFGND pins and placed as close to the pins as possible is recommended. The load current from the external reference is about 1 mA. Note: The internal reference is also used for other functions inside the device; therefore, the reference amplifier should only be powered down in power down state but not during normal operation. xINP xINM VCM 0.95V VREF (1.6V) Reference 1.6V CVREF REFBUF (1.2V) x1.33 VREF1.2 REFGND Figure 8-16. External 1.6V reference 8.3.3.3 External voltage reference with internal buffer (REFBUF) The ADC364x is equipped with an on-chip reference buffer that also includes gain to generate the 1.6 V reference voltage from an external 1.2 V reference. A 10 μF and a 0.1 μF ceramic bypass capacitor (C VREF) between the VREF and REFGND pins and a 10 μF and a 0.1 μF ceramic bypass capacitor between the REFBUF and REFGND pins are recommended. Both capacitors should be placed as close to the pins as possible. The load current from the external reference is less than 100 μA. xINP xINM VCM 0.95V VREF (1.6V) Reference 1.2V x1.33 REFBUF (1.2V) VREF1.2 CREFBUF CVREF REFGND Figure 8-17. External 1.2V reference using internal reference buffer 28 Submit Document Feedback Copyright © 2020 Texas Instruments Incorporated Product Folder Links: ADC3643 ADC3643 www.ti.com SBAS886 – OCTOBER 2020 8.3.4 Digital Down Converter The ADC364x includes an optional on-chip digital down conversion (DDC) decimation filter that can be enabled via SPI register setting. It supports complex decimation by 2, 4, 8, 16 and 32 using a digital mixer and a 32-bit numerically controlled oscillator (NCO) as shown in Figure 8-18. Furthermore it supports a mode with real decimation where the complex mixer is bypassed (NCO should be set to 0 for lowest power consumption) and the digital filter acts as a low pass filter. Internally the decimation filter calculations are performed with a 20-bit resolution in order to avoid any SNR degradation due to quantization noise. The Section 8.3.5.4 truncates to the selected resolution prior to outputting the data on the digital interface. NCO 32bit Filter I Q ADC NN I Q Digital Interface SYNC Figure 8-18. Internal Digital Decimation Filter 8.3.4.1 DDC MUX The ADC364x family contains a MUX in front of the digital decimation filter which allows the ADC channel A input to be connected to the DDC of channel B and vice versa. Digital Downconverter DDC MUX NCO N ADC NCO N ADC Figure 8-19. DDC MUX Submit Document Feedback Copyright © 2020 Texas Instruments Incorporated Product Folder Links: ADC3643 29 ADC3643 www.ti.com SBAS886 – OCTOBER 2020 8.3.4.2 Digital Filter Operation The complex decimation operation is illustrated with an example in Figure 8-20. First the input signal (and the negative image) are frequency shifted by the NCO frequency as shown on the left. Next a digital filter is applied (centered around 0 Hz) and the output data rate is decimated - in this example the output data rate FS,OUT = FS/8 with a Nyquist zone of F S/16. During the complex mixing the spectrum (signal and noise) is split into real and complex parts and thus the amplitude is reduced by 6-dB. In order to compensate this loss, there is a 6-dB digital gain option in the decimation filter block that can be enabled via SPI write. Input Signal (Alias) -FIN + FNCO Shifted Input Signal (Alias) Shifted Input Signal Negative Image Input Signal Negative Image Decimation by 8 FIN + FNCO 0 -FS/2 FS/2 FNCO -FS/2 -FS/16 0 FS/16 FS/2 NCO Tuning Range Figure 8-20. Complex decimation illustration The real decimation operation is illustrated with an example in Figure 8-21. There is no frequency shift happening and only the real portion of the complex digital filter is exercised. The output data rate is decimated a decimation of 8 would result in an output data rate FS,OUT = FS/8 with a Nyquist zone of FS/16. During the real mixing the spectrum (signal and noise) amplitude is reduced by 3-dB. In order to compensate this loss, there is a 3-dB digital gain option in the decimation filter block that can be enabled via SPI write. Input Signal Decimation by 32 Decimation by 16 Decimation by 2 Decimation by 4 Decimation by 8 FS/32 FS/16 FS/8 FS/4 FS/2 FS/64 Figure 8-21. Real decimation illustration 30 Submit Document Feedback Copyright © 2020 Texas Instruments Incorporated Product Folder Links: ADC3643 ADC3643 www.ti.com SBAS886 – OCTOBER 2020 8.3.4.2.1 FS/4 Mixing with Real Output In this mode, the output after complex decimation gets mixed with FS/4 (FS = output data rate in this case). Instead of a complex output with the input signal centered around 0 Hz, the output is transmitted as a real output at twice the data rate and the signal is centered around FS/4 (Fout/4) as illustrated in Figure 8-22. In this example, complex decimation by 8 is used. The output data is transmitted as a real output with an output rate of Fout = FS'/4 (FS' = ADC sampling rate). The input signal is now centered around FS/4 (Fout/4) or FS'/16. FIN FNCO - FIN + FNCO -FIN + FNCO + FS/4 /8 FS/4 mix Fout/4 mix Complex Decimation /8 0 0 FS/2 0 )6¶/2 FS/16 )6¶/2 FS/8 Figure 8-22. FS/4 Mixing with real output 8.3.4.3 Numerically Controlled Oscillator (NCO) and Digital Mixer The decimation block is equipped with a 32-bit NCO and a digital mixer to fine tune the frequency placement prior to the digital filtering. The oscillator generates a complex exponential sequence of: ejωn (default) or e–jωn where: frequency (ω) is specified as a signed number by the 32-bit register setting The complex exponential sequence is multiplied with the real input from the ADC to mix the desired carrier to a frequency equal to f IN + f NCO. The NCO frequency can be tuned from –F S/2 to +F S/2 and is processed as a signed, 2s complement number. After programming a new NCO frequency, the MIXER RESTART register bit or SYNC pin has to be toggled for the new frequency to get active. Additionally the ADC364x provides the option via SPI to invert the mixer phase. The NCO frequency setting is set by the 32-bit register value given and calculated as: NCO frequency = 0 to + FS/2: NCO = fNCO × 232 / FS NCO frequency = -FS/2 to 0: NCO = (fNCO + FS) × 232 / FS where: • NCO = NCO register setting (decimal value) • fNCO = Desired NCO frequency (MHz) • FS = ADC sampling rate (MSPS) The NCO programming is further illustrated with this example: • • • ADC sampling rate FS = 65 MSPS Input signal fIN = 10 MHz Desired output frequency fOUT = 0 MHz For this example there are actually four ways to program the NCO and achieve the desired output frequency as shown in Table 8-2. Table 8-2. NCO value calculations example Alias or negative image fNCO NCO Value fIN = –10 MHz fNCO = 10 MHz 660764199 fIN = 10 MHz fNCO = –10 MHz 3634203097 fIN = 10 MHz fNCO = 10 MHz 660764199 fIN = –10 MHz fNCO = –10 MHz 3634203097 Mixer Phase as is inverted Frequency translation for fOUT fOUT = fIN + fNCO = –10 MHz +10 MHz = 0 MHz fOUT = fIN + fNCO = 10 MHz + (–10 MHz) = 0 MHz fOUT = fIN – fNCO = 10 MHz – 10 MHz = 0 MHz fOUT = fIN – fNCO = –10 MHz – (–10 MHz) = 0 MHz Submit Document Feedback Copyright © 2020 Texas Instruments Incorporated Product Folder Links: ADC3643 31 ADC3643 www.ti.com SBAS886 – OCTOBER 2020 8.3.4.4 Decimation Filter The ADC364x supports complex decimation by 2, 4, 8, 16 and 32 with a pass-band bandwidth of ~ 80% and a stopband rejection of at least 85dB. Table 8-3 gives an overview of the pass-band bandwidth of the different decimation settings with respect to ADC sampling rate FS. In real decimation mode the output bandwidth is half of the complex bandwidth. Table 8-3. Decimation Filter Summary and Maximum Available Output Bandwidth REAL/COMPLEX DECIMATION Complex Real DECIMATION SETTING N OUTPUT RATE OUTPUT BANDWIDTH OUTPUT RATE (FS = 65 MSPS) OUTPUT BANDWIDTH (FS = 65 MSPS) 2 FS / 2 complex 4 FS / 4 complex 0.8 × FS / 2 32.5 MSPS complex 26 MHz 0.8 × FS / 4 16.25 MSPS complex 8 13 MHz FS / 8 complex 0.8 × FS / 8 8.125 MSPS complex 6.5 MHz 16 FS / 16 complex 0.8 × FS / 16 4.0625 MSPS complex 3.25 MHz 32 FS / 32 complex 0.8 × FS / 32 2.03125 MSPS complex 1.625 MHz 2 FS / 2 real 0.4 × FS / 2 32.5 MSPS 13 MHz 4 FS / 4 real 0.4 × FS / 4 16.25 MSPS 6.5 MHz 8 FS / 8 real 0.4 × FS / 8 8.125 MSPS 3.25 MHz 16 FS / 16 real 0.4 × FS / 16 4.0625 MSPS 1.625 MHz 32 FS / 32 real 0.4 × FS / 32 2.03125 MSPS 0.8125 MHz The decimation filter responses normalized tot he ADC sampling clock frequency are illustrated in . They are interpreted as follows: Each figure contains the filter pass-band, transition band(s) and alias or stop-band(s) as shown in Figure 8-24 to Figure 8-33. The x-axis shows the offset frequency (after the NCO frequency shift) normalized to the ADC sampling rate FS. For example, in the divide-by-4 complex setup, the output data rate is FS / 4 complex with a Nyquist zone of FS / 8 or 0.125 × F S. The transition band is centered around 0.125 × F S and the alias transition band is centered at 0.375 × FS (colored in blue). The stop-bands, which alias on top of the pass-band, are centered at 0.25 × FS and 0.5 × FS and are colored in red. The stop-band attenuation is greater than 85 dB. 0 Passband Transition Band Alias Band Attn Spec -20 Filter Transition Bands Amplitude (dB) -40 Bands that alias on top of signal band Pass Band -60 -80 -100 -120 0 0.1 0.2 0.3 0.4 0.5 Normalized Frequency (Fs) Figure 8-23. Interpretation of the Decimation Filter Plots 32 Submit Document Feedback Copyright © 2020 Texas Instruments Incorporated Product Folder Links: ADC3643 ADC3643 www.ti.com SBAS886 – OCTOBER 2020 0 Passband Transition Band Alias Band Attn Spec -40 Amplitude (dB) Amplitude (dB) -20 -60 -80 -100 -120 0 0.05 0.1 0.15 0.2 0.25 0.3 0.35 0.4 0.45 0.5 Normalized Frequency (Fs) Passband Transition Band Alias Band Attn Spec 0 0.025 0.05 0.075 0.1 0.125 0.15 0.175 0.2 0.225 0.25 Normalized Frequency (Fs) Decb Figure 8-24. Decimation by 2 complex frequency response Decb Figure 8-25. Decimation by 2 complex passband ripple response 0 0 Passband Transition Band Alias Band Attn Spec -20 Passband Transition Band Alias Band Attn Spec -0.01 -0.02 -0.03 -40 Amplitude (dB) Amplitude (dB) 0.1 0.09 0.08 0.07 0.06 0.05 0.04 0.03 0.02 0.01 0 -0.01 -0.02 -0.03 -0.04 -0.05 -0.06 -0.07 -0.08 -0.09 -0.1 -60 -80 -0.04 -0.05 -0.06 -0.07 -0.08 -100 -0.09 -120 -0.1 0 0.05 0.1 0.15 0.2 0.25 0.3 0.35 0.4 0.45 0.5 Normalized Frequency (Fs) 0 Figure 8-26. Decimation by 4 complex frequency response Amplitude (dB) Amplitude (dB) -40 -60 -80 -100 -120 0.05 0.1 0.15 0.2 0.25 0.3 0.35 Normalized Frequency (Fs) 0.03 0.4 0.45 0.5 0.05 0.06 0.07 0.08 0.09 -0.08 -0.081 -0.082 -0.083 -0.084 -0.085 -0.086 -0.087 -0.088 -0.089 -0.09 -0.091 -0.092 -0.093 -0.094 -0.095 -0.096 -0.097 -0.098 -0.099 -0.1 0.1 0.11 0.12 Decb Passband Transition Band Alias Band Attn Spec 0 0.006 0.012 0.018 0.024 0.03 0.036 0.042 Normalized Frequency (Fs) Decb Figure 8-28. Decimation by 8 complex frequency response 0.04 Figure 8-27. Decimation by 4 complex passband ripple response Passband Transition Band Alias Band Attn Spec 0 0.02 Normalized Frequency (Fs) 0 -20 0.01 Decb 0.048 0.054 0.06 Decb Figure 8-29. Decimation by 8 complex passband ripple response Submit Document Feedback Copyright © 2020 Texas Instruments Incorporated Product Folder Links: ADC3643 33 ADC3643 www.ti.com SBAS886 – OCTOBER 2020 -0.1 0 Passband Transition Band Alias Band Attn Spec -0.12 -0.13 -40 Amplitude (dB) Amplitude (dB) -20 Passband Transition Band Alias Band Attn Spec -0.11 -60 -80 -0.14 -0.15 -0.16 -0.17 -0.18 -100 -0.19 -120 -0.2 0 0.05 0.1 0.15 0.2 0.25 0.3 0.35 0.4 0.45 0.5 Normalized Frequency (Fs) 0 0.006 0.009 0.012 0.015 0.018 0.021 0.024 0.027 0.03 Normalized Frequency (Fs) Figure 8-30. Decimation by 16 complex frequency response Decb Figure 8-31. Decimation by 16 complex passband ripple response -0.2 0 Passband Transition Band Alias Band Attn Spec -20 Passband Transition Band Alias Band Attn Spec -0.205 -0.21 -0.215 -40 Amplitude (dB) Amplitude (dB) 0.003 Decb -60 -80 -0.22 -0.225 -0.23 -0.235 -0.24 -100 -0.245 -120 -0.25 0 0.05 0.1 0.15 0.2 0.25 0.3 0.35 0.4 Normalized Frequency (Fs) 0.45 0.5 0 0.002 0.004 0.006 0.008 0.01 0.012 0.014 Normalized Frequency (Fs) Decb Figure 8-32. Decimation by 32 complex frequency response 0.016 0.018 0.02 Decb Figure 8-33. Decimation by 32 complex passband ripple response 8.3.4.5 SYNC The PDN/SYNC pin can be used to synchronize multiple devices using an external SYNC signal. The PDN/ SYNC pin can be configured via SPI (SYNC EN bit) from power down to synchronization functionality and is latched in by the rising edge of the sampling clock as shown in Figure 8-34. CLK tS,SYNC tH,SYNC SYNC Figure 8-34. External SYNC timing diagram The synchronization signal is only required when using the decimation filter - either using the SPI SYNC register or the PDN/SYNC pin. It resets internal clock dividers used in the decimation filter and aligns the internal clocks as well as I and Q data within the same sample. If no SYNC signal is given the internal clock dividers will not be synchronized, which can lead to a fractional delay across different devices. The SYNC signal also resets the NCO phase and loads the new NCO frequency (same as the MIXER RESTART bit). When trying to resynchronize during operation, the SYNC toggle should occur at 64*K clock cycles, where K is an integer. This ensures phase continuity of the clock divider. 34 Submit Document Feedback Copyright © 2020 Texas Instruments Incorporated Product Folder Links: ADC3643 ADC3643 www.ti.com SBAS886 – OCTOBER 2020 8.3.4.6 Output Formatting with Decimation 8.3.4.6.1 Parallel CMOS In parallel CMOS mode, the ADC364x device only supports real output with DDR CMOS interface as shown in Figure 8-35 (real decimation). Here the output format is selected to 14-bit since the parallel output bus only supports up to 14-bit. DDR CMOS ChA/B: DA0..DB0 DCLK DCLK DB6 (MSB) D13 DB0 D0 D7 DA6 (MSB) D6 D13 D0 D7 ... D6 ... DA0 Figure 8-35. Output Data Format in Real Decimation Table 8-4 illustrates the output interface data rate along with the corresponding DCLK frequency based on real decimation setting (M). Furthermore the table shows an actual lane rate example with complex decimation by 4. Table 8-4. Parallel CMOS Data Rate Examples with Decimation REAL/COMPLEX DECIMATION Real DECIMATION SETTING ADC SAMPLING RATE DDR CMOS DCLK DOUT M FS 4 65 MHz DDR FS / M FS x 2 / M DDR 16.25 MHz 32.5 MHz Submit Document Feedback Copyright © 2020 Texas Instruments Incorporated Product Folder Links: ADC3643 35 ADC3643 www.ti.com SBAS886 – OCTOBER 2020 8.3.4.6.2 Serialized CMOS In serialized CMOS mode, the ADC364x device supports complex decimation output Figure 8-36 and real decimation output Figure 8-37. The examples are shown for 16-bit output for 2-wire (8x serialization) and 1-wire (16x serialization). FCLK DA5 AI D15 AI D13 AI D11 AI D9 AI D7 AI D5 AI D3 AI D1 AQ D15 AQ D13 AQ D11 AQ D9 AQ D7 AQ D5 AQ D3 AQ D1 DA6 AI D14 AI D12 AI D10 AI D8 AI D6 AI D4 AI D2 AI D0 AQ D14 AQ D12 AQ D10 AQ D8 AQ D6 AQ D4 AQ D2 AQ D0 DB5 BI D15 BI D13 BI D11 BI D9 BI D7 BI D5 BI D3 BI D1 BQ D15 BQ D13 BQ D11 BQ D9 BQ D7 BQ D5 BQ D3 BQ D1 DB6 BI D14 BI D12 BI D10 BI D8 BI D6 BI D4 BI D2 BI D0 BQ D14 BQ D12 BQ D10 BQ D8 BQ D6 BQ D4 BQ D2 BQ D0 2-Wire 8x Serialization DCLK FCLK 1-Wire 16x Serialization DA6 AI AQ DB6 BI BQ DCLK FCLK 1/2-Wire (32x Serialization) DA6 AI BI AQ BQ DCLK Figure 8-36. Output Data Format in Complex Decimation Table 8-5 illustrates the output interface data rate along with the corresponding DCLK/DCLKIN and FCLK frequencies based on output resolution (R), number of serial CMOS lanes (L) and complex decimation setting (N). Furthermore the table shows an actual lane rate example for the 2-, 1- and 1/2-wire interface, 16-bit output resolution and complex decimation by 16. Table 8-5. Serial CMOS Lane Rate Examples with Complex Decimation and 16-bit Output Resolution DECIMATION SETTING ADC SAMPLING RATE OUTPUT RESOLUTION N FS R 16 65 MSPS 62.5 MSPS 36 # of WIRES FCLK DCLKIN, DCLK DOUT L FS / N [DOUT] / 2 FS x 2 x R / L / N 32.5 MHz 65 MHz 2 16 1 1/2 4.0625 MHz 3.90625 MHz Submit Document Feedback 65 MHz 130 MHz 125 MHz 250 MHz Copyright © 2020 Texas Instruments Incorporated Product Folder Links: ADC3643 ADC3643 www.ti.com SBAS886 – OCTOBER 2020 FCLK DA5 A0 D15 A0 D13 A0 D11 A0 D9 A0 D7 A0 D5 A0 D3 A0 D1 A1 D15 A1 D13 A1 D11 A1 D9 A1 D7 A1 D5 A1 D3 A1 D1 DA6 A0 D14 A0 D12 A0 D10 A0 D8 A0 D6 A0 D4 A0 D2 A0 D0 A1 D14 A1 D12 A1 D10 A1 D8 A1 D6 A1 D4 A1 D2 A1 D0 DB5 B0 D15 B0 D13 B0 D11 B0 D9 B0 D7 B0 D5 B0 D3 B0 D1 B1 D15 B1 D13 B1 D11 B1 D9 B1 D7 B1 D5 B1 D3 B1 D1 DB6 B0 D14 B0 D12 B0 D10 B0 D8 B0 D6 B0 D4 B0 D2 B0 D0 B1 D14 B1 D12 B1 D10 B1 D8 B1 D6 B1 D4 B1 D2 B1 D0 2-Wire 8x Serialization DCLK FCLK 1-Wire 16x Serialization DA6 A0 A1 DB6 B0 B1 A0 B0 DCLK FCLK 1/2-Wire (32x Serialization) DA6 DCLK Figure 8-37. Output Data Format in Real Decimation Table 8-6 illustrates the output interface data rate along with the corresponding DCLK/DCLKIN and FCLK frequencies based on output resolution (R), number of serial CMOS lanes (L) and real decimation setting (M). Furthermore the table shows an actual lane rate example for the 2-, 1- and 1/2-wire interface, 16-bit output resolution and real decimation by 16. Table 8-6. Serial CMOS Lane Rate Examples with Real Decimation and 16-bit Output Resolution DECIMATION SETTING ADC SAMPLING RATE OUTPUT RESOLUTION # of WIRES FCLK DCLKIN, DCLK DOUT M FS R L FS / M / 2 (L = 2) FS / M (L = 1, 1/2) [DOUT] / 2 FS x R / L / M 2 2.03125 MHz 16.25 MHz 32.5 MHz 16 65 MSPS 16 1 1/2 4.0625 MHz 32.5 MHz 65 MHz 65 MHz 130 MHz Submit Document Feedback Copyright © 2020 Texas Instruments Incorporated Product Folder Links: ADC3643 37 ADC3643 www.ti.com SBAS886 – OCTOBER 2020 8.3.5 Digital Interface The ADC364x family supports two different CMOS output modes - parallel DDR output and serialized CMOS output formats. 8.3.5.1 Parallel CMOS Output The low power CMOS interface supports a double data rate (DDR) output interface. In DDR output mode the output clock is generated inside the ADC364x. The digital interface can be configured using SPI register writes. 8.3.5.2 Serialized CMOS output In this mode the output data is serialized and transmitted over 2, 1 or 1/2 wires. Due to CMOS output speed limitation this mode is only available for reduced output data rates. This mode is similar to the multi-SPI interface. In this operating mode, the ADC364x requires an external serial clock input (DCLKIN), which is used to transmit the data out of the ADC along with the data clock (DCLK). The phase relationship between DCLKIN and the sampling clock is irrelevant but both clocks need to be frequency locked. The serial CMOS interface is configured using SPI register writes. 8.3.5.2.1 SDR Output Clocking The ADC364x provides a SDR output clocking option for all serial CMOS output modes (including decimation) which is enabled using the SPI interface. In serial CMOS mode by default the data is output on rising and falling edge of DCLK. In SDR clocking mode, DCLKIN has to be twice as fast as the default DCLKIN so that the output data are clocked out only on DCLK rising edge. Internally DCLKIN is divided by 2 for data processing and this operation can add 1 extra clock cycle latency to the ADC latency. Latency (2 clock cycles) Sample N Sample N+1 Sample N+2 Sample N+3 Sample N+4 Sample N+5 Sample N+6 tAD tPD Continous Clock DCLKIN DCLKIN SDR DCLK DCLK SDR tCD FCLK DA/B5 (MSB) DA/B6 (LSB) Sample N-1 Sample N Sample N+1 Sample N+2 Figure 8-38. SDR Output Clocking 38 Submit Document Feedback Copyright © 2020 Texas Instruments Incorporated Product Folder Links: ADC3643 ADC3643 www.ti.com SBAS886 – OCTOBER 2020 8.3.5.3 Output Data Format The output data can be configured to two's complement (default) or offset binary formatting using SPI register writes (register 0x8F and 0x92). Table 8-7 provides an overview for minimum and maximum output codes for the two formatting options. The actual output resolution is set by the output bit mapper. Table 8-7. Overview of minimum and maximum output codes vs output resolution for different formatting Two's Complement (default) RESOLUTION (BIT) 14 VIN,MAX 0x1FFF 0 Offset Binary 16 14 16 0x7FFF 0x3FFF 0xFFFF 0x2000 0x8000 0x0000 VIN,MIN 0x2000 0x8000 0x0000 8.3.5.4 Output Formatter The digital output interface utilizes a flexible output bit mapper as shown in Figure 8-39. The bit mapper takes the 14-bit output directly from the ADC or from digital filter block and reformats it to a resolution of 14, 16, 18 or 20-bit. With parallel output format the maximum output resolution supported is 14-bit. With serial CMOS output the output serialization factor gets adjusted accordingly for 2-, 1- and 1/2-wire interface mode. When using a higher resolution output in non-decimation mode, the 2 LSBs are set to 0. The maximum output data rate can not be exceeded independently of output resolution and serialization factor. 14-Bit ADC Output Bit Mapping 14 Bit 16 Bit 18 Bit 20 Bit NCO 14-Bit Output N CMOS Interface Figure 8-39. Interface output bit mapper Table 8-8 provides an overview for the resulting serialization factor depending on output resolution and output modes. Note that the DCLKIN frequency needs to be adjusted accordingly as well. Changing the output resolution to 16-bit, 2-wire mode for example would result in DCLKIN = FS * 4 instead of * 3.5. The output bit mapper can be used for bypass and decimation filter. Table 8-8. Serialization factor vs output resolution for different output modes OUTPUT RESOLUTION 14-bit (default) 16-bit 18-bit 20-bit Interface SERIALIZATION FCLK DCLKIN DCLK D0/D1 2-Wire 7x FS/2 FS* 3.5 FS* 3.5 FS* 7 1-Wire 14x FS FS* 7 FS* 7 FS* 14 ½-Wire 28x FS FS* 14 FS* 14 FS* 28 2-Wire 8x FS/2 FS* 4 FS* 4 FS* 8 1-Wire 16x FS FS* 8 FS* 8 FS* 16 ½-Wire 32x FS FS* 16 FS* 16 FS* 32 2-Wire 9x FS/2 FS* 4.5 FS* 4.5 FS* 9 1-Wire 18x FS FS* 9 FS* 9 FS* 18 ½-Wire 36x FS FS* 18 FS* 18 FS* 36 2-Wire 10x FS/2 FS* 5 FS* 5 FS* 10 1-Wire 20x FS FS* 10 FS* 10 FS* 20 ½-Wire 40x FS FS* 20 FS* 20 FS* 40 The programming sequence to change the output interface and/or resolution from default settings is shown in Section 8.3.5.5. Submit Document Feedback Copyright © 2020 Texas Instruments Incorporated Product Folder Links: ADC3643 39 ADC3643 www.ti.com SBAS886 – OCTOBER 2020 8.3.5.5 Output Interface/Mode Configuration The following sequence summarizes all the relevant registers for changing the output interface and/or enabling the decimation filter. Steps 1 and 2 must come first since the E-Fuse load reset the SPI writes, the remaining steps can come in any order. Table 8-9. Configuration steps for changing interface or decimation STEP FEATURE 1 ADDRESS 0x07 DESCRIPTION Select the output interface bit mapping depending on resolution and output interface. Output Resolution 14-bit 16-bit DDR 2-wire 1-wire 1/2-wire 0x6C 0x8D 0x2B 0xA9 0x4B 18-bit N/A 0x2B 20-bit N/A 0x4B 2 0x13 Load the output interface bit mapping using the E-fuse loader (0x13, D0). Program register 0x13 to 0x01, wait ~ 1ms so that bit mapping is loaded properly followed by 0x13 0x00 3 0x0A/B/C When changing the output interface bit mapper (0x07), the CMOS output buffer register has to be configured again. 4 0x18 For serial CMOS modes, DCLKIN EN (D4) needs to be enabled. 5 0x19 In serial CMOS, configure the FCLK registers based on bypass/decimation and # of lanes used. Bypass/Decimation Bypass/ Real Decimation Output Interface Complex Decimation SCMOS FCLK SRC (D7) FCLK DIV (D4) TOG FCLK (D0) 2-wire 0 1 0 1-wire 0 0 0 1/2-wire 0 0 0 2-wire 1 0 0 1-wire 1 0 0 1/2-wire 0 0 1 6 0x1B Select the output interface resolution using the bit mapper (D5-D3). 7 0x1F For serial CMOS modes, DCLKIN EN (D6) and DCLK OB EN (D4) need to be enabled. In serial CMOS, select the FCLK pattern for decimation for proper duty cycle output of the FCLK. Output Resolution Decimation 0x20 0x21 0x22 8 Real Decimation 2-wire 14-bit 0xFE000 16-bit 0xFF000 18-bit 0xFF800 20-bit use default 14-bit Complex Decimation 1-wire 16-bit 1/2-wire use default 0xFFC00 0xFFFFF 18-bit 0xFFFFF 20-bit 9 0x24 Enable the decimation filter 10 0x25 Configure the decimation filter 11 0x2A/B/C/D 0x31/2/3/4 Program the NCO frequency for complex decimation (can be skipped for real decimation) Configure the complex output data stream (set both bits to 0 for real decimation) Decimation Filter 12 13 40 Serial CMOS 0x27 0x2E 0x26 OP-Order (D4) Q-Delay (D3) 2-wire 1 0 1-wire 0 1 1/2-wire 1 1 Set the mixer gain and toggle the mixer reset bit to update the NCO frequency. Submit Document Feedback Copyright © 2020 Texas Instruments Incorporated Product Folder Links: ADC3643 ADC3643 www.ti.com SBAS886 – OCTOBER 2020 8.3.5.5.1 Configuration Example The following is a step by step programming example to configure the ADC364x to complex decimation by 8 with 1-wire serial CMOS and 16-bit output. 1. 0x07 (address) 0x6C (load bit mapper configuration for 16-bit output with 1-wire serial CMOS) 2. 0x13 0x01, wait 1 ms, 0x13 0x00 (load e-fuse) 3. 0x0A 0xFF, 0x0B 0xEE, 0x0C 0xFD (Power down unused CMOS output buffers to avoid contention) 4. 0x18 0x10 (DCLKIN EN for serial CMOS mode) 5. 0x19 0x82 (configure FCLK) 6. 0x1B 0x88 (select 16-bit output resolution) 7. 0x1F 0x50 (DCLKIN EN for serial CMOS mode) 8. 0x20 0xFF, 0x21 0xFF, 0x22 0x0F (configure FCLK pattern) 9. 0x24 0x06 (enable decimation filter) 10.0x25 0x30 (configure complex decimation by 8) 11. 0x2A/B/C/D and 0x31/32/33/34 (program NCO frequency) 12.0x27/0x2E 0x08 (configure Q-delay register bit) 13.0x26 0xAA, 0x26 0x88 (set digital mixer gain to 6-dB and toggle the mixer update) 8.3.6 Test Pattern In order to enable in-circuit testing of the digital interface, the following test patterns are supported and enabled via SPI register writes (0x14/0x15/0x16). In decimation mode (real and complex), the test patterns replace the output data of the DDC - however channel A controls the test patterns for both channels. • RAMP Pattern: The step size needs to be configured in the CUSTOM PAT register according to the native resolution of the ADC. When selecting a higher output resolution then the additional LSBs will still be 0 in RAMP pattern mode. – 00001: 18-bit output resolution – 00100: 16-bit output resolution – 10000: 14-bit output resolution • Custom Pattern: Configured in the CUSTOM PAT register Submit Document Feedback Copyright © 2020 Texas Instruments Incorporated Product Folder Links: ADC3643 41 ADC3643 www.ti.com SBAS886 – OCTOBER 2020 8.4 Device Functional Modes 8.4.1 Normal operation In normal operating mode, the entire ADC full scale range gets converted to a digital output with 14-bit resolution. The output is available in as little as 1 clock cycle on the digital CMOS outputs. 8.4.2 Power Down Options A global power down mode can be enabled via SPI as well as using the power down pin (PDN/SYNC). There is an internal pull-down 21 kΩ resistor on the PDN/SYNC input pin and the pin is active high - so the pin needs to be pulled high externally to enter global power down mode. The SPI register map provides the capability to enable/disable individual blocks directly or via PDN pin mask in order to trade off power consumption vs wake up time as shown in Table 8-10. REFBUF 1.2V REF Digital Downconverter VREF Crosspoint Switch AIN NCO N ADC NCO BIN Dig I/F N ADC CLK Figure 8-40. Power Down Configurations Table 8-10. Overview of Power Down Options Function/ Register PDN via SPI Mask for Global PDN Feature Default ADC Yes - Enabled Reference gain amplifier Yes Internal 1.2 V reference Yes Power Impact Wake-up time Both ADC channels are included in Global PDN automatically Enabled ~ 0.4 mA ~3 us Should only be powered down in power down state. External ref ~ 1-3.5 mA ~3 ms Internal/external reference selection is available through SPI and REFBUF pin. Yes 42 Comment Differential clock ~ 1 mA n/a Single ended clock input saves ~ 1mA compared to differential. Some programmability is available through the REFBUF pin. Depending on output interface mode, unused output drivers can be powered down for maximum power savings Clock buffer Yes Output interface drivers Yes - Enabled varies n/a Decimation filter Yes - Disabled see electrical table n/a Submit Document Feedback Copyright © 2020 Texas Instruments Incorporated Product Folder Links: ADC3643 ADC3643 www.ti.com SBAS886 – OCTOBER 2020 8.5 Programming The device is primarily configured and controlled using the serial programming interface (SPI) however it can operate in a default configuration without requiring the SPI interface. Furthermore the power down function as well as internal/external reference configuration is possible via pin control (PDN/SYNC pin). Note The power down command (via PIN or SPI) only goes in effect with the ADC sampling clock present. 8.5.1 Configuration using PINs only The ADC voltage reference can be selected using the REFBUF pin. Even though there is an internal 100 kΩ pull-up resistor to AVDD, the REFBUF pin should be set to a voltage externally and not left floating. Table 8-11. REFBUF voltage levels control voltage reference selection REFBUF VOLTAGE VOLTAGE REFERENCE OPTION CLOCKING OPTION Digital Interface > 1.7 V (Default) External reference Differential clock input DDR CMOS 1.2 V (1.15-1.25V) External 1.2V input on REFBUF pin using internal gain buffer Differential clock input DDR CMOS 0.5 - 0.7V Internal reference Differential clock input DDR CMOS < 0.1V Internal reference Single ended clock input Serial CMOS 2-wire 8.5.2 Configuration using the SPI interface The device has a set of internal registers that can be accessed by the serial interface formed by the SEN (serial interface enable), SCLK (serial interface clock) and SDIO (serial interface data input/output) pins. Serially shifting bits into the device is enabled when SEN is low. Serial data input are latched at every SCLK rising edge when SEN is active (low). The serial data are loaded into the register at every 24th SCLK rising edge when SEN is low. When the word length exceeds a multiple of 24 bits, the excess bits are ignored. Data can be loaded in multiples of 24-bit words within a single active SEN pulse. The interface can function with SCLK frequencies from 12 MHz down to very low speeds (of a few hertz) and also with a non-50% SCLK duty cycle. 8.5.2.1 Register Write The internal registers can be programmed following these steps: 1. 2. 3. 4. Drive the SEN pin low Set the R/W bit to 0 (bit A15 of the 16-bit address) and bits A[14:12] in address field to 0. Initiate a serial interface cycle by specifying the address of the register (A[11:0]) whose content is written and Write the 8-bit data that are latched in on the SCLK rising edges Figure 8-41 shows the timing requirements for the serial register write operation. Submit Document Feedback Copyright © 2020 Texas Instruments Incorporated Product Folder Links: ADC3643 43 ADC3643 www.ti.com SBAS886 – OCTOBER 2020 Register Address R/W SDIO 0 0 0 0 A11 A10 A9 A8 A7 A6 A5 A4 Register Data A3 A2 A1 A0 D7 D6 D5 D4 D3 D2 D1 D0 tH,SDIO tSCLK tS,SDIO SCLK tS,SEN tH,SEN SEN RESET Figure 8-41. Serial Register Write Timing Diagram 8.5.2.2 Register Read The device includes a mode where the contents of the internal registers can be read back using the SDIO pin. This readback mode can be useful as a diagnostic check to verify the serial interface communication between the external controller and the ADC. The procedure to read the contents of the serial registers is as follows: 1. Drive the SEN pin low 2. Set the R/W bit (A15) to 1. This setting disables any further writes to the registers. Set A[14:12] in address field to 0. 3. Initiate a serial interface cycle specifying the address of the register (A[11:0]) whose content must be read 4. The device outputs the contents (D[7:0]) of the selected register on the SDIO pin 5. The external controller can latch the contents at the SCLK falling edge Register Address R/W SDIO 1 0 0 0 A11 A10 A9 A8 A7 A6 A5 A4 Register Data tOZD A3 A2 A1 A0 D7 D6 D5 D4 D3 D2 D1 D0 tOD SCLK tODZ SEN Figure 8-42. Serial Register Read Timing Diagram 44 Submit Document Feedback Copyright © 2020 Texas Instruments Incorporated Product Folder Links: ADC3643 ADC3643 www.ti.com SBAS886 – OCTOBER 2020 8.6 Register Maps Table 8-12. Register Map Summary REGISTER ADDRESS REGISTER DATA A[11:0] D7 0x00 0 D6 0 0x07 0x08 D5 0 OP IF MAPPER 0 0 PDN CLKBUF D4 D3 D2 0 0 0 OP IF EN PDN REFAMP 0 0x0A CMOS OB DIS [7:0] 0x0B CMOS OB DIS [15:8] 0x0C 0 D1 D0 0 RESET OP IF SEL PDN A PDN B PDN GLOBAL CMOS OB DIS [23:16] 0x0D 0 0 0 0 0x0E SYNC PIN EN SPI SYNC SPI SYNC EN 0 MASK CLKBUF MASK REFAMP REF CTRL 0x11 0 0 SE A SE B 0 DLL PDN 0 AZ EN 0x13 0 0 0 0 0 0 0 E-FUSE LD 0x14 CUSTOM PAT [7:0] 0x15 CUSTOM PAT [15:8] 0x16 TEST PAT B MASK BG DIS REF SEL TEST PAT A 0 SE CLK EN CUSTOM PAT [17:16] 0x18 0 0 0 DCLKIN EN 0 0 0 0 0x19 FCLK SRC 0 0 FCLK DIV 0 0 FCLK EN TOG FCLK 0x1B MAPPER EN 20B EN 0 0 0 0 0 0 0 2X DCLK 0 0 0 0x1E 0 0 0x1F LOW DR EN DCLKIN EN BIT MAPPER RES CMOS DCLK DEL 0 DCLK OB EN 0x20 FCLK PAT [7:0] 0x21 0x22 FCLK PAT [15:8] 0 0 0x24 0 0 0x25 DDC MUX EN 0x26 0x27 0 CH AVG EN FCLK PAT [19:16] DDC MUX DECIMATION MIX GAIN A 0 0 0 MIX RES A FS/4 MIX A 0 OP ORDER A 0x2A DDC EN 0 0 0 MIX PHASE MIX GAIN B Q-DEL A MIX RES B FS/4 MIX B FS/4 MIX PH A 0 0 FS/4 MIX PH B 0 0 NCO A [7:0] 0x2B NCO A [15:8] 0x2C NCO A [23:16] 0x2D 0x2E DIG BYP REAL OUT NCO A [31:24] 0 0 0 OP ORDER B Q-DEL B 0x31 NCO B [7:0] 0x32 NCO B [15:8] 0x33 NCO B [23:16] 0x34 NCO B [31:24] 0x8F 0 0 0 0 0 0 FORMAT A 0 0x92 0 0 0 0 0 0 FORMAT B 0 Submit Document Feedback Copyright © 2020 Texas Instruments Incorporated Product Folder Links: ADC3643 45 ADC3643 www.ti.com SBAS886 – OCTOBER 2020 8.6.1 Detailed Register Description Figure 8-43. Register 0x00 7 6 5 4 3 2 1 0 0 0 0 0 0 0 0 RESET R/W-0 R/W-0 R/W-0 R/W-0 R/W-0 R/W-0 R/W-0 R/W-0 Table 8-13. Register 0x00 Field Descriptions Bit Field Type Reset Description 7-1 0 R/W 0 Must write 0 RESET R/W 0 This bit resets all internal registers to the default values and self clears to 0. 0 Figure 8-44. Register 0x07 7 6 5 4 3 0 OP IF EN R/W-0 R/W-0 R/W-0 OP IF MAPPER R/W-0 R/W-0 2 1 0 OP IF SEL R/W-0 R/W-0 R/W-0 Table 8-14. Register 0x07 Field Descriptions 46 Bit Field Type Reset Description 7-5 OP IF MAPPER R/W 000 Output interface mapper. This register contains the proper output interface bit mapping for the different interfaces. The interface bit mapping is internally loaded from e-fuses and also requires a fuse load command to go into effect (0x13, D0). Register 0x07 along with the E-Fuse Load (0x13, D0) needs to be loaded first in the programming sequence since the E-Fuse load resets the SPI writes. After initial reset the default output interface variant is loaded automatically from fuse internally. However when reading back this register reads 000 until a value is written using SPI. 001: 2-wire, 18 and 14-bit 010: 2-wire, 16-bit 011: 1-wire 100: 0.5-wire 101: DDR others: not used 4 0 R/W 0 Must write 0 3 OP IF EN R/W 0 Enables changing the default output interface mode (D2-D0). 2-0 OP IF SEL R/W 000 Selection of the output interface mode. OP IF EN (D3) needs to be enabled also. After initial reset the default output interface is loaded automatically from fuse internally. However when reading back this register reads 000 until a value is written using SPI. 001: DDR CMOS 011: 2-wire 100: 1-wire 101: 0.5-wire others: not used Submit Document Feedback Copyright © 2020 Texas Instruments Incorporated Product Folder Links: ADC3643 ADC3643 www.ti.com SBAS886 – OCTOBER 2020 Figure 8-45. Register 0x08 7 6 5 4 3 2 1 0 0 0 PDN CLKBUF PDN REFAMP 0 PDN A PDN B PDN GLOBAL R/W-0 R/W-0 R/W-0 R/W-0 R/W-0 R/W-0 R/W-0 R/W-0 Table 8-15. Register 0x08 Field Descriptions Bit Field Type Reset Description 7-6 0 R/W 0 Must write 0 5 PDN CLKBUF R/W 0 Powers down sampling clock buffer 0: Clock buffer enabled 1: Clock buffer powered down 4 PDN REFAMP R/W 0 Powers down internal reference gain amplifier 0: REFAMP enabled 1: REFAMP powered down 3 0 R/W 0 Must write 0 2 PDN A R/W 0 Powers down ADC channel A 0: ADC channel A enabled 1: ADC channel A powered down 1 PDN B R/W 0 Powers down ADC channel B 0: ADC channel B enabled 1: ADC channel B powered down 0 PDN GLOBAL R/W 0 Global power down via SPI 0: Global power disabled 1: Global power down enabled. Power down mask (register 0x0D) determines which internal blocks are powered down. Submit Document Feedback Copyright © 2020 Texas Instruments Incorporated Product Folder Links: ADC3643 47 ADC3643 www.ti.com SBAS886 – OCTOBER 2020 Figure 8-46. Register 0x0A/B/C 7 6 5 4 3 2 1 0 R/W-0 R/W-0 R/W-0 CMOS OB DIS [23:0] R/W-0 R/W-0 R/W-0 R/W-0 R/W-0 Table 8-16. Register 0x0A/B/C Field Descriptions Bit Field Type Reset Description 7:0 CMOS OB DIS [23:0] R/W 0 These register bits power down the individual CMOS output buffers. See Table 8-17 for the actual bit to pin mapping. Unused pins should be powered down (ie set to 1) for maximum power savings. Even though unused outputs don't toggle there is still a small amount of static power (< 1mA) that can be saved by disabling the output buffers. There is a separate control to enable the DCLKIN buffer in register 0x1F (D6) and 0x18 (D4). DCLK output buffer is powered down using register 0x1F (D4). NOTE: When using serial CMOS interface the CMOS output buffer (0x0A, D3 (DB1)) has to be powered down because it shares the pin with DCLKIN. 0: Output buffer enabled 1: Output buffer powered down Table 8-17. Output buffer enable bit mapping vs output interface mode ADDRESS (HEX) 0x0A BIT PIN NAME D7 DB5 DB5 DB5 - - D6 DB4 DB4 - - - SCMOS 1/2-w - - - - - DB2 DB2 - - - D3 DB1 DB1 DCLKIN DCLKIN DCLKIN D2 DB0 DB0 - - - D7 DA4 - - - - 0x23 0x7F 0xFF 0xFF DA4 - - - D6 - - - - - D5 DA2 DA2 - - - D4 DA1 DA1 FCLK FCLK FCLK D3 DA0 DA0 - - - D2/D1 - - - - - D0 DB6 DB6 DB6 DB6 - Register setting 0x46 0xEE 0xEE 0xEF D7/D6/D5/D4 - - - - - D3 DA3 DA3 - - - D2 DB3 DB3 - - - D1 DA6 DA6 DA6 DA6 DA6 D0 DA5 DA5 DA5 - - 0xF0 0xFC 0xFD 0xFD Register setting 48 SCMOS 1-w D4 Register setting 0x0C SCMOS 2-w D5 D1/D0 0x0B DDR CMOS Submit Document Feedback Copyright © 2020 Texas Instruments Incorporated Product Folder Links: ADC3643 ADC3643 www.ti.com SBAS886 – OCTOBER 2020 Figure 8-47. Register 0x0D (PDN GLOBAL MASK) 7 6 5 4 0 0 0 0 3 R/W-0 R/W-0 R/W-0 R/W-0 2 1 MASK CLKBUF MASK REFAMP MASK BG DIS R/W-0 R/W-0 R/W-0 0 0 R/W-0 Table 8-18. Register 0x0D Field Descriptions Bit Field Type Reset Description 7-4 0 R/W 0 Must write 0 3 MASK CLKBUF R/W 0 Global power down mask control for sampling clock input buffer. 0: Clock buffer will get powered down when global power down is exercised. 1: Clock buffer will NOT get powered down when global power down is exercised. 2 MASK REFAMP R/W 0 Global power down mask control for reference amplifier. 0: Reference amplifier will get powered down when global power down is exercised. 1: Reference amplifier will NOT get powered down when global power down is exercised. 1 MASK BG DIS R/W 0 Global power down mask control for internal 1.2V bandgap voltage reference. Setting this bit reduces power consumption in global power down mode but increases the wake up time. See the power down option overview. 0: Internal 1.2V bandgap voltage reference will NOT get powered down when global power down is exercised. 1: Internal 1.2V bandgap voltage reference will get powered down when global power down is exercised. 0 0 R/W 0 Must write 0 Submit Document Feedback Copyright © 2020 Texas Instruments Incorporated Product Folder Links: ADC3643 49 ADC3643 www.ti.com SBAS886 – OCTOBER 2020 Figure 8-48. Register 0x0E 7 6 5 4 3 SYNC PIN EN SPI SYNC SPI SYNC EN 0 REF CTL R/W-0 R/W-0 R/W-0 R/W-0 R/W-0 2 1 REF SEL R/W-0 0 SE CLK EN R/W-0 R/W-0 Table 8-19. Register 0x0E Field Descriptions Bit Field Type Reset Description 7 SYNC PIN EN R/W 0 This bit controls the functionality of the SYNC/PDN pin. 0: SYNC/PDN pin exercises global power down mode when pin is pulled high. 1: SYNC/PDN pin issues the SYNC command when pin is pulled high. 6 SPI SYNC R/W 0 Toggling this bit issues the SYNC command using the SPI register write. SYNC using SPI must be enabled as well (D5). This bit doesn't self reset to 0. 0: Normal operation 1: SYNC command issued. 5 SPI SYNC EN R/W 0 This bit enables synchronization using SPI instead of the SYNC/PDN pin. 0: Synchronization using SPI register bit disabled. 1: Synchronization using SPI register bit enabled. 4 0 R/W 0 Must write 0 3 REF CTL R/W 0 This bit determines if the REFBUF pin controls the voltage reference selection or the SPI register (D2-D1). 0: The REFBUF pin selects the voltage reference option. 1: Voltage reference is selected using SPI (D2-D1) and single ended clock using D0. 2-1 REF SEL R/W 00 Selects of the voltage reference option. REF CTRL (D3) must be set to 1. 00: Internal reference 01: External voltage reference (1.2V) using internal reference buffer (REFBUF) 10: External voltage reference 11: not used SE CLK EN R/W 0 Selects single ended clock input and powers down the differential sampling clock input buffer. REF CRTL (D3) must be set to 1. 0: Differential clock input 1: Single ended clock input 0 50 Submit Document Feedback Copyright © 2020 Texas Instruments Incorporated Product Folder Links: ADC3643 ADC3643 www.ti.com SBAS886 – OCTOBER 2020 Figure 8-49. Register 0x11 7 6 5 4 3 2 1 0 0 0 SE A SE B 0 DLL PDN 0 AZ EN R/W-0 R/W-0 R/W-0 R/W-0 R/W-0 R/W-0 R/W-0 R/W-0 Table 8-20. Register 0x11 Field Descriptions Bit Field Type Reset Description 7-6 0 R/W 0 Must write 0 5 SE A R/W 0 This bit enables single ended analog input, channel A. In this mode the SNR reduces by 3-dB. 0: Differential input 1: Single ended input 4 SE B R/W 0 This bit enables single ended analog input, channel B. In this mode the SNR reduces by 3-dB. 0: Differential input 1: Single ended input 3 0 R/W 0 Must write 0 2 DLL PDN R/W 0 This register applies ONLY to the ADC3643. It powers down the internal DLL, which is used to adjust the sampling time. This register must only be enabled when operating at sampling rates below 40 MSPS. When DLL PDN bit is enabled the sampling time is directly dependent on sampling clock duty cycle (with a 50/50 duty the sampling time is TS/2). 0: Sampling time is TS/ 4 1: Sampling time is TS/2 (only for sampling rates below 40 MSPS). 1 0 R/W 0 Must write 0 0 AZ EN R/W 0/1 This bit enables the internal auto-zero circuitry. It is enabled by default for the ADC3641/42 and disabled for the ADC3643. 0: Auto-zero disabled 1: Auto-zero enabled Figure 8-50. Register 0x13 7 6 5 4 3 2 0 0 0 0 0 0 R/W-0 R/W-0 R/W-0 R/W-0 R/W-0 R/W-0 1 0 E-FUSE LD R/W-0 R/W-0 Table 8-21. Register 0x13 Field Descriptions Bit Field Type Reset Description 7-1 0 R/W 0 Must write 0 E-FUSE LD R/W 0 This register bit loads the internal bit mapping for different interfaces. After setting the interface in register 0x07, this EFUSE LD bit needs to be set to 1 and reset to 0 for loading to go into effect. Register 0x07 along with the E-Fuse Load (0x12, D0) needs to be loaded first in the programming sequence since the E-Fuse load resets the SPI writes. 0: E-FUSE LOAD set 1: E-FUSE LOAD reset 0 Submit Document Feedback Copyright © 2020 Texas Instruments Incorporated Product Folder Links: ADC3643 51 ADC3643 www.ti.com SBAS886 – OCTOBER 2020 Figure 8-51. Register 0x14/15/16 7 6 5 4 3 2 1 0 CUSTOM PAT [7:0] CUSTOM PAT [15:8] TEST PAT B R/W-0 R/W-0 TEST PAT A R/W-0 R/W-0 R/W-0 CUSTOM PAT [17:16] R/W-0 R/W-0 R/W-0 Table 8-22. Register 0x14/15/16 Field Descriptions Bit Field Type Reset Description 7-0 CUSTOM PAT [17:0] R/W 00000000 This register is used for two purposes: • It sets the constant custom pattern starting from MSB • It sets the RAMP pattern increment step size. 00001: Ramp pattern for 18-bit ADC 00100: Ramp pattern for 16-bit ADC 10000: Ramp pattern for 14-bit ADC 7-5 TEST PAT B R/W 000 Enables test pattern output mode for channel B (NOTE: The test pattern is set prior to the bit mapper and is based on native resolution of the ADC starting from the MSB). These work in either output format. 000: Normal output mode (test pattern output disabled) 010: Ramp pattern: need to set proper increment using CUSTOM PAT register 011: Constant Pattern using CUSTOM PAT [17:0] in register 0x14/15/16. others: not used 4-2 TEST PAT A R/W 000 Enables test pattern output mode for channel A (NOTE: The test pattern is set prior to the bit mapper and is based on native resolution of the ADC starting from the MSB). These work in either output format. 000: Normal output mode (test pattern output disabled) 010: Ramp pattern: need to set proper increment using CUSTOM PAT register 011: Constant Pattern using CUSTOM PAT [17:0] in register 0x14/15/16. others: not used Figure 8-52. Register 0x18 7 6 5 4 3 2 1 0 0 0 0 DCLKIN EN 0 0 0 0 R/W-0 R/W-0 R/W-0 R/W-0 R/W-0 R/W-0 R/W-0 R/W-0 Table 8-23. Register 0x18 Field Descriptions Bit Field Type Reset Description 7-5 0 R/W 0 Must write 0 DCLKIN EN R/W 0 This bit enables the DCLKIN clock input buffer for serial CMOS modes. Also DCLKIN EN (0x1F, D6) needs to be set as well. 0: DCLKIN buffer powered down. 1: DCLKIN buffer enabled. 0 R/W 0 Must write 0 4 3-0 52 Submit Document Feedback Copyright © 2020 Texas Instruments Incorporated Product Folder Links: ADC3643 ADC3643 www.ti.com SBAS886 – OCTOBER 2020 Figure 8-53. Register 0x19 7 6 5 4 3 2 1 0 FCLK SRC 0 0 FCLK DIV 0 0 FCLK EN TOG FCLK R/W-0 R/W-0 R/W-0 R/W-0 R/W-0 R/W-0 R/W-0 R/W-0 Table 8-24. Register 0x19 Field Descriptions Bit 7 6-5 4 3-2 Field Type Reset Description FCLK SRC R/W 0 User has to select if FCLK signal comes from ADC or from DDC block. Here real decimation is treated same as bypass mode 0: FCLK generated from ADC. FCLK SRC set to 0 for DDC bypass, real decimation mode and 1/2-w complex decimation mode. 1: FCLK generated from DDC block. In complex decimation mode only this bit needs to be set for 2-w and 1-w output interface mode but NOT for 1/2-w mode. 0 R/W 0 Must write 0 FCLK DIV R/W 0 This bit needs to be set to 1 for 2-w output mode in bypass mode only (non decimation). 0: All output interface modes except 2-w bypass mode.. 1: 2-w output interface mode. 0 R/W 0 Must write 0 1 FCLK EN R/W 0 This bit enables FCLK output for CMOS output. 0: Data output pin is used for parallel output data. 1: Data output pin is used for FCLK output in serialized CMOS mode. 0 TOG FCLK R/W 0 This bit adjusts the FCLK signal appropriately for 1/2-wire mode where FCLK is stretched to cover channel A and channel B. This bit ONLY needs to be set in 1/2-wire mode with complex decimation mode. 0: all other modes. 1: FCLK for 1/2-wire complex decimation mode. Table 8-25. Configuration of FCLK SRC and FCLK DIV Register Bits vs Serial Interface BYPASS/DECIMATION Decimation Bypass/ Real Decimation Complex Decimation SERIAL INTERFACE FCLK SRC FCLK DIV TOG FCLK 2-wire 0 1 0 1-wire 0 0 0 1/2-wire 0 0 0 2-wire 1 0 0 1-wire 1 0 0 1/2-wire 0 0 1 Submit Document Feedback Copyright © 2020 Texas Instruments Incorporated Product Folder Links: ADC3643 53 ADC3643 www.ti.com SBAS886 – OCTOBER 2020 Figure 8-54. Register 0x1B 7 6 5 MAPPER EN 20B EN R/W-0 R/W-0 4 3 BIT MAPPER RES R/W-0 R/W-0 R/W-0 2 1 0 0 0 0 R/W-0 R/W-0 R/W-0 Table 8-26. Register 0x1B Field Descriptions Bit Field Type Reset Description 7 MAPPER EN R/W 0 This bit enables changing the resolution of the output (including output serialization factor) in bypass mode only. This bit is not needed for 20-bit resolution output. 0: Output bit mapper disabled. 1: Output bit mapper enabled. 6 20B EN R/W 0 This bit enables 20-bit output resolution which can be useful for very high decimation settings so that quantization noise doesn't impact the ADC performance. 0: 20-bit output resolution disabled. 1: 20-bit output resolution enabled. 5-3 BIT MAPPER RES R/W 000 Sets the output resolution using the bit mapper. MAPPER EN bit (D6) needs to be enabled when operating in bypass mode.. 000: 18 bit 001: 16 bit 010: 14 bit all others, n/a 2-0 0 R/W 0 Must write 0 Table 8-27. Register Settings for Output Bit Mapper vs Operating Mode BYPASS/ DECIMATION OUTPUT RESOLUTION MAPPER EN (D7) Decimation Bypass Resolution Change 1 Real Decimation 000: 18-bit 001: 16-bit 010: 14-bit 0 Resolution Change (default 18-bit) Complex Decimation BIT MAPPER RES (D5-D3) 0 Figure 8-55. Register 0x1E 7 6 0 0 R/W-0 R/W-0 5 4 3 CMOS DCLK DEL R/W-0 R/W-0 2 1 0 0 0 0 0 R/W-0 R/W-0 R/W-0 R/W-0 Table 8-28. Register 0x1E Field Descriptions 54 Bit Field Type Reset Description 7-6 0 R/W 0 Must write 0 5-4 CMOS DCLK DEL R/W 00 These bits adjust the output timing of CMOS DCLK output. 00: no delay 01: DCLK advanced by 50 ps 10: DCLK delayed by 50 ps 11: DCLK delayed by 100 ps 3-0 0 R/W 0 Must write 0 Submit Document Feedback Copyright © 2020 Texas Instruments Incorporated Product Folder Links: ADC3643 ADC3643 www.ti.com SBAS886 – OCTOBER 2020 Figure 8-56. Register 0x1F 7 6 5 4 3 2 1 0 LOW DR EN DCLKIN EN 0 DCLK OB EN 2X DCLK 0 0 0 R/W-0 R/W-0 R/W-0 R/W-0 R/W-0 R/W-0 R/W-0 R/W-0 Table 8-29. Register 0x1F Field Descriptions Bit Field Type Reset Description 7 LOW DR EN R/W 0 This bit impacts the output drive strength of the CMOS output buffers. It can be enabled at slow speeds in order to save power consumption but it will also degrade the rise and fall times. 0: Low drive strength disabled.1: Low drive strength enabled. 6 DCLKIN EN R/W 0 This bit enables the DCLKIN clock input buffer for serial CMOS modes. Also DCLKIN EN (0x18, D4) needs to be set as well. 0: DCLKIN buffer powered down. 1: DCLKIN buffer enabled. 5 0 R/W 0 Must write 0 4 DCLK OB EN R/W 1 This bit enables DCLK output buffer. 0: DCLK output buffer powered down. 1: DCLK output buffer enabled. 3 2X DCLK R/W 0 This bit enables SDR output clocking with serial CMOS mode. When this mode is enabled, DCLKIN required is twice as fast and data is output only on rising edge of DCLK. 0: Serial data output on DCLK rising and falling edge. 1: Serial data output on DCLK rising edge only. 0 R/W 0 Must write 0 2-0 Figure 8-57. Register 0x20/21/22 7 6 5 4 3 2 1 0 FCLK PAT [7:0] FCLK PAT [15:8] 0 0 0 0 R/W-0 R/W-0 R/W-0 R/W-0 FCLK PAT [19:16] R/W-0 R/W-0 R/W-0 R/W-0 Table 8-30. Register 0x20/21/22 Field Descriptions Bit Field Type Reset Description 7-0 FCLK PAT [19:0] R/W 0xFFC00 These bits can adjust the duty cycle of the FCLK. In decimation bypass mode the FCLK pattern gets adjusted automatically for the different output resolutions. Table 8-31 shows the proper FCLK pattern values for 1-wire and 1/2-wire in real/complex decimation. Table 8-31. FCLK Pattern for different resolution based on interface DECIMATION OUTPUT RESOLUTION REAL DECIMATION 1-WIRE 0xFE000 16-bit 0xFF000 18-bit 0xFF800 20-bit 14-bit COMPLEX DECIMATION 2-WIRE 14-bit Use Default 16-bit Use Default 0xFFC00 0xFFFFF 18-bit 1/2-WIRE 0xFFFFF 20-bit Submit Document Feedback Copyright © 2020 Texas Instruments Incorporated Product Folder Links: ADC3643 55 ADC3643 www.ti.com SBAS886 – OCTOBER 2020 Figure 8-58. Register 0x24 7 6 5 0 0 CH AVG EN R/W-0 R/W-0 R/W-0 4 3 DDC MUX R/W-0 R/W-0 2 1 0 DIG BYP DDC EN 0 R/W-0 R/W-0 R/W-0 Table 8-32. Register 0x24 Field Descriptions Bit Field Type Reset Description 7-6 0 R/W 0 Must write 0 CH AVG EN R/W 0 Averages the output of ADC channel A and channel B together. The DDC MUX has to be enabled and set to '11'. The decimation filter needs to be enabled and set to bypass (fullrate output) or decimation and DIG BYP set to 1. 0: Channel averaging feature disabled 1: Output of channel A and channel B are averaged: (A+B)/2. DDC MUX R/W 0 Configures DDC MUX in front of the decimation filter. 00: ADC channel A connected to DDC A; ADC Channel B connected to DDC B 01: ADC channel A connected to DDC A and DDC B. 10: ADC channel B connected to DDC A and DDC B. 11: Output of ADC averaging block (see CH AVG EN) given to DDC A and DDC B. 2 DIG BYP R/W 0 This bit needs to be set to enable digital features block which includes decimation. 0: Digital feature block bypassed - lowest latency 1: Data path includes digital features 1 DDC EN R/W 0 Enables internal decimation filter for both channels 0: DDC disabled. 1: DDC enabled. 0 0 R/W 0 Must write 0 5 4-3 To output interface DDC N CH Average DECIMATION DIG BYP DDC N DDC MUX To output interface Figure 8-59. Register control for digital features 56 Submit Document Feedback Copyright © 2020 Texas Instruments Incorporated Product Folder Links: ADC3643 ADC3643 www.ti.com SBAS886 – OCTOBER 2020 Figure 8-60. Register 0x25 7 6 DDC MUX EN R/W-0 5 4 DECIMATION R/W-0 R/W-0 R/W-0 3 2 1 0 REAL OUT 0 0 MIX PHASE R/W-0 R/W-0 R/W-0 R/W-0 Table 8-33. Register 0x25 Field Descriptions Bit Field Type Reset Description 7 DDC MUX EN R/W 0 Enables the digital mux between ADCs and decimation filters. This bit is required for DDC mux settings in register 0x024 (D4, D3) to go into effect. 0: DDC mux disabled 1: DDC mux enabled 6-4 DECIMATION R/W 000 Complex decimation setting. This applies to both channels. 000: Bypass mode (no decimation) 001: Decimation by 2 010: Decimation by 4 011: Decimation by 8 100: Decimation by 16 101: Decimation by 32 others: not used REAL OUT R/W 0 This bit selects real output decimation. This mode applies to both channels. In this mode, the decimation filter is a low pass filter and no complex mixing is performed to reduce power consumption. For maximum power savings the NCO in this case should be set to 0. 0: Complex decimation 1: Real decimation 0 R/W 0 Must write 0 MIX PHASE R/W 0 This bit used to invert the NCO phase 0: NCO phase as is. 1: NCO phase inverted. 3 2-1 0 Submit Document Feedback Copyright © 2020 Texas Instruments Incorporated Product Folder Links: ADC3643 57 ADC3643 www.ti.com SBAS886 – OCTOBER 2020 Figure 8-61. Register 0x26 7 6 MIX GAIN A R/W-0 R/W-0 5 4 MIX RES A FS/4 MIX A 3 R/W-0 R/W-0 2 MIX GAIN B R/W-0 R/W-0 1 0 MIX RES B FS/4 MIX B R/W-0 R/W-0 Table 8-34. Register 0x26 Field Descriptions Bit Field Type Reset Description 7-6 MIX GAIN A R/W 00 This bit applies a 0, 3 or 6-dB digital gain to the output of digital mixer to compensate for the mixing loss for channel A. 00: no digital gain added 01: 3-dB digital gain added 10: 6-dB digital gain added 11: not used 5 MIX RES A R/W 0 Toggling this bit resets the NCO phase of channel A and loads the new NCO frequency. This bit does not self reset. 4 FS/4 MIX A R/W 0 Enables FS/4 mixing for DDC A (complex decimation only). 0: FS/4 mixing disabled. 1: FS/4 mixing enabled. 3-2 MIX GAIN B R/W 00 This bit applies a 0, 3 or 6-dB digital gain to the output of digital mixer to compensate for the mixing loss for channel B. 00: no digital gain added 01: 3-dB digital gain added 10: 6-dB digital gain added 11: not used 1 MIX RES B R/W 0 Toggling this bit resets the NCO phase of channel B and loads the new NCO frequency. This bit does not self reset. 0 FS/4 MIX B R/W 0 Enables FS/4 mixing for DDC B (complex decimation only). 0: FS/4 mixing disabled. 1: FS/4 mixing enabled. Figure 8-62. Register 0x27 7 6 5 4 3 2 1 0 0 0 0 OP ORDER A Q-DEL A FS/4 MIX PH A 0 0 R/W-0 R/W-0 R/W-0 R/W-0 R/W-0 R/W-0 R/W-0 R/W-0 Table 8-35. Register 0x27 Field Descriptions Bit Field Type Reset Description 7-5 0 R/W 0 Must write 0 4 OP ORDER A R/W 0 Swaps the I and Q output order for channel A. See Table 8-36 for recommended settings. Only used with complex decimation. Set to 0 with real decimation. 0: Output order is I[n], Q[n] 1: Output order is swapped: Q[n], I[n] 3 Q-DEL A R/W 0 This delays the Q-sample output of channel A by one. See Table 8-36 for recommended settings. Only used with complex decimation. Set to 0 with real decimation. 0: Output order is I[n], Q[n] 1: Q-sample is delayed by 1 sample: I[n], Q[n+1], I[n+1], Q[n+2] 2 FS/4 MIX PH A R/W 0 Inverts the mixer phase for channel A when using FS/4 mixer 0: Mixer phase is non-inverted 1: Mixer phase is inverted 0 R/W 0 Must write 0 1-0 58 Submit Document Feedback Copyright © 2020 Texas Instruments Incorporated Product Folder Links: ADC3643 ADC3643 www.ti.com SBAS886 – OCTOBER 2020 Table 8-36. OP-ORDER and Q-DELAY Register Settings for Complex Decimation SCMOS INTERFACE OP-ORDER Q-DELAY 2-wire 1 0 1-wire 0 1 1/2-wire 1 1 Figure 8-63. Register 0x2A/B/C/D 7 6 5 4 3 2 1 0 R/W-0 R/W-0 R/W-0 R/W-0 NCO A [7:0] NCO A [15:8] NCO A [23:16] NCO A [31:24] R/W-0 R/W-0 R/W-0 R/W-0 Table 8-37. Register 0x2A/2B/2C/2D Field Descriptions Bit Field Type Reset Description 7-0 NCO A [31:0] R/W 0 Sets the 32 bit NCO value for decimation filter channel A. The NCO value is fNCO× 232/FS In real decimation mode these registers are automatically set to 0. Figure 8-64. Register 0x2E/2F/30 7 6 5 4 3 2 1 0 0 0 0 OP ORDER B Q-DEL B FS/4 MIX PH B 0 0 R/W-0 R/W-0 R/W-0 R/W-0 R/W-0 R/W-0 R/W-0 R/W-0 Table 8-38. Register 0x2E/2F/30 Field Descriptions Bit Field Type Reset Description 7-5 0 R/W 0 Must write 0 4 OP ORDER B R/W 0 Swaps the I and Q output order for channel B. See Table 8-36 for recommended settings. Only used with complex decimation. Set to 0 with real decimation. 0: Output order is I[n], Q[n] 1: Output order is swapped: Q[n], I[n] 3 Q-DEL B R/W 0 This delays the Q-sample output of channel B by one. See Table 8-36 for recommended settings. Only used with complex decimation. Set to 0 with real decimation. 0: Output order is I[n], Q[n] 1: Q-sample is delayed by 1 sample: I[n], Q[n+1], I[n+1], Q[n+2] 2 FS/4 MIX PH B R/W 0 Inverts the mixer phase for channel B when using FS/4 mixer 0: Mixer phase is non-inverted 1: Mixer phase is inverted 0 R/W 0 Must write 0 1-0 Submit Document Feedback Copyright © 2020 Texas Instruments Incorporated Product Folder Links: ADC3643 59 ADC3643 www.ti.com SBAS886 – OCTOBER 2020 Figure 8-65. Register 0x31/32/33/34 7 6 5 4 3 2 1 0 R/W-0 R/W-0 R/W-0 R/W-0 NCO B [7:0] NCO B [15:8] NCO B [23:16] NCO B [31:24] R/W-0 R/W-0 R/W-0 R/W-0 Table 8-39. Register 0x31/32/33/34 Field Descriptions Bit Field Type Reset Description 7-0 NCO B [31:0] R/W 0 Sets the 32 bit NCO value for decimation filter channel B. The NCO value is fNCO× 232/FS In real decimation mode these registers are automatically set to 0. Figure 8-66. Register 0x8F 7 6 5 4 3 2 1 0 0 0 0 0 0 0 FORMAT A 0 R/W-0 R/W-0 R/W-0 R/W-0 R/W-0 R/W-0 R/W-0 R/W-0 Table 8-40. Register 0x8F Field Descriptions Bit Field Type Reset Description 7-2 0 R/W 0 Must write 0 1 FORMAT A R/W 0 This bit sets the output data format for channel A. 0: 2s complement 1: Offset binary 0 0 R/W 0 Must write 0 Figure 8-67. Register 0x92 7 6 5 4 3 2 1 0 0 0 0 0 0 0 FORMAT B 0 R/W-0 R/W-0 R/W-0 R/W-0 R/W-0 R/W-0 R/W-0 R/W-0 Table 8-41. Register 0x92 Field Descriptions 60 Bit Field Type Reset Description 7-2 0 R/W 0 Must write 0 1 FORMAT B R/W 0 This bit sets the output data format for channel B. 0: 2s complement 1: Offset binary 0 0 R/W 0 Must write 0 Submit Document Feedback Copyright © 2020 Texas Instruments Incorporated Product Folder Links: ADC3643 ADC3643 www.ti.com SBAS886 – OCTOBER 2020 9 Application and Implementation Note Information in the following applications sections is not part of the TI component specification, and TI does not warrant its accuracy or completeness. TI’s customers are responsible for determining suitability of components for their purposes. Customers should validate and test their design implementation to confirm system functionality. 9.1 Typical Application A spectrum analyzer is a typical frequency domain application for the ADC364x and its front end circuitry is very similar to several other systems such as software defined radio (SDR), radar or communications. Some applications require frequency coverage including DC or near DC (e.g. sonar) so it’s included in this example. 0.6V 10 uF VREF 10 k REFBUF Glitch Filter 1.2V REF 33 Low Pass Filter 100 pF 10 NCO 180nH AMP AIN 33 ADC N 10 180nH VCM DCLK 0.95V 33 Low Pass Filter 100 pF FPGA Dig I/F CVCM DA0..6 NCO 10 DB0..6 180nH AMP BIN 33 N ADC 10 180nH Glitch Filter Device Clock CLK SCLK SEN SDIO RESET PDN/ SYNC Control Figure 9-1. Typical configuration for a spectrum analyzer with DC support 9.1.1 Design Requirements Frequency domain applications cover a wide range of frequencies from low input frequencies at or near DC in the 1st Nyquist zone to undersampling in higher Nyquist zones. If very low input frequency is supported then the input has to be DC coupled and the ADC driven by a fully differential amplifier (FDA). If low frequency support is not needed then AC coupling and use of a balun may be more suitable. The internal reference is used since DC precision is not needed. However the ADC AC performance is highly dependent on the quality of the external clock source. If in-band interferers can be present then the ADC SFDR performance will be a key care about as well. A higher ADC sampling rate is desirable in order to relax the external anti-aliasing filter – an internal decimation filter can be used to reduce the digital output rate afterwards. Table 9-1. Design key care-abouts FEATURE DESCRIPTION Signal Bandwidth DC to 20 MHz Input Driver Single ended to differential signal conversion and DC coupling Clock Source External clock with low jitter Submit Document Feedback Copyright © 2020 Texas Instruments Incorporated Product Folder Links: ADC3643 61 ADC3643 www.ti.com SBAS886 – OCTOBER 2020 When designing the amplifier/filter driving circuit, the ADC input full-scale voltage needs to be taken into consideration. For example, the ADC364x input full-scale is 2.25 Vpp. When factoring in ~ 1 dB for insertion loss of the filter, then the amplifier needs to deliver close to 2.5 Vpp. The amplifier distortion performance will degrade with a larger output swing and considering the ADC common mode input voltage the amplifier may not be able to deliver the full swing. The ADC364x provides an output common mode voltage of 0.95V and the THS4541 for example can only swing within 250 mV of its negative supply. A unipolar 3.3 V amplifier power supply will thus limit the maximum voltage swing to ~ 2.8Vpp. Additionally input voltage protection diodes may be needed to protect the ADC from over-voltage events. Table 9-2. Output voltage swing of THS4541 vs power supply DEVICE MIN OUTPUT VOLTAGE MAX SWING WITH 3.3 V/ 0 V SUPPLY THS4541 VS- + 250 mV 2.8 Vpp 9.1.2 Detailed Design Procedure 9.1.2.1 Input Signal Path Depending on desired input signal frequency range the THS4551 and THS4541 provide very good low power options to drive the ADC inputs. Table 9-3 provides a comparison between the THS4551 and THS4541 and the power consumption vs usable frequency trade off. Table 9-3. Fully Differential Amplifier Options DEVICE CURRENT (IQ) PER CHANNEL USABLE FREQUENCY RANGE THS4561 0.8 mA < 3 MHz THS4551 1.4 mA < 10 MHz THS4541 10 mA < 70 MHz The low pass filter design (topology, filter order) is driven by the application itself. However, when designing the low pass filter, the optimum load impedance for the amplifier should be taken into consideration as well. Between the low pass filter and the ADC input the sampling glitch filter needs to added as well as shown in Section 8.3.1.2.1. In this example the DC - 30 MHz glitch filter is selected. 9.1.2.2 Sampling Clock Applications operating with low input frequencies (such as DC to 20 MHz) typically are less sensitive to performance degradation due to clock jitter. The internal ADC aperture jitter improves with faster rise and fall times (i.e. square wave vs sine wave). Table 9-4 provides an overview of the estimated SNR performance of the ADC364x based on different amounts of jitter of the external clock source. The SNR is estimated based on ADC364x thermal noise of 79 dBFS and input signal at -1dBFS. Table 9-4. ADC SNR performance across vs input frequency for different amounts of external clock jitter INPUT FREQUENCY TJ,EXT = 100 fs TJ,EXT = 250 fs TJ,EXT = 500 fs TJ,EXT = 1 ps 5 MHz 79.0 79.0 78.9 78.7 10 MHz 79.0 78.9 78.7 78.0 20 MHz 78.8 78.6 77.9 75.9 Termination of the clock input should be considered for long clock traces. 9.1.2.3 Voltage Reference The ADC364x is configured to internal reference operation by applying 0.6 V to the REFBUF pin. 62 Submit Document Feedback Copyright © 2020 Texas Instruments Incorporated Product Folder Links: ADC3643 ADC3643 www.ti.com SBAS886 – OCTOBER 2020 9.1.3 Application Curves 0 0 -20 -20 -40 -40 Amplitude (dBFS) Amplitude (dBFS) The following FFT plots show the performance of THS4541 driving the ADC364x operated at 65 MSPS with a full-scale input at -1 dBFS with input frequencies at 1, 5, 10 and 20 MHz. -60 -80 -60 -80 -100 -100 -120 -120 -140 -140 0 10 20 Input Frequency (MHz) 0 30 10 20 Input Frequency (MHz) 30 ADC3 ADC3 SNR = 78.7 dBFS, SFDR = 90 dBc SNR = 78.6 dBFS, SFDR = 96 dBc Figure 9-3. Single Tone FFT at FIN = 5 MHz 0 0 -20 -20 -40 -40 Amplitude (dBFS) Amplitude (dBFS) Figure 9-2. Single Tone FFT at FIN = 1 MHz -60 -80 -60 -80 -100 -100 -120 -120 -140 -140 0 10 20 Input Frequency (MHz) 0 30 10 20 Input Frequency (MHz) 30 ADC3 ADC3 SNR = 78.0 dBFS, SFDR = 92 dBc Figure 9-4. Single Tone FFT at FIN = 10 MHz SNR = 75.9 dBFS, SFDR = 81 dBc Figure 9-5. Single Tone FFT at FIN = 20 MHz Submit Document Feedback Copyright © 2020 Texas Instruments Incorporated Product Folder Links: ADC3643 63 ADC3643 www.ti.com SBAS886 – OCTOBER 2020 10 Initialization Set Up After power-up, the internal registers must be initialized to their default values through a hardware reset by applying a high pulse on the RESET pin, as shown in Figure 10-1. 1. Apply AVDD and IOVDD (no specific sequence required). After AVDD is applied the internal bandgap reference will power up and settle out in ~ 2ms. 2. Configure REFBUF pin (pull high or low even if configured via SPI later on) and apply the sampling clock. 3. Apply hardware reset. After hardware reset is released, the default registers are loaded from internal fuses and the internal power up capacitor calibration is initiated. The calibration takes approximately 200000 clock cycles. 4. Begin programming using SPI interface. AVDD IOVDD t1 REFBUF Ext VREF CLK t3 t2 RESET SEN Figure 10-1. Initialization of serial registers after power up Table 10-1. Power-up timing MIN t1 Power-on delay: delay from power up to logic level of REFBUF pin t2 Delay from REFBUF pin logic level to RESET rising edge t4 RESET pulse width t5 Delay from RESET disable to SEN active TYP MAX UNIT 2 ms 100 ns 1 us ~ 200000 clock cycles 10.1 Register Initialization During Operation If required, the serial interface registers can be cleared and reset to default settings during operation either: • • through a hardware reset or by applying a software reset. When using the serial interface, set the RESET bit (D0 in register address 0x00) high. This setting initializes the internal registers to the default values and then self-resets the RESET bit low. In this case, the RESET pin is kept low. After hardware or software reset the wait time is also ~ 200000 clock cycles before the SPI registers can be programmed. 64 Submit Document Feedback Copyright © 2020 Texas Instruments Incorporated Product Folder Links: ADC3643 ADC3643 www.ti.com SBAS886 – OCTOBER 2020 11 Power Supply Recommendations The ADC364x requires two different power-supplies. The AVDD rail provides power for the internal analog circuits and the ADC itself while the IOVDD rail powers the digital interface and the internal digital circuits like decimation filter or output interface mapper. Power sequencing is not required. The AVDD power supply must be low noise in order to achieve data sheet performance. In applications operating near DC, the 1/f noise contribution of the power supply needs to be considered as well. The ADC is designed for very good PSRR which aides with the power supply filter design. 55 PSRR (dB) 50 45 40 35 30 0.05 0.1 1 10 Frequency of Signal on AVDD (MHz) 100 D42_ Figure 11-1. Power supply rejection ratio (PSRR) vs frequency There are two recommended power-supply architectures: 1. Step down using high-efficiency switching converters, followed by a second stage of regulation using a low noise LDO to provide switching noise reduction and improved voltage accuracy. 2. Directly step down the final ADC supply voltage using high-efficiency switching converters. This approach provides the best efficiency, but care must be taken to ensure switching noise is minimized to prevent degraded ADC performance. TI WEBENCH Power Designer can be used to select and design the individual power-supply elements needed: see the WEBENCH Power Designer Recommended switching regulators for the first stage include the TPS62821, and similar devices. Recommended low dropout (LDO) linear regulators include the TPS7A4701, TPS7A90, LP5901, and similar devices. For the switch regulator only approach, the ripple filter must be designed with a notch frequency that aligns with the switching ripple frequency of the DC/DC converter. Note the switching frequency reported from WEBENCH and design the EMI filter and capacitor combination to have the notch frequency centered as needed. Figure 11-2 and Figure 11-3 illustrate the two approaches. AVDD and IOVDD supply voltages should not be shared in order to prevent digital switching noise from coupling into the analog signal chain. Submit Document Feedback Copyright © 2020 Texas Instruments Incorporated Product Folder Links: ADC3643 65 ADC3643 www.ti.com SBAS886 – OCTOBER 2020 2.1V DC/DC Regulator 5V-12V FB FB 1.8V AVDD LDO 10uF 10uF 0.1uF 47uF 47uF GND GND GND FB IOVDD 10uF 10uF 0.1uF FB = Ferrite bead filter GND Figure 11-2. Example: LDO Linear Regulator Approach 5V-12V 1.8V DC/DC Regulator EMI FILTER FB AVDD 10uF 10uF 10uF 10uF 10uF 0.1uF GND GND FB IOVDD 10uF 10uF 0.1uF GND Ripple filter notch frequency to match switching frequency of the DC/DC regulator FB = Ferrite bead filter Figure 11-3. Example Switcher-Only Approach 66 Submit Document Feedback Copyright © 2020 Texas Instruments Incorporated Product Folder Links: ADC3643 ADC3643 www.ti.com SBAS886 – OCTOBER 2020 12 Layout 12.1 Layout Guidelines There are several critical signals which require specific care during board design: 1. Analog input and clock signals • Traces should be as short as possible and vias should be avoided where possible to minimize impedance discontinuities. • Traces should be routed using loosely coupled 100-Ω differential traces. • Differential trace lengths should be matched as close as possible to minimize phase imbalance and HD2 degradation. 2. Digital output interface • A 20 Ω series isolation resistor should be used on each CMOS output and placed close the digital output. This isolation resistor limits the output current into the capacitive load and thus minimizes the switching noise inside the ADC. When driving longer distances a buffer should be used. The resistor value should be optimized for the desired output data rate. 3. Voltage reference • The bypass capacitor should be placed as close to the device pins as possible and connected between VREF and REFGND – on top layer avoiding vias. • Depending on configuration an additional bypass capacitor between REFBUF and REFGND may be recommended and should also be placed as close to pins as possible on top layer. 4. Power and ground connections • Provide low resistance connection paths to all power and ground pins. • Use power and ground planes instead of traces. • Avoid narrow, isolated paths which increase the connection resistance. • Use a signal/ground/power circuit board stackup to maximize coupling between the ground and power plane. 12.2 Layout Example The following screen shot shows the top layer of the ADC364x EVM. • • • Signal and clock inputs are routed as differential signals on the top layer avoiding vias. Serial CMOS output interface lanes with isolation resistor and digital buffer. Bypass caps are close to the VREF pin on the top layer avoiding vias. Bypass caps on VREF close to the pins CMOS output lines with isolation resistor and buffer close by Clock routing without vias Analog inputs on top layer (no vias) Figure 12-1. Layout example: top layer of ADC364x EVM Submit Document Feedback Copyright © 2020 Texas Instruments Incorporated Product Folder Links: ADC3643 67 ADC3643 www.ti.com SBAS886 – OCTOBER 2020 13 Device and Documentation Support 13.1 Receiving Notification of Documentation Updates To receive notification of documentation updates, navigate to the device product folder on ti.com. Click on Subscribe to updates to register and receive a weekly digest of any product information that has changed. For change details, review the revision history included in any revised document. 13.2 Support Resources TI E2E™ support forums are an engineer's go-to source for fast, verified answers and design help — straight from the experts. Search existing answers or ask your own question to get the quick design help you need. Linked content is provided "AS IS" by the respective contributors. They do not constitute TI specifications and do not necessarily reflect TI's views; see TI's Terms of Use. 13.3 Trademarks TI E2E™ is a trademark of Texas Instruments. All trademarks are the property of their respective owners. 13.4 Electrostatic Discharge Caution This integrated circuit can be damaged by ESD. Texas Instruments recommends that all integrated circuits be handled with appropriate precautions. Failure to observe proper handling and installation procedures can cause damage. ESD damage can range from subtle performance degradation to complete device failure. Precision integrated circuits may be more susceptible to damage because very small parametric changes could cause the device not to meet its published specifications. 13.5 Glossary TI Glossary This glossary lists and explains terms, acronyms, and definitions. 14 Mechanical, Packaging, and Orderable Information The following pages include mechanical, packaging, and orderable information. This information is the most current data available for the designated devices. This data is subject to change without notice and revision of this document. For browser-based versions of this data sheet, refer to the left-hand navigation. 68 Submit Document Feedback Copyright © 2020 Texas Instruments Incorporated Product Folder Links: ADC3643 PACKAGE OPTION ADDENDUM www.ti.com 10-Dec-2020 PACKAGING INFORMATION Orderable Device Status (1) Package Type Package Pins Package Drawing Qty Eco Plan (2) Lead finish/ Ball material MSL Peak Temp Op Temp (°C) Device Marking (3) (4/5) (6) ADC3643IRSBR ACTIVE WQFN RSB 40 3000 RoHS & Green NIPDAU Level-3-260C-168 HR -40 to 105 AZ3643 ADC3643IRSBT ACTIVE WQFN RSB 40 250 RoHS & Green NIPDAU Level-3-260C-168 HR -40 to 105 AZ3643 (1) The marketing status values are defined as follows: ACTIVE: Product device recommended for new designs. LIFEBUY: TI has announced that the device will be discontinued, and a lifetime-buy period is in effect. NRND: Not recommended for new designs. Device is in production to support existing customers, but TI does not recommend using this part in a new design. PREVIEW: Device has been announced but is not in production. Samples may or may not be available. OBSOLETE: TI has discontinued the production of the device. (2) RoHS: TI defines "RoHS" to mean semiconductor products that are compliant with the current EU RoHS requirements for all 10 RoHS substances, including the requirement that RoHS substance do not exceed 0.1% by weight in homogeneous materials. Where designed to be soldered at high temperatures, "RoHS" products are suitable for use in specified lead-free processes. TI may reference these types of products as "Pb-Free". RoHS Exempt: TI defines "RoHS Exempt" to mean products that contain lead but are compliant with EU RoHS pursuant to a specific EU RoHS exemption. Green: TI defines "Green" to mean the content of Chlorine (Cl) and Bromine (Br) based flame retardants meet JS709B low halogen requirements of