Product
Folder
Sample &
Buy
Technical
Documents
Support &
Community
Tools &
Software
TPS61160A, TPS61161A
SLVS937C – MARCH 2009 – REVISED JULY 2016
TPS6116xA White LED Driver with PWM Brightness Control in
2-mm x 2-mm WSON Package
1 Features
3 Description
•
•
With a 40-V rated integrated switch FET, the
TPS61160A/61A is a boost converter that drives
LEDs in series. The boost converter runs at 600-kHz
fixed switching frequency to reduce output ripple,
improve conversion efficiency, and allows for the use
of small external components.
1
•
•
•
•
•
Input Voltage Range: 2.7 V to 18 V
26-V Open LED Protection for TPS61160A
38-V Open LED Protection for TPS61161A
200mV Reference Voltage With ±2% Accuracy
PWM Interface for Brightness Control
Built-in Soft Start
Up to 90% Efficiency
2-mm × 2-mm × 0.8-mm 6-Pin WSON Package
With Thermal Pad
The default white LED current is set with the external
sensor resistor Rset, and the feedback voltage is
regulated to 200 mV, as shown in the typical
application. During the operation, the LED current can
be controlled by a pulse width modulation (PWM)
signal applied to the CTRL pin through which the duty
cycle determines the feedback reference voltage. In
PWM dimming mode, the TPS61160A/61A does not
burst the LED current; therefore, it does not generate
audible noises on the output capacitor. For maximum
protection, the device features integrated open LED
protection that disables the TPS61160A/61A to
prevent the output from exceeding the absolute
maximum ratings during open LED conditions.
2 Applications
•
•
•
•
•
Cellular Phones
Portable Media Players
Ultra Mobile Devices
GPS Receivers
White LED Backlighting for Media Form Factor
Display
The TPS61160A/61A is available in a space-saving,
2-mm × 2-mm WSON package with thermal pad.
Device Information(1)
PART NUMBER PACKAGE
OPEN LED PROTECTION
TPS61160A
TPS61160A use 26 V (typical)
WSON (6)
TPS61161A
TPS61161A use 38 V (typical)
(1) For all available packages, see the orderable addendum at
the end of the data sheet.
Typical Application of TPS61161A
L1
22 mH
VI 3 V to 18 V
C1
1 mF
TPS61161A
ON/OFF
DIMMING
CONTROL
VIN
SW
CTRL
FB
COMP GND
C3
220 nF
L1: TDK VLCF5020T-220MR75-1
C1: Murata GRM188R61E105K
C2: Murata GRM21BR71H105K
D1: ONsemi MBR0540T1
D1
38V MAX
C2
1 mF
Rset
10 W
20 mA
1
An IMPORTANT NOTICE at the end of this data sheet addresses availability, warranty, changes, use in safety-critical applications,
intellectual property matters and other important disclaimers. PRODUCTION DATA.
TPS61160A, TPS61161A
SLVS937C – MARCH 2009 – REVISED JULY 2016
www.ti.com
Table of Contents
1
2
3
4
5
6
7
Features ..................................................................
Applications ...........................................................
Description .............................................................
Revision History.....................................................
Pin Configuration and Functions .........................
Specifications.........................................................
1
1
1
2
3
4
6.1
6.2
6.3
6.4
6.5
6.6
6.7
4
4
4
5
5
6
7
Absolute Maximum Ratings ......................................
ESD Ratings..............................................................
Recommended Operating Conditions.......................
Thermal Information ..................................................
Dissipation Ratings ...................................................
Electrical Characteristics...........................................
Typical Characteristics ..............................................
Detailed Description .............................................. 9
7.1
7.2
7.3
7.4
Overview ................................................................... 9
Functional Block Diagram ......................................... 9
Feature Description................................................... 9
Device Functional Modes........................................ 11
8
Application and Implementation ........................ 12
8.1 Application Information............................................ 12
8.2 Typical Applications ................................................ 12
9 Power Supply Recommendations...................... 20
10 Layout................................................................... 21
10.1 Layout Guidelines ................................................. 21
10.2 Layout Example .................................................... 21
10.3 Thermal Considerations ........................................ 21
11 Device and Documentation Support ................. 22
11.1
11.2
11.3
11.4
11.5
11.6
11.7
11.8
Device Support......................................................
Documentation Support ........................................
Related Links ........................................................
Receiving Notification of Documentation Updates
Community Resources..........................................
Trademarks ...........................................................
Electrostatic Discharge Caution ............................
Glossary ................................................................
22
22
22
22
22
22
22
23
12 Mechanical, Packaging, and Orderable
Information ........................................................... 23
4 Revision History
NOTE: Page numbers for previous revisions may differ from page numbers in the current version.
Changes from Revision B (October 2014) to Revision C
Page
•
Changed Handling Ratings to ESD Ratings; moved storage temperature to Abs Max table ................................................ 4
•
Deleted the "Duty" rows the Recommended Operating Conditions; added "tPWM_MIN" row .................................................... 4
•
Added Receiving Notification of Documentation Updates and Community Resources ....................................................... 22
Changes from Revision A (July 2011) to Revision B
Page
•
Added Device Information and Handling Rating tables, Feature Description, Device Functional Modes, Application
and Implementation, Power Supply Recommendations, Layout, Device and Documentation Support, and
Mechanical, Packaging, and Orderable Information sections; moved some curves to Application Curves section;
change "QFN" to "SON" ......................................................................................................................................................... 1
•
Changed (reversed) the Vi=5V and Vi=3.6V characteristic labels in Figure 3 ....................................................................... 7
Changes from Original (March 2009) to Revision A
Page
•
Deleted "6 LEDs" and "10 LEDs" from the second feature bullet for TPS61160A and TPS61161A Open-LED
Protection, respectively........................................................................................................................................................... 1
•
Deleted "for up to 10 LEDs in Series" from title ..................................................................................................................... 1
•
Added "38V Max" to Typical Application of TPS61161A, top of LED string........................................................................... 1
•
Changed from "...for driving up to 10 white LED" to "...for driving white LED" in first sentence of OPERATION section. .... 9
•
Changed text of last sentence in "OPEN LED PROTECTION" section to clarify circuit description.................................... 10
•
Changed Figure 11 to show separate terminals for COMP and FB..................................................................................... 11
•
Changed Li-Ion Driver for 6 White LEDs With External PWM Dimming Network to clarify schematic ................................ 15
2
Submit Documentation Feedback
Copyright © 2009–2016, Texas Instruments Incorporated
Product Folder Links: TPS61160A TPS61161A
TPS61160A, TPS61161A
www.ti.com
SLVS937C – MARCH 2009 – REVISED JULY 2016
5 Pin Configuration and Functions
DRV Package
6-Pin WSON With Thermal Pad
Top View
Pin Functions
PIN
I/O
DESCRIPTION
2
O
Output of the transconductance error amplifier. Connect an external capacitor to this pin to compensate the
regulator.
CTRL
5
I
Control pin of the boost regulator. Enable and disable device. PWM signal can be applied to the pin for
LED brightness dimming as well.
FB
1
I
Feedback pin for current. Connect the sense resistor from FB to GND.
GND
3
O
Ground
SW
4
I
This is the switching node of the IC. Connect the inductor between the VIN and SW pin. This pin is also
used to sense the output voltage for open LED protection
VIN
6
I
The input supply pin for the IC. Connect VIN to a supply voltage between 2.7 V and 18 V.
NAME
NO.
COMP
Thermal Pad
The thermal pad should be soldered to the analog ground plane. If possible, use thermal via to connect to
ground plane for ideal power dissipation.
Copyright © 2009–2016, Texas Instruments Incorporated
Product Folder Links: TPS61160A TPS61161A
Submit Documentation Feedback
3
TPS61160A, TPS61161A
SLVS937C – MARCH 2009 – REVISED JULY 2016
www.ti.com
6 Specifications
6.1 Absolute Maximum Ratings
over operating free-air temperature range (unless otherwise noted) (1)
Supply voltages on VIN (2)
Voltages on CTRL
(2)
MIN
MAX
UNIT
–0.3
20
V
–0.3
20
V
Voltage on FB and COMP (2)
–0.3
3
V
Voltage on SW (2)
–0.3
40
V
PD
Continuous power dissipation
See Dissipation Ratings
TJ
Operating junction temperature
–40
150
°C
Tstg
Storage temperature
–65
150
°C
VI
(1)
(2)
Stresses beyond those listed under Absolute Maximum Ratings may cause permanent damage to the device. These are stress ratings
only, and functional operation of the device at these or any other conditions beyond those indicated under Recommended Operating
Conditions is not implied. Exposure to absolute-maximum-rated conditions for extended periods may affect device reliability.
All voltage values are with respect to network ground terminal.
6.2 ESD Ratings
MIN
V(ESD)
(1)
(2)
Electrostatic discharge
MAX
Human body model (HBM), per ANSI/ESDA/JEDEC JS-001, all
pins (1)
4000
Charged device model (CDM), per JEDEC specification
JESD22-C101, all pins (2)
1000
UNIT
V
JEDEC document JEP155 states that 500-V HBM allows safe manufacturing with a standard ESD control process.
JEDEC document JEP157 states that 250-V CDM allows safe manufacturing with a standard ESD control process.
6.3 Recommended Operating Conditions
MIN
NOM
MAX
UNIT
VI
Input voltage, VIN
2.7
18
V
VO
Output voltage
VIN
38
V
(1)
L
Inductor
fdim
PWM dimming frequency (2)
tPWM_MIN
Minimum pulse width at PWM input
CIN
Input capacitor
CO
Output capacitor (1)
0.47
10
μF
TA
Operating ambient temperature
–40
85
°C
TJ
Operating junction temperature
–40
125
°C
(1)
(2)
4
10
22
μH
5
100
kHz
50
ns
1
μF
These values are recommended values that have been successfully tested in several applications. Other values may be acceptable in
other applications but should be fully tested by the user.
The device can support the frequency range from 1 kHz to 5 kHz, based on the specification, toff . The output ripple needs to be
considered in the range of 1 kHz to 5 kHz.
Submit Documentation Feedback
Copyright © 2009–2016, Texas Instruments Incorporated
Product Folder Links: TPS61160A TPS61161A
TPS61160A, TPS61161A
www.ti.com
SLVS937C – MARCH 2009 – REVISED JULY 2016
6.4 Thermal Information
THERMAL METRIC
TPS61160A,
TPS61161A
(1)
DRV (WSON)
UNIT
6 PINS
RθJA
Junction-to-ambient thermal resistance
140
RθJC(top)
Junction-to-case (top) thermal resistance
20
(1)
°C/W
For more information about traditional and new thermal metrics, see the IC Package Thermal Metrics application report, SPRA953.
6.5 Dissipation Ratings
BOARD PACKAGE
RθJC
RθJA
Low-K (1)DRV
20°C/W
140°C/W
20°C/W
65°C/W
High-K
(1)
(2)
(2)
DRV
DERATING FACTOR
ABOVE TA = 25°C
TA < 25°C
TA = 70°C
TA = 85°C
7.1 mW/°C
715 mW
395 mW
285 mW
15.4 mW/°C
1540 mW
845 mW
615 mW
The JEDEC low-K (1s) board used to derive this data was a 3 in × 3 in, two-layer board with 2-ounce copper traces on top of the board.
The JEDEC high-K (2s2p) board used to derive this data was a 3 in × 3 in, multilayer board with 1-ounce internal power and ground
planes and 2-ounce copper traces on top and bottom of the board.
Copyright © 2009–2016, Texas Instruments Incorporated
Product Folder Links: TPS61160A TPS61161A
Submit Documentation Feedback
5
TPS61160A, TPS61161A
SLVS937C – MARCH 2009 – REVISED JULY 2016
www.ti.com
6.6 Electrical Characteristics
VIN = 3.6 V, CTRL = VIN; for Min/Max values TA = –40°C to 85°C, typical values are at TA = 25°C (unless otherwise noted)
PARAMETER
TEST CONDITIONS
MIN
TYP
MAX
UNIT
SUPPLY CURRENT
VI
Input voltage range, VIN
IQ
Operating quiescent current into VIN
Device PWM switching no load
2.7
ISD
Shutdown current
CRTL = GND, VIN = 4.2 V
UVLO
Undervoltage lockout threshold
VIN falling
Vhys
Undervoltage lockout hysteresis
2.2
18
V
1.8
mA
1
μA
2.5
70
V
mV
ENABLE AND REFERENCE CONTROL
V(CTRLh)
CTRL logic high voltage
VIN = 2.7 V to 18 V
V(CTRLl)
CTRL logic low voltage
VIN = 2.7 V to 18 V
R(CTRL)
CTRL pull down resistor
toff
CTRL pulse width to shutdown
1.2
V
0.4
400
CTRL high to low
800
1600
2.5
V
kΩ
ms
VOLTAGE AND CURRENT CONTROL
VREF
Voltage feedback regulation voltage
196
200
204
mV
V(REF_PWM)
Voltage feedback regulation voltage
under brightness control
VFB = 50 mV
47
50
53
mV
VFB = 20 mV
17
20
23
IFB
Voltage feedback input bias current
VFB = 200 mV
2
μA
fS
Oscillator frequency
500
600
700
kHz
Dmax
Maximum duty cycle
90%
93%
tmin_on
Minimum on pulse width
Isink
Comp pin sink current
Isource
Comp pin source current
Gea
Error amplifier transconductance
Rea
Error amplifier output resistance
fea
Error amplifier crossover frequency
VFB = 100 mV
40
ns
100
μA
100
240
320
μA
400
μmho
6
MΩ
5 pF connected to COMP
500
kHz
VIN = 3.6 V
0.3
POWER SWITCH
N-channel MOSFET on-resistance
RDS(on)
VIN = 3 V
ILN_NFET
0.6
0.7
N-channel leakage current
VSW = 35 V, TA = 25°C
ILIM
N-Channel MOSFET current limit
D = Dmax
ILIM_Start
Start up current limit
D = Dmax
tHalf_LIM
Time step for half current limit
Vovp
Open LED protection threshold
Measured on the SW pin,
TPS61160A
TPS61161A
Open LED protection threshold on FB
Measured on the FB pin, percentage
of Vref,
Vref = 200 mV and 20 mV
Ω
1
μA
0.84
A
OC and OLP
0.56
0.7
0.4
A
5
V(FB_OVP)
25
37
26
38
ms
27
39
V
50%
tREF
VREF filter time constant
180
μs
tstep
VREF ramp up time
213
μs
160
°C
15
°C
THERMAL SHUTDOWN
Tshutdown
Thermal shutdown threshold
Thysteresis
Thermal shutdown threshold hysteresis
6
Submit Documentation Feedback
Copyright © 2009–2016, Texas Instruments Incorporated
Product Folder Links: TPS61160A TPS61161A
TPS61160A, TPS61161A
www.ti.com
SLVS937C – MARCH 2009 – REVISED JULY 2016
6.7 Typical Characteristics
Table 1. Table of Graphs
FIGURE
Efficiency TPS61160A/61A
VIN = 3.6 V; 4, 6, 8, 10 LEDs; L = 22 μH
Figure 1
Efficiency TPS61160A
Figure 2
Efficiency TPS61161A
Figure 3
Current limit
TA = 25°C
Figure 4
Current limit
Figure 5
PWM dimming linearity
VIN = 3.6 V; PWM Freq = 10 kHz and 40 kHz
Figure 6
Output ripple at PWM dimming
8 LEDs; VIN = 3.6 V; ILOAD = 20 mA; PWM Freq = 10 kHz
Figure 7
Switching waveform
8 LEDs; VIN = 3.6 V; ILOAD = 20 mA; L = 22 μH
Figure 8
Start-up
8 LEDs; VIN = 3.6 V; ILOAD = 20 mA; L =22 μH
Figure 9
Open LED protection
8 LEDs; VIN = 3.6 V; ILOAD = 20 mA; L = 22 μH
Figure 10
100
100
VI = 3.6 V
4 LEDs
VI = 4.2 V
6 LEDs
90
90
8 LEDs
VI = 3 V
80
Efficiency - %
Efficiency - %
80
10 LEDs
70
VI = 3.6 V
70
60
60
4 (12.8 V), 6 (19.2 V) LEDs
8 (25.6 V),10 (32 V) LEDs
50
50
6 LEDs - TPS61160A
40
40
0
10
20
30
Output Current - mA
40
50
0
10
20
30
Output Current - mA
40
50
Figure 2. Efficiency vs Output Current
Figure 1. Efficiency vs Output Current
100
1000
VI = 12 V
900
Efficiency - %
80
Switch Current Limit - mA
90
VI = 3.6 V
VI = 5 V
70
60
50
800
700
600
500
400
10 LEDs - TPS61161A
40
0
10
20
30
Output Current - mA
40
Figure 3. Efficiency vs Output Current
50
300
20
30
40
50
60
Duty Cycle - %
70
80
90
Figure 4. Switch Current Limit vs Duty Cycle
Copyright © 2009–2016, Texas Instruments Incorporated
Product Folder Links: TPS61160A TPS61161A
Submit Documentation Feedback
7
TPS61160A, TPS61161A
SLVS937C – MARCH 2009 – REVISED JULY 2016
www.ti.com
1000
200
10 kHz, 40 kHz
900
FB Voltage - mV
Switch Current Limit - mA
160
800
700
600
120
80
500
40
400
300
-40
0
-20
0
20
40
60
80
Temperature - °C
100
120
140
Figure 5. Switch Current Limit vs Temperature
0
20
40
60
PWM Duty Cycle - %
80
100
Figure 6. FB Voltage vs PWM Duty Cycle
PWM 2 V/div
SW
20 V/div
VOUT
20 mV/div
AC
VOUT 20 mV/div AC
IL
200 mA/div
ILED 10 mA/div
t - 1 ms/div
t - 100 ms/div
Figure 8. Switching Waveform
Figure 7. Output Ripple at PWM Dimming
CTRL
5 V/div
OPEN LED
5 V/div
FB
200 mV/div
VOUT
10 V/div
VOUT
10 V/div
COMP
500 mV/div
IL
200 mA/div
IL
200 mA/div
t - 100 ms/div
t - 2 ms/div
Figure 9. Start-Up
8
Submit Documentation Feedback
Figure 10. Open LED Protection
Copyright © 2009–2016, Texas Instruments Incorporated
Product Folder Links: TPS61160A TPS61161A
TPS61160A, TPS61161A
www.ti.com
SLVS937C – MARCH 2009 – REVISED JULY 2016
7 Detailed Description
7.1 Overview
The TPS61160A/61A is a high-efficiency, high output voltage boost converter in small package size that is ideal
for driving white LED in series. The serial LED connection provides even illumination by sourcing the same
output current through all LEDs, eliminating the need for expensive factory calibration. The device integrates 40V/0.7-A switch FET and operates in pulse width modulation (PWM) with 600-kHz fixed switching frequency. For
operation see the block diagram. The duty cycle of the converter is set by the error amplifier output and the
current signal applied to the PWM control comparator. The control architecture is based on traditional currentmode control; therefore, a slope compensation is added to the current signal to allow stable operation for duty
cycles larger than 50%. The feedback loop regulates the FB pin to a low reference voltage (200 mV typical),
reducing the power dissipation in the current sense resistor.
7.2 Functional Block Diagram
C2
D1
1
Rset
4
L1
FB
SW
Reference
Control
Error
Amplifer
OLP
Vin
6
COMP
2
C1
PWM Control
C3
5
CTRL
Soft
Start-up
Ramp
Generator
+
Current
Sensor
Oscillator
GND
3
7.3 Feature Description
7.3.1 Soft Start-Up
Soft-start circuitry is integrated into the IC to avoid a high inrush current during start-up. After the device is
enabled, the voltage at FB pin ramps up to the reference voltage in 32 steps, each step takes 213 μs. This
ensures that the output voltage rises slowly to reduce the input current. Additionally, for the first 5 msec after the
COMP voltage ramps, the current limit of the switch is set to half of the normal current limit spec. During this
period, the input current is kept below 400 mA (typical). See the start-up waveform of a typical example,
Figure 9.
Copyright © 2009–2016, Texas Instruments Incorporated
Product Folder Links: TPS61160A TPS61161A
Submit Documentation Feedback
9
TPS61160A, TPS61161A
SLVS937C – MARCH 2009 – REVISED JULY 2016
www.ti.com
Feature Description (continued)
7.3.2 Open LED Protection
Open LED protection circuitry prevents IC damage as the result of white LED disconnection. The
TPS61160A/61A monitors the voltage at the SW pin and FB pin during each switching cycle. The circuitry turns
off the switch FET and shuts down the IC when both of the following conditions persist for 8 switching clock
cycles: (1) the SW voltage exceeds the VOVP threshold and (2) the FB voltage is less than half of regulation
voltage. As a result, the output voltage falls to the level of the input supply. The device remains in shutdown
mode until it is enabled by toggling the CTRL pin logic. To allow the use of inexpensive low-voltage output
capacitor, the TPS61160A/61A has different open lamp protection thresholds. The threshold is set at 26 V for the
TPS61160A and 38 V for the TPS61161A. Select the appropriate device so that the product of the number of
external LEDs and each LED's maximum forward voltage plus the 200 mV reference voltage does not exceed
the minimum OVP threshold or (nLEDS X VLED(MAX)) + 200 mV ≤ VOVP(MIN).
7.3.3 Shutdown
The TPS61160A/61A enters shutdown mode when the CTRL voltage is logic low for more than 2.5 ms. During
shutdown, the input supply current for the device is less than 1 μA (max). Although the internal FET does not
switch in shutdown, there is still a DC current path between the input and the LEDs through the inductor and
Schottky diode. The minimum forward voltage of the LED array must exceed the maximum input voltage to
ensure that the LEDs remain off in shutdown; however, in the typical application with two or more LEDs, the
forward voltage is large enough to reverse bias the Schottky and keep leakage current low.
7.3.4 Current Program
The FB voltage is regulated by a low 0.2-V reference voltage. The LED current is programmed externally using a
current-sense resistor in series with the LED string. The value of the RSET is calculated using Equation 1:
VFB
ILED
RSET
where
•
•
•
ILED = output current of LEDs
VFB = regulated voltage of FB
RSET = current sense resistor
(1)
The output current tolerance depends on the FB accuracy and the current sensor resistor accuracy.
7.3.5 PWM Brightness Dimming
When the CTRL pin is constantly high, the FB voltage is regulated to 200 mV typically. However, the CTRL pin
allows a PWM signal to reduce this regulation voltage; therefore, it achieves LED brightness dimming. The
relationship between the duty cycle and FB voltage is given by Equation 2.
VFB Duty u 200 mV
where
•
•
Duty = duty cycle of the PWM signal
200 mV = internal reference voltage
(2)
As shown in Figure 11, the IC chops up the internal 200-mV reference voltage at the duty cycle of the PWM
signal. The pulse signal is then filtered by an internal low pass filter. The output of the filter is connected to the
error amplifier as the reference voltage for the FB pin regulation. Therefore, although a PWM signal is used for
brightness dimming, only the WLED DC current is modulated, which is often referred as analog dimming. This
eliminates the audible noise which often occurs when the LED current is pulsed in replica of the frequency and
duty cycle of PWM control. Unlike other scheme which filters the PWM signal for analog dimming,
TPS61160A/61A regulation voltage is independent of the PWM logic voltage level which often has large
variations.
For optimum performance, use the PWM dimming frequency in the range of 5 kHz to 100 kHz. The requirement
of minimum dimming frequency comes from the output ripple. Low frequency causes high output ripple. Because
the CTRL pin is logic only pin, applying an external RC filter to the pin does not work.
10
Submit Documentation Feedback
Copyright © 2009–2016, Texas Instruments Incorporated
Product Folder Links: TPS61160A TPS61161A
TPS61160A, TPS61161A
www.ti.com
SLVS937C – MARCH 2009 – REVISED JULY 2016
Feature Description (continued)
VBG
200 mV
CTRL
Error
Amplifier
COMP
FB
Figure 11. Block Diagram of Programmable FB Voltage Using PWM Signal
To use lower PWM dimming, add an external RC network connected to the FB pin as shown in Figure 15).
7.3.6 Undervoltage Lockout
An undervoltage lockout prevents operation of the device at input voltages below typical 2.2 V. When the input
voltage is below the undervoltage threshold, the device is shutdown and the internal switch FET is turned off. If
the input voltage rises by undervoltage lockout hysteresis, the IC restarts.
7.3.7 Thermal Shutdown
An internal thermal shutdown turns off the device when the typical junction temperature of 160°C is exceeded.
The device is released from shutdown automatically when the junction temperature decreases by 15°C.
7.4 Device Functional Modes
7.4.1 Operation with CTRL
When the CTRL pin is held below the VIL threshold, the device is disabled, and switching is inhibited. The IC
quiescent current is reduced in this state. When VIN is above the UVLO threshold, and the CTRL terminal is
increased above the VIH threshold the soft-start sequence initiates then the device becomes active.
7.4.2 External PWM Dimming
For assistance in selecting the proper values for Rset, R1-R3, RFLTR, CFLTR and D2 for the specific
application, refer to How to Use Analog Dimming With the TPS6116x (SLVA471) and/or Design Tool for Analog
Dimming Using a PWM Signal (http://www.ti.com/lit/zip/slvc366). Also see Choosing Component Values section
below.
Copyright © 2009–2016, Texas Instruments Incorporated
Product Folder Links: TPS61160A TPS61161A
Submit Documentation Feedback
11
TPS61160A, TPS61161A
SLVS937C – MARCH 2009 – REVISED JULY 2016
www.ti.com
8 Application and Implementation
NOTE
Information in the following applications sections is not part of the TI component
specification, and TI does not warrant its accuracy or completeness. TI’s customers are
responsible for determining suitability of components for their purposes. Customers should
validate and test their design implementation to confirm system functionality.
8.1 Application Information
The TPS61160A/61A provides a complete high-performance LED lighting solution for mobile devices supporting
a single string of 6 (TPS61160A) or 10 (TPS61161A) white LEDs.
8.2 Typical Applications
8.2.1 Typical Application of TPS61161A
L1
22 mH
VI 3 V to 18 V
C1
1 mF
TPS61161A
ON/OFF
DIMMING
CONTROL
VIN
SW
CTRL
FB
COMP GND
C3
220 nF
D1
38V MAX
C2
1 mF
Rset
10 W
L1: TDK VLCF5020T-220MR75-1
C1: Murata GRM188R61E105K
C2: Murata GRM21BR71H105K
D1: ONsemi MBR0540T1
20 mA
Figure 12. Typical Application of TPS61161A
8.2.1.1 Design Requirements
12
DESIGN PARAMETER
EXAMPLE VALUE
Inductor
22 µH
Minimum input voltage
3V
Number of series LED
10
LED maximum forward voltage (Vf)
3.3 V
Schottky diode forward voltage (Vf)
0.2 V
Efficiency (η)
85%
Switching frequency (SW)
600 kHz
Submit Documentation Feedback
Copyright © 2009–2016, Texas Instruments Incorporated
Product Folder Links: TPS61160A TPS61161A
TPS61160A, TPS61161A
www.ti.com
SLVS937C – MARCH 2009 – REVISED JULY 2016
Applying Equation 3 and Equation 4, when VIN is 3 V, 10 LEDs output equivalent to VOUT of 32.2 V, the inductor
is 22 μH, the Schottky forward voltage is 0.2 V, the maximum output current is 47 mA in typical condition.
8.2.1.2 Detailed Design Procedure
8.2.1.2.1 Maximum Output Current
The overcurrent limit in a boost converter limits the maximum input current, and thus maximum input power for a
given input voltage. Maximum output power is less than maximum input power due to power conversion losses.
Therefore, the current limit setting, input voltage, output voltage and efficiency can all change maximum current
output. The current limit clamps the peak inductor current; therefore, the ripple has to be subtracted to derive
maximum DC current. The ripple current is a function of switching frequency, inductor value and duty cycle.
Equation 3 and Equation 4 take into account of all the above factors for maximum output current calculation.
1
Ip
ª
§
1
1 ·º
«L u Fs u ¨
¸»
© Vout Vf Vin Vin ¹ ¼»
¬«
where
•
•
•
•
•
Ip = inductor peak to peak ripple
L = inductor value
Vf = Schottky diode forward voltage
Fs = switching frequency
Vout = output voltage of the boost converter. It is equal to the sum of VFB and the voltage drop across LEDs
(3)
I out _max
Vin u I lim
Ip / 2 u K
Vout
where
•
•
•
Iout_max = maximum output current of the boost converter
Ilim = over current limit
η = efficiency
(4)
8.2.1.2.2 Inductor Selection
The selection of the inductor affects steady state operation as well as transient behavior and loop stability. These
factors make it the most important component in power regulator design. There are three important inductor
specifications, inductor value, DC resistance and saturation current. Considering inductor value alone is not
enough.
The inductor value determines the inductor ripple current. Choose an inductor that can handle the necessary
peak current without saturating, according to half of the peak-to-peak ripple current given by Equation 3, pause
the inductor DC current given by:
Vout u Iout
I in _DC
Vin u K
(5)
Inductor values can have ±20% tolerance with no current bias. When the inductor current approaches saturation
level, its inductance can decrease 20% to 35% from the 0A value depending on how the inductor vendor defines
saturation current. Using an inductor with a smaller inductance value forces discontinuous PWM when the
inductor current ramps down to zero before the end of each switching cycle. This reduces the boost converter’s
maximum output current, causes large input voltage ripple and reduces efficiency. Large inductance value
provides much more output current and higher conversion efficiency. For these reasons, a 10 μH to 22 μH
inductor value range is recommended. A 22 μH inductor optimized the efficiency for most application while
maintaining low inductor peak to peak ripple. Table 2 lists the recommended inductor for the TPS61160A/61A.
When recommending inductor value, the factory has considered –40% and +20% tolerance from its nominal
value.
Copyright © 2009–2016, Texas Instruments Incorporated
Product Folder Links: TPS61160A TPS61161A
Submit Documentation Feedback
13
TPS61160A, TPS61161A
SLVS937C – MARCH 2009 – REVISED JULY 2016
www.ti.com
TPS61160A/61A has built-in slope compensation to avoid sub-harmonic oscillation associated with current mode
control. If the inductor value is lower than 10 μH, the slope compensation may not be adequate, and the loop can
be unstable. Therefore, customers need to verify the inductor in their application if it is different from the
recommended values.
Table 2. Recommended Inductors for TPS61160A/61A
PART NUMBER
L
(μH)
DCR MAX
(Ω)
SATURATION CURRENT
(mA)
SIZE
(L × W × H mm)
VENDOR
Murata
LQH3NPN100NM0
10
0.3
750
3 × 3 × 1.5
VLCF5020T-220MR75-1
22
0.4
750
5 × 5 × 2.0
TDK
CDH3809/SLD
10
0.3
570
4 × 4 × 1.0
Sumida
A997AS-220M
22
0.4
510
4 × 4 × 1.8
TOKO
8.2.1.2.3 Schottky Diode Selection
The high switching frequency of the TPS61160A/61A demands a high-speed rectification for optimum efficiency.
Ensure that the diode average and peak current rating exceeds the average output current and peak inductor
current. In addition, the diode’s reverse breakdown voltage must exceed the open LED protection voltage. The
ONSemi MBR0540 and the ZETEX ZHCS400 are recommended for TPS61160A/61A.
8.2.1.2.4 Compensation Capacitor Selection
The compensation capacitor C3 (see Functional Block Diagram), connected from COMP pin to GND, is used to
stabilize the feedback loop of the TPS61160A/61A. Use a 220-nF ceramic capacitor for C3.
8.2.1.2.5 Input and Output Capacitor Selection
The output capacitor is mainly selected to meet the requirements for the output ripple and loop stability. This
ripple voltage is related to the capacitor’s capacitance and its equivalent series resistance (ESR). Assuming a
capacitor with zero ESR, the minimum capacitance needed for a given ripple can be calculated by
(Vout Vin ) u I out
Cout
Vout u Fs u Vripple
where
•
Vripple = peak-to-peak output ripple
(6)
The additional output ripple component caused by ESR is calculated using:
Vripple _ESR RESR u Iout
(7)
Due to its low ESR, Vripple_ESR can be neglected for ceramic capacitors, but must be considered if tantalum or
electrolytic capacitors are used.
Care must be taken when evaluating a ceramic capacitor’s derating under dc bias, aging and AC signal. For
example, larger form factor capacitors (in 1206 size) have a resonant frequencies in the range of the switching
frequency. So the effective capacitance is significantly lower. The DC bias can also significantly reduce
capacitance. Ceramic capacitors can loss as much as 50% of its capacitance at its rated voltage. Therefore,
leave the margin on the voltage rating to ensure adequate capacitance at the required output voltage.
The capacitor in the range of 1 μF to 4.7 μF is recommended for input side. The output requires a capacitor in
the range of 0.47 μF to 10 μF. The output capacitor affects the loop stability of the boost regulator. If the output
capacitor is below the range, the boost regulator can potentially become unstable. For example, if use the output
capacitor of 0.1 μF, a 470 nF compensation capacitor has to be used for the loop stable.
The popular vendors for high value ceramic capacitors are:
TDK (http://www.component.tdk.com/components.php)
Murata (http://www.murata.com/cap/index.html)
14
Submit Documentation Feedback
Copyright © 2009–2016, Texas Instruments Incorporated
Product Folder Links: TPS61160A TPS61161A
TPS61160A, TPS61161A
www.ti.com
SLVS937C – MARCH 2009 – REVISED JULY 2016
8.2.1.3 Application Curves
100
90
EFFICIENCY (%)
80
70
60
50
40
VIN = 3.0 V
30
VIN = 3.6 V
20
VIN = 4.2 V
10
VIN = 5.0 V
0
0
10 20 30 40 50 60 70 80 90 100
DIMMING DUTY CYCLE (%)
C002
Figure 14. Start-Up with 10 Series LEDs (DPWM = 100%)
Figure 13. Efficiency vs Dimming Duty Cycle
8.2.2 Li-Ion Driver for 6 White LEDs
L1
10 mH
D1
C2
C1
D2
TPS61160A
ON/OFF
DIMMING
CONTROL
C3
220nF
VIN
SW
CTRL
FB
100Ω
R2
COMP GND
R1
RFLTR
L1: Murata LQH3NPN100NM0
C1: Murata GRM188R61A105K
C2: Murata GRM188R61E474K
D1: ONsemi MBR0540T1
D2: ONsemi MMSZ4711
Rset
10 W
CFLTR
Figure 15. Li-Ion Driver for 6 White LEDs With External PWM Dimming Network
8.2.2.1 Design Requirements
DESIGN PARAMETER
EXAMPLE VALUE
Inductor
22 µH
Minimum input voltage
3V
Number of series LED
6
LED maximum forward voltage (Vf)
3.2 V
Schottky diode forward voltage (Vf)
0.2 V
Efficiency
82%
Switching frequency (fSW)
600 kHz
External PWM output voltage
3V
External PWM frequency
20 kHz
Copyright © 2009–2016, Texas Instruments Incorporated
Product Folder Links: TPS61160A TPS61161A
Submit Documentation Feedback
15
TPS61160A, TPS61161A
SLVS937C – MARCH 2009 – REVISED JULY 2016
www.ti.com
Applying Equation 3 and Equation 4, when VIN is 3 V, 6 LEDs output equivalent to VOUT of 19.4 V, the inductor is
22 μH, the Schottky forward voltage is 0.2 V, the maximum output current is 76 mA in typical condition.
8.2.2.2 Detailed Design Procedure
8.2.2.2.1 Choosing Component Values
As per SLVA471, the values of RFLTR, CFLTR, R1, R2, and RSET are determined by the system parameters and
error tolerance. The main source of LED current error is leakage current from the FB pin. The error gets worse
as the LED current decreases. The error due to leakage current is given by Functional Block Diagram, where the
impedance seen by the FB pin has a major impact. To reduce error due to the leakage current, the impedance
seen by the FB pin needs to be small. Because R2 is much smaller than R1 + RFLTR, R2 must be chosen to be
small to minimize the impedance seen by the FB pin. In general, R2 must be chosen to be 1 kΩ or less. If greater
accuracy at smaller currents is needed, then R2 must be chosen to be even smaller.
% error =
IFB
D ´ VPWM ( H ) + (1 - D ) VPWM ( L )
VFB
(R 1 + R FLTR ) // R 2
R 1 + R FLTR
(8)
Once R2 has been chosen, the value of RSET and R1 + RFLTR can be calculated using Equation 9, Equation 10,
Equation 11, and Equation 12. The individual values of R1 and RFLTR can be any combination that sums up to R1
+ RFLTR . In general, choosing R1 and RFLTR to be the same value gives a minimum requirement for CFLTR.
VPWM(min) = D(min)VPWM(H) + (1 - D(min) )VPWM(L)
(9)
VPWM(max) = D(max) VPWM(H) + (1 - D(max) )VPWM(L)
R SET =
(
VFB VPWM(max) - VPWM(min)
(10)
)
VP WM(ma x)ILE D(max) VFBILED(max) + VFBIL ED(min ) - VPWM(min)IL ED(min )
R1 + R FLTR =
R 2 (IL ED(ma x) (VPW M(max) - VFB ) - ILED(min) (VPW M(min) - VFB ))
VFB (ILED(max) - ILED(min) )
(11)
+
VPWM(max) - VPWM(min)
ILE D(max) - ILED(min)
(12)
Finally, CFLTR can be chosen based on the amount of filtering desired or to provide a gradual dimming effect that
is popular in many lighting products. At a minimum, CFLTR must be chosen to provide at least 20 dB of
attenuation at the PWM frequency. Equation 13 can be used to calculate the minimum capacitor value to provide
this attenuation.
1
CFLTR =
f pwm
2p (RFLTR // R1)
10
(13)
To provide gradual dimming, a large capacitor must be chosen to provide a long transient time when changing
the PWM duty cycle. Equation 14 shows how to calculate the recommended corner frequency of the RC filter
based on the 10% to 90% rise time. Once the corner frequency is known, it can be used to calculate the required
capacitor using Equation 15.
0.35
fRC =
tr
(14)
CFLTR =
1
2p (RFLTR // R1 ) fRC
(15)
For example, a design with RFLTR and R1 equal to 10 kΩ and a desired rise time of 500 ms requires a corner
frequency of 0.7 Hz and a capacitor of 47 μF.
16
Submit Documentation Feedback
Copyright © 2009–2016, Texas Instruments Incorporated
Product Folder Links: TPS61160A TPS61161A
TPS61160A, TPS61161A
www.ti.com
SLVS937C – MARCH 2009 – REVISED JULY 2016
8.2.2.3 Application Curves
100
90
EFFICIENCY (%)
80
70
60
50
40
VIN = 3.0 V
30
VIN = 3.6 V
20
VIN = 4.2 V
10
VIN = 5.0 V
0
0
10 20 30 40 50 60 70 80 90 100
DIMMING DUTY CYCLE (%)
C002
Figure 16. Efficiency vs Dimming Duty Cycle
Figure 17. Start-Up with 6 series LEDs (External PWM,
DPWM = 10%)
Figure 18. Start-Up with 6 Series LEDs (External PWM,
DPWM = 50%)
Figure 19. Start-Up with 6 Series LEDs (External PWM,
DPWM = 100%)
Copyright © 2009–2016, Texas Instruments Incorporated
Product Folder Links: TPS61160A TPS61161A
Submit Documentation Feedback
17
TPS61160A, TPS61161A
SLVS937C – MARCH 2009 – REVISED JULY 2016
www.ti.com
8.2.3 Li-Ion Driver for 6 White LEDs With External PWM Dimming Network
L1
10 mH
Vin 3 V to 5 V
C1
1 mF
D1
TPS61160A
ON/OFF
DIMMING
CONTROL
VIN
SW
CTRL
FB
COMP
GND
C3
220 nF
C2
0.47 mF
Rset
10 W
20 mA
L1: Murata LQH3NPN100NM0
C1: Murata GRM188R61A105K
C2: Murata GRM188R61E474K
D1: ONsemi MBR0540T1
Figure 20. Li-Ion Driver for 6 White LEDs
8.2.3.1 Design Requirements
DESIGN PARAMETER
EXAMPLE VALUE
Inductor
22 µH
Minimum input voltage
3V
Number of series LED
6
LED maximum forward voltage (Vf)
3.2 V
Schottky diode forward voltage (Vf)
0.2 V
Efficiency (η)
82%
Switching frequency
600 kHz
Applying Equation 3 and Equation 4, when VIN is 3 V, 6 LEDs output equivalent to VOUT of 19.4 V, the inductor is
22 μH, the Schottky forward voltage is 0.2 V, the maximum output current is 76 mA in typical condition.
8.2.3.2 Detailed Design Procedure
See Detailed Design Procedure.
8.2.3.3 Application Curves
100
90
EFFICIENCY (%)
80
70
60
50
40
VIN = 3.0 V
30
VIN = 3.6 V
20
VIN = 4.2 V
10
VIN = 5.0 V
0
0
10 20 30 40 50 60 70 80 90 100
DIMMING DUTY CYCLE (%)
C002
Figure 21. Efficiency vs Duty Cycle
18
Submit Documentation Feedback
Figure 22. Start-Up with 6 Series LEDs (DPWM = 50%)
Copyright © 2009–2016, Texas Instruments Incorporated
Product Folder Links: TPS61160A TPS61161A
TPS61160A, TPS61161A
www.ti.com
SLVS937C – MARCH 2009 – REVISED JULY 2016
Figure 23. Start-Up with 6 Series LEDs (DPWM = 100%)
8.2.4 Li-Ion Driver for 8 White LEDs
L1
22 mH
Vin 3 V to 5 V
D1
C2
C1
TPS61161A
ON/OFF
DIMMING
CONTROL
VIN
SW
CTRL
FB
COMP
GND
C3
220 nF
Rset
10 W
L1: TDK VLCF5020T-220MR75-1
C1: Murata GRM188R61A105K
C2: Murata GRM21BR71H105K
D1: ONsemi MBR0540T1
20mA
Figure 24. Li-Ion Driver for 8 White LEDs
Copyright © 2009–2016, Texas Instruments Incorporated
Product Folder Links: TPS61160A TPS61161A
Submit Documentation Feedback
19
TPS61160A, TPS61161A
SLVS937C – MARCH 2009 – REVISED JULY 2016
www.ti.com
8.2.4.1 Design Requirements
DESIGN PARAMETER
EXAMPLE VALUE
LED current
0.02 A
Minimum input voltage
3V
Number of series LED
8
LED maximum forward voltage (Vf)
3.3 V
Schottky diode forward voltage
0.2 V
Efficiency (η)
86%
Switching frequency
600 kHz
Applying Equation 3 and Equation 4, when VIN is 3 V, 8 LEDs output equivalent to VOUT of 25.8 V, the inductor is
22 μH, the Schottky forward voltage is 0.2 V, the maximum output current is 60 mA in typical condition.
8.2.4.2 Detailed Design Procedure
See Detailed Design Procedure.
8.2.4.3 Application Curves
100
90
EFFICIENCY (%)
80
70
60
50
40
VIN = 3.0 V
30
VIN = 3.6 V
20
VIN = 4.2 V
10
VIN = 5.0 V
0
0
10 20 30 40 50 60 70 80 90 100
DIMMING DUTY CYCLE (%)
C002
Figure 25. Efficiency vs. Dimming Duty Cycle
Figure 26. Start-Up with 8 Series LEDs (DPWM = 100%)
9 Power Supply Recommendations
The TPS61160A/61A is designed to operate from an input supply range of 2.7 V to 18 V. This input supply must
be well regulated and provide the peak current required by the number of series LEDs and inductor selected.
20
Submit Documentation Feedback
Copyright © 2009–2016, Texas Instruments Incorporated
Product Folder Links: TPS61160A TPS61161A
TPS61160A, TPS61161A
www.ti.com
SLVS937C – MARCH 2009 – REVISED JULY 2016
10 Layout
10.1 Layout Guidelines
As for all switching power supplies, especially those high frequency and high current ones, layout is an important
design step. If layout is not carefully done, the regulator could suffer from instability as well as noise problems.
To reduce switching losses, the SW pin rise and fall times are made as short as possible. To prevent radiation of
high frequency resonance problems, proper layout of the high frequency switching path is essential. Minimize the
length and area of all traces connected to the SW pin and always use a ground plane under the switching
regulator to minimize inter-plane coupling. The loop including the PWM switch, Schottky diode, and output
capacitor, contains high current rising and falling in nanosecond and should be kept as short as possible. The
input capacitor needs not only to be close to the VIN pin, but also to the GND pin in order to reduce the supply
ripple of the device. Figure 27 shows a sample layout.
10.2 Layout Example
C1
Rset
Vin
LEDs Out
Vin
FB
L1
CTRL
COMP
CTRL
GND
SW
C3
C2
GND
Place enough
VIAs around
thermal pad to
enhance thermal
performance
LEDs IN
Minimize the
area of this
trace
Figure 27. Sample Layout
10.3 Thermal Considerations
The maximum junction temperature of the device must be restricted to 125°C under normal operating conditions.
This restriction limits the power dissipation of the TPS61160A/61A. Calculate the maximum allowable dissipation,
PD(max), and keep the actual dissipation less than or equal to PD(max). The maximum-power-dissipation limit is
determined using Equation 16:
PD(max)
125qC - TA
RTJA
where
•
•
TA is the maximum ambient temperature for the application.
RθJA is the thermal resistance junction-to-ambient given in Dissipation Ratings .
(16)
The TPS61160A/61A comes in a thermally enhanced QFN package. This package includes a thermal pad that
improves the thermal capabilities of the package. The RθJA of the QFN package greatly depends on the PCB
layout and thermal pad connection. The thermal pad must be soldered to the analog ground on the PCB. Using
thermal vias underneath the thermal pad as illustrated in the layout example. Also see the QFN/SON PCB
Attachment application report (SLUA271).
Copyright © 2009–2016, Texas Instruments Incorporated
Product Folder Links: TPS61160A TPS61161A
Submit Documentation Feedback
21
TPS61160A, TPS61161A
SLVS937C – MARCH 2009 – REVISED JULY 2016
www.ti.com
11 Device and Documentation Support
11.1 Device Support
11.1.1 Third-Party Products Disclaimer
TI'S PUBLICATION OF INFORMATION REGARDING THIRD-PARTY PRODUCTS OR SERVICES DOES NOT
CONSTITUTE AN ENDORSEMENT REGARDING THE SUITABILITY OF SUCH PRODUCTS OR SERVICES
OR A WARRANTY, REPRESENTATION OR ENDORSEMENT OF SUCH PRODUCTS OR SERVICES, EITHER
ALONE OR IN COMBINATION WITH ANY TI PRODUCT OR SERVICE.
11.2 Documentation Support
11.2.1 Related Documentation
For related documentation, see the following application reports:
QFN/SON PCB Attachment (SLUA271).
How to Use Analog Dimming With the TPS6116x (SLVA471).
Design Tool for Analog Dimming Using a PWM Signal (http://www.ti.com/lit/zip/slvc366).
11.3 Related Links
Table 3 below lists quick access links. Categories include technical documents, support and community
resources, tools and software, and quick access to sample or buy.
Table 3. Related Links
PARTS
PRODUCT FOLDER
SAMPLE & BUY
TECHNICAL
DOCUMENTS
TOOLS &
SOFTWARE
SUPPORT &
COMMUNITY
TPS61160A
Click here
Click here
Click here
Click here
Click here
TPS61161A
Click here
Click here
Click here
Click here
Click here
11.4 Receiving Notification of Documentation Updates
To receive notification of documentation updates, navigate to the device product folder on ti.com. In the upper
right corner, click on Alert me to register and receive a weekly digest of any product information that has
changed. For change details, review the revision history included in any revised document.
11.5 Community Resources
The following links connect to TI community resources. Linked contents are provided "AS IS" by the respective
contributors. They do not constitute TI specifications and do not necessarily reflect TI's views; see TI's Terms of
Use.
TI E2E™ Online Community TI's Engineer-to-Engineer (E2E) Community. Created to foster collaboration
among engineers. At e2e.ti.com, you can ask questions, share knowledge, explore ideas and help
solve problems with fellow engineers.
Design Support TI's Design Support Quickly find helpful E2E forums along with design support tools and
contact information for technical support.
11.6 Trademarks
E2E is a trademark of Texas Instruments.
All other trademarks are the property of their respective owners.
11.7 Electrostatic Discharge Caution
These devices have limited built-in ESD protection. The leads should be shorted together or the device placed in conductive foam
during storage or handling to prevent electrostatic damage to the MOS gates.
22
Submit Documentation Feedback
Copyright © 2009–2016, Texas Instruments Incorporated
Product Folder Links: TPS61160A TPS61161A
TPS61160A, TPS61161A
www.ti.com
SLVS937C – MARCH 2009 – REVISED JULY 2016
11.8 Glossary
SLYZ022 — TI Glossary.
This glossary lists and explains terms, acronyms, and definitions.
12 Mechanical, Packaging, and Orderable Information
The following pages include mechanical, packaging, and orderable information. This information is the most
current data available for the designated devices. This data is subject to change without notice and revision of
this document. For browser-based versions of this data sheet, refer to the left-hand navigation.
Copyright © 2009–2016, Texas Instruments Incorporated
Product Folder Links: TPS61160A TPS61161A
Submit Documentation Feedback
23
PACKAGE OPTION ADDENDUM
www.ti.com
19-Oct-2022
PACKAGING INFORMATION
Orderable Device
Status
(1)
Package Type Package Pins Package
Drawing
Qty
Eco Plan
(2)
Lead finish/
Ball material
MSL Peak Temp
Op Temp (°C)
Device Marking
(3)
Samples
(4/5)
(6)
TPS61160ADRVR
ACTIVE
WSON
DRV
6
3000
RoHS & Green
NIPDAU
Level-2-260C-1 YEAR
-40 to 85
OBV
Samples
TPS61160ADRVT
ACTIVE
WSON
DRV
6
250
RoHS & Green
NIPDAU
Level-2-260C-1 YEAR
-40 to 85
OBV
Samples
TPS61161ADRVR
ACTIVE
WSON
DRV
6
3000
RoHS & Green
NIPDAU
Level-2-260C-1 YEAR
-40 to 85
OBT
Samples
TPS61161ADRVT
ACTIVE
WSON
DRV
6
250
RoHS & Green NIPDAU | NIPDAUAG
Level-2-260C-1 YEAR
-40 to 85
OBT
Samples
(1)
The marketing status values are defined as follows:
ACTIVE: Product device recommended for new designs.
LIFEBUY: TI has announced that the device will be discontinued, and a lifetime-buy period is in effect.
NRND: Not recommended for new designs. Device is in production to support existing customers, but TI does not recommend using this part in a new design.
PREVIEW: Device has been announced but is not in production. Samples may or may not be available.
OBSOLETE: TI has discontinued the production of the device.
(2)
RoHS: TI defines "RoHS" to mean semiconductor products that are compliant with the current EU RoHS requirements for all 10 RoHS substances, including the requirement that RoHS substance
do not exceed 0.1% by weight in homogeneous materials. Where designed to be soldered at high temperatures, "RoHS" products are suitable for use in specified lead-free processes. TI may
reference these types of products as "Pb-Free".
RoHS Exempt: TI defines "RoHS Exempt" to mean products that contain lead but are compliant with EU RoHS pursuant to a specific EU RoHS exemption.
Green: TI defines "Green" to mean the content of Chlorine (Cl) and Bromine (Br) based flame retardants meet JS709B low halogen requirements of
工商网监
湘ICP备2023018690号
