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TPS61160, TPS61161
SLVS791E – NOVEMBER 2007 – REVISED JULY 2016
TPS6116x White LED Drivers With Digital and PWM Brightness Control in 2-mm x 2-mm
WSON Package
1 Features
•
•
•
•
•
•
•
1
The default white LED current is set with the external
sensor resistor RSET, and the feedback voltage is
regulated to 200 mV, as shown in the Typical
Application. During the operation, the LED current
can be controlled using the one-wire digital interface
(EasyScale™ protocol) through the CTRL pin.
Alternatively, a pulse width modulation (PWM) signal
can be applied to the CTRL pin through which the
duty cycle determines the feedback reference
voltage. In either digital or PWM mode, the
TPS61160 and TPS61161 do not burst the LED
current; therefore, they do not generate audible
noises on the output capacitor. For maximum
protection, the device features integrated open LED
protection that disable the TPS61160 and/or
TPS61161 to prevent the output voltage from
exceeding the device's absolute maximum voltage
ratings during open LED conditions.
2.7-V to 18-V Input Voltage Range
26-V Open LED Protection (TPS61160)
38-V Open LED Protection (TPS61161)
200-mV Reference Voltage With ±2% Accuracy
Flexible Digital and PWM Brightness Control
Built-in Soft Start
Up to 90% Efficiency
2 Applications
•
•
•
•
•
Cellular Phones
Portable Media Players
Ultra Mobile Devices
GPS Receivers
White LED Backlighting for Media Form Factor
Display
The TPS61160 and TPS61161 are available in a
space-saving, 2-mm × 2-mm WSON package with
thermal pad.
3 Description
Device Information(1)
With a 40-V rated integrated switch FET, the
TPS61160 and TPS61161 are boost converters that
drive LEDs in series. The boost converters run at
600-kHz fixed switching frequency to reduce output
ripple, improve conversion efficiency, and allow for
the use of small external components.
PART NUMBER
TPS61160
PACKAGE
WSON (6)
TPS61161
OPEN LED PROTECTION
TPS61160 use 26 V (typical)
TPS61161 use 38 V (typical)
(1) For all available packages, see the orderable addendum at
the end of the data sheet.
Typical Application
L1
22 mH
VI 3 V to 18 V
C1
1 mF
TPS61161–Q1
ON/OFF
DIMMING
CONTROL
VIN
SW
CTRL
FB
COMP GND
C3
220 nF
L1: TDK VLCF5020T-220MR75-1
C1: Murata GRM188R61E105K
C2: Murata GRM21BR71H105K
D1: ONsemi MBR0540T1
D1
38 V Max
C2
1 mF
Rset
10 W
20 mA
1
An IMPORTANT NOTICE at the end of this data sheet addresses availability, warranty, changes, use in safety-critical applications,
intellectual property matters and other important disclaimers. PRODUCTION DATA.
TPS61160, TPS61161
SLVS791E – NOVEMBER 2007 – REVISED JULY 2016
www.ti.com
Table of Contents
1
2
3
4
5
6
7
Features ..................................................................
Applications ...........................................................
Description .............................................................
Revision History.....................................................
Pin Configuration and Functions .........................
Specifications.........................................................
1
1
1
2
4
5
6.1
6.2
6.3
6.4
6.5
6.6
6.7
5
5
5
5
6
7
8
Absolute Maximum Ratings ......................................
ESD Ratings..............................................................
Recommended Operating Conditions.......................
Thermal Information ..................................................
Electrical Characteristics...........................................
Timing Requirements ...............................................
Typical Characteristics ..............................................
Detailed Description ............................................ 11
7.1
7.2
7.3
7.4
7.5
Overview .................................................................
Functional Block Diagram .......................................
Feature Description.................................................
Device Functional Modes........................................
Programming...........................................................
11
11
11
13
15
8
Application and Implementation Information ... 19
8.1 Application Information............................................ 19
8.2 Typical Applications ............................................... 19
9 Power Supply Recommendations...................... 28
10 Layout................................................................... 29
10.1 Layout Guidelines ................................................. 29
10.2 Layout Example .................................................... 29
10.3 Thermal Considerations ........................................ 29
11 Device and Documentation Support ................. 30
11.1
11.2
11.3
11.4
11.5
11.6
11.7
11.8
Device Support......................................................
Documentation Support ........................................
Related Links ........................................................
Receiving Notification of Documentation Updates
Community Resources..........................................
Trademarks ...........................................................
Electrostatic Discharge Caution ............................
Glossary ................................................................
30
30
30
30
30
30
30
31
12 Mechanical, Packaging, and Orderable
Information ........................................................... 31
4 Revision History
NOTE: Page numbers for previous revisions may differ from page numbers in the current version.
Changes from Revision D (June 2015) to Revision E
Page
•
Changed package name from "SON" to "WSON" throughout document .............................................................................. 1
•
Deleted the "Duty" rows the Recommended Operating Conditions; added "tPWM_MIN" row .................................................... 5
Changes from Revision C (April 2012) to Revision D
Page
•
Added Pin Configuration and Functions section, ESD Rating table, Feature Description , Device Functional Modes,
Application and Implementation, Power Supply Recommendations, Dos and Don'ts, Layout, Device and
Documentation Support , and Mechanical, Packaging, and Orderable Information sections; change package name
from QFN to SON; remove Ordering Information table - info duplicated in POA................................................................... 1
•
Deleted Dissipation Ratings table - replaced by updated Thermal Information. ................................................................... 5
•
Added paragraph re: not using EasyScale to change feedback voltage from 0 mV............................................................ 14
Changes from Revision B (July 2011) to Revision C
Page
•
Changed the Maximum duty cycle MIN value From: 90% To: 93% and the TYP value From: 93% To: 95% ...................... 6
•
Changed position of VI = 5 V and VI = 3.6 V in Figure 3........................................................................................................ 8
Changes from Revision A (September 2008) to Revision B
Page
•
Changed Features item From: 26V Open LED Protection for 6 LEDs (TPS61160) To: 26-V Open LED Protection
(TPS61160) ............................................................................................................................................................................ 1
•
Changed Features item From: 38V Open LED Protection for 10 LEDs (TPS61161) To: 38-V Open LED Protection
(TPS61161) ............................................................................................................................................................................ 1
•
; added 38V max to Typical Application diagram; . ............................................................................................................... 1
•
Changed the COMP and CTRL Description in the Terminal Function Table......................................................................... 4
•
Changed text to clarify the "Open LED Protection" description. .......................................................................................... 12
2
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SLVS791E – NOVEMBER 2007 – REVISED JULY 2016
•
Changed Figure 13............................................................................................................................................................... 14
•
Changed the COMPENSATION CAPACITOR SELECTION section................................................................................... 21
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SLVS791E – NOVEMBER 2007 – REVISED JULY 2016
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5 Pin Configuration and Functions
DRV Package
6-Pin WSON with Exposed Thermal Pad
Top View
FB
COMP
VIN
Thermal
Pad
GND
CTRL
SW
Pin Functions
PIN
NAME
NO.
I/O
DESCRIPTION
COMP
2
O
Output of the transconductance error amplifier. Connect an external capacitor to this pin to
compensate the converter.
CTRL
5
I
Control pin of the boost converter. It is a multi-functional pin which can be used for enable control,
PWM and digital dimming.
FB
1
I
Feedback pin for current. Connect the sense resistor from FB to GND.
GND
3
O
Ground
SW
4
I
This is the switching node of the device. Connect the inductor between the VIN and SW pin. This pin
is also used to sense the output voltage for open LED protection
VIN
6
I
The input supply pin for the device. Connect VIN to a supply voltage between 2.7 V and 18 V.
Thermal Pad
—
—
4
Solder the thermal pad to the analog ground plane. If possible, use thermal via to connect to ground
plane for ideal power dissipation.
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SLVS791E – NOVEMBER 2007 – REVISED JULY 2016
6 Specifications
6.1 Absolute Maximum Ratings
over operating free-air temperature range (unless otherwise noted)
(1)
Supply voltages on VIN (2)
Voltages on CTRL
VI
(2)
MIN
MAX
UNIT
–0.3
20
V
–0.3
20
V
Voltage on FB and COMP (2)
–0.3
3
V
Voltage on SW (2)
–0.3
40
V
TJ
Operating junction temperature
40
150
°C
Tstg
Storage temperature
–65
150
°C
(1)
(2)
Stresses beyond those listed under Absolute Maximum Ratings may cause permanent damage to the device. These are stress ratings
only, which do not imply functional operation of the device at these or any other conditions beyond those indicated under Recommended
Operating Conditions. Exposure to absolute-maximum-rated conditions for extended periods may affect device reliability.
All voltage values are with respect to network ground pin.
6.2 ESD Ratings
VALUE
V(ESD)
(1)
(2)
Electrostatic
discharge
Human-body model (HBM), per ANSI/ESDA/JEDEC JS-001 (1)
±4000
Charged-device model (CDM), per JEDEC specification JESD22-C101 (2)
±1000
UNIT
V
JEDEC document JEP155 states that 500-V HBM allows safe manufacturing with a standard ESD control process.
JEDEC document JEP157 states that 250-V CDM allows safe manufacturing with a standard ESD control process.
6.3 Recommended Operating Conditions
MIN
NOM
MAX
UNIT
VI
Input voltage
2.7
18
VO
Output voltage
VIN
38
V
L
Inductor (1)
10
22
μH
ƒdim
PWM dimming frequency
100
kHz
tPWM_MIN
Minimum pulse width at PWM input
CIN
Input capacitor
CO
Output capacitor (1)
0.47
10
μF
TA
Operating ambient temperature
–40
85
°C
TJ
Operating junction temperature
–40
125
°C
(1)
5
V
50
ns
1
μF
These values are recommended values that have been successfully tested in several applications. Other values may be acceptable in
other applications but should be fully tested by the user.
6.4 Thermal Information
THERMAL METRIC (1)
TPS61160,
TPS61161
DRV (WSON)
UNIT
6 PINS
RθJA
Junction-to-ambient thermal resistance
RθJC(top)
Junction-to-case (top) thermal resistance
RθJB
Junction-to-board thermal resistance
ψJT
Junction-to-top characterization parameter
3.2
°C/W
ψJB
Junction-to-board characterization parameter
66.3
°C/W
RθJC(bot)
Junction-to-case (bottom) thermal resistance
40.8
°C/W
(1)
96.1
°C/W
89
°C/W
65.9
°C/W
For more information about traditional and new thermal metrics, see Semiconductor and IC Package Thermal Metrics.
Copyright © 2007–2016, Texas Instruments Incorporated
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6.5 Electrical Characteristics
VIN = 3.6 V, CTRL = VIN, TA = –40°C to +85°C, typical values are at TA = 25°C (unless otherwise noted).
PARAMETER
TEST CONDITIONS
MIN
TYP
MAX
UNIT
SUPPLY CURRENT
VI
Input voltage
IQ
Operating quiescent current into VIN
Device PWM switching no load
2.7
ISD
Shutdown current
CRTL=GND, VIN = 4.2 V
UVLO
Undervoltage lockout threshold
VIN falling
Vhys
Undervoltage lockout hysterisis
2.2
18
V
1.8
mA
1
μA
2.5
70
V
mV
ENABLE AND REFERENCE CONTROL
V(CTRLh)
CTRL logic high voltage
VIN = 2.7 V to 18 V
V(CTRLl)
CTRL logic low voltage
VIN = 2.7 V to 18 V
R(CTRL)
CTRL pull down resistor
1.2
V
0.4
V
400
800
1600
kΩ
mV
VOLTAGE AND CURRENT CONTROL
VREF
Voltage feedback regulation voltage
196
200
204
V(REF_PWM)
Voltage feedback regulation voltage
under brightness control
VFB = 50 mV
47
50
53
VFB = 20 mV
17
20
23
IFB
Voltage feedback input bias current
VFB = 200 mV
2
μA
ƒS
Oscillator frequency
500
600
700
kHz
Dmax
Maximum duty cycle
93%
95%
tmin_on
Minimum on pulse width
40
ns
Isink
Comp pin sink current
100
μA
Isource
Comp pin source current
100
μA
Gea
Error amplifier transconductance
Rea
Error amplifier output resistance
ƒea
Error amplifier crossover frequency
VFB = 100 mV, measured on the
drive signal of the switching FET
240
320
400
mV
μmho
6
MΩ
5 pF connected to COMP
500
kHz
VIN = 3.6 V
0.3
POWER SWITCH
RDS(on)
N-channel MOSFET on-resistance
ILN_NFET
N-channel leakage current
6
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VIN = 3 V
0.6
0.7
VSW = 35 V, TA = 25°C
1
Ω
μA
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SLVS791E – NOVEMBER 2007 – REVISED JULY 2016
Electrical Characteristics (continued)
VIN = 3.6 V, CTRL = VIN, TA = –40°C to +85°C, typical values are at TA = 25°C (unless otherwise noted).
PARAMETER
TEST CONDITIONS
MIN
TYP
MAX
UNIT
0.56
0.7
0.84
A
OC and OLP
ILIM
N-Channel MOSFET current limit
D = Dmax
ILIM_Start
Start up current limit
D = Dmax
tHalf_LIM
Time step for half current limit
0.4
A
5
Vovp
Open LED protection threshold
Measured on the SW pin,
TPS61160
TPS61161
25
37
V(FB_OVP)
Open LED protection threshold on FB
Measured on the FB pin,
percentage of VREF
VREF= 200 mV and 20 mV
VACKNL
Acknowledge output voltage low
Open drain, Rpullup =15 kΩ to VIN
26
38
ms
27
39
V
0.4
V
50%
THERMAL SHUTDOWN
Tshutdown
Thermal shutdown threshold
Thysteresis
Thermal shutdown threshold hysteresis
160
°C
15
°C
6.6 Timing Requirements
MIN
NOM
MAX
UNIT
OC and OLP
tREF
VREF filter time constant
180
μs
tstep
VREF ramp up time
213
μs
EasyScale
tvalACKN
Acknowledge valid time (1)
tACKN
Duration of acknowledge condition (1)
toff
CTRL pulse width to shutdown, CTRL high to low
2.5
ms
tes_det
Easy Scale detection time (2)
260
μs
tes_delay
EasyScale detection delay, Measured from CTRL high
100
μs
tes_win
EasyScale detection window time
1
ms
tSTART
Start time of program stream
2
tEOS
End time of program stream
2
360
μs
tH_LB
High time low bit, logic 0
2
180
μs
tL_LB
Low time low bit, logic 0
2 × tH_LB
360
μs
tH_HB
High time high bit, logic 1
2 × tL_HB
360
μs
tL_HB
Low time high bit, logic 1
2
180
μs
(1)
(2)
2
μs
512
μs
μs
Acknowledge condition active 0, this condition will only be applied in case the RFA bit is set. Open drain output, line needs to be pulled
high by the host with resistor load.
To select EasyScale mode, the CTRL pin has to be low for more than tes_det during tes_win.
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6.7 Typical Characteristics
6.7.1 Table Of Graphs
FIGURE
Efficiency TPS61160/1
VIN = 3.6 V; 4, 6, 8, 10 LEDs; L = 22 μH
Figure 1
Efficiency TPS61160
Figure 2
Efficiency TPS61161
Figure 3
Current limit
TA = 25°C
Figure 4
Current limit
Figure 5
EasyScale step
Figure 6
PWM dimming linearity
VIN = 3.6 V; PWM Freq = 10 kHz and 40 kHz
Figure 6
Output ripple at PWM dimming
8 LEDs; VIN = 3.6 V; ILOAD = 20 mA; PWM Freq = 10 kHz
Figure 8
Switching waveform
8 LEDs; VIN = 3.6 V; ILOAD = 20 mA; L = 22 μH
Figure 9
Start-up
8 LEDs; VIN = 3.6 V; ILOAD = 20 mA; L =22 μH
Figure 10
Open LED protection
8 LEDs; VIN = 3.6 V; ILOAD = 20 mA; L = 22 μH
Figure 11
100
100
VI = 3.6 V
4 LEDs
VI = 4.2 V
6 LEDs
90
90
8 LEDs
VI = 3 V
80
Efficiency - %
Efficiency - %
80
10 LEDs
70
VI = 3.6 V
70
60
60
4 (12.8 V), 6 (19.2 V) LEDs
8 (25.6 V),10 (32 V) LEDs
50
50
6 LEDs - TPS61160
40
40
0
10
20
30
Output Current - mA
40
50
0
10
20
30
Output Current - mA
40
50
Figure 2. Efficiency vs Output Current
Figure 1. Efficiency vs Output Current
100
1000
VI = 12 V
900
Efficiency - %
80
VI = 3.6 V
Switch Current Limit - mA
90
VI = 5 V
70
60
50
800
700
600
500
400
10 LEDs - TPS61161 – Q1
40
0
10
20
30
Output Current - mA
40
Figure 3. Efficiency vs Output Current
8
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50
300
20
30
40
50
60
Duty Cycle - %
70
80
90
Figure 4. Switch Current Limit vs Duty Cycle
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SLVS791E – NOVEMBER 2007 – REVISED JULY 2016
1000
200
180
900
140
FB Voltage - mV
Switch Current Limit - mA
160
800
700
600
120
100
80
60
500
40
400
20
300
-40
0
-20
0
20
40
60
80
Temperature - °C
100
120
0
140
Figure 5. Switch Current Limit vs Temperature
2
4
6
8
10 12 14 16 18 20 22 24 26
Easy Scale Step Step
28 30 32
Figure 6. FB Voltage vs EasyScale Step
200
PWM 2 V/div
10 kHz, 40 kHz
FB Voltage - mV
160
120
VOUT 20 mV/div AC
80
ILED 10 mA/div
40
0
0
20
40
60
PWM Duty Cycle - %
80
100
t - 100 ms/div
Figure 7. FB Voltage vs PWM Duty Cycle
Figure 8. Output Ripple At PWM Dimming
CTRL
5 V/div
SW
20 V/div
VOUT
20 mV/div
AC
VOUT
10 V/div
COMP
500 mV/div
IL
200 mA/div
IL
200 mA/div
t - 2 ms/div
t - 1 ms/div
Figure 9. Switching Waveform
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Figure 10. Start-Up
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OPEN LED
5 V/div
FB
200 mV/div
VOUT
10 V/div
IL
200 mA/div
t - 100 ms/div
Figure 11. Open LED Protection
10
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SLVS791E – NOVEMBER 2007 – REVISED JULY 2016
7 Detailed Description
7.1 Overview
The TPS61160 and TPS61161 are high-efficiency, high-output voltage boost converters in a small package size.
These devices are ideal for driving white LED in series. The serial LED connection provides even illumination by
sourcing the same output current through all LEDs, eliminating the need for expensive factory calibration. Each
device integrate a 40-V, 0.7-A switch FET and operatea in pulse width modulation (PWM) with 600-kHz fixed
switching frequency. For operation see the block diagram. The duty cycle of the converter is set by the error
amplifier output and the current signal applied to the PWM control comparator. The control architecture is based
on traditional current-mode control; therefore, a slope compensation is added to the current signal to allow stable
operation for duty cycles larger than 50%. The feedback loop regulates the FB pin to a low reference voltage
(200 mV typical), reducing the power dissipation in the current sense resistor.
7.2 Functional Block Diagram
C2
D1
1
Rset
4
L1
FB
SW
Reference
Control
Error
Amplifer
OLP
Vin
6
COMP
2
C1
PWM Control
C3
5
CTRL
Soft
Start-up
Ramp
Generator
+
Current
Sensor
Oscillator
GND
3
7.3 Feature Description
7.3.1 Soft Start-Up
Soft-start circuitry is integrated into the device to avoid a high inrush current during start-up. After the device is
enabled, the voltage at FB pin ramps up to the reference voltage in 32 steps with each step taking 213 μs. This
ensures that the output voltage rises slowly to reduce the input current. Additionally, for the first 5 msec after the
COMP voltage ramps, the current limit of the switch is set to half of the normal current limit spec. During this
period, the input current is kept below 400 mA (typical). See the start-up waveform of a typical example,
Figure 10.
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Feature Description (continued)
7.3.2 Open LED Protection
Open LED protection circuitry prevents device damage as the result of white LED disconnection. The TPS61160
and TPS61161 monitor the voltage at the SW pin and FB pin during each switching cycle. The circuitry turns off
the switch FET and shuts down the device when both of the following conditions persist for 8 switching clock
cycles:
1. The SW voltage exceeds the VOVP threshold; and
2. The FB voltage is less than half of regulation voltage.
As a result, the output voltage falls to the level of the input supply. The device remains in shutdown mode until it
is enabled by toggling the CTRL pin logic. To allow the use of inexpensive low-voltage output capacitor, the
TPS61160/1 has different open lamp protection thresholds. The threshold is set at 26 V for the TPS61160 and
38 V for the TPS61161. Select the appropriate device so that the product of the number of external LEDs and
each LED's maximum forward voltage plus the 200 mV reference voltage does not exceed the minimum OVP
threshold or (nLEDS × VLED(MAX)) + 200 mV ≤ VOVP(MIN).
7.3.3 Current Program
The FB voltage is regulated by a low 0.2-V reference voltage. The LED current is programmed externally using a
current-sense resistor in series with the LED string. The value of the RSET is calculated using Equation 1:
VFB
ILED
RSET
where
•
•
•
ILED = output current of LEDs
VFB = regulated voltage of FB
RSET = current sense resistor
(1)
The output current tolerance depends on the FB accuracy and the current sensor resistor accuracy.
7.3.4 LED Brightness Dimming Mode Selection
The CTRL pin is used for the control input for both dimming modes, PWM dimming and one-wire dimming. The
dimming mode for the TPS61160 or TPS61161 is selected each time the device is enabled. The default dimming
mode is PWM dimming. To enter the one-wire mode, the following digital pattern on the CTRL pin must be
recognized by the device every time the device starts from the shutdown mode.
1. Pull CTRL pin high to enable the TPS61160 or TPS61161 and to start the one-wire detection window.
2. After the EasyScale detection delay (tes_delay, 100 μs) expires, drive CTRL low for more than the EasyScale
detection time (tes_detect, 260 μs).
3. The CTRL pin has to be low for more than EasyScale detection time before the EasyScale detection window
(tes_win, 1 msec) expires. EasyScale detection window starts from the first CTRL pin low to high transition.
The device immediately enters the one-wire mode once the above three conditions are met. the EasyScale
communication can start before the detection window expires. Once the dimming mode is programmed, it can
not be changed without another start-up. This means the device needs to be shutdown by pulling the CTRL low
for 2.5 ms and restarts. See Figure 12 for a graphical explanation.
12
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Feature Description (continued)
Insert battery
PWM signal
high
CTRL
low
PWM
mode
Startup
delay
FB ramp
Shutdown delay
200mV x duty cycle
FB
t
Insert battery
Enter ES mode
Enter ES mode
Timing window
Programming
code
Programming code
high
CTRL
low
ES detect time
ES
mode
ES detect delay
Shutdown
delay
IC
Shutdown
Programmed value
(if not programmed, 200mV default )
50mV
Startup delay
FB
FB ramp
FB ramp
Startup delay
50mV
Figure 12. Dimming Mode Detection and Soft Start PWM Brightness Dimming
7.3.5 Undervoltage Lockout
An undervoltage lockout prevents operation of the device at input voltages below typical 2.2 V. When the input
voltage is below the undervoltage threshold, the device is shutdown and the internal switch FET is turned off. If
the input voltage rises by undervoltage lockout hysteresis, the device restarts.
7.3.6 Thermal Shutdown
An internal thermal shutdown turns off the device when the typical junction temperature of 160°C is exceeded.
The device is released from shutdown automatically when the junction temperature decreases by 15°C.
7.4 Device Functional Modes
7.4.1 Shutdown
The TPS61160 or TPS61161 enters shutdown mode when the CTRL voltage is logic low for more than 2.5 ms.
During shutdown, the input supply current for the device is less than 1 μA (maximum). Although the internal FET
does not switch in shutdown, there is still a DC current path between the input and the LEDs through the inductor
and Schottky diode. The minimum forward voltage of the LED array must exceed the maximum input voltage to
ensure that the LEDs remain off in shutdown. However, in the typical application with two or more LEDs, the
forward voltage is large enough to reverse bias the Schottky and keep leakage current low.
7.4.2 PWM Brightness Dimming
When the CTRL pin is constantly high, the FB voltage is regulated to 200 mV typically. However, the CTRL pin
allows a PWM signal to reduce this regulation voltage; therefore, it achieves LED brightness dimming. The
relationship between the duty cycle and FB voltage is given by Equation 2.
VFB Duty u 200 mV
where
•
•
Duty = duty cycle of the PWM signal
200 mV = internal reference voltage
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Device Functional Modes (continued)
As shown in Figure 13, the device chops up the internal 200-mV reference voltage at the duty cycle of the PWM
signal. The pulse signal is then filtered by an internal low pass filter. The output of the filter is connected to the
error amplifier as the reference voltage for the FB pin regulation. Therefore, although a PWM signal is used for
brightness dimming, only the WLED DC current is modulated, which is often referred as analog dimming. This
eliminates the audible noise which often occurs when the LED current is pulsed in replica of the frequency and
duty cycle of PWM control. Unlike other scheme which filters the PWM signal for analog dimming, TPS61160,
TPS61161 regulation voltage is independent of the PWM logic voltage level which often has large variations.
For optimum performance, use the PWM dimming frequency in the range of 5 kHz to 100 kHz. The requirement
of minimum dimming frequency comes from the EasyScale detection delay and detection time specification in the
dimming mode selection. Since the CTRL pin is logic only pin, adding an external RC filter applied to the pin
does not work.
VBG
200 mV
CTRL
Error
Amplifier
COMP
FB
Figure 13. Block Diagram of Programmable FB Voltage Using PWM Signal
To use lower PWM dimming, add an external RC network connected to the FB pin as shown in Figure 19.
7.4.3 Digital One-Wire Brightness Dimming
The CTRL pin features a simple digital interface to allow digital brightness control. The digital dimming can save
the processor power and battery life as it does not require a PWM signal all the time, and the processor can
enter idle mode if available.
The TPS61160 or TPS61161 adopts the EasyScale protocol for the digital dimming, which can program the FB
voltage to any of the 32 steps with single command. The step increment increases with the voltage to produce
pseudo logarithmic curve for the brightness step. See the Table 1 for the FB pin voltage steps. The default step
is full scale when the device is first enabled (VFB = 200 mV). The programmed reference voltage is stored in an
internal register. A power reset clears the register value and reset it to default.
Do not use EasyScale to change the feedback voltage from 0 mV, effectively disabling the device, to any other
voltage. One alternative is to start with VFB = 10 mV and go to a higher voltage. Another alternative is to disable
the device by taking the CTRL pin low for 2.5 ms and then re-enter EasyScale to force a soft start from VFB = 0
mV to the default 200 mV.
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Device Functional Modes (continued)
7.4.4 External PWM Dimming
For assistance in selecting the proper values for RSET, R1-R3, RFLTR, CFLTR and D2 for the specific
application, refer to How to Use Analog Dimming With the TPS6116x (SLVA471) and/or Design Tool for Analog
Dimming Using a PWM Signal (SLVC366). Also see Choosing Component Values.
7.5 Programming
7.5.1 EasyScale: One-Wire Digital Dimming
EasyScale is a simple but flexible one pin interface to configure the FB voltage. The interface is based on a
master-slave structure, where the master is typically a microcontroller or application processor. Figure 14 and
Table 2 give an overview of the protocol. The protocol consists of a device specific address byte and a data byte.
The device specific address byte is fixed to 72 hex. The data byte consists of five bits for information, two
address bits, and the RFA bit. The RFA bit set to high indicates the Request for Acknowledge condition. The
Acknowledge condition is only applied if the protocol was received correctly. The advantage of EasyScale
compared with other one-pin interfaces is that its bit detection is in a large extent independent from the bit
transmission rate. It can automatically detect bit rates from 1.7 kBit/sec and up to 160 kBit/sec.
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Table 1. Selectable FB Voltages (1)
(1)
FB voltage
(mV)
D4
D3
D2
D1
D0
0
0
0
0
0
0
0
1
5
0
0
0
0
1
2
8
0
0
0
1
0
3
11
0
0
0
1
1
4
14
0
0
1
0
0
5
17
0
0
1
0
1
6
20
0
0
1
1
0
7
23
0
0
1
1
1
8
26
0
1
0
0
0
9
29
0
1
0
0
1
10
32
0
1
0
1
0
11
35
0
1
0
1
1
12
38
0
1
1
0
0
13
44
0
1
1
0
1
14
50
0
1
1
1
0
15
56
0
1
1
1
1
16
62
1
0
0
0
0
17
68
1
0
0
0
1
18
74
1
0
0
1
0
19
80
1
0
0
1
1
20
86
1
0
1
0
0
21
92
1
0
1
0
1
22
98
1
0
1
1
0
23
104
1
0
1
1
1
24
116
1
1
0
0
0
25
128
1
1
0
0
1
26
140
1
1
0
1
0
27
152
1
1
0
1
1
28
164
1
1
1
0
0
29
176
1
1
1
0
1
30
188
1
1
1
1
0
31
200
1
1
1
1
1
See Digital One-Wire Brightness Dimming.
DATA IN
DATABYTE
Device Address
Start
Start DA7 DA6 DA5 DA4 DA3 DA2 DA1
0
1
1
1
0
0
1
DA0 EOS Start RFA
0
A1
A0
D4
D3
D2
D1
D0
EOS
DATA OUT
ACK
Figure 14. EasyScale Protocol Overview
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Table 2. EasyScale Bit Descriptions
BYTE
Device
Address
Byte
72 hex
Data byte
BIT
NUMBER
NAME
TRANSMISSION
DIRECTION
7
DA7
0 MSB device address
6
DA6
1
5
DA5
1
4
DA4
3
DA3
2
DA2
0
1
DA1
1
DESCRIPTION
1
IN
0
0
DA0
0 LSB device address
7 (MSB)
RFA
Request for acknowledge. If high, acknowledge is applied by device
6
A1
0 Address bit 1
5
A0
0 Address bit 0
4
D4
3
D3
2
D2
Data bit 2
1
D1
Data bit 1
0 (LSB)
D0
Data bit 0
Data bit 4
IN
ACK
Data bit 3
Acknowledge condition active 0, this condition will only be applied in case RFA bit is
set. Open drain output, Line needs to be pulled high by the host with a pullup
resistor. This feature can only be used if the master has an open drain output stage.
In case of a push pull output stage Acknowledge condition may not be requested!
OUT
Easy Scale Timing, without acknowledge RFA = 0
t Start
DATA IN
t Start
Address Byte
DATA Byte
Static High
Static High
DA7
0
DA0
0
D0
1
RFA
0
TEOS
TEOS
Easy Scale Timing, with acknowledge RFA = 1
t Start
DATA IN
t Start
Address Byte
DATA Byte
Static High
Static High
DA7
0
DA0
0
TEOS
RFA
1
D0
1
Controller needs to
Pullup Data Line via a
resistor to detect ACKN
DATA OUT
tLow
Low Bit
(Logic 0)
t High
tLOW
t valACK
ACKN
t ACKN
Acknowledge
true, Data Line
pulled down by
device
Acknowledge
false, no pull
down
tHigh
High Bit
(Logic 1)
Figure 15. EasyScale Bit Coding
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All bits are transmitted MSB first and LSB last. Figure 15 shows the protocol without acknowledge request (Bit
RFA = 0) as well as the with acknowledge (Bit RFA = 1) request. Prior to both bytes, device address byte and
data byte, a start condition must be applied. For this, the CTRL pin must be pulled high for at least tstart (2 μs)
before the bit transmission starts with the falling edge. If the CTRL pin is already at high level, no start condition
is needed prior to the device address byte. The transmission of each byte is closed with an End-of-Stream
condition for at least tEOS (2 μs).
The bit detection is based on a Logic Detection scheme, where the criterion is the relation between tLOW and
tHIGH. It can be simplified to:
High Bit: tHIGH > tLOW, but with tHIGH at least 2 × tLOW, see Figure 15.
Low Bit: tHIGH < tLOW, but with tLOW at least 2 × tHIGH, see Figure 15.
The bit detection starts with a falling edge on the CTRL pin and ends with the next falling edge. Depending on
the relation between tHIGH and tLOW, the logic 0 or 1 is detected.
The acknowledge condition is only applied if:
• Acknowledge is requested by a set RFA bit.
• The transmitted device address matches with the device address of the device.
• 16 bits is received correctly.
If the device turns on the internal ACKN-MOSFET and pulls the CTRL pin low for the time tACKN, which is 512 μs
maximum then the Acknowledge condition is valid after an internal delay time tvalACK. This means that the internal
ACKN-MOSFET is turned on after tvalACK, when the last falling edge of the protocol was detected. The master
controller keeps the line low in this period. The master device can detect the acknowledge condition with its input
by releasing the CTRL pin after tvalACK and read back a logic 0. The CTRL pin can be used again after the
acknowledge condition ends.
Note that the acknowledge condition may only be requested in case the master device has an open drain output.
For a push-pull output stage, the use a series resistor in the CRTL line to limit the current to 500 μA is
recommended to for such cases as:
• an accidentally requested acknowledge, or
• to protect the internal ACKN-MOSFET.
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8 Application and Implementation Information
NOTE
Information in the following applications sections is not part of the TI component
specification, and TI does not warrant its accuracy or completeness. TI’s customers are
responsible for determining suitability of components for their purposes. Customers should
validate and test their design implementation to confirm system functionality.
8.1 Application Information
The TPS61160 and TPS61161 provide a complete high-performance LED lighting solution for mobile devices
supporting a single string of 6 (TPS61160) or 10 (TPS61161) white LEDs.
8.2 Typical Applications
8.2.1 Typical Application of TPS61161
L1
22 mH
VI 3 V to 18 V
C1
1 mF
TPS61161–Q1
ON/OFF
DIMMING
CONTROL
VIN
SW
CTRL
FB
COMP GND
C3
220 nF
D1
38 V Max
C2
1 mF
Rset
10 W
L1: TDK VLCF5020T-220MR75-1
C1: Murata GRM188R61E105K
C2: Murata GRM21BR71H105K
D1: ONsemi MBR0540T1
20 mA
Figure 16. Typical Application of TPS61161
8.2.1.1 Design Requirements
Example requirements for white-LED-driver applications:
Table 3. Design Parameters
DESIGN PARAMETER
EXAMPLE VALUE
Inductor
22 µH
Minimum input voltage
3V
Number of series LED
10
LED maximum forward voltage (Vf)
3.2 V
Schottky diode forward voltage (Vf)
0.2 V
Efficiency (η)
85%
Switching frequency (SW)
600 kHz
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Applying Equation 3 and Equation 4, when VIN is 3 V, 10 LEDs output equivalent to VOUT of 32.2 V, the inductor
is 22 μH, the Schottky forward voltage is 0.2 V, the maximum output current is 47 mA in typical condition.
8.2.1.2 Detailed Design Procedure
8.2.1.2.1 Maximum Output Current
The overcurrent limit in a boost converter limits the maximum input current and thus maximum input power for a
given input voltage. Maximum output power is less than maximum input power due to power conversion losses.
Therefore, the current limit setting, input voltage, output voltage and efficiency can all change maximum current
output. The current limit clamps the peak inductor current; therefore, the ripple has to be subtracted to derive
maximum DC current. The ripple current is a function of switching frequency, inductor value and duty cycle.
Equation 3 and Equation 4 take into account of all the above factors for maximum output current calculation.
1
IP
ª
§
1
1 ·º
«L u FS u ¨
¸»
© VOUT VF VIN VIN ¹ ¼»
¬«
where
•
•
•
•
•
Ip = inductor peak-to-peak ripple
L = inductor value
Vf = Schottky diode forward voltage
Fs = switching frequency
Vout = output voltage of the boost converter. It is equal to the sum of VFB and the voltage drop across
LEDs.
IOUT _ MAX
(3)
I ·
§
VIN u ¨ ILIM P ¸ u K
2¹
©
VOUT
where
•
•
•
Iout_max = maximum output current of the boost converter
Ilim = overcurrent limit
η = efficiency
(4)
For instance, when VIN is 3 V, 8 LEDs output equivalent to VOUT of 26 V, the inductor is 22 μH, the Schottky
forward voltage is 0.2 V; and then the maximum output current is 65 mA in typical condition. When VIN is 5 V, 10
LEDs output equivalent to VOUT of 32 V, the inductor is 22 μH, the Schottky forward voltage is 0.2 V; and then
the maximum output current is 85 mA in typical condition.
8.2.1.2.2 Inductor Selection
The selection of the inductor affects steady state operation as well as transient behavior and loop stability. These
factors make it the most important component in power regulator design. There are three important inductor
specifications, inductor value, DC resistance and saturation current. Considering inductor value alone is not
enough.
The inductor value determines the inductor ripple current. Choose an inductor that can handle the necessary
peak current without saturating, according to half of the peak-to-peak ripple current given by Equation 3, pause
the inductor DC current given by:
VOUT u IOUT
IIN _ DC
VIN u K
(5)
Inductor values can have ±20% tolerance with no current bias. When the inductor current approaches saturation
level, its inductance can decrease 20% to 35% from the 0A value depending on how the inductor vendor defines
saturation current. Using an inductor with a smaller inductance value forces discontinuous PWM when the
inductor current ramps down to zero before the end of each switching cycle. This reduces the boost converter’s
maximum output current, causes large input voltage ripple and reduces efficiency. Large inductance value
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provides much more output current and higher conversion efficiency. For these reasons, a 10-μH to 22-μH
inductor value range is recommended. A 22-μH inductor optimized the efficiency for most application while
maintaining low inductor peak-to-peak ripple. Table 4 lists the recommended inductor for the TPS61160 or
TPS61161. When recommending inductor value, the factory has considered –40% and 20% tolerance from its
nominal value.
The TPS61160 and TPS61161 have built-in slope compensation to avoid sub-harmonic oscillation associated
with current mode control. If the inductor value is lower than 10 μH, the slope compensation may not be
adequate, and the loop can be unstable. Therefore, customers need to verify the inductor in their application if it
is different from the recommended values.
Table 4. Recommended Inductors for TPS61160 and TPS61161
L (μH)
DCR MAX (Ω)
SATURATION CURRENT (mA)
LQH3NPN100NM0
10
0.3
VLCF5020T-220MR75-1
22
0.4
CDH3809/SLD
10
A997AS-220M
22
PART NUMBER
SIZE
(L × W × H mm)
VENDOR
750
3 ×3 ×1.5
Murata
750
5 ×5 × 2.0
TDK
0.3
570
4 × 4 × 1.0
Sumida
0.4
510
4 × 4 × 1.8
TOKO
8.2.1.2.3 Schottky Diode Selection
The high switching frequency of the TPS61160, TPS61161 demands a high-speed rectification for optimum
efficiency. Ensure that the diode average and peak current rating exceeds the average output current and peak
inductor current. In addition, the diode’s reverse breakdown voltage must exceed the open LED protection
voltage. The ONSemi MBR0540 and the ZETEX ZHCS400 are recommended for TPS61160 and TPS61161.
8.2.1.2.4 Compensation Capacitor Selection
The compensation capacitor C3 (see the Functional Block Diagram), connected from COMP pin to GND, is used
to stabilize the feedback loop of the TPS61160, TPS61161. A 220-nF ceramic capacitor for C3 is suitable for
most applications.
8.2.1.2.5 Input and Output Capacitor Selection
The output capacitor is mainly selected to meet the requirements for the output ripple and loop stability. This
ripple voltage is related to the capacitor’s capacitance and its equivalent series resistance (ESR). Assuming a
capacitor with zero ESR, the minimum capacitance needed for a given ripple can be calculated by:
(VOUT VIN )IOUT
COUT
VOUT u FS u VRIPPLE
where
•
Vripple = peak-to-peak output ripple
(6)
The additional output ripple component caused by ESR is calculated using:
VRIPPLE _ ESR IOUT u RESR
(7)
Due to its low ESR, Vripple_ESR can be neglected for ceramic capacitors, but must be considered if tantalum or
electrolytic capacitors are used.
Care must be taken when evaluating a ceramic capacitor’s derating under DC bias, aging and AC signal. For
example, larger form factor capacitors (in 1206 size) have a resonant frequencies in the range of the switching
frequency. So the effective capacitance is significantly lower. The DC bias can also significantly reduce
capacitance. Ceramic capacitors can loss as much as 50% of its capacitance at its rated voltage. Therefore,
leave the margin on the voltage rating to ensure adequate capacitance at the required output voltage.
The capacitor in the range of 1 μF to 4.7 μF is recommended for input side. The output requires a capacitor in
the range of 0.47 μF to 10 μF. The output capacitor affects the loop stability of the boost regulator. If the output
capacitor is below the range, the boost regulator can potentially become unstable. For example, when using an
output capacitor of 0.1 μF, a 470-nF compensation capacitor has to be used for the loop stable.
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The popular vendors for high value ceramic capacitors are:
TDK (http://www.component.tdk.com/components.php)
Murata (http://www.murata.com/cap/index.html)
8.2.1.3 Application Curves
100
90
EFFICIENCY (%)
80
70
60
50
40
VIN = 3.0 V
30
VIN = 3.6 V
20
VIN = 4.2 V
10
VIN = 5.0 V
0
0
10 20 30 40 50 60 70 80 90 100
DIMMING DUTY CYCLE (%)
C002
Figure 18. Start-Up with 10 Series LEDs (DPWM = 100%)
Figure 17. Efficiency vs Dimming Duty Cycle
8.2.2 Li-Ion Driver for 6 White LEDs with External PWM Dimming Network
L1
10 mH
D1
C1
C2
D2
TPS61160
ON/OFF
DIMMING
CONTROL
C3
220 nF
VIN
SW
CTRL
FB
100 Ω
R2
COMP GND
R1
RSET
10 W
RFLTR
L1: Murata LQH3NPN100NM0
C1: Murata GRM188R61A105K
C2: Murata GRM188R61E474K
D1: ONsemi MBR0540T1
D2: ONsemi MMSZ4711
CFLTR
Figure 19. Li-Ion Driver for 6 White LEDs with External PWM Dimming
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8.2.2.1 Design Requirements
Example parameters for white LEDs with external PWM dimming:
Table 5. Design Parameters for White LEDs with External PWM Dimming
DESIGN PARAMETER
EXAMPLE VALUE
Inductor
10 µH
Minimum input voltage
3.6 V
Number of series LED
6
LED maximum forward voltage (Vf)
3.2 V
Schottky diode forward voltage (Vf)
0.2 V
Efficiency
90%
Switching frequency (fSW)
600 kHz
External PWM output voltage
3V
External PWM frequency
20 kHz
Applying Equation 3 and Equation 4 when VIN is 3 V, 6 LEDs output equivalent to VOUT of 19.4 V, the inductor is
10 μH, the Schottky forward voltage is 0.2 V, the maximum output current is 76 mA in typical condition.
8.2.2.2 Detailed Design Procedure
8.2.2.2.1 Choosing Component Values
As per SLVA471, the values of RFLTR, CFLTR, R1, R2, and RSET are determined by the system parameters and
error tolerance. The main source of LED current error is leakage current from the FB pin. The error gets worse
as the LED current decreases. The error due to leakage current is given by Functional Block Diagram, where the
impedance seen by the FB pin has a major impact. To reduce error due to the leakage current, the impedance
seen by the FB pin needs to be small. Because R2 is much smaller than R1 + RFLTR, R2 must be chosen to be
small to minimize the impedance seen by the FB pin. In general, R2 must be chosen to be 1 kΩ or less. If greater
accuracy at smaller currents is needed, then R2 must be chosen to be even smaller.
% error =
IFB
D ´ VPWM ( H ) + (1 - D ) VPWM ( L )
VFB
(R 1 + R FLTR ) // R 2
R 1 + R FLTR
(8)
Once R2 has been chosen, the value of RSET and R1 + RFLTR can be calculated using Equation 9, Equation 10,
Equation 11, and Equation 12. The individual values of R1 and RFLTR can be any combination that sums up to R1
+ RFLTR . In general, choosing R1 and RFLTR to be the same value gives a minimum requirement for CFLTR.
VPWM(min) = D(min)VPWM(H) + (1 - D(min) )VPWM(L)
(9)
VPWM(max) = D(max) VPWM(H) + (1 - D(max) )VPWM(L)
R SET =
(
VFB VPWM(max) - VPWM(min)
(10)
)
VP WM(ma x)ILE D(max) VFBILED(max) + VFBIL ED(min ) - VPWM(min)IL ED(min )
R1 + R FLTR =
(11)
R 2 (IL ED(ma x) (VPW M(max) - VFB ) - ILED(min) (VPW M(min) - VFB ))
VFB (ILED(max) - ILED(min) )
+
VPWM(max) - VPWM(min)
ILE D(max) - ILED(min)
(12)
Finally, CFLTR can be chosen based on the amount of filtering desired or to provide a gradual dimming effect that
is popular in many lighting products. At a minimum, CFLTR must be chosen to provide at least 20 dB of
attenuation at the PWM frequency. Equation 13 can be used to calculate the minimum capacitor value to provide
this attenuation.
1
CFLTR =
f pwm
2p (RFLTR // R1)
10
(13)
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To provide gradual dimming, a large capacitor must be chosen to provide a long transient time when changing
the PWM duty cycle. Equation 14 shows how to calculate the recommended corner frequency of the RC filter
based on the 10% to 90% rise time. Once the corner frequency is known, it can be used to calculate the required
capacitor using Equation 15.
0.35
fRC =
tr
(14)
CFLTR =
1
2p (RFLTR // R1 ) fRC
(15)
For example, a design with RFLTR and R1 equal to 10 kΩ and a desired rise time of 500 ms requires a corner
frequency of 0.7 Hz and a capacitor of 47 μF.
8.2.2.3 Application Curves
100
90
EFFICIENCY (%)
80
70
60
50
40
VIN = 3.0 V
30
VIN = 3.6 V
20
VIN = 4.2 V
10
VIN = 5.0 V
0
0
10 20 30 40 50 60 70 80 90 100
DIMMING DUTY CYCLE (%)
C002
Figure 20. Efficiency vs Dimming Duty Cycle
Figure 21. Start-Up with 6 Series LEDs (External PWM,
DPWM = 50%)
Figure 22. Start-Up with 6 Series LEDs (External PWM, DPWM = 100%)
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8.2.3 Li-Ion Driver for 6 White LEDs
VIN 3 V to 5 V
C1
1 mF
L1
10 mH
D1
TPS61160
ON/OFF
DIMMING
CONTROL
VIN
SW
CTRL
FB
COMP
GND
C3
220 nF
C2
0.47 mF
RSET
10 W
20 mA
L1: Murata LQH3NPN100NM0
C1: Murata GRM188R61A105K
C2: Murata GRM188R61E474K
D1: ONsemi MBR0540T1
Figure 23. Li-Ion Driver for 6 White LEDs
8.2.3.1 Design Requirements
Example parameters for Li-Ion drivers with 6 white LEDs:
Table 6. Design Parameters for Li-Ion Driver with 6 White LEDs
DESIGN PARAMETER
EXAMPLE VALUE
Inductor
10 µH
Minimum input voltage
3V
Number of series LED
6
LED maximum forward voltage (Vf)
3.2 V
Schottky diode forward voltage (Vf)
0.6 V
Efficiency (η)
88%
Switching frequency
600 kHz
Applying Equation 3 and Equation 4, when VIN is 3 V, 6 LEDs output equivalent to VOUT of 19.4 V, the inductor is
10 μH, the Schottky forward voltage is 0.2 V, the maximum output current is 66 mA in typical condition.
8.2.3.2 Detailed Design Procedure
See Detailed Design Procedure.
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8.2.3.3 Application Curves
100
90
EFFICIENCY (%)
80
70
60
50
40
VIN = 3.0 V
30
VIN = 3.6 V
20
VIN = 4.2 V
10
VIN = 5.0 V
0
0
10 20 30 40 50 60 70 80 90 100
DIMMING DUTY CYCLE (%)
C002
Figure 24. Efficiency vs Duty Cycle
Figure 25. Start-Up with 6 Series LEDs (DPWM = 50%)
Figure 26. Start-Up with 6 Series LEDs (DPWM = 100%)
8.2.4 Li-Ion Driver for 8 White LEDs
For assistance in selecting the proper values for RSET, R1-R3, RFLTR, CFLTR and D2 for the specific
application, refer to SLVA471 and/or SLVC366.
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L1
22 mH
Vin 3 V to 5 V
D1
C2
C1
TPS61161
ON/OFF
DIMMING
CONTROL
VIN
SW
CTRL
FB
COMP
GND
C3
220 nF
Rset
10 W
L1: TDK VLCF5020T-220MR75-1
C1: Murata GRM188R61A105K
C2: Murata GRM21BR71H105K
D1: ONsemi MBR0540T1
20mA
Figure 27. Li-Ion Driver for 8 White LEDs
8.2.4.1 Design Requirements
Example parameters for Li-Ion driver with 8 white LEDs:
Table 7. Design Parameters for Li-Ion Driver with 8 White LEDs
DESIGN PARAMETER
EXAMPLE VALUE
Inductor
22 µH
Minimum input voltage
3V
Number of series LED
8
LED maximum forward voltage (Vf)
3.2 V
Schottky diode forward voltage
0.2 V
Efficiency (η)
85%
Switching frequency
600 kHz
Applying Equation 3 and Equation 4, when VIN is 3 V, 8 LEDs output equivalent to VOUT of 25.8 V, the inductor is
22 μH, the Schottky forward voltage is 0.2 V, the maximum output current is 60 mA in typical condition.
8.2.4.2 Detailed Design Procedure
See Detailed Design Procedure.
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8.2.4.3 Application Curves
100
90
EFFICIENCY (%)
80
70
60
50
40
VIN = 3.0 V
30
VIN = 3.6 V
20
VIN = 4.2 V
10
VIN = 5.0 V
0
0
10 20 30 40 50 60 70 80 90 100
DIMMING DUTY CYCLE (%)
C002
Figure 28. Efficiency vs Duty Cycle
Figure 29. Start-Up with 8 Series LEDs (DPWM = 100%)
9 Power Supply Recommendations
The TPS61160 and TPS61161 are designed to operate from an input supply range of 2.7 V to 18 V. This input
supply must be well regulated and be able to provide the peak current required by the LED configuration and
inductor selected without voltage drop under load transients (start-up or rapid brightness change). The resistance
of the input supply rail must be low enough such that the input current transient does not cause the TPS61160
and TPS61161 supply voltage to droop more than 5%. Additional bulk decoupling located close to the input
capacitor (CIN) may be required to minimize the impact of the input supply rail resistance.
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10 Layout
10.1 Layout Guidelines
As for all switching power supplies, especially those high frequency and high current ones, layout is an important
design step. If layout is not carefully done, the regulator could suffer from instability as well as noise problems.
To reduce switching losses, the SW pin rise and fall times are made as short as possible. To prevent radiation of
high frequency resonance problems, proper layout of the high frequency switching path is essential. Minimize the
length and area of all traces connected to the SW pin and always use a ground plane under the switching
regulator to minimize inter-plane coupling. The loop including the PWM switch, Schottky diode, and output
capacitor, contains high current rising and falling in nanosecond and must be kept as short as possible. The input
capacitor must not only be close to the VIN pin, but also to the GND pin in order to reduce the device supply
ripple. Figure 30 shows a sample layout.
10.2 Layout Example
C1
Rset
Vin
LEDs Out
Vin
FB
L1
CTRL
COMP
CTRL
GND
SW
C3
C2
GND
Place enough
VIAs around
thermal pad to
enhance thermal
performance
LEDs IN
Minimize the
area of this
trace
Figure 30. TPS6116x Sample Layout
10.3 Thermal Considerations
The maximum device junction temperature should be restricted to 125°C under normal operating conditions. This
restriction limits the power dissipation of the TPS61160 or TPS61161. Calculate the maximum allowable
dissipation, PD(max), and keep the actual dissipation less than or equal to PD(max). The maximum-power-dissipation
limit is determined using values in Equation 16:
125°C - TA
PD(max) =
RqJA
where
•
•
TA is the maximum ambient temperature for the application
RθJA is the thermal resistance junction-to-ambient given in Thermal Information.
(16)
The TPS61160 and TSP61161 come in a thermally enhanced WSON package. This package includes a thermal
pad that improves the thermal capabilities of the package. The RθJA of the WSON package greatly depends on
the PCB layout and thermal pad connection. The thermal pad must be soldered to the analog ground on the
PCB. Using thermal vias underneath the thermal pad as illustrated in the layout example. Also see the QFN/SON
PCB Attachment application report (SLUA271).
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11 Device and Documentation Support
11.1 Device Support
11.1.1 Third-Party Products Disclaimer
TI'S PUBLICATION OF INFORMATION REGARDING THIRD-PARTY PRODUCTS OR SERVICES DOES NOT
CONSTITUTE AN ENDORSEMENT REGARDING THE SUITABILITY OF SUCH PRODUCTS OR SERVICES
OR A WARRANTY, REPRESENTATION OR ENDORSEMENT OF SUCH PRODUCTS OR SERVICES, EITHER
ALONE OR IN COMBINATION WITH ANY TI PRODUCT OR SERVICE.
11.2 Documentation Support
11.2.1 Related Documentation
For related documentation, see the following:
• QFN/SON PCB Attachment
• How to Use Analog Dimming With the TPS6116x
• Design Tool for Analog Dimming Using a PWM Signal
11.3 Related Links
11.3.1 Related Links
Table 8 lists quick access links. Categories include technical documents, support and community resources,
tools and software, and quick access to sample or buy.
Table 8. Related Links
PARTS
PRODUCT FOLDER
SAMPLE & BUY
TECHNICAL
DOCUMENTS
TOOLS &
SOFTWARE
SUPPORT &
COMMUNITY
TPS61160
Click here
Click here
Click here
Click here
Click here
TPS61161
Click here
Click here
Click here
Click here
Click here
11.4 Receiving Notification of Documentation Updates
To receive notification of documentation updates, navigate to the device product folder on ti.com. In the upper
right corner, click on Alert me to register and receive a weekly digest of any product information that has
changed. For change details, review the revision history included in any revised document.
11.5 Community Resources
The following links connect to TI community resources. Linked contents are provided "AS IS" by the respective
contributors. They do not constitute TI specifications and do not necessarily reflect TI's views; see TI's Terms of
Use.
TI E2E™ Online Community TI's Engineer-to-Engineer (E2E) Community. Created to foster collaboration
among engineers. At e2e.ti.com, you can ask questions, share knowledge, explore ideas and help
solve problems with fellow engineers.
Design Support TI's Design Support Quickly find helpful E2E forums along with design support tools and
contact information for technical support.
11.6 Trademarks
EasyScale, E2E are trademarks of Texas Instruments.
All other trademarks are the property of their respective owners.
11.7 Electrostatic Discharge Caution
These devices have limited built-in ESD protection. The leads should be shorted together or the device placed in conductive foam
during storage or handling to prevent electrostatic damage to the MOS gates.
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SLVS791E – NOVEMBER 2007 – REVISED JULY 2016
11.8 Glossary
SLYZ022 — TI Glossary.
This glossary lists and explains terms, acronyms, and definitions.
12 Mechanical, Packaging, and Orderable Information
The following pages include mechanical, packaging, and orderable information. This information is the most
current data available for the designated devices. This data is subject to change without notice and revision of
this document. For browser-based versions of this data sheet, refer to the left-hand navigation.
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PACKAGE OPTION ADDENDUM
www.ti.com
14-Oct-2022
PACKAGING INFORMATION
Orderable Device
Status
(1)
Package Type Package Pins Package
Drawing
Qty
Eco Plan
(2)
Lead finish/
Ball material
MSL Peak Temp
Op Temp (°C)
Device Marking
(3)
Samples
(4/5)
(6)
HPA00667DRVR
ACTIVE
WSON
DRV
6
3000
TBD
Call TI
Call TI
-40 to 85
Samples
HPA00810-2/2
ACTIVE
WSON
DRV
6
3000
TBD
Call TI
Call TI
-40 to 85
Samples
TPS61160DRVR
ACTIVE
WSON
DRV
6
3000
RoHS & Green
NIPDAU
Level-2-260C-1 YEAR
-40 to 85
BZQ
Samples
TPS61160DRVRG4
ACTIVE
WSON
DRV
6
3000
RoHS & Green
NIPDAU
Level-2-260C-1 YEAR
-40 to 85
BZQ
Samples
TPS61160DRVT
ACTIVE
WSON
DRV
6
250
RoHS & Green
NIPDAU
Level-2-260C-1 YEAR
-40 to 85
BZQ
Samples
TPS61161DRVR
ACTIVE
WSON
DRV
6
3000
RoHS & Green
NIPDAU
Level-2-260C-1 YEAR
-40 to 85
BZR
Samples
TPS61161DRVRG4
ACTIVE
WSON
DRV
6
3000
RoHS & Green
NIPDAU
Level-2-260C-1 YEAR
-40 to 85
BZR
Samples
TPS61161DRVT
ACTIVE
WSON
DRV
6
250
RoHS & Green
NIPDAU
Level-2-260C-1 YEAR
-40 to 85
BZR
Samples
TPS61161DRVTG4
ACTIVE
WSON
DRV
6
250
RoHS & Green
NIPDAU
Level-2-260C-1 YEAR
-40 to 85
BZR
Samples
(1)
The marketing status values are defined as follows:
ACTIVE: Product device recommended for new designs.
LIFEBUY: TI has announced that the device will be discontinued, and a lifetime-buy period is in effect.
NRND: Not recommended for new designs. Device is in production to support existing customers, but TI does not recommend using this part in a new design.
PREVIEW: Device has been announced but is not in production. Samples may or may not be available.
OBSOLETE: TI has discontinued the production of the device.
(2)
RoHS: TI defines "RoHS" to mean semiconductor products that are compliant with the current EU RoHS requirements for all 10 RoHS substances, including the requirement that RoHS substance
do not exceed 0.1% by weight in homogeneous materials. Where designed to be soldered at high temperatures, "RoHS" products are suitable for use in specified lead-free processes. TI may
reference these types of products as "Pb-Free".
RoHS Exempt: TI defines "RoHS Exempt" to mean products that contain lead but are compliant with EU RoHS pursuant to a specific EU RoHS exemption.
Green: TI defines "Green" to mean the content of Chlorine (Cl) and Bromine (Br) based flame retardants meet JS709B low halogen requirements of
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