TSM9118

TSM9117-TSM9120 1.6V Nanopower Comparators with/without Internal References FEATURES ♦ Second-source for MAX9117-MAX9120 ♦ Guaranteed to Operate Down to +1.6V ♦ Ultra-Low Supply Current 350nA - TSM9119/TSM9120 600nA - TSM9117/TSM9118 ♦ Internal 1.252V ±1.75% Reference ♦ Input Voltage Range Extends 200mV Outside-the-Rails ♦ No Phase Reversal for Overdriven Inputs ♦ Push-pull and Open-Drain Output Versions Available ♦ Crowbar-Current-Free Switching ♦ Internal Hysteresis for Clean Switching ♦ 5-pin SC70 and 8-pin SOIC Packaging DESCRIPTION The TSM9117–TSM9120 family of nanopower comparators is electrically and form-factor identical to the MAX9117-MAX9120 family of analog comparators. Ideally suited for all 2-cell batterymanagement/monitoring applications, these 5-pin SC70 analog comparators guarantee +1.6V operation, draw very little supply current, and have robust input stages that can tolerate input voltages beyond the power supply. The TSM9117 and the TSM9118 draw 600nA of supply current and include an on-board 1.252V ±1.75% reference. The comparator-only TSM9119 and the TSM9120 draw a supply current of 350nA. The TSM9117 and TSM9119’s push-push output drivers were designed to drive 5mA loads from one supply rail to the other supply rail. The TSM9118 and the TSM9120’s open-drain output stages make it easy to incorporate these comparators into systems that operate on different supply voltages. APPLICATIONS 2-Cell Battery Monitoring/Management Medical Instruments Threshold Detectors/Discriminators Sensing at Ground or Supply Line Ultra-Low-Power Systems Mobile Communications Telemetry and Remote Systems TYPICAL APPLICATION CIRCUIT PART TSM9117 TSM9118 TSM9119 TSM9120 The Touchstone Semiconductor logo is a registered trademark of Touchstone Semiconductor, Incorporated. INTERNAL REFERENCE Yes Yes No No OUTPUT TYPE Push-Pull Open-Drain Push-Pull Open-Drain SUPPLY CURRENT (nA) 600 600 350 350 Page 1 © 2011 Touchstone Semiconductor, Inc. All rights reserved. TSM9117-TSM9120 ABSOLUTE MAXIMUM RATINGS Supply Voltage (VCC to VEE) ............................................ +6V Voltage Inputs (IN+, IN-, REF) .... (VEE - 0.3V) to (VCC + 0.3V) Output Voltage TSM9117/9119 ........................ (VEE - 0.3V) to (VCC + 0.3V) TSM9118/9120 ...................................... (VEE - 0.3V) to +6V Current Into Input Pins ................................................ ±20mA Output Current ............................................................ ±50mA Output Short-Circuit Duration ............................................ 10s Continuous Power Dissipation (TA = +70°C) 5-Pin SC70 (Derate 2.5mW/°C above +70°C) ........ 200mW 8-Pin SOIC (Derate 5.88mW/°C above +70°C) ...... 471mW Operating Temperature Range ...................... -40°C to +85°C Junction Temperature ................................................ +150°C Storage Temperature Range ....................... -65°C to +150°C Lead Temperature (soldering, 10s) ............................... +300° Electrical and thermal stresses beyond those listed under “Absolute Maximum Ratings” may cause permanent damage to the device. These are stress ratings only and functional operation of the device at these or any other condition beyond those indicated in the operational sections of the specifications is not implied. Exposure to any absolute maximum rating conditions for extended periods may affect device reliability and lifetime. PACKAGE/ORDERING INFORMATION ORDER NUMBER PART CARRIER QUANTITY ORDER NUMBER MARKING PART CARRIERQUANTITY MARKING TSM9117EXK+T TSM9118EXK+T TSM9119EXK+T TSM9120EXK+T TAA TAB TAC TAD Tape & Reel Tape & Reel Tape & Reel Tape & Reel 3000 3000 3000 3000 TSM9117ESA+ TS9117E TSM9117ESA+T TSM9120ESA+ TS9120E TSM9120ESA+T Tube Tape & Reel Tube Tape & Reel 97 2500 97 2500 Lead-free Program: Touchstone Semiconductor supplies only lead-free packaging. Consult Touchstone Semiconductor for products specified with wider operating temperature ranges. Page 2 TSM9117_20DS r1p0 RTFDS TSM9117-TSM9120 ELECTRICAL CHARACTERISTICS: TSM9117 & TSM9118 VCC = +5V, VEE = 0V, VIN+ = VREF, TA = -40°C to +85°C, unless otherwise noted. Typical values are at TA = +25°C. See Note 1. PARAMETER Supply Voltage Range Supply Current IN+ Voltage Range Input Offset Voltage Input-Referred Hysteresis Input Bias Current Power-Supply Rejection Ratio SYMBOL VCC ICC VIN+ VOS VHB IB PSRR TA = +25°C TA = TMIN to TMAX TA = +25°C TA = +25°C VCC = 5V TA = TMIN to TMAX Inferred from the output swing test TA = +25°C (Note 2) TA = TMIN to TMAX (Note 3) TA = +25°C TA = TMIN to TMAX VCC = 1.6V to 5.5V, TA = +25°C VCC = 1.8V to 5.5V, TA = TMIN to TMAX TA = +25°C TSM9117, VCC = 5V, ISOURCE = 5mA TA = TMIN to TMAX VCC = 1.6V, TA = +25°C TSM9117, ISOURCE = 1mA VCC = 1.8V, TA = TMIN to TMAX TA = +25°C VCC = 5V, ISINK = 5mA TA = TMIN to TMAX VCC = 1.6V, TA = +25°C ISINK = 1mA VCC = 1.8V, TA = TMIN to TMAX TSM9118 only, VO = 5.5V VCC = 5V Sourcing, VO = VEE VCC = 1.6V VCC = 5V Sinking, VO = VCC VCC = 1.6V VCC = 1.6V VCC = 5V VCC = 1.6V TSM9117 only VCC = 5V VCC = 1.6V, RPULLUP = 100kΩ TSM9118 only VCC = 5V, RPULLUP = 100kΩ TSM9117 only, CL = 15pF CL = 15pF TA = +25°C TA = TMIN to TMAX BW = 10Hz to 100kHz BW = 10Hz to 100kHz, CREF = 1nF VCC = 1.6V to 5.5V CONDITIONS Inferred from the PSRR test VCC = 1.6V MIN 1.6 1.8 TYP MAX 5.5 5.5 1 1.30 1.60 VCC + 0.2 5 10 1 2 1 1 400 500 200 300 190 100 400 500 200 300 0.002 35 3 35 3 16 14 15 40 16 45 1.6 0.2 1.2 1.230 1.196 1.252 100 1.1 0.2 0.25 ±1 1.274 1.308 µs µs ms V ppm/°C mVRMS mV/V mV/nA 1 μA mA mV UNITS V μA V mV mV nA mV/V mV/V 0.6 0.68 VEE - 0.2 1 4 0.15 0.1 190 100 Output-Voltage Swing High VCC - VOH mV Output-Voltage Swing Low VOL Output Leakage Current Output Short-Circuit Current High-to-Low Propagation Delay (Note 4) ILEAK ISC tPD- µs Low-to-High Propagation Delay (Note 4) tPD+ µs Rise Time Fall Time Power-Up Time Reference Voltage Reference Voltage Temperature Coefficient Reference Output Voltage Noise Reference Line Regulation Reference Load Regulation tRISE tFALL tON VREF TCVREF en ∆VREF/ ∆VCC ∆VREF/ ∆IOUT ∆IOUT = 10nA TSM9117_20DS r1p0 Page 3 RTFDS TSM9117-TSM9120 ELECTRICAL CHARACTERISTICS: TSM9119 & TSM9120 VCC = +5V, VEE = 0V, VCM = 0V, TA = -40°C to +85°C, unless otherwise noted. Typical values are at TA = +25°C. See Note 1. PARAMETER Supply Voltage Range Supply Current Input Common-Mode Voltage Range Input Offset Voltage Input-Referred Hysteresis Input Bias Current Input Offset Current Power-Supply Rejection Ratio Common-Mode Rejection Ratio SYMBOL VCC ICC VCM VOS VHB IB IOS PSRR CMRR VCC = 1.6V to 5.5V, TA = +25°C VCC = 1.8V to 5.5V, TA = TMIN to TMAX (VEE - 0.2V) ≤ VCM ≤ (VCC + 0.2V) TA = +25°C TSM9119 only, VCC = 5V, ISOURCE = 5mA TA = TMIN to TMAX VCC = 1.6V, TA = +25°C TSM9119 only, ISOURCE = 1mA VCC = 1.8V, TA = TMIN to TMAX TA = +25°C VCC = 5V, ISINK = 5mA TA = TMIN to TMAX VCC = 1.6V, TA = +25°C ISINK = 1mA VCC = 1.8V, TA = TMIN to TMAX TSM9120 only, VO = 5.5V VCC = 5V Sourcing, VO = VEE VCC = 1.6V VCC = 5V Sinking, VO = VCC VCC = 1.6V VCC = 1.6V VCC = 5V VCC = 1.6V TSM9119 only VCC = 5V VCC = 1.6V, RPULLUP = 100kΩ TSM9120 only VCC = 5V, RPULLUP = 100kΩ TSM9119 only, CL = 15pF CL = 15pF CONDITIONS Inferred from the PSRR test VCC = 1.6V VCC = 5V Inferred from the CMRR test TA = +25°C -0.2V ≤ VCM ≤ (VCC+0.2V) (Note 2) TA = TMIN to TMAX -0.2V ≤ VCM ≤ (VCC+0.2V) (Note 3) TA = +25°C TA = TMIN to TMAX TA = +25°C TA = TMIN to TMAX TA = +25°C TA = +25°C TA = TMIN to TMAX MIN 1.6 1.8 TYP MAX 5.5 5.5 0.80 0.80 1.20 VCC + 0.2 1 4 0.15 75 0.1 0.5 190 100 5 10 1 2 1 1 3 400 500 200 300 190 100 400 500 200 300 0.001 35 3 35 3 16 14 15 40 16 45 1.6 0.2 1.2 µs µs ms 1 μA mA mV UNITS V μA V mV mV nA pA mV/V mV/V mV/V 0.35 0.45 VEE - 0.2 Output-Voltage Swing High VCC - VOH mV Output-Voltage Swing Low VOL Output Leakage Current Output Short-Circuit Current High-to-Low Propagation Delay (Note 4) ILEAK ISC tPD- µs Low-to-High Propagation Delay (Note 4) tPD+ µs Rise Time Fall Time Power-Up Time tRISE tFALL tON Note 1: All specifications are 100% tested at TA = +25°C. Specification limits over temperature (TA = TMIN to TMAX) are guaranteed by design, not production tested. Note 2: VOS is defined as the center of the hysteresis band at the input. Note 3: The hysteresis-related trip points are defined by the edges of the hysteresis band, measured with respect to the center of the hysteresis band (i.e., VOS) (See Figure 2). Note 4: Specified with an input overdrive (VOVERDRIVE) of 100mV, and load capacitance of CL = 15pF. VOVERDRIVE is defined above and beyond the offset voltage and hysteresis of the comparator input. For the TSM9117/TSM9118, reference voltage error should also be added. Page 4 TSM9117_20DS r1p0 RTFDS TSM9117-TSM9120 TYPICAL PERFORMANCE CHARACTERISTICS VCC = +5V; VEE = 0V; CL = 15pF; VOVERDRIVE = 100mV; TA = +25°C, unless otherwise noted. TSM9117/9118 Supply Current vs TSM9119/9120 Supply Current Supply Voltage and Temperature vs Supply Voltage and Temperature 1 1.25 1.15 SUPPLY CURENT - µA 1.05 0.95 0.85 0.75 0.65 0.55 0.45 0.2 1.5 2.5 3.5 4.5 5.5 1.5 2.5 3.5 4.5 5.5 SUPPLY VOLTAGE - Volt SUPPLY VOLTAGE - Volt TA = -40°C TA = +25°C TA = +85°C 0.9 SUPPLY CURENT - µA 0.8 0.7 0.6 0.5 0.4 0.3 TA = -40°C TA = +25°C TA = +85°C TSM9117/9118 Supply Current vs Temperature 1.1 1 SUPPLY CURENT - µA SUPPLY CURENT - µA 0.9 0.8 0.7 0.6 VCC =+1.8V 0.5 0.4 -40 -15 10 35 60 85 TEMPERATURE - °C TSM9117/9118 Supply Current vs Output Transition Frequency 35 30 SUPPLY CURRENT - µA 25 20 15 10 VCC =+1.8V 5 0 1 10 100 1k 10k OUTPUT TRANSITION FREQUENCY - Hz VCC =+5V VCC =+3V SUPPLY CURRENT - µA VCC =+3V VCC =+5V TSM9119/9120 Supply Current vs Temperature 1 0.9 0.8 0.7 0.6 0.5 0.4 0.3 0.2 -40 -15 10 35 60 85 TEMPERATURE - °C TSM9119/9120 Supply Current vs Output Transition Frequency 35 30 25 20 15 10 5 0 1 10 100 1k 10k OUTPUT TRANSITION FREQUENCY- Hz VCC =+5V VCC =+3V VCC =+1.8V VCC =+1.8V VCC =+3V VCC =+5V TSM9117_20DS r1p0 Page 5 RTFDS TSM9117-TSM9120 TYPICAL PERFORMANCE CHARACTERISTICS VCC = +5V; VEE = 0V; CL = 15pF; VOVERDRIVE = 100mV; TA = +25°C, unless otherwise noted. Output Voltage Low vs. Sink Current 700 TA = +25°C 600 500 VOL - mV 400 300 200 100 0 VCC =+5V VCC =+1.8V VOL - mV VCC =+3V 500 400 300 TA = +85°C 200 100 0 0 2 4 6 8 10 0 2 4 6 8 10 SINK CURRENT- mA TSM9117/9119 Output Voltage High vs Source Current 0.7 0.6 VCC =+1.8V 0.5 VCC – VOH - V 0.4 0.3 0.2 0.1 0 VCC =+5V VCC =+3V VCC – VOH - V 0.4 0.3 TA = +85°C 0.2 0.1 0 0 2 4 6 8 10 0 2 4 6 8 10 SOURCE CURRENT- mA SOURCE CURRENT- mA TSM9117/9119 Short-Circuit Source Current vs Temperature 50 45 SOURCE CURRENT- mA VCC =+5V 40 35 30 25 20 15 10 5 0 -40 -15 10 35 60 85 -40 -15 10 35 60 85 TEMPERATURE - °C TEMPERATURE - °C VCC =+1.8V VCC =+3V VCC =+5V TA = -40°C 0.6 0.5 TA = +25°C SINK CURRENT- mA TSM9117/9119 Output Voltage High vs Source Current and Temperature TA = -40°C 600 Output Voltage Low vs. Sink Current and Temperature TA = +25°C Short-Circuit Sink Current vs Temperature 40 35 SINK CURRENT- mA 30 25 20 15 10 5 0 VCC =+1.8V VCC =+3V Page 6 TSM9117_20DS r1p0 RTFDS TSM9117-TSM9120 TYPICAL PERFORMANCE CHARACTERISTICS VCC = +5V; VEE = 0V; CL = 15pF; VOVERDRIVE = 100mV; TA = +25°C, unless otherwise noted. Offset Voltage vs Temperature 2.8 VCC =+1.8V 2.6 5 VOS - mV 2.4 VCC =+3V VHB - mV 4.5 4 2.2 VCC =+5V 3.5 2 -40 -15 10 35 60 85 TEMPERATURE - °C TSM9117/9118 Reference Voltage vs Temperature 1.260 1.258 REFERENCE VOLTAGE - V 1.256 1.254 1.252 1.250 1.248 1.246 1.244 1.242 1.240 -40 -15 10 35 60 85 VCC =+3V VCC =+5V REFERENCE VOLTAGE - V VCC =+1.8V 1.253 1.252 1.251 1.250 1.249 1.5 2.5 3.5 4.5 5.5 1.254 3 -40 -15 10 35 60 85 TEMPERATURE - °C TSM9117/9118 Reference Voltage vs Supply Voltage 6 5.5 Hysteresis Voltage vs Temperature TEMPERATURE - °C TSM9117/9118 Reference Voltage vs Reference Source Current 1.260 1.258 REFERENCE VOLTAGE - V REFERENCE VOLTAGE - V 1.256 1.254 1.252 1.250 1.248 1.246 1.244 1.242 1.240 0 2 4 6 8 10 SOURCE CURRENT- nA VCC =+3V, 5V VCC =+1.8V 1.260 1.258 1.256 1.254 1.252 1.250 1.248 1.246 1.244 1.242 1.240 0 SUPPLY VOLTAGE - Volt TSM9117/9118 Reference Voltage vs Reference Sink Current VCC =+1.8V VCC =+3V, 5V 2 4 6 8 10 SINK CURRENT- nA TSM9117_20DS r1p0 Page 7 RTFDS TSM9117-TSM9120 TYPICAL PERFORMANCE CHARACTERISTICS VCC = +5V; VEE = 0V; CL = 15pF; VOVERDRIVE = 100mV; TA = +25°C, unless otherwise noted. 28 26 24 22 20 tPD- - µs 18 16 14 12 10 8 6 -40 -15 10 35 60 85 0 -40 -15 10 35 60 85 VCC =+1.8V VCC =+3V VCC =+5V tPD+ - µs 40 30 20 10 VCC =+1.8V 50 VCC =+5V VCC =+3V Propagation Delay (tPD-) vs Temperature TSM9117/9119 Propagation Delay (tPD+) vs Temperature 60 TEMPERATURE - °C TEMPERATURE - °C Propagation Delay (tPD-) vs Capacitive Load 200 180 160 140 tPD- - µs 120 100 80 60 40 20 0 0.01 0.1 1 10 100 1000 CAPACITIVE LOAD - nF VCC =+3V VCC =+5V VCC =+1.8V TSM9117/9119 Propagation Delay (tPD+) vs Capacitive Load 180 160 140 120 tPD+ - µs 100 80 60 40 20 0 0.01 0.1 1 10 100 1000 CAPACITIVE LOAD - nF VCC =+5V VCC =+3V VCC =+1.8V Propagation Delay (tPD-) vs Input Overdrive 80 70 60 tPD+ - µs 50 tPD- - µs 40 30 20 10 0 0 10 20 30 40 50 INPUT OVERDRIVE - mV VCC =+1.8V VCC =+3V VCC =+5V TSM9117/9119 Propagation Delay (tPD+) vs Input Overdrive 70 60 50 VCC =+3V 40 30 20 10 0 0 10 20 30 40 50 INPUT OVERDRIVE - mV VCC =+1.8V VCC =+5V Page 8 TSM9117_20DS r1p0 RTFDS TSM9117-TSM9120 TYPICAL PERFORMANCE CHARACTERISTICS VCC = +5V; VEE = 0V; CL = 15pF; VOVERDRIVE = 100mV; TA = +25°C, unless otherwise noted. TSM9118/9120 Propagation Delay (tPD-) vs Pullup Resistance 15 14 13 12 tPD- - µs 11 10 9 8 7 6 10 VCC =+1.8V 100 RPULLUP - kΩ Propagation Delay (tPD-) at VCC = +5V 1k 10k VCC =+3V tPD+ - µs VCC =+5V TSM9118/9120 Propagation Delay (tPD+) vs Pullup Resistance 200 180 160 140 120 100 80 60 40 20 0 10 100 RPULLUP - kΩ TSM9117/9119 Propagation Delay (tPD+) at VCC = +5V 1k 100k VCC =+1.8V VCC =+3V VCC =+5V OUTPUT INPUT 20µs/DIV OUTPUT INPUT 20µs/DIV TSM9117/9119 Propagation Delay (tPD+) at VCC = +3V Propagation Delay (tPD-) at VCC = +3V INPUT OUTPUT 20µs/DIV OUTPUT INPUT 20µs/DIV TSM9117_20DS r1p0 Page 9 RTFDS TSM9117-TSM9120 TYPICAL PERFORMANCE CHARACTERISTICS VCC = +5V; VEE = 0V; CL = 15pF; VOVERDRIVE = 100mV; TA = +25°C, unless otherwise noted. Propagation Delay (tPD-) at VCC = +1.8V TSM9117/9119 Propagation Delay (tPD+) at VCC = +1.8V INPUT OUTPUT 20µs/DIV TSM9117/9119 10kHz Transient Response at VCC = +1.8V OUTPUT INPUT 20µs/DIV TSM9117/9119 1kHz Transient Response at VCC = +5V INPUT OUTPUT 20µs/DIV OUTPUT INPUT 200µs/DIV Power-Up/Power-Down Transient Response OUTPUT INPUT 0.2s/DIV Page 10 TSM9117_20DS r1p0 RTFDS TSM9117-TSM9120 PIN FUNCTIONS TSM9117/TSM9118 SC70 SO 1 6 2 4 3 3 4 5 — — 2 7 — 1, 5, 8 TSM9119/TSM9120 SC70 SO 1 6 2 4 3 3 — 5 4 — — 7 2 1, 5, 8 NAME OUT VEE IN+ REF VCC INNC FUNCTION Comparator Output Negative Supply Voltage Comparator Noninverting Input 1.252V Reference Output and Comparator Inverting Input Positive Supply Voltage Comparator Inverting Input No Connection. Not internally connected. BLOCK DIAGRAMS DESCRIPTION OF OPERATION Guaranteed to operate from +1.6V supplies, the TSM9117 and the TSM9118 comparators only draw 600nA supply current, feature a robust input stage that can tolerate input voltages 200mV beyond the power supply rails, and include an on-board +1.252V ±1.75% voltage reference. The comparator-only TSM9119 and the TSM9120 have the same attributes and only draw a supply current of 350nA. To insure clean output switching behavior, all four analog comparators feature 4mV internal hysteresis. The TSM9117 and the TSM9119’s push-pull output drivers were designed to minimize supply-current surges while driving ±5mA loads with rail-to-rail output swings. The open-drain output stage TSM9118 and TSM9120 can be connected to supply voltages above VCC to an absolute maximum of 6V above VEE. Where wired-OR logic connections are needed, their open-drain output stages make it easy to use these analog comparators. Input Stage Circuitry The robust design of the analog comparators’ input stage can accommodate any differential input voltage from VEE - 0.2V to VCC + 0.2V. Input bias currents are typically ±0.15nA so long as the applied input voltage remains between the supply rails. ESD protection diodes - connected internally to the supply rails protect comparator inputs against overvoltage conditions. However, if the applied input voltage exceeds either or both supply rails, an increase in input current can occur when these ESD protection diodes start to conduct. TSM9117_20DS r1p0 Page 11 RTFDS TSM9117-TSM9120 Output Stage Circuitry Many conventional analog comparators can draw orders of magnitude higher supply current when switching. Because of this behavior, additional power supply bypass capacitance may be required to provide additional charge storage during switching. The design of the TSM9117–TSM9120’s rail-to-rail output stage implements a technique that virtually eliminates supply-current surges when output transitions occur. As shown on Page 5 of the Typical Operating Characteristics, the supply-current change as a function of output transition frequency exhibited by this analog comparator family is very small. Material benefits of this attribute to batterypower applications is the increase in operating time and in reducing the size of power-supply filter capacitors. TSM9117/9118’s Internal +1.252V VREF The TSM9117 and the TSM9118’s internal +1.252V voltage reference exhibits a typical temperature coefficient of 100ppm/°C over the full -40°C to +85°C temperature range. An equivalent circuit for the reference section is illustrated in Figure 1. Since the output impedance of the voltage reference voltage reference is typically 200kΩ, preventing the reference from driving large loads. The reference is Figure 1: TSM9117 & TSM9118 Internal VREF Output Equivalent Circuit typically 200kΩ, its output can be bypassed with a low-leakage capacitor and is stable for any capacitive load. An external buffer – such as the TS1001 – can be used to buffer the voltage reference output for higher output current drive or to reduce reference output impedance. APPLICATIONS INFORMATION Low-Voltage, Low-Power Operation Designed specifically for low-power applications, the TSM9117–TSM9120 comparators are an excellent choice. Under nominal conditions, approximate operating times for this analog comparator family is illustrated in Table 1 for a number of battery types and their charge capacities. Internal Hysteresis As a result of circuit noise or unintended parasitic feedback, many analog comparators often break into oscillation within their linear region of operation especially when the applied differential input voltage approaches 0V (zero volt). Externally-introduced hysteresis is a well-established technique to stabilizing analog comparator behavior and requires external components. As shown in Figure 2, adding comparator hysteresis creates two trip points: VTHR (for the rising input voltage) and VTHF (for the falling input voltage). The hysteresis band (VHB) is defined as the voltage difference between the two trip points. When a comparator’s input voltages are equal, TSM9117/TSM9118 OPERATING TIME (hrs) 6 2.5 x 10 937,500 1.25 x 10 1.25 x 10 6 6 Table 1: Battery Applications using the TSM9117- TSM9120 BATTERY TYPE Alkaline (2 Cells) Nickel-Cadmium (2 Cells) Lithium-Ion (1 Cell) Nickel-MetalHydride (2 Cells) RECHARGEABLE No Yes Yes Yes VFRESH (V) 3.0 2.4 3.5 2.4 VEND-OF-LIFE (V) 1.8 1.8 2.7 1.8 CAPACITY, AA SIZE (mA-h) 2000 750 1000 1000 TSM9119/TSM9120 OPERATING TIME (hrs) 6 5 x 10 1.875 x 10 2.5 x 10 2.5 x 10 6 6 6 Page 12 TSM9117_20DS r1p0 RTFDS TSM9117-TSM9120 hysteresis effectively forces one comparator input to move quickly past the other input, moving the input out of the region where oscillation occurs. out of the region where oscillation occurs. Figure 2 illustrates the case in which an IN- input is a fixed voltage and an IN+ is varied. If the input signals were reversed, the figure would be the same with an inverted output. To save cost and external pcb area, an internal 4mV hysteresis circuit was added to the TSM9117–TSM9120. 1) Setting R2. As the leakage current at the IN pin is less than 2nA, the current through R2 should be at least 0.2μA to minimize offset voltage errors caused by the input leakage current. The current through R2 at the trip point is (VREF - VOUT)/R2. In solving for R2, there are two formulas – one each for the two possible output states: R2 = VREF/IR2 or R2 = (VCC - VREF)/IR2 From the results of the two formulae, the smaller of the two resulting resistor values is chosen. For example, when using the TSM9117 (VREF = 1.252V) at a VCC = 3.3V and if IR2 = 0.2μA is chosen, then the formulae above produce two resistor values: 6.26MΩ and 10.24MΩ - the 6.2MΩ standard value for R2 is selected. Figure 2: TSM9117-TSM9120 Threshold Hysteresis Band 2) Next, the desired hysteresis band (VHYSB) is set. In this example, VHYSB is set to 100mV. 3) Resistor R1 is calculated according to the following equation: R1 = R2 x (VHYSB/VCC) and substituting the values selected in 1) and 2) above yields: R1 = 6.2MΩ x (100mV/3.3V) = 187.88kΩ. The 187kΩ standard value for R1 is chosen. 4) The trip point for VIN rising (VTHR) is chosen such that VTHR > VREF x (R1 + R2)/R2 (VTHF is the trip point for VIN falling). This is the threshold voltage at which the comparator switches its output from low to high as VIN rises above the trip point. In this example, VTHR is set to 3V. Adding Hysteresis to the TSM9117/TSM9119 The TSM9117/TSM9119 exhibit an internal hysteresis band (VHYSB) of 4mV. Additional hysteresis can be generated with three external resistors using positive feedback as shown in Figure 3. Unfortunately, this method also reduces the ` Figure 3: Using Three Resistors Introduces Additional Hysteresis in the TSM9117 & TSM9119. hysteresis response time. Use the procedure to calculate resistor values. following 5) With the VTHR from Step 4 above, resistor R3 is then computed as follows: R3 = 1/[VTHR/(VREF x R1) - (1/R1) - (1/R2)] R3 = 1/[3V/(1.252V x 187kΩ) - (1/187kΩ) - (1/6.2MΩ)] = 136.9kΩ TSM9117_20DS r1p0 Page 13 RTFDS TSM9117-TSM9120 In this example, a 137kΩ, 1% standard value resistor is selected for R3. 6) The last step is to verify the trip voltages and hysteresis band using the standard resistance values: For VIN rising: VTHR = VREF x R1 [(1/R1) + (1/R2) + (1/R3)] = 3V and, for VIN falling: VTHF = VTHR - (R1 x VCC/R2) = 2.9V and Hysteresis Band = VTHR – VTHF = 100mV Adding Hysteresis to the TSM9118/TSM9120 The TSM9118/TSM9120 have a 4mV internal hysteresis band. Both products have open-drain outputs and require an external pullup resistor to VCC as shown in Figure 4. Additional hysteresis can be where the smaller of the two resulting resistor values is the best starting value. 2) As before, the desired hysteresis band (VHYSB) is set to 100mV. 3) Next, resistor R1 is then computed according to the following equation: R1 = (R2 + R4) x (VHYSB/VCC) 4) The trip point for VIN rising (VTHR) is chosen (again, remember that VTHF is the trip point for VIN falling). This is the threshold voltage at which the comparator switches its output from low to high as VIN rises above the trip point. 5) With the VTHR from Step 4 above, resistor R3 is computed as follows: R3 = 1/[VTHR/(VREF x R1) - (1/R1) - (1/R2)] 6) As before, the last step is to verify the trip voltages and hysteresis band with the standard resistor values used in the circuit: For VIN rising: VTHR = VREF x R1 x (1/R1+1/R2+1/R3) and, for VIN falling: VTHF = VREF x R1 x [1/R1+1/R3+1/(R2+R4)] -[R1/(R2+R4)] x VCC and Hysteresis Band is given by VTHR - VTHF Figure 4: Using Four Resistors Introduces Additional Hysteresis in the TSM9118 & TSM9120. generated using positive feedback; however, formulae differ slightly from those of TSM9117/TSM9119. The procedure to calculate resistor values for the TSM9118/TSM9120 is follows: 1) As in the previous section, resistor R2 is chosen according to the formulae: R2 = VREF/0.2µA or R2 = (VCC - VREF)/0.2μA - R4 the the the as PC Board Layout and Power-Supply Bypassing While power-supply bypass capacitors are not typically required, it is good engineering practice to use 0.1µF bypass capacitors close to the device’s power supply pins when the power supply impedance is high, the power supply leads are long, or there is excessive noise on the power supply traces. To reduce stray capacitance, it is also good engineering practice to make signal trace lengths as short as possible. Also recommended are a ground plane and surface mount resistors and capacitors. Page 14 TSM9117_20DS r1p0 RTFDS TSM9117-TSM9120 A Zero-Crossing Detector To configure a zero-crossing detector using a TSM9119 is illustrated in Figure 5. In this example, the TSM9119’s inverting input is connected to ground and its noninverting input is connected to a 100mVP-P signal source. The TSM9119’s output changes state as the signal at the noninverting input crosses 0V. A Logic-Level Translator Logic-level translation between two different voltage systems is easy using the TSM9120 as shown in Figure 6. This application circuit converts 5V logic to Figure 6: A 5V-to-3V Logic Level Translator 3V logic levels. In this case, the TSM9120 is powered by a +5V system and the external pullup resistor for the TSM9120’s open-drain output is connected to a +3V system. This configuration allows the full 5V logic swing without creating overvoltage on the 3V logic inputs. For 3V to 5V logic-level translations, simply interchange the +3V supply voltage connection on the comparator’s VCC and the +5V supply voltage to the external pullup resistor Figure 5: A Simple Zero-Crossing Detector TSM9117_20DS r1p0 Page 15 RTFDS TSM9117-TSM9120 PACKAGE OUTLINE DRAWING 5-Pin SC70 Package Outline Drawing (N.B., Drawings are not to scale) Page 16 TSM9117_20DS r1p0 RTFDS TSM9117-TSM9120 PACKAGE OUTLINE DRAWING 8-Pin SOIC Package Outline Drawing (N.B., Drawings are not to scale) Information furnished by Touchstone Semiconductor is believed to be accurate and reliable. However, Touchstone Semiconductor does not assume any responsibility for its use nor for any infringements of patents or other rights of third parties that may result from its use, and all information provided by Touchstone Semiconductor and its suppliers is provided on an AS IS basis, WITHOUT WARRANTY OF ANY KIND. Touchstone Semiconductor reserves the right to change product specifications and product descriptions at any time without any advance notice. No license is granted by implication or otherwise under any patent or patent rights of Touchstone Semiconductor. Touchstone Semiconductor assumes no liability for applications assistance or customer product design. Customers are responsible for their products and applications using Touchstone Semiconductor components. To minimize the risk associated with customer products and applications, customers should provide adequate design and operating safeguards. Trademarks and registered trademarks are the property of their respective owners. Touchstone Semiconductor, Inc. 630 Alder Drive, Milpitas, CA 95035 +1 (408) 215 - 1220 ▪ www.touchstonesemi.com Page 17 TSM9117_20DS r1p0 RTFDS