1 A/1.5 A/2 A Synchronous,
Step-Down DC-to-DC Converters
ADP2105/ADP2106/ADP2107
Data Sheet
FEATURES
GENERAL DESCRIPTION
Extremely high 97% efficiency
Ultralow quiescent current: 20 μA
1.2 MHz switching frequency
0.1 μA shutdown supply current
Maximum load current
ADP2105: 1 A
ADP2106: 1.5 A
ADP2107: 2 A
Input voltage: 2.7 V to 5.5 V
Output voltage: 0.8 V to VIN
Maximum duty cycle: 100%
Smoothly transitions into low dropout (LDO) mode
Internal synchronous rectifier
Small 16-lead 4 mm × 4 mm LFCSP package
Optimized for small ceramic output capacitors
Enable/shutdown logic input
Undervoltage lockout
Soft start
Supported by ADIsimPower™ design tool
The ADP2105/ADP2106/ADP2107 are low quiescent current,
synchronous, step-down dc-to-dc converters in a compact 4 mm ×
4 mm LFCSP package. At medium to high load currents, these
devices use a current mode, constant frequency pulse-width
modulation (PWM) control scheme for excellent stability and
transient response. To ensure the longest battery life in portable
applications, the ADP2105/ADP2106/ADP2107 use a pulse
frequency modulation (PFM) control scheme under light load
conditions that reduces switching frequency to save power.
The ADP2105/ADP2106/ADP2107 run from input voltages of
2.7 V to 5.5 V, allowing single Li+/Li− polymer cell, multiple
alkaline/NiMH cells, PCMCIA, and other standard power sources.
The output voltage of ADP2105/ADP2106/ADP2107 is adjustable
from 0.8 V to the input voltage (indicated by ADJ), whereas the
ADP2105/ADP2106/ADP2107 are available in preset output
voltage options of 3.3 V, 1.8 V, 1.5 V, and 1.2 V (indicated by x.x V).
Each of these variations is available in three maximum current
levels: 1 A (ADP2105), 1.5 A (ADP2106), and 2 A (ADP2107).
The power switch and synchronous rectifier are integrated for
minimal external part count and high efficiency. During logic
controlled shutdown, the input is disconnected from the output,
and it draws less than 0.1 µA from the input source. Other key
features include undervoltage lockout to prevent deep battery
discharge and programmable soft start to limit inrush current at
startup.
APPLICATIONS
Mobile handsets
PDAs and palmtop computers
Telecommunication/networking equipment
Set top boxes
Audio/video consumer electronics
100
TYPICAL OPERATING CIRCUIT
0.1μF
10Ω
VIN
VIN = 3.3V
INPUT VOLTAGE = 2.7V TO 5.5V
VOUT = 2.5V
VIN = 3.6V
95
10μF
OFF
16
15
14
13
FB
GND
IN
PWIN1
OUTPUT VOLTAGE = 2.5V
LX2 12
1 EN
2μH
PGND 11
2 GND
ADP2107-ADJ
PWIN2 9
4 GND
COMP SS
70kΩ
AGND NC
6
7
8
10μF
4.7μF
80
FB
VIN
VIN = 5V
85
40kΩ
LOAD
0A TO 2A
10μF
75
0
200
400
600
800
1000 1200 1400 1600 1800 2000
LOAD CURRENT (mA)
1nF
Figure 2. Efficiency vs. Load Current for the ADP2107 with VOUT = 2.5 V
120pF
NC = NO CONNECT
06079-002
5
85kΩ
LX1 10
3 GND
90
06079-001
ON
EFFICIENCY (%)
FB
Figure 1. Circuit Configuration of ADP2107 with VOUT = 2.5 V
Rev. E
Document Feedback
Information furnished by Analog Devices is believed to be accurate and reliable. However, no
responsibility is assumed by Analog Devices for its use, nor for any infringements of patents or other
rights of third parties that may result from its use. Specifications subject to change without notice. No
license is granted by implication or otherwise under any patent or patent rights of Analog Devices.
Trademarks and registered trademarks are the property of their respective owners.
One Technology Way, P.O. Box 9106, Norwood, MA 02062-9106, U.S.A.
Tel: 781.329.4700 ©2006–2016 Analog Devices, Inc. All rights reserved.
Technical Support
www.analog.com
ADP2105/ADP2106/ADP2107
Data Sheet
TABLE OF CONTENTS
Features .............................................................................................. 1
External Component Selection ................................................ 17
Applications ....................................................................................... 1
Setting the Output Voltage ........................................................ 17
General Description ......................................................................... 1
Inductor Selection ...................................................................... 18
Typical Operating Circuit ................................................................ 1
Output Capacitor Selection....................................................... 19
Revision History ............................................................................... 3
Input Capacitor Selection .......................................................... 20
Functional Block Diagram .............................................................. 4
Input Filter................................................................................... 20
Specifications..................................................................................... 5
Soft Start Period.......................................................................... 20
Absolute Maximum Ratings ............................................................ 7
Loop Compensation .................................................................. 20
Thermal Resistance ...................................................................... 7
Bode Plots .................................................................................... 21
Boundary Condition .................................................................... 7
Load Transient Response .......................................................... 22
ESD Caution .................................................................................. 7
Efficiency Considerations ......................................................... 24
Pin Configuration and Function Descriptions ............................. 8
Thermal Considerations............................................................ 24
Typical Performance Characteristics ............................................. 9
Design Example .............................................................................. 26
Theory of Operation ...................................................................... 15
External Component Recommendations .................................... 27
Control Scheme .......................................................................... 15
Circuit Board Layout Recommendations ................................... 29
PWM Mode Operation .............................................................. 15
Evaluation Board ............................................................................ 30
PFM Mode Operation................................................................ 15
Evaluation Board Schematic for ADP2107 (1.8 V) ............... 30
Pulse-Skipping Threshold ......................................................... 15
100% Duty Cycle Operation (LDO Mode) ............................. 15
Recommended PCB Board Layout (Evaluation Board
Layout) ......................................................................................... 30
Slope Compensation .................................................................. 16
Application Circuits ....................................................................... 32
Design Features ........................................................................... 16
Outline Dimensions ....................................................................... 34
Applications Information .............................................................. 17
Ordering Guide .......................................................................... 34
Rev. E | Page 2 of 36
Data Sheet
ADP2105/ADP2106/ADP2107
REVISION HISTORY
4/16—Rev. D to Rev. E
Changed LFCSP_VQ to LFCSP................................... Throughout
Change to Figure 4 ............................................................................ 8
Updated Outline Dimensions ........................................................34
Changes to Ordering Guide ...........................................................34
8/12—Rev. C to Rev. D
Change to Features Section .............................................................. 1
Added Exposed Pad Notation to Pin Configuration and
Function Description Section .......................................................... 7
Added ADIsimPower Design Tool Section .................................16
Updated Outline Dimensions ........................................................33
3/07—Rev. 0 to Rev. A
Updated Format ................................................................. Universal
Changes to Output Characteristics and
LX (Switch Node) Characteristics Sections ................................... 3
Changes to Typical Performance Characteristics Section ........... 7
Changes to Load Transient Response Section............................. 21
7/06—Revision 0: Initial Version
9/08—Rev. B to Rev. C
Changes to Table Summary Statement ........................................... 4
Changes to LX Minimum On-Time Parameter, Table 1 .............. 5
7/08—Rev. A to Rev. B
Changes to General Description Section ....................................... 1
Changes to Figure 3........................................................................... 3
Changes to Table 1 ............................................................................ 4
Changes to Table 2 ............................................................................ 6
Changes to Figure 4........................................................................... 7
Changes to Table 4 ............................................................................ 7
Changes to Figure 26 ......................................................................11
Changes to Figure 31 Through Figure 34 ....................................12
Changes to Figure 35 ......................................................................13
Changes to PMW Mode Operation Section and Pulse Skipping
Threshold Section ...........................................................................14
Changes to Slope Compensation Section ....................................15
Changes to Setting the Output Voltage Section .........................16
Changes to Figure 37 ......................................................................16
Changes to Inductor Selection Section ........................................17
Changes to Input Capacitor Selection Section ............................18
Changes to Figure 47 through Figure 52 ......................................21
Changes to Transition Losses Section and Thermal
Considerations Section ...................................................................22
Changes to Table 11 ........................................................................25
Changes to Circuit Board Layout Recommendations Section..27
Changes to Table 12 ........................................................................26
Changes to Figure 53 ......................................................................28
Changes to Figure 56 Through Figure 57 ....................................30
Changes to Figure 58 Through Figure 59 ....................................31
Changes to Outline Dimensions ...................................................33
Rev. E | Page 3 of 36
ADP2105/ADP2106/ADP2107
Data Sheet
FUNCTIONAL BLOCK DIAGRAM
COMP 5
SS 6
SOFT
START
REFERENCE
0.8V
CURRENT SENSE
AMPLIFIER
14
IN
9
PWIN2
13
PWIN1
10
LX1
12
LX2
11
PGND
FB 16
FB 16
GM ERROR
AMP
PWM/
PFM
CONTROL
AGND 7
GND 2
FOR PRESET
VOLTAGE
OPTIONS ONLY
DRIVER
AND
ANTISHOOT
THROUGH
GND 3
GND 4
CURRENT
LIMIT
SLOPE
COMPENSATION
NC 8
GND 15
OSCILLATOR
ZERO CROSS
COMPARATOR
THERMAL
SHUTDOWN
06079-037
EN 1
Figure 3.
Rev. E | Page 4 of 36
Data Sheet
ADP2105/ADP2106/ADP2107
SPECIFICATIONS
VIN = 3.6 V at TA = 25°C, unless otherwise noted. 1
Table 1.
Parameter
INPUT CHARACTERISTICS
Input Voltage Range
Undervoltage Lockout Threshold
Min
Typ
2.7
Max
Unit
Test Conditions/Comments
5.5
V
V
V
V
V
mV
−40°C ≤ TJ ≤ +125°C
VIN rising
VIN rising, −40°C ≤ TJ ≤ +125°C
VIN falling
VIN falling, −40°C ≤ TJ ≤ +125°C
VIN falling
V
V
V
2.4
2.2
2.6
2.2
2.0
Undervoltage Lockout Hysteresis 2
OUTPUT CHARACTERISTICS
Output Regulation Voltage
2.5
200
3.267
3.3
3.3
3.201
1.782
1.8
1.8
1.5
1.5
1.2
1.2
0.4
0.5
0.6
0.1
0.1
Line Regulation 3
Output Voltage Range
FEEDBACK CHARACTERISTICS
FB Regulation Voltage
FB Bias Current
0.33
0.3
VIN
%/A
%/A
%/A
%/V
%/V
V
V
V
µA
µA
µA
µA
µA
µA
µA
µA
µA
ADJ
ADJ, −40°C ≤ TJ ≤ +125°C
ADJ, −40°C ≤ TJ ≤ +125°C
1.2 V output voltage
1.2 V output voltage, −40°C ≤ TJ ≤ +125°C
1.5 V output voltage
1.5 V output voltage, −40°C ≤ TJ ≤ +125°C
1.8 V output voltage
1.8 V output voltage, −40°C ≤ TJ ≤ +125°C
3.3 V output voltage
3.3 V output voltage, −40°C ≤ TJ ≤ +125°C
1.515
1.545
1.164
Load Regulation
1.236
V
V
V
1.818
1.854
1.455
1.188
3.3 V, load = 10 mA
3.3 V, VIN = 3.6 V to 5.5 V, no load to full load
3.3 V, VIN = 3.6 V to 5.5 V, no load to full load,
−40°C ≤ TJ ≤ +125°C
1.8 V, load = 10 mA
1.8 V, VIN = 2.7 V to 5.5 V, no load to full load
1.8 V, VIN = 2.7 V to 5.5 V, no load to full load,
−40°C ≤ TJ ≤ +125°C
1.5, load = 10 mA
ADP210x-1.5 V, VIN = 2.7 V to 5.5 V, no load to full load
ADP210x-1.5 V, VIN = 2.7 V to 5.5 V, no load to full load,
−40°C ≤ TJ ≤ +125°C
1.2 V, load = 10 mA
1.2 V, VIN = 2.7 V to 5.5 V, no load to full load
1.2 V, VIN = 2.7 V to 5.5 V, no load to full load,
−40°C ≤ TJ ≤ +125°C
ADP2105
ADP2106
ADP2107
ADP2105, measured in servo loop
ADP2106 and ADP2107, measured in servo loop
ADJ
3.399
1.746
1.485
3.333
0.8
1.212
0.8
0.784
−0.1
0.816
+0.1
3
6
4
8
5
10
10
20
V
V
V
V
V
V
Rev. E | Page 5 of 36
ADP2105/ADP2106/ADP2107
Parameter
INPUT CURRENT CHARACTERISTICS
IN Operating Current
Min
Data Sheet
Typ
Max
Unit
Test Conditions/Comments
30
µA
µA
ADP2105/ADP2106/ADP2107 (ADJ), VFB = 0.9 V
ADP2105/ADP2106/ADP2107 (ADJ), VFB = 0.9 V, −40°C ≤ TJ ≤
+125°C
ADP2105/ADP2106/ADP2107 (x.x V) output voltage 10%
above regulation voltage
ADP2105/ADP2106/ADP2107 (x.x V) output voltage 10%
above regulation voltage, −40°C ≤ TJ ≤ +125°C
VEN = 0 V
20
20
IN Shutdown Current4
LX (SWITCH) NODE CHARACTERISTICS
LX On Resistance 4
0.1
µA
30
µA
1
µA
190
165
mΩ
mΩ
mΩ
mΩ
230
mΩ
mΩ
140
mΩ
mΩ
270
100
160
90
LX Leakage Current4, 5
LX Peak Current Limit5
0.1
2.9
2.6
1
3.3
2.25
2.0
2.6
1.5
1.3
LX Minimum On-Time
ENABLE CHARACTERISTICS
EN Input High Voltage
EN Input Low Voltage
EN Input Leakage Current
1.8
110
2
0.4
−0.1
−1
OSCILLATOR FREQUENCY
SOFT START PERIOD
THERMAL CHARACTERISTICS
Thermal Shutdown Threshold
Thermal Shutdown Hysteresis
COMPENSATOR
TRANSCONDUCTANCE (gm)
CURRENT SENSE AMPLIFIER GAIN (GCS)2
+1
1.2
1
750
1000
1.4
1200
µA
A
A
A
A
A
A
ns
P-channel switch, ADP2105
P-channel switch, ADP2105, −40°C ≤ TJ ≤ +125°C
P-channel switch, ADP2106 and ADP2107
P-channel switch, ADP2106 and ADP2107,
−40°C ≤ TJ ≤ +125°C
N-channel synchronous rectifier, ADP2105
N-channel synchronous rectifier, ADP2105,
−40°C ≤ TJ ≤ +125°C
N-channel synchronous rectifier, ADP2106 and ADP2107
N-channel synchronous rectifier, ADP2106 and ADP2107,
−40°C ≤ TJ ≤ +125°C
VIN = 5.5 V, VLX = 0 V, 5.5 V
P-channel switch, ADP2107
P-channel switch, ADP2107, −40°C ≤ TJ ≤ +125°C
P-channel switch, ADP2106
P-channel switch, ADP2106, −40°C ≤ TJ ≤ +125°C
P-channel switch, ADP2105
P-channel switch, ADP2105, −40°C ≤ TJ ≤ +125°C
In PWM mode of operation, −40°C ≤ TJ ≤ +125°C
V
V
µA
µA
MHz
MHz
µs
VIN = 2.7 V to 5.5 V, −40°C ≤ TJ ≤ +125°C
VIN = 2.7 V to 5.5 V, −40°C ≤ TJ ≤ +125°C
VIN = 5.5 V, VEN = 0 V, 5.5 V
VIN = 5.5 V, VEN = 0 V, 5.5 V, −40°C ≤ TJ ≤ +125°C
VIN = 2.7 V to 5.5 V
VIN = 2.7 V to 5.5 V, −40°C ≤ TJ ≤ +125°C
CSS = 1 nF
50
°C
°C
µA/V
1.875
2.8125
3.625
A/V
A/V
A/V
140
40
ADP2105
ADP2106
ADP2107
All limits at temperature extremes are guaranteed via correlation using standard statistical quality control (SQC). Typical values are at TA = 25°C.
Guaranteed by design.
3
The ADP2105/ADP2106/ADP2107 line regulation was measured in a servo loop on the automated test equipment that adjusts the feedback voltage to achieve a
specific COMP voltage.
4
All LX (switch) node characteristics are guaranteed only when the LX1 pin and LX2 pin are tied together.
5
These specifications are guaranteed from −40°C to +85°C.
1
2
Rev. E | Page 6 of 36
Data Sheet
ADP2105/ADP2106/ADP2107
ABSOLUTE MAXIMUM RATINGS
THERMAL RESISTANCE
Table 2.
Parameter
IN, EN, SS, COMP, FB to AGND
LX1, LX2 to PGND
PWIN1, PWIN2 to PGND
PGND to AGND
GND to AGND
PWIN1, PWIN2 to IN
Operating Junction Temperature Range
Storage Temperature Range
Soldering Conditions
Rating
−0.3 V to +6 V
−0.3 V to (VIN + 0.3 V)
−0.3 V to +6 V
−0.3 V to +0.3 V
−0.3 V to +0.3 V
−0.3 V to +0.3 V
−40°C to +125°C
−65°C to +150°C
JEDEC J-STD-020
Stresses at or above those listed under Absolute Maximum
Ratings may cause permanent damage to the product. This is a
stress rating only; functional operation of the product at these
or any other conditions above those indicated in the operational
section of this specification is not implied. Operation beyond
the maximum operating conditions for extended periods may
affect product reliability.
θJA is specified for the worst-case conditions, that is, a device
soldered in a circuit board for surface-mount packages.
Table 3. Thermal Resistance
Package Type
16-Lead LFCSP
Maximum Power Dissipation
θJA
40
1
Unit
°C/W
W
BOUNDARY CONDITION
Natural convection, 4-layer board, exposed pad soldered to the PCB.
ESD CAUTION
Rev. E | Page 7 of 36
ADP2105/ADP2106/ADP2107
Data Sheet
13 PWIN1
14 IN
16 FB
15 GND
PIN CONFIGURATION AND FUNCTION DESCRIPTIONS
EN 1
11 PGND
10 LX1
9
PWIN2
NOTES
1. NC = NO CONNECT. DO NOT CONNECT TO THIS PIN.
2. THE EXPOSED PAD SHOULD BE SOLDERED TO AN
EXTERNAL GROUND PLANE UNDERNEATH THE IC FOR
THERMAL DISSIPATION.
06079-003
NC 8
TOP VIEW
COMP 5
GND 4
AGND 7
GND 3
12 LX2
ADP2105/
ADP2106/
ADP2107
SS 6
GND 2
Figure 4. Pin Configuration
Table 4. Pin Function Descriptions
Pin No.
1
Mnemonic
EN
2, 3, 4, 15
GND
5
COMP
6
SS
7
AGND
8
9, 13
NC
PWIN2,
PWIN1
10, 12
LX1, LX2
11
PGND
14
IN
16
FB
EP
Description
Enable Input. Drive EN high to turn on the device. Drive EN low to turn off the device and reduce the input
current to 0.1 µA.
Test Pins. These pins are used for internal testing and are not ground return pins. These pins are to be tied to the
AGND plane as close as possible to the ADP2105/ADP2106/ADP2107.
Feedback Loop Compensation Node. COMP is the output of the internal transconductance error amplifier. Place
a series RC network from COMP to AGND to compensate the converter. See the Loop Compensation section.
Soft Start Input. Place a capacitor from SS to AGND to set the soft start period. A 1 nF capacitor sets a 1 ms soft
start period.
Analog Ground. Connect the ground of the compensation components, the soft start capacitor, and the voltage
divider on the FB pin to the AGND pin as close as possible to the ADP2105/ ADP2106/ADP2107. The AGND is
also to be connected to the exposed pad of ADP2105/ADP2106/ADP2107.
No Connect. This is not internally connected and can be connected to other pins or left unconnected.
Power Source Inputs. The source of the PFET high-side switch. Bypass each PWIN pin to the nearest PGND plane with a
4.7 µF or greater capacitor as close as possible to the ADP2105/ADP2106/ ADP2107. See the Input Capacitor
Selection section.
Switch Outputs. The drain of the P-channel power switch and N-channel synchronous rectifier. These pins are to
be tied together and connected to the output LC filter between LX and the output voltage.
Power Ground. Connect the ground return of all input and output capacitors to the PGND pin using a power
ground plane as close as possible to the ADP2105/ADP2106/ADP2107. The PGND is then to be connected to the
exposed pad of the ADP2105/ADP2106/ADP2107.
Power Input. The power source for the ADP2105/ADP2106/ADP2107 internal circuitry. Connect IN and PWIN1
with a 10 Ω resistor as close as possible to the ADP2105/ADP2106/ADP2107. Bypass IN to AGND with a 0.1 µF or
greater capacitor. See the Input Filter section.
Output Voltage Sense or Feedback Input. For fixed output versions, connect to the output voltage. For
adjustable versions, FB is the input to the error amplifier. Drive FB through a resistive voltage divider to set the
output voltage. The FB regulation voltage is 0.8 V.
Exposed Pad. The exposed pad should be soldered to an external ground plane underneath the IC for thermal
dissipation.
Rev. E | Page 8 of 36
Data Sheet
ADP2105/ADP2106/ADP2107
TYPICAL PERFORMANCE CHARACTERISTICS
100
100
95
95
VIN = 3.6V
EFFICIENCY (%)
80
VIN = 4.2V
VIN = 5.5V
70
INDUCTOR: SD14, 2.5µH
DCR: 60mΩ
TA = 25°C
1
VIN = 4.2V
VIN = 5.5V
80
75
65
10
100
70
65
1000
INDUCTOR: SD3814, 3.3µH
DCR: 93mΩ
TA = 25°C
1
10
Figure 8. Efficiency—ADP2105 (1.8 V Output)
Figure 5. Efficiency—ADP2105 (1.2 V Output)
100
100
VIN = 3.6V
95
95
90
VIN = 5.5V
VIN = 4.2V
VIN = 2.7V
VIN = 3.6V
85
EFFICIENCY (%)
85
80
75
80
VIN = 4.2V
75
70
VIN = 5.5V
65
70
1
10
06079-085
60
INDUCTOR: CDRH5D18, 4.1μH
DCR: 43mΩ
TA = 25°C
65
50
1000
100
INDUCTOR: D62LCB, 2µH
DCR: 28mΩ
TA = 25°C
55
1
10
10k
Figure 9. Efficiency—ADP2106 (1.2 V Output)
Figure 6. Efficiency—ADP2105 (3.3 V Output)
100
100
VIN = 3.6V
95
90
95
90
VIN = 2.7V
85
EFFICIENCY (%)
85
VIN = 4.2V
80
75
VIN = 5.5V
70
VIN = 5.5V
80
VIN = 4.2V
75
70
65
65
60
60
INDUCTOR: D62LCB, 2µH
DCR: 28mΩ
TA = 25°C
55
1
10
100
1k
06079-062
EFFICIENCY (%)
1k
LOAD CURRENT (mA)
LOAD CURRENT (mA)
50
100
06079-008
EFFICIENCY (%)
90
60
1000
100
LOAD CURRENT (mA)
LOAD CURRENT (mA)
VIN = 3.6V
INDUCTOR: D62LCB, 3.3µH
DCR: 47mΩ
TA = 25°C
55
50
10k
1
10
100
1k
LOAD CURRENT (mA)
LOAD CURRENT (mA)
Figure 10. Efficiency—ADP2106 (3.3 V Output)
Figure 7. Efficiency—ADP2106 (1.8 V Output)
Rev. E | Page 9 of 36
06079-053
60
85
06079-086
75
VIN = 2.7V
VIN = 3.6V
90
VIN = 2.7V
85
06079-084
EFFICIENCY (%)
90
10k
ADP2105/ADP2106/ADP2107
Data Sheet
100
100
95
95
VIN = 3.6V
VIN = 2.7V
90
85
EFFICIENCY (%)
85
80
VIN = 4.2V
75
70
VIN = 5.5V
65
VIN = 4.2V
80
VIN = 5.5V
75
70
65
60
60
50
1
10
100
06079-010
INDUCTOR: SD12, 1.2µH
DCR: 37mΩ
TA = 25°C
55
50
10k
1k
INDUCTOR: D62LCB, 1.5µH
DCR: 21mΩ
TA = 25°C
55
1
10k
1k
LOAD CURRENT (mA)
Figure 11. Efficiency—ADP2107 (1.2 V)
Figure 14. Efficiency—ADP2107 (1.8 V)
1.23
100
95
2.7V, –40°C
3.6V, –40°C
5.5V, –40°C
2.7V, +25°C
3.6V, +25°C
5.5V, +25°C
2.7V, +125°C
3.6V, +125°C
5.5V, +125°C
1.22
85
OUTPUT VOLTAGE (V)
90
EFFICIENCY (%)
100
10
LOAD CURRENT (mA)
06079-063
EFFICIENCY (%)
90
VIN = 2.7V
VIN = 3.6V
VIN = 5.5V
80
VIN = 4.2V
75
70
65
1.21
1.20
1.19
VIN = 3.6V
60
1
10
100
1.17
0.01
10k
1k
06079-082
50
06079-054
1.18
INDUCTOR: CDRH5D28, 2.5µH
DCR: 13mΩ
TA = 25°C
55
0.1
1
10
100
1k
10k
LOAD CURRENT (mA)
LOAD CURRENT (mA)
Figure 12. Efficiency—ADP2107 (3.3 V)
Figure 15. Output Voltage Accuracy—ADP2107 (1.2 V)
1.85
3.38
3.6V, –40°C
5.5V, –40°C
3.6V, +25°C
5.5V, +25°C
3.6V, +125°C
5.5V, +125°C
3.36
OUTPUT VOLTAGE (V)
1.81
1.79
3.34
3.32
3.30
3.28
3.26
1.77
1.75
0.1
1
2.7V, +25°C
3.6V, +25°C
5.5V, +25°C
10
2.7V, +125°C
3.6V, +125°C
5.5V, +125°C
100
1k
3.24
3.22
0.01
10k
LOAD CURRENT (mA)
06079-081
2.7V, –40°C
3.6V, –40°C
5.5V, –40°C
06079-064
OUTPUT VOLTAGE (V)
1.83
0.1
1
10
100
1k
LOAD CURRENT (mA)
Figure 13. Output Voltage Accuracy—ADP2107 (1.8 V)
Figure 16. Output Voltage Accuracy—ADP2107 (3.3 V)
Rev. E | Page 10 of 36
10k
Data Sheet
ADP2105/ADP2106/ADP2107
10k
190
SWITCH ON RESISTANCE (mΩ)
1k
+25°C
–40°C
10
1
0.8
1.2
1.6
2.0
2.4
2.8
3.2
3.6
4.0
4.4
4.8
PMOS POWER SWITCH
150
140
130
NMOS SYNCHRONOUS RECTIFIER
120
110
06079-016
+125°C
160
100
2.7
5.2
06079-093
100
170
3.0
3.3
INPUT VOLTAGE (V)
0.802
120
0.801
100
0.799
0.798
0.797
5.4
80
NMOS SYNCHRONOUS RECTIFIER
60
40
20
06079-017
0.796
–20
0
20
40
60
80
100
0
2.7
120 125
TA = 25°C
3.0
3.3
3.6
3.9
4.2
4.5
4.8
5.1
5.4
INPUT VOLTAGE (V)
TEMPERATURE (°C)
Figure 21. Switch On Resistance vs. Input Voltage—ADP2106 and ADP2107
Figure 18. Feedback Voltage vs. Temperature
1260
1.75
1.70
SWITCHING FREQUENCY (kHz)
1250
1.65
1.60
1.55
ADP2105 (1A)
1.50
1.45
1.40
1.35
1240
1230
+125°C
1220
+25°C
–40°C
1210
1.25
2.7
TA = 25°C
3.0
3.3
3.6
3.9
4.2
4.5
4.8
5.1
5.4
1190
2.7
5.7
06079-021
1200
1.30
06079-073
PEAK CURRENT LIMIT (A)
5.1
PMOS POWER SWITCH
0.800
0.795
–40
4.8
Figure 20. Switch On Resistance vs. Input Voltage—ADP2105
SWITCH ON RESISTANCE (mΩ)
FEEDBACK VOLTAGE (V)
Figure 17. Quiescent Current vs. Input Voltage
3.9
3.6
4.2
4.5
INPUT VOLTAGE (V)
06079-018
QUIESCENT CURRENT (µA)
180
3.0
3.3
3.6
3.9
4.2
4.5
4.8
5.1
INPUT VOLTAGE (V)
INPUT VOLTAGE (V)
Figure 22. Switching Frequency vs. Input Voltage
Figure 19. Peak Current Limit of ADP2105
Rev. E | Page 11 of 36
5.4
ADP2105/ADP2106/ADP2107
Data Sheet
2.35
LX (SWITCH) NODE
2.30
3
ADP2106 (1.5A)
2.20
2.15
INDUCTOR CURRENT
2.05
2.00
1
1.95
OUTPUT VOLTAGE
3.0
3.3
3.6
3.9
4.2
4.5
4.8
5.1
5.4
06079-074
TA = 25°C
CH1 1V
CH3 5V
5.7
INPUT VOLTAGE (V)
Figure 23. Peak Current Limit of ADP2106
2.85
ADP2107 (2A)
2.80
2.75
2.70
2.65
2.55
TA = 25°C
3.0
3.3
3.6
3.9
4.2
4.5
4.8
5.1
5.4
06079-071
2.60
PULSE-SKIPPING THRESHOLD CURRENT (mA)
PEAK CURRENT LIMIT (A)
2.90
120
105
90
VOUT = 1.2V
75
60
45
VOUT = 2.5V
15
0
2.7
5.7
VOUT = 1.8V
30
TA = 25°C
3.0
3.3
3.6
INPUT VOLTAGE (V)
3.9
4.2
4.5
4.8
5.1
5.4
5.7
INPUT VOLTAGE (V)
Figure 24. Peak Current Limit of ADP2107
Figure 27. Pulse-Skipping Threshold vs. Input Voltage for ADP2105
150
120
105
VOUT = 1.2V
90
75
60
VOUT = 2.5V
VOUT = 1.8V
15
TA = 25°C
3.0
3.3
3.6
3.9
4.2
4.5
4.8
5.1
5.4
06079-067
30
5.7
INPUT VOLTAGE (V)
PULSE-SKIPPING THRESHOLD CURRENT (mA)
195
135
0
2.7
1.78V
135
2.95
45
A CH1
Figure 26. Short-Circuit Response at Output
3.00
2.50
2.7
M 10µs
T 45.8%
CH4 1AΩ
06079-066
1.85
2.7
4
06079-072
1.90
PULSE-SKIPPING THRESHOLD CURRENT (mA)
∆: 260mV
@: 3.26V
2.10
180
VOUT = 1.2V
165
150
135
VOUT = 1.8V
120
105
90
VOUT = 2.5V
75
60
45
30
15
0
2.7
TA = 25°C
3.0
3.3
3.6
3.9
4.2
4.5
4.8
5.1
5.4
06079-068
PEAK CURRENT LIMIT (A)
2.25
5.7
INPUT VOLTAGE (V)
Figure 25. Pulse-Skipping Threshold vs. Input Voltage for ADP2106
Figure 28. Pulse-Skipping Threshold vs. Input Voltage for ADP2107
Rev. E | Page 12 of 36
Data Sheet
ADP2105/ADP2106/ADP2107
190
170
160
3
PMOS POWER SWITCH
150
LX (SWITCH) NODE
140
1
130
120
OUTPUT VOLTAGE (AC-COUPLED)
NMOS SYNCHRONOUS RECTIFIER
4
06079-093
110
100
2.7
3.0
3.3
3.6
3.9
4.2
4.5
INPUT VOLTAGE (V)
4.8
5.1
06079-033
SWITCH ON RESISTANCE (mΩ)
180
INDUCTOR CURRENT
CH1 50mV
CH3 2V
5.4
CH4 200mAΩ
M 400ns
T 17.4%
A CH3
3.88V
Figure 32. DCM Mode of Operation at Light Load (100 mA)
Figure 29. Switch On Resistance vs. Temperature—ADP2105
140
LX (SWITCH) NODE
SWITCH ON RESISTANCE (mΩ)
120
PMOS POWER SWITCH
100
3
80
NMOS SYNCHRONOUS RECTIFIER
60
1
0
–40
06079-083
20
–20
0
20
40
60
80
100
06079-034
OUTPUT VOLTAGE (AC-COUPLED)
40
INDUCTOR CURRENT
4
CH1 20mV
CH3 2V
120
CH4 1AΩ
M 2µs
T 13.4%
A CH3
1.84V
JUNCTION TEMPERATURE (°C)
Figure 30. Switch On Resistance vs. Temperature—ADP2106 and ADP2107
Figure 33. Minimum Off Time Control at Dropout
LX (SWITCH) NODE
LX (SWITCH)
NODE
3
3
1
1
OUTPUT VOLTAGE (AC-COUPLED)
OUTPUT VOLTAGE (AC-COUPLED)
CH4 200mAΩ
M 2µs
T 6%
A CH3
06079-031
INDUCTOR CURRENT
CH1 50mV
CH3 2V
INDUCTOR CURRENT
06079-030
4
4
3.88V
CH1 20mV
CH3 2V
Figure 31. PFM Mode of Operation at Very Light Load (10 mA)
CH4 1AΩ
M 1µs
T 17.4%
A CH3
3.88V
Figure 34. PWM Mode of Operation at Medium/Heavy Load (1.5 A)
Rev. E | Page 13 of 36
ADP2105/ADP2106/ADP2107
Data Sheet
LX (SWITCH) NODE
ENABLE VOLTAGE
3
3
OUTPUT VOLTAGE
CHANNEL 3
FREQUENCY
= 336.6kHz
∆: 2.86A
@: 2.86A
1
INDUCTOR CURRENT
INDUCTOR CURRENT
OUTPUT VOLTAGE
1
CH1 1V
CH3 5V
CH4 1AΩ
M 4µs
T 45%
A CH3
1.8V
Figure 35. Current Limit Behavior of ADP2107 (Frequency Foldback)
06079-035
4
06079-032
4
CH1 1V
CH3 5V
CH4 500mAΩ
M 400µs
T 20.2%
A CH1
1.84V
Figure 36. Startup and Shutdown Waveform (CSS = 1 nF → SS Time = 1 ms)
Rev. E | Page 14 of 36
Data Sheet
ADP2105/ADP2106/ADP2107
THEORY OF OPERATION
The ADP2105/ADP2106/ADP2107 are step-down, dc-to-dc
converters that use a fixed frequency, peak current mode architecture with an integrated high-side switch and low-side synchronous rectifier. The high 1.2 MHz switching frequency and tiny
16-lead, 4 mm × 4 mm LFCSP package allow for a small stepdown dc-to-dc converter solution. The integrated high-side switch
(P-channel MOSFET) and synchronous rectifier (N-channel
MOSFET) yield high efficiency at medium to heavy loads. Light
load efficiency is improved by smoothly transitioning to variable
frequency PFM mode.
The ADP2105/ADP2106/ADP2107 (ADJ) operate with an input
voltage from 2.7 V to 5.5 V and regulate an output voltage down to
0.8 V. The ADP2105/ADP2106/ADP2107 are also available with
preset output voltage options of 3.3 V, 1.8 V, 1.5 V, and 1.2 V.
CONTROL SCHEME
The ADP2105/ADP2106/ADP2107 operate with a fixed
frequency, peak current mode PWM control architecture at
medium to high loads for high efficiency, but shift to a variable
frequency PFM control scheme at light loads for lower quiescent current. When operating in fixed frequency PWM mode,
the duty cycle of the integrated switches is adjusted to regulate
the output voltage, but when operating in PFM mode at light
loads, the switching frequency is adjusted to regulate the output
voltage.
The ADP2105/ADP2106/ADP2107 operate in the PWM mode
only when the load current is greater than the pulse-skipping
threshold current. At load currents below this value, the converter
smoothly transitions to the PFM mode of operation.
PWM MODE OPERATION
In PWM mode, the ADP2105/ADP2106/ADP2107 operate at a
fixed frequency of 1.2 MHz set by an internal oscillator. At the
start of each oscillator cycle, the P-channel MOSFET switch is
turned on, putting a positive voltage across the inductor. Current
in the inductor increases until the current sense signal crosses
the peak inductor current level that turns off the P-channel
MOSFET switch and turns on the N-channel MOSFET synchronous rectifier. This puts a negative voltage across the inductor,
causing the inductor current to decrease. The synchronous
rectifier stays on for the remainder of the cycle, unless the
inductor current reaches zero, which causes the zero-crossing
comparator to turn off the N-channel MOSFET. The peak
inductor current is set by the voltage on the COMP pin. The
COMP pin is the output of a transconductance error amplifier that
compares the feedback voltage with an internal 0.8 V reference.
PFM MODE OPERATION
The ADP2105/ADP2106/ADP2107 smoothly transition to the
variable frequency PFM mode of operation when the load current
decreases below the pulse skipping threshold current, switching
only as necessary to maintain the output voltage within regulation.
When the output voltage dips below regulation, the ADP2105/
ADP2106/ADP2107 enter PWM mode for a few oscillator cycles
to increase the output voltage back to regulation. During the wait
time between bursts, both power switches are off, and the output
capacitor supplies all the load current. Because the output voltage
dips and recovers occasionally, the output voltage ripple in this
mode is larger than the ripple in the PWM mode of operation.
PULSE-SKIPPING THRESHOLD
The output current at which the ADP2105/ADP2106/ADP2107
transition from variable frequency PFM control to fixed frequency
PWM control is called the pulse-skipping threshold. The pulseskipping threshold is optimized for excellent efficiency over all
load currents. The variation of pulse-skipping threshold with
input voltage and output voltage is shown in Figure 25, Figure 27,
and Figure 28.
100% DUTY CYCLE OPERATION (LDO MODE)
As the input voltage drops, approaching the output voltage, the
ADP2105/ADP2106/ADP2107 smoothly transition to 100% duty
cycle, maintaining the P-channel MOSFET switch-on continuously.
This allows the ADP2105/ADP2106/ADP2107 to regulate the
output voltage until the drop in input voltage forces the P-channel
MOSFET switch to enter dropout, as shown in the following
equation:
VIN(MIN) = IOUT × (RDS(ON) − P + DCRIND) + VOUT(NOM)
The ADP2105/ADP2106/ADP2107 achieve 100% duty cycle
operation by stretching the P-channel MOSFET switch-on time
if the inductor current does not reach the peak inductor current
level by the end of the clock cycle. When this happens, the oscillator remains off until the inductor current reaches the peak
inductor current level, at which time the switch is turned off and
the synchronous rectifier is turned on for a fixed off time. At
the end of the fixed off time, another cycle is initiated. As the
ADP2105/ADP2106/ADP2107 approach dropout, the switching
frequency decreases gradually to smoothly transition to 100%
duty cycle operation.
Rev. E | Page 15 of 36
ADP2105/ADP2106/ADP2107
Data Sheet
SLOPE COMPENSATION
Short-Circuit Protection
Slope compensation stabilizes the internal current control loop
of the ADP2105/ADP2106/ADP2107 when operating beyond
50% duty cycle to prevent subharmonic oscillations. It is implemented by summing a fixed, scaled voltage ramp to the current
sense signal during the on-time of the P-channel MOSFET switch.
The ADP2105/ADP2106/ADP2107 include frequency foldback
to prevent output current runaway on a hard short. When the
voltage at the feedback pin falls below 0.3 V, indicating the possibility of a hard short at the output, the switching frequency is
reduced to 1/4 of the internal oscillator frequency. The reduction
in the switching frequency results in more time for the inductor to
discharge, preventing a runaway of output current.
The slope compensation ramp value determines the minimum
inductor that can prevent subharmonic oscillations at a given
output voltage. For slope compensation ramp values, see Table 5.
For more information see the Inductor Selection section.
Table 5. Slope Compensation Ramp Values
Device
ADP2105
ADP2106
ADP2107
Slope Compensation Ramp Values
0.72 A/µs
1.07 A/µs
1.38 A/µs
Undervoltage Lockout (UVLO)
To protect against deep battery discharge, UVLO circuitry is
integrated on the ADP2105/ADP2106/ADP2107. If the input
voltage drops below the 2.2 V UVLO threshold, the ADP2105/
ADP2106/ADP2107 shut down, and both the power switch and
synchronous rectifier turn off. When the voltage again rises above
the UVLO threshold, the soft start period is initiated, and the
device is enabled.
Thermal Protection
DESIGN FEATURES
Enable/Shutdown
Drive EN high to turn on the ADP2105/ADP2106/ADP2107.
Drive EN low to turn off the ADP2105/ADP2106/ADP2107,
reducing the input current below 0.1 µA. To force the ADP2105/
ADP2106/ADP2107 to automatically start when input power is
applied, connect EN to IN. When shut down, the ADP2105/
ADP2106/ADP2107 discharge the soft start capacitor, causing a
new soft start cycle every time they are re-enabled.
Synchronous Rectification
In addition to the P-channel MOSFET switch, the ADP2105/
ADP2106/ADP2107 include an integrated N-channel MOSFET
synchronous rectifier. The synchronous rectifier improves efficiency, especially at low output voltage, and reduces cost and
board space by eliminating the need for an external rectifier.
Current Limit
The ADP2105/ADP2106/ADP2107 have protection circuitry to
limit the direction and amount of current flowing through the
power switch and synchronous rectifier. The positive current
limit on the power switch limits the amount of current that can
flow from the input to the output, and the negative current limit
on the synchronous rectifier prevents the inductor current from
reversing direction and flowing out of the load.
In the event that the ADP2105/ADP2106/ADP2107 junction
temperatures rise above 140°C, the thermal shutdown circuit turns
off the converter. Extreme junction temperatures can be the result
of high current operation, poor circuit board design, and/or high
ambient temperature. A 40°C hysteresis is included so that when
thermal shutdown occurs, the ADP2105/ADP2106/ ADP2107
do not return to operation until the on-chip temperature drops
below 100°C. When coming out of thermal shutdown, soft start
is initiated.
Soft Start
The ADP2105/ADP2106/ADP2107 include soft start circuitry
to limit the output voltage rise time to reduce inrush current at
startup. To set the soft start period, connect the soft start capacitor
(CSS) from SS to AGND. When the ADP2105/ADP2106/ADP2107
are disabled, or if the input voltage is below the undervoltage
lockout threshold, CSS is internally discharged. When the
ADP2105/ADP2106/ADP2107 are enabled, CSS is charged through
an internal 0.8 µA current source, causing the voltage at SS to rise
linearly. The output voltage rises linearly with the voltage at SS.
Rev. E | Page 16 of 36
Data Sheet
ADP2105/ADP2106/ADP2107
APPLICATIONS INFORMATION
ADIsimPower DESIGN TOOL
SETTING THE OUTPUT VOLTAGE
The ADP2105/ADP2106/ADP2107 is supported by
ADIsimPower design tool set. ADIsimPower is a collection
of tools that produce complete power designs optimized for a
specific design goal. The tools enable the user to generate a
full schematic, bill of materials, and calculate performance in
minutes. ADIsimPower can optimize designs for cost, area,
efficiency, and parts count while taking into consideration the
operating conditions and limitations of the IC and all real external
components. For more information about ADIsimPower design
tools, refer to www.analog.com/ADIsimPower. The tool set is
available from this website, and users can also request an
unpopulated board through the tool.
The output voltage of ADP2105/ADP2106/ADP2107 (ADJ) is
externally set by a resistive voltage divider from the output voltage
to FB. The ratio of the resistive voltage divider sets the output
voltage, and the absolute value of those resistors sets the divider
string current. For lower divider string currents, the small 10 nA
(0.1 μA maximum) FB bias current is to be taken into account
when calculating resistor values. The FB bias current can be
ignored for a higher divider string current, but this degrades
efficiency at very light loads.
To limit output voltage accuracy degradation due to FB bias
current to less than 0.05% (0.5% maximum), ensure that the
divider string current is greater than 20 μA. To calculate the
desired resistor values, first determine the value of the bottom
divider string resistor (RBOT) using the following equation:
EXTERNAL COMPONENT SELECTION
The external component selection for the ADP2105/ADP2106/
ADP2107 application circuits shown in Figure 37 and Figure 38
depend on input voltage, output voltage, and load current
requirements. Additionally, trade-offs between performance
parameters like efficiency and transient response can be made
by varying the choice of external components.
0.1μF
VIN
10Ω
RBOT
VFB
I STRING
where:
VFB = 0.8 V, the internal reference.
ISTRING is the resistor divider string current.
INPUT VOLTAGE = 2.7V TO 5.5V
CIN1
VOUT
OFF
1
15
14
GND IN
13
PWIN1
LX2 12
EN
OUTPUT VOLTAGE = 1.2V, 1.5V, 1.8V, 3.3V
L
2
GND
3
GND
4
GND
ADP2105/
ADP2106/
ADP2107
SS
5
6
LX1 10
LOAD
VIN
AGND NC
7
VOUT
COUT
PWIN2 9
COMP
RCOMP
PGND 11
CIN2
8
CSS
CCOMP
NC = NO CONNECT
06079-065
16
FB
ON
Figure 37. Typical Applications Circuit for Fixed Output Voltage Options of ADP2105/ADP2106/ADP2107(x.x V)
Rev. E | Page 17 of 36
ADP2105/ADP2106/ADP2107
Data Sheet
0.1μF
10Ω
VIN
INPUT VOLTAGE = 2.7V TO 5.5V
CIN1
FB
ON
OFF
16
15
14
13
FB
GND
IN
PWIN1
LX2 12
1
EN
2
GND
3
GND
4
GND
OUTPUT VOLTAGE
= 0.8V TO VIN
L
ADP2105/
ADP2106/
ADP2107
RTOP
SS
5
6
VIN
AGND NC
7
COUT
LX1 10
PWIN2 9
COMP
RCOMP
PGND 11
LOAD
FB
CIN2
RBOT
8
CSS
06079-038
CCOMP
NC = NO CONNECT
Figure 38. Typical Applications Circuit for Adjustable Output Voltage Option of ADP2105/ADP2106/ADP2107 (ADJ)
When RBOT is determined, calculate the value of the top resistor
(RTOP) by using the following equation:
V − VFB
RTOP = RBOT OUT
VFB
L > (0.83 µH/V) × VOUT
INDUCTOR SELECTION
The high switching frequency of ADP2105/ADP2106/ADP2107
allows minimal output voltage ripple even with small inductors.
The sizing of the inductor is a trade-off between efficiency and
transient response. A small inductor leads to larger inductor
current ripple that provides excellent transient response but
degrades efficiency. Due to the high switching frequency of
ADP2105/ADP2106/ADP2107, shielded ferrite core inductors
are recommended for their low core losses and low electromagnetic
interference (EMI).
As a guideline, the inductor peak-to-peak current ripple (ΔIL) is
typically set to 1/3 of the maximum load current for optimal
transient response and efficiency, as shown in the following
equations:
VOUT × (V IN − VOUT ) I LOAD(MAX )
≈
3
VIN × f SW × L
⇒ LIDEAL =
L > (1.12 µH/V) × VOUT
For the ADP2106
The ADP2105/ADP2106/ADP2107(x.x V) include the resistive
voltage divider internally, reducing the external circuitry required.
For improved load regulation, connect the FB to the output
voltage as close as possible to the load.
∆I L =
For the ADP2105
For the ADP2107
L > (0.66 µH/V) × VOUT
Inductors 4.7 µH or larger are not recommended because they
may cause instability in discontinuous conduction mode under
light load conditions. It is also important that the inductor be
capable of handling the maximum peak inductor current (IPK)
determined by the following equation:
∆I
I PK = I LOAD ( MAX ) + L
2
Table 6. Minimum Inductor Value for Common Output
Voltage Options for the ADP2105 (1 A)
VOUT
1.2 V
1.5 V
1.8 V
2.5 V
3.3 V
2.7 V
1.67 µH
1.68 µH
2.02 µH
2.80 µH
3.70 µH
3.6 V
2.00 µH
2.19 µH
2.25 µH
2.80 µH
3.70 µH
VIN
4.2 V
2.14 µH
2.41 µH
2.57 µH
2.80 µH
3.70 µH
5.5 V
2.35 µH
2.73 µH
3.03 µH
3.41 µH
3.70 µH
Table 7. Minimum Inductor Value for Common Output
Voltage Options for the ADP2106 (1.5 A)
2.5 × VOUT × (VIN − VOUT )
μH
VIN × I LOAD(MAX )
where fSW is the switching frequency (1.2 MHz).
The ADP2105/ADP2106/ADP2107 use slope compensation in
the current control loop to prevent subharmonic oscillations
when operating beyond 50% duty cycle. The fixed slope compensation limits the minimum inductor value as a function of
output voltage.
VOUT
1.2 V
1.5 V
1.8 V
2.5 V
3.3 V
Rev. E | Page 18 of 36
2.7 V
1.11 µH
1.25 µH
1.49 µH
2.08 µH
2.74 µH
3.6 V
2.33 µH
1.46 µH
1.50 µH
2.08 µH
2.74 µH
VIN
4.2 V
2.43 µH
1.61 µH
1.71 µH
2.08 µH
2.74 µH
5.5 V
1.56 µH
1.82 µH
2.02 µH
2.27 µH
2.74 µH
ADP2105/ADP2106/ADP2107
3.6 V
1.00 µH
1.09 µH
1.19 µH
1.65 µH
2.18 µH
VIN
4.2 V
1.07 µH
1.21 µH
1.29 µH
1.65 µH
2.18 µH
5.5 V
1.17 µH
1.36 µH
1.51 µH
1.70 µH
2.18 µH
Table 9. Inductor Recommendations for the ADP2105/
ADP2106/ADP2107
Vendor
Sumida
Toko
Coilcraft
Cooper
Bussmann
Small-Sized Inductors
(< 5 mm × 5 mm)
CDRH2D14, 3D16,
3D28
1069AS-DB3018,
1098AS-DE2812,
1070AS-DB3020
LPS3015, LPS4012,
DO3314
SD3110, SD3112,
SD3114, SD3118,
SD3812, SD3814
Large-Sized Inductors
(> 5 mm × 5 mm)
CDRH4D18, 4D22,
4D28, 5D18, 6D12
D52LC, D518LC,
D62LCB
18
17
16
15
14
13
12
11
10
9
8
7
6
5
4
3
2
1
0
15
20
25
30
35
40
45
50
55
60
65
70
OUTPUT CAPACITOR × OUTPUT VOLTAGE (μC)
Figure 39. Percentage Overshoot for a 1 A Load Transient Response vs.
Output Capacitor × Output Voltage
For example, if the desired 1 A load transient response (overshoot)
is 5% for an output voltage of 2.5 V, then from Figure 39
Output Capacitor × Output Voltage = 50 μC
DO1605T
⇒ Output Capacitor =
SD10, SD12, SD14, SD52
OUTPUT CAPACITOR SELECTION
The output capacitor selection affects both the output voltage ripple
and the loop dynamics of the converter. For a given loop crossover
frequency (the frequency at which the loop gain drops to 0 dB), the
maximum voltage transient excursion (overshoot) is inversely
proportional to the value of the output capacitor. Therefore, larger
output capacitors result in improved load transient response. To
minimize the effects of the dc-to-dc converter switching, the crossover frequency of the compensation loop must be less than 1/10
of the switching frequency. Higher crossover frequency leads to
faster settling time for a load transient response, but it can also
cause ringing due to poor phase margin. Lower crossover
frequency helps to provide stable operation but needs large output
capacitors to achieve competitive overshoot specifications.
Therefore, the optimal crossover frequency for the control loop of
ADP2105/ADP2106/ADP2107 is 80 kHz, 1/15 of the switching
frequency. For a crossover frequency of 80 kHz, Figure 39 shows
the maximum output voltage excursion during a 1 A load transient,
as the product of the output voltage and the output capacitor is
varied. Choose the output capacitor based on the desired load
transient response and target output voltage.
50 μ C
2. 5
≈ 20 μ F
The ADP2105/ADP2106/ADP2107 have been designed for
operation with small ceramic output capacitors that have low
ESR and ESL. Therefore, they are comfortably able to meet tight
output voltage ripple specifications. X5R or X7R dielectrics are
recommended with a voltage rating of 6.3 V or 10 V. Y5V and Z5U
dielectrics are not recommended, due to their poor temperature
and dc bias characteristics. Table 10 shows a list of recommended
MLCC capacitors from Murata and Taiyo Yuden.
When choosing output capacitors, it is also important to
account for the loss of capacitance due to output voltage dc bias.
Figure 40 shows the loss of capacitance due to output voltage dc
bias for three X5R MLCC capacitors from Murata.
20
0
–20
1
–40
2
3
–60
–80
14.7µF 0805 X5R MURATA GRM21BR61A475K
210µF 0805 X5R MURATA GRM21BR61A106K
322µF 0805 X5R MURATA GRM21BR60J226M
–100
0
2
4
06079-060
2.7 V
0.83 µH
0.99 µH
1.19 µH
1.65 µH
2.18 µH
CAPACITANCE CHANGE (%)
VOUT
1.2 V
1.5 V
1.8 V
2.5 V
3.3 V
OVERSHOOT OF OUTPUT VOLTAGE (%)
Table 8. Minimum Inductor Value for Common Output
Voltage Options for the ADP2107 (2 A)
06079-070
Data Sheet
6
VOLTAGE (VDC)
Figure 40. Percentage Drop-In Capacitance vs. DC Bias for Ceramic
Capacitors (Information Provided by Murata Corporation)
Rev. E | Page 19 of 36
ADP2105/ADP2106/ADP2107
Data Sheet
For example, to get 20 μF output capacitance at an output voltage
of 2.5 V, based on Figure 40, as well as to give some margin for
temperature variance, a 22 μF and a 10 μF capacitor are to be
used in parallel to ensure that the output capacitance is sufficient
under all conditions for stable behavior.
LOOP COMPENSATION
The ADP2105/ADP2106/ADP2107 utilize a transconductance
error amplifier to compensate the external voltage loop. The
open loop transfer function at angular frequency (s) is given by
Z
(s) V
H (s) GmGCS COMP REF
sCOUT VOUT
Table 10. Recommended Input and Output Capacitor
Selection for the ADP2105/ADP2106/ADP2107
Capacitor
4.7 μF, 10 V
X5R 0805
10 μF, 10 V
X5R 0805
22 μF, 6.3 V
X5R 0805
Vendor
Murata
Taiyo Yuden
GRM21BR61A475K
LMK212BJ475KG
GRM21BR61A106K
LMK212BJ106KG
GRM21BR60J226M
JMK212BJ226MG
where:
VREF is the internal reference voltage (0.8 V).
VOUT is the nominal output voltage.
ZCOMP(s) is the impedance of the compensation network at the
angular frequency.
COUT is the output capacitor.
gm is the transconductance of the error amplifier (50 μA/V
nominal).
GCS is the effective transconductance of the current loop.
INPUT CAPACITOR SELECTION
The input capacitor reduces input voltage ripple caused by the
switch currents on the PWIN pins. Place the input capacitors as
close as possible to the PWIN pins. Select an input capacitor
capable of withstanding the rms input current for the maximum
load current in your application.
For the ADP2105, it is recommended that each PWIN pin be
bypassed with a 4.7 μF or larger input capacitor. For the ADP2106,
bypass each PWIN pin with a 10 μF and a 4.7 μF capacitor, and
for the ADP2107, bypass each PWIN pin with a 10 μF capacitor.
As with the output capacitor, a low ESR ceramic capacitor is
recommended to minimize input voltage ripple. X5R or X7R
dielectrics are recommended, with a voltage rating of 6.3 V or
10 V. Y5V and Z5U dielectrics are not recommended due to
their poor temperature and dc bias characteristics. Refer to
Table 10 for input capacitor recommendations.
GCS = 1.875 A/V for the ADP2105.
GCS = 2.8125 A/V for the ADP2106.
GCS = 3.625 A/V for the ADP2107.
The transconductance error amplifier drives the compensation
network that consists of a resistor (RCOMP) and capacitor (CCOMP)
connected in series to form a pole and a zero, as shown in the
following equation:
1
ZCOMP (s) RCOMP
sC
COMP
SOFT START PERIOD
At the crossover frequency, the gain of the open loop transfer
function is unity. For the compensation network impedance at
the crossover frequency, this yields the following equation:
(2π )FCROSS COUTVOUT
ZCOMP (FCROSS )
G G
V
m
REF
CS
INPUT FILTER
The IN pin is the power source for the ADP2105/ADP2106/
ADP2107 internal circuitry, including the voltage reference and
current sense amplifier that are sensitive to power supply noise.
To prevent high frequency switching noise on the PWIN pins from
corrupting the internal circuitry of the ADP2105/ADP2106/
ADP2107, a low-pass RC filter must be placed between the IN
pin and the PWIN1 pin. The suggested input filter consists of a
small 0.1 μF ceramic capacitor placed between IN and AGND and
a 10 Ω resistor placed between IN and PWIN1. This forms a
150 kHz low-pass filter between PWIN1 and IN that prevents any
high frequency noise on PWIN1 from coupling into the IN pin.
1 sRCOMP CCOMP
sCCOMP
where:
FCROSS = 80 kHz, the crossover frequency of the loop.
COUTVOUT is determined from the Output Capacitor Selection
section.
To ensure that there is sufficient phase margin at the crossover
frequency, place the compensator zero at 1/4 of the crossover
frequency, as shown in the following equation:
F
(2 π) CROSS
4
R
COMP CCOMP 1
Solving the three equations in this section simultaneously yields
the value for the compensation resistor and compensation
capacitor, as shown in the following equation:
To set the soft start period, connect a soft start capacitor (CSS) from
SS to AGND. The soft start period varies linearly with the size
of the soft start capacitor, as shown in the following equation:
(2 π)FCROSS
RCOMP 0.8
GmGCS
TSS = CSS × 109 ms
CCOMP
For a soft start period of 1 ms, a 1 nF capacitor must be
connected between SS and AGND.
Rev. E | Page 20 of 36
2
πFCROSS RCOMP
COUT VOUT
V
REF
Data Sheet
ADP2105/ADP2106/ADP2107
BODE PLOTS
60
60
ADP2106
50
180
NOTES
1. EXTERNAL COMPONENTS WERE CHOSEN FOR A
5% OVERSHOOT FOR A 1A LOAD TRANSIENT.
60
ADP2106
50
135
LOOP PHASE
180
0
CROSSOVER
OUTPUT VOLTAGE = 1.8V
–10 INPUT VOLTAGE = 3.6V
FREQUENCY = 83kHz
LOAD CURRENT = 1A
–20 INDUCTOR = 2.2µH (LPS4012)
OUTPUT CAPACITOR = 22µF + 22µF
–30 COMPENSATION RESISTOR = 180kΩ
COMPENSATION CAPACITOR = 56pF
–40
10
100
1
FREQUENCY (kHz)
NOTES
1. EXTERNAL COMPONENTS WERE CHOSEN FOR A
5% OVERSHOOT FOR A 1A LOAD TRANSIENT.
LOOP GAIN (dB)
10
90
300
Figure 45. ADP2107 Bode Plot at VIN = 5 V, VOUT = 2.5 V and Load = 1 A
60
ADP2107
50
LOOP GAIN
40
0
0
135
180
CROSSOVER
OUTPUT VOLTAGE = 1.2V
FREQUENCY = 71kHz
INPUT VOLTAGE = 3.6V
LOAD CURRENT = 1A
–20 INDUCTOR = 3.3µH (SD3814)
OUTPUT CAPACITOR = 22µF + 22µF + 4.7µF
–30 COMPENSATION RESISTOR = 267kΩ
COMPENSATION CAPACITOR = 39pF
–40
1
10
100
FREQUENCY (kHz)
–10
300
NOTES
1. EXTERNAL COMPONENTS WERE CHOSEN FOR A
5% OVERSHOOT FOR A 1A LOAD TRANSIENT.
Figure 43. ADP2105 Bode Plot at VIN = 3.6 V, VOUT = 1.2 V, and Load = 1 A
0
LOOP GAIN
45
30
LOOP GAIN (dB)
LOOP PHASE
90
LOOP PHASE (Degrees)
45
PHASE
MARGIN = 51°
40
06079-057
30
LOOP GAIN (dB)
180
NOTES
1. EXTERNAL COMPONENTS WERE CHOSEN FOR A
10% OVERSHOOT FOR A 1A LOAD TRANSIENT.
50
10
135
CROSSOVER
OUTPUT VOLTAGE = 2.5V
–10 INPUT VOLTAGE = 5V
FREQUENCY = 76kHz
LOAD CURRENT = 1A
–20 INDUCTOR = 2µH (D62LCB)
OUTPUT CAPACITOR = 10µF + 4.7µF
–30 COMPENSATION RESISTOR = 70kΩ
COMPENSATION CAPACITOR = 120pF
–40
10
100
1
FREQUENCY (kHz)
ADP2105
20
90
LOOP PHASE
0
300
Figure 42. ADP2106 Bode Plot at VIN = 3.6 V, VOUT = 1.8 V, and Load = 1 A
60
45
PHASE
MARGIN = 65°
20
10
0
LOOP GAIN
30
06079-056
LOOP GAIN (dB)
PHASE
MARGIN = 52°
LOOP PHASE (Degrees)
45
30
20
40
0
LOOP GAIN
ADP2107
50
PHASE
MARGIN = 70°
20
10
LOOP PHASE
90
135
180
0
CROSSOVER
OUTPUT VOLTAGE = 3.3V
–10 INPUT VOLTAGE = 5V
FREQUENCY = 67kHz
LOAD CURRENT = 1A
–20 INDUCTOR = 2.5µH (CDRH5D28)
OUTPUT CAPACITOR = 10µF + 4.7µF
–30 COMPENSATION RESISTOR = 70kΩ
COMPENSATION CAPACITOR = 120pF
–40
10
100
1
FREQUENCY (kHz)
LOOP PHASE (Degrees)
60
300
Figure 44. ADP2105 Bode Plot at VIN = 5.5 V, VOUT = 1.2 V and Load = 1 A
Figure 41. ADP2106 Bode Plot at VIN = 5.5 V, VOUT = 1.8 V and Load = 1 A
40
180
CROSSOVER
OUTPUT VOLTAGE = 1.2V
–10
FREQUENCY = 79kHz
INPUT VOLTAGE = 5.5V
LOAD CURRENT = 1A
–20 INDUCTOR = 3.3µH (SD3814)
OUTPUT CAPACITOR = 22µF + 22µF + 4.7µF
–30 COMPENSATION RESISTOR = 267kΩ
COMPENSATION CAPACITOR = 39pF
–40
1
10
100
FREQUENCY (kHz)
300
NOTES
1. EXTERNAL COMPONENTS WERE CHOSEN FOR A
5% OVERSHOOT FOR A 1A LOAD TRANSIENT.
135
0
LOOP PHASE (Degrees)
CROSSOVER
OUTPUT VOLTAGE = 1.8V
FREQUENCY = 87kHz
–10 INPUT VOLTAGE = 5.5V
LOAD CURRENT = 1A
–20 INDUCTOR = 2.2µH (LPS4012)
OUTPUT CAPACITOR = 22µF + 22µF
–30 COMPENSATION RESISTOR = 180kΩ
COMPENSATION CAPACITOR = 56pF
–40
10
100
1
FREQUENCY (kHz)
10
90
LOOP PHASE
06079-059
0
20
06079-058
135
LOOP PHASE
45
PHASE
MARGIN = 49°
300
NOTES
1. EXTERNAL COMPONENTS WERE CHOSEN FOR A
10% OVERSHOOT FOR A 1A LOAD TRANSIENT.
Figure 46. ADP2107 Bode Plot at VIN = 5 V, VOUT = 3.3 V, and Load = 1 A
Rev. E | Page 21 of 36
06079-069
10
90
0
LOOP GAIN
30
06079-055
LOOP GAIN (dB)
PHASE
MARGIN = 48°
20
40
LOOP GAIN (dB)
45
LOOP PHASE (Degrees)
0
LOOP GAIN
30
LOOP PHASE (Degrees)
40
ADP2105
50
ADP2105/ADP2106/ADP2107
Data Sheet
LOAD TRANSIENT RESPONSE
T
T
OUTPUT CURRENT
OUTPUT CURRENT
3
3
OUTPUT VOLTAGE (AC-COUPLED)
OUTPUT VOLTAGE (AC-COUPLED)
2
2
1
1
LX NODE (SWITCH NODE)
M 20.0µs
T 10.00%
A
CH3
CH1 2.00V
CH2 200mV~
CH3 1.00A Ω
700mA
Figure 47. 1 A Load Transient Response for ADP2105-1.2
with External Components Chosen for 5% Overshoot
T
A
CH3
700mA
OUTPUT CAPACITOR: 22µF + 4.7µF
INDUCTOR: CDRH5D18, 4.1µH
COMPENSATION RESISTOR: 270kΩ
COMPENSATION CAPACITOR: 39pF
06079-087
OUTPUT CAPACITOR: 22µF + 22µF + 4.7µF
INDUCTOR: SD14, 2.5µH
COMPENSATION RESISTOR: 270kΩ
COMPENSATION CAPACITOR: 39pF
M 20.0µs
T 10.00%
06079-089
CH1 2.00V
CH2 100mV~
CH3 1.00A Ω
LX NODE (SWITCH NODE)
Figure 49. 1 A Load Transient Response for ADP2105-3.3
with External Components Chosen for 5% Overshoot
OUTPUT CURRENT
T
3
OUTPUT CURRENT
3
2
OUTPUT VOLTAGE (AC-COUPLED)
OUTPUT VOLTAGE (AC-COUPLED)
2
1
LX NODE (SWITCH NODE)
A
1
CH3
LX NODE (SWITCH NODE)
700mA
OUTPUT CAPACITOR: 22µF + 22µF
INDUCTOR: SD3814, 3.3µH
COMPENSATION RESISTOR: 270kΩ
COMPENSATION CAPACITOR: 39pF
CH1 2.00V
CH2 100mV~
CH3 1.00A Ω
M 20.0µs
T 10.00%
A
CH3
700mA
OUTPUT CAPACITOR: 22µF + 4.7µF
INDUCTOR: SD14, 2.5µH
COMPENSATION RESISTOR: 135kΩ
COMPENSATION CAPACITOR: 82pF
Figure 48. 1 A Load Transient Response for ADP2105-1.8
with External Components Chosen for 5% Overshoot
Figure 50. 1 A Load Transient Response for ADP2105-1.2
with External Components Chosen for 10% Overshoot
Rev. E | Page 22 of 36
06079-090
M 20.0µs
T 10.00%
06079-088
CH1 2.00V
CH2 100mV~
CH3 1.00A Ω
Data Sheet
T
ADP2105/ADP2106/ADP2107
T
OUTPUT CURRENT
3
OUTPUT CURRENT
3
OUTPUT VOLTAGE (AC-COUPLED)
OUTPUT VOLTAGE (AC-COUPLED)
2
2
1
1
LX NODE (SWITCH NODE)
A
LX NODE (SWITCH NODE)
CH3
700mA
OUTPUT CAPACITOR: 10µF + 10µF
INDUCTOR: SD3814, 3.3µH
COMPENSATION RESISTOR: 135kΩ
COMPENSATION CAPACITOR: 82pF
CH1 2.00V
CH2 200mV~
CH3 1.00A Ω
M 20.0µs
T 10.00%
A
CH3
700mA
OUTPUT CAPACITOR: 10µF + 4.7µF
INDUCTOR: CDRH5D18, 4.1µH
COMPENSATION RESISTOR: 135kΩ
COMPENSATION CAPACITOR: 82pF
Figure 52. 1 A Load Transient Response for ADP2105-3.3
with External Components Chosen for 10% Overshoot
Figure 51. 1 A Load Transient Response for ADP2105-1.8
with External Components Chosen for 10% Overshoot
Rev. E | Page 23 of 36
06079-092
M 20.0µs
T 10.00%
06079-091
CH1 2.00V
CH2 100mV~
CH3 1.00A Ω
ADP2105/ADP2106/ADP2107
Data Sheet
Transition Losses
EFFICIENCY CONSIDERATIONS
Efficiency is the ratio of output power to input power. The high
efficiency of the ADP2105/ADP2106/ADP2107 has two distinct
advantages. First, only a small amount of power is lost in the dcto-dc converter package that reduces thermal constraints. Second,
the high efficiency delivers the maximum output power for the
given input power, extending battery life in portable applications.
There are four major sources of power loss in dc-to-dc
converters like the ADP2105/ADP2106/ADP2107:
•
•
•
•
The amount of power loss can be calculated by
Power switch conduction losses
Inductor losses
Switching losses
Transition losses
PTRAN =
THERMAL CONSIDERATIONS
Power switch conduction losses are caused by the flow of output
current through the P-channel power switch and the N-channel
synchronous rectifier, which have internal resistances (RDS(ON))
associated with them. The amount of power loss can be approximated by
PSW − COND = [RDS(ON) − P × D + RDS(ON) − N × (1 − D)] × IOUT2
where D = VOUT/VIN.
The internal resistance of the power switches increases with
temperature but decreases with higher input voltage. Figure 20
and Figure 21 show the change in RDS(ON) vs. input voltage,
whereas Figure 29 and Figure 30 show the change in RDS(ON) vs.
temperature for both power devices.
Inductor Losses
Inductor conduction losses are caused by the flow of current
through the inductor, which has an internal resistance (DCR)
associated with it. Larger sized inductors have smaller DCR,
which can improve inductor conduction losses.
Inductor core losses are related to the magnetic permeability of
the core material. Because the ADP2105/ADP2106/ADP2107
are high switching frequency dc-to-dc converters, shielded ferrite
core material is recommended for the low core losses and low EMI.
The total amount of inductor power loss can be calculated by
PL = DCR × IOUT2 + Core Losses
Switching Losses
Switching losses are associated with the current drawn by the
driver to turn on and turn off the power devices at the
switching frequency. Each time a power device gate is turned on
and turned off, the driver transfers a charge ΔQ from the input
supply to the gate and then from the gate to ground.
PSW = (CGATE − P + CGATE − N) × VIN2 × fSW
V IN
× I OUT × (t ON + t OFF ) × f SW
2
where tON and tOFF are the rise time and fall time of the LX
(switch) node, and are both approximately 3 ns.
Power Switch Conduction Losses
The amount of power loss can by calculated by
Transition losses occur because the P-channel MOSFET power
switch cannot turn on or turn off instantaneously. At the middle of
an LX (switch) node transition, the power switch is providing all
the inductor current, while the source to drain voltage of the
power switch is half the input voltage, resulting in power loss.
Transition losses increase with load current and input voltage
and occur twice for each switching cycle.
In most applications, the ADP2105/ADP2106/ADP2107 do not
dissipate a lot of heat due to their high efficiency. However, in
applications with high ambient temperature, low supply voltage,
and high duty cycle, the heat dissipated in the package is large
enough that it can cause the junction temperature of the die to
exceed the maximum junction temperature of 125°C. Once the
junction temperature exceeds 140°C, the converter goes into
thermal shutdown. To prevent any permanent damage it recovers
only after the junction temperature has decreased below 100°C.
Therefore, thermal analysis for the chosen application solution
is very important to guarantee reliable performance over all
conditions.
The junction temperature of the die is the sum of the ambient
temperature of the environment and the temperature rise of the
package due to the power dissipation, as shown in the following
equation:
TJ = TA + TR
where:
TJ is the junction temperature.
TA is the ambient temperature.
TR is the rise in temperature of the package due to the power
dissipation in the package.
The rise in temperature of the package is directly proportional
to the power dissipation in the package. The proportionality
constant for this relationship is defined as the thermal resistance
from the junction of the die to the ambient temperature, as
shown in the following equation:
TR = θJA × PD
where:
TR is the rise in temperature of the package.
PD is the power dissipation in the package.
θJA is the thermal resistance from the junction of the die to the
ambient temperature of the package.
where:
(CGATE − P + CGATE − N) ≈ 600 pF.
fSW = 1.2 MHz, the switching frequency.
Rev. E | Page 24 of 36
Data Sheet
ADP2105/ADP2106/ADP2107
For example, in an application where the ADP2107(1.8 V) is
used with an input voltage of 3.6 V, a load current of 2 A, and a
maximum ambient temperature of 85°C, at a load current of 2 A,
the most significant contributor of power dissipation in the dc-todc converter package is the conduction loss of the power switches.
Using the graph of switch on resistance vs. temperature (see
Figure 30), as well as the equation of power loss given in the
Power Switch Conduction Losses section, the power dissipation
in the package can be calculated by the following:
PSW − COND = [RDS(ON) − P × D + RDS(ON) − N × (1 − D)] × IOUT2 =
The θJA for the LFCSP package is 40°C/W, as shown in Table 3.
Therefore, the rise in temperature of the package due to power
dissipation is
TR = θJA × PD = 40°C/W × 0.40 W = 16°C
The junction temperature of the converter is
TJ = TA + TR = 85°C + 16°C = 101°C
Because the junction temperature of the converter is below the
maximum junction temperature of 125°C, this application operates
reliably from a thermal point of view.
[109 mΩ × 0.5 + 90 mΩ × 0.5] × (2 A)2 ≈ 400 mW
Rev. E | Page 25 of 36
ADP2105/ADP2106/ADP2107
Data Sheet
DESIGN EXAMPLE
4.
Consider an application with the following specifications:
• Input Voltage = 3.6 V to 4.2 V.
• Output Voltage = 2 V.
• Typical Output Current = 600 mA.
• Maximum Output Current = 1.2 A.
• Soft Start Time = 2 ms.
Overshoot ≤ 100 mV under all load transient conditions.
1.
2.
3.
5.
Choose the dc-to-dc converter that satisfies the maximum
output current requirement. Because the maximum output
current for this application is 1.2 A, the ADP2106 with a
maximum output current of 1.5 A is ideal for this
application.
See whether the output voltage desired is available as a
fixed output voltage option. Because 2 V is not one of the
fixed output voltage options available, choose the adjustable
version of ADP2106.
The first step in external component selection for an
adjustable version converter is to calculate the resistance of
the resistive voltage divider that sets the output voltage.
R BOT =
V FB
I STRING
=
0. 8 V
20 μA
For the ADP2106:
L > (0.83 μH/V) × VOUT
⇒ L > 0.83 μH/V × 2 V
⇒ L > 1.66 μH
Next, calculate the ideal inductor value that sets the
inductor peak-to-peak current ripple (ΔIL) to 1/3 of the
maximum load current at the maximum input voltage as
follows:
L IDEAL =
Output Capacitor × Output Voltage = 60 μC
⇒ Output Capacitor =
6.
= 40 kΩ
2 V − 0. 8 V
V
− V FB
RTOP = R BOT OUT
= 60 kΩ
= 40 kΩ ×
0.8 V
V FB
Calculate the minimum inductor value as follows:
The closest standard inductor value is 2.2 μH. The maximum
rms current of the inductor is to be greater than 1.2 A, and
the saturation current of the inductor is to be greater than
2 A. One inductor that meets these criteria is the LPS40122.2 μH from Coilcraft.
Choose the output capacitor based on the transient response
requirements. The worst-case load transient is 1.2 A, for
which the overshoot must be less than 100 mV, which is 5%
of the output voltage. For a 1 A load transient, the overshoot
must be less than 4% of the output voltage, then from
Figure 39:
7.
8.
9.
2.5 × VOUT × (VIN − VOUT )
μH =
VIN × I LOAD (MAX )
Rev. E | Page 26 of 36
2. 0 V
≈ 30 μF
Taking into account the loss of capacitance due to dc bias, as
shown in Figure 40, two 22 μF X5R MLCC capacitors from
Murata (GRM21BR60J226M) are sufficient for this
application.
Because the ADP2106 is being used in this application, the
input capacitors are 10 μF and 4.7 μF X5R Murata capacitors
(GRM21BR61A106K and GRM21BR61A475K).
The input filter consists of a small 0.1 μF ceramic capacitor
placed between IN and AGND and a 10 Ω resistor placed
between IN and PWIN1.
Choose a soft start capacitor of 2 nF to achieve a soft start
time of 2 ms.
Calculate the compensation resistor and capacitor as
follows:
(2π)FCROSS
RCOMP = 0.8
GmGCS
COUTVOUT
V
REF
=
30 μF × 2 V
(2π) × 80 kHz
= 215 kΩ
0. 8
50 μA / V × 2.8125 A / V 0.8 V
C COMP =
2.5 × 2 × (4.2 − 2)
μH = 2.18 μH
4. 2 × 1. 2
60 μC
2
2
=
= 39 pF
πFCROSS RCOMP π × 80 kHz × 215 kΩ
Data Sheet
ADP2105/ADP2106/ADP2107
EXTERNAL COMPONENT RECOMMENDATIONS
For popular output voltage options at 80 kHz crossover frequency with 10% overshoot for a 1 A load transient (refer to Figure 37 and
Figure 38).
Table 11. Recommended External Components
Device
ADP2105 (ADJ)
ADP2105 (ADJ)
ADP2105 (ADJ)
ADP2105 (ADJ)
ADP2105 (ADJ)
ADP2105 (ADJ)
ADP2106 (ADJ)
ADP2106 (ADJ)
ADP2106 (ADJ)
ADP2106 (ADJ)
ADP2106 (ADJ)
ADP2106 (ADJ)
ADP2107 (ADJ)
ADP2107 (ADJ)
ADP2107 (ADJ)
ADP2107 (ADJ)
ADP2107 (ADJ)
ADP2107 (ADJ)
ADP2105-1.2
ADP2105-1.5
ADP2105-1.8
ADP2105-3.3
ADP2106-1.2
ADP2106-1.5
ADP2106-1.8
ADP2106-3.3
ADP2107-1.2
ADP2107-1.5
ADP2107-1.8
ADP2107-3.3
VOUT (V)
0.9
1.2
1.5
1.8
2.5
3.3
0.9
1.2
1.5
1.8
2.5
3.3
0.9
1.2
1.5
1.8
2.5
3.3
1.2
1.5
1.8
3.3
1.2
1.5
1.8
3.3
1.2
1.5
1.8
3.3
CIN1 1 (μF)
4.7
4.7
4.7
4.7
4.7
4.7
4.7
4.7
4.7
4.7
4.7
4.7
10
10
10
10
10
10
4.7
4.7
4.7
4.7
4.7
4.7
4.7
4.7
10
10
10
10
CIN21 (μF)
4.7
4.7
4.7
4.7
4.7
4.7
10
10
10
10
10
10
10
10
10
10
10
10
4.7
4.7
4.7
4.7
10
10
10
10
10
10
10
10
COUT 2 (μF)
22 + 10
22 + 4.7
10 + 10
10 + 10
10 + 4.7
10 + 4.7
22 + 10
22 + 4.7
10 + 10
10 + 10
10 + 4.7
10 + 4.7
22 + 10
22 + 4.7
10 + 10
10 + 10
10 + 4.7
10 + 4.7
22 + 4.7
10 + 10
10 + 10
10 + 4.7
22 + 4.7
10 + 10
10 + 10
10 + 4.7
22 + 4.7
10 + 10
10 + 10
10 + 4.7
L (μH)
2.0
2.5
3.0
3.3
3.6
4.1
1.5
1.8
2.0
2.2
2.5
3.0
1.2
1.5
1.5
1.8
1.8
2.5
2.5
3.0
3.3
4.1
1.8
2.0
2.2
3.0
1.5
1.5
1.8
2.5
RCOMP (kΩ)
135
135
135
135
135
135
90
90
90
90
90
90
70
70
70
70
70
70
135
135
135
135
90
90
90
90
70
70
70
70
CCOMP (pF)
82
82
82
82
82
82
100
100
100
100
100
100
120
120
120
120
120
120
82
82
82
82
100
100
100
100
120
120
120
120
RTOP 3 (kΩ)
5
20
35
50
85
125
5
20
35
50
85
125
5
20
35
50
85
125
N/A
N/A
N/A
N/A
N/A
N/A
N/A
N/A
N/A
N/A
N/A
N/A
RBOT3 (kΩ)
40
40
40
40
40
40
40
40
40
40
40
40
40
40
40
40
40
40
N/A
N/A
N/A
N/A
N/A
N/A
N/A
N/A
N/A
N/A
N/A
N/A
4.7 μF 0805 X5R 10 V Murata—GRM21BR61A475KA73L. 10 μF 0805 X5R 10 V Murata—GRM21BR61A106KE19L.
4.7 μF 0805 X5R 10 V Murata—GRM21BR61A475KA73L. 10 μF 0805 X5R 10 V Murata—GRM21BR61A106KE19L. 22 μF 0805 X5R 6.3 V Murata—GRM21BR60J226ME39L.
3
0.5% accuracy resistor.
1
2
Rev. E | Page 27 of 36
ADP2105/ADP2106/ADP2107
Data Sheet
For popular output voltage options at 80 kHz crossover frequency with 5% overshoot for a 1 A load transient (refer to Figure 37 and
Figure 38).
Table 12. Recommended External Components
Device
ADP2105 (ADJ)
ADP2105 (ADJ)
ADP2105 (ADJ)
ADP2105 (ADJ)
ADP2105 (ADJ)
ADP2105 (ADJ)
ADP2106 (ADJ)
ADP2106 (ADJ)
ADP2106 (ADJ)
ADP2106 (ADJ)
ADP2106 (ADJ)
ADP2106 (ADJ)
ADP2107 (ADJ)
ADP2107 (ADJ)
ADP2107 (ADJ)
ADP2107 (ADJ)
ADP2107 (ADJ)
ADP2107 (ADJ)
ADP2105-1.2
ADP2105-1.5
ADP2105-1.8
ADP2105-3.3
ADP2106-1.2
ADP2106-1.5
ADP2106-1.8
ADP2106-3.3
ADP2107-1.2
ADP2107-1.5
ADP2107-1.8
ADP2107-3.3
VOUT (V)
0.9
1.2
1.5
1.8
2.5
3.3
0.9
1.2
1.5
1.8
2.5
3.3
0.9
1.2
1.5
1.8
2.5
3.3
1.2
1.5
1.8
3.3
1.2
1.5
1.8
3.3
1.2
1.5
1.8
3.3
CIN1 1 (μF)
4.7
4.7
4.7
4.7
4.7
4.7
4.7
4.7
4.7
4.7
4.7
4.7
10
10
10
10
10
10
4.7
4.7
4.7
4.7
4.7
4.7
4.7
4.7
10
10
10
10
CIN21 (μF)
4.7
4.7
4.7
4.7
4.7
4.7
10
10
10
10
10
10
10
10
10
10
10
10
4.7
4.7
4.7
4.7
10
10
10
10
10
10
10
10
COUT 2 (μF)
22 + 22 + 22
22 + 22 + 4.7
22 + 22
22 + 22
22 + 10
22 + 4.7
22 + 22 + 22
22 + 22 + 4.7
22 + 22
22 + 22
22 + 10
22 + 4.7
22 + 22 + 22
22 + 22 + 4.7
22 + 22
22 + 22
22 + 10
22 + 4.7
22 + 22 + 4.7
22 + 22
22 + 22
22 + 4.7
22 + 22 + 4.7
22 + 22
22 + 22
22 + 4.7
22 + 22 + 4.7
22 + 22
22 + 22
22 + 4.7
L (μH)
2.0
2.5
3.0
3.3
3.6
4.1
1.5
1.8
2.0
2.2
2.5
3.0
1.2
1.5
1.5
1.8
1.8
2.5
2.5
3.0
3.3
4.1
1.8
2.0
2.2
3.0
1.5
1.5
1.8
2.5
RCOMP (kΩ)
270
270
270
270
270
270
180
180
180
180
180
180
140
140
140
140
140
140
270
270
270
270
180
180
180
180
140
140
140
140
CCOMP (pF)
39
39
39
39
39
39
56
56
56
56
56
56
68
68
68
68
68
68
39
39
39
39
56
56
56
56
68
68
68
68
RTOP 3 (kΩ)
5
20
35
50
85
125
5
20
35
50
85
125
5
20
35
50
85
125
N/A
N/A
N/A
N/A
N/A
N/A
N/A
N/A
N/A
N/A
N/A
N/A
RBOT 3(kΩ)
40
40
40
40
40
40
40
40
40
40
40
40
40
40
40
40
40
40
N/A
N/A
N/A
N/A
N/A
N/A
N/A
N/A
N/A
N/A
N/A
N/A
4.7μF 0805 X5R 10V Murata—GRM21BR61A475KA73L. 10μF 0805 X5R 10V Murata—GRM21BR61A106KE19L.
4.7μF 0805 X5R 10V Murata—GRM21BR61A475KA73L. 10μF 0805 X5R 10V Murata—GRM21BR61A106KE19L. 22μF 0805 X5R 6.3V Murata—GRM21BR60J226ME39L.
3
0.5% accuracy resistor.
1
2
Rev. E | Page 28 of 36
Data Sheet
ADP2105/ADP2106/ADP2107
CIRCUIT BOARD LAYOUT RECOMMENDATIONS
Good circuit board layout is essential to obtaining the best
performance from the ADP2105/ADP2106/ADP2107. Poor
circuit layout degrades the output ripple, as well as the
electromagnetic interference (EMI) and electromagnetic
compatibility (EMC) performance.
•
Make the high current path from the PGND pin through L
and COUT back to the PGND plane as short as possible. To
accomplish this, ensure that the PGND pin is tied to the
PGND plane as close as possible to the input and output
capacitors.
Figure 54 and Figure 55 show the ideal circuit board layout for
the ADP2105/ADP2106/ADP2107 to achieve the highest
performance. Refer to the following guidelines if adjustments to
the suggested layout are needed:
•
The feedback resistor divider network is to be placed as
close as possible to the FB pin to prevent noise pickup. The
length of trace connecting the top of the feedback resistor
divider to the output is to be as short as possible while
keeping away from the high current traces and the LX
(switch) node that can lead to noise pickup. An analog
ground plane is to be placed on either side of the FB trace
to reduce noise pickup. For the low fixed voltage options
(1.2 V and 1.5 V), poor routing of the OUT_SENSE trace
can lead to noise pickup, adversely affecting load regulation.
This can be fixed by placing a 1 nF bypass capacitor close to
the FB pin.
•
The placement and routing of the compensation components
are critical for proper behavior of the ADP2105/ADP2106/
ADP2107. The compensation components are to be placed
as close to the COMP pin as possible. It is advisable to use
0402-sized compensation components for closer placement,
leading to smaller parasitics. Surround the compensation
components with an analog ground plane to prevent noise
pickup. The metal layer under the compensation components
is to be the analog ground plane.
•
Use separate analog and power ground planes. Connect the
ground reference of sensitive analog circuitry (such as
compensation and output voltage divider components) to
analog ground; connect the ground reference of power
components (such as input and output capacitors) to power
ground. In addition, connect both the ground planes to the
exposed pad of the ADP2105/ADP2106/ADP2107.
•
For each PWIN pin, place an input capacitor as close to the
PWIN pin as possible and connect the other end to the closest
power ground plane.
•
Place the 0.1 μF, 10 Ω low-pass input filter between the IN
pin and the PWIN1 pin, as close to the IN pin as possible.
•
Ensure that the high current loops are as short and as wide
as possible. Make the high current path from CIN through
L, COUT, and the PGND plane back to CIN as short as possible.
To accomplish this, ensure that the input and output
capacitors share a common PGND plane.
Rev. E | Page 29 of 36
ADP2105/ADP2106/ADP2107
Data Sheet
EVALUATION BOARD
EVALUATION BOARD SCHEMATIC FOR ADP2107 (1.8 V)
C7
0.1µF
VCC
R3
10Ω
C1
10µF1
OUT
U1
J1
GND
16
15
FB
GND IN
1
EN
2
GND
INPUT VOLTAGE = 2.7V TO 5.5V
VIN
VCC
14
13
PWIN1
LX2 12
EN
PGND 11
ADP2107-1.8
3
GND
LX1 10
4
GND
PWIN2 9
1
L12
2µH
VCC
OUT
6
7
8
C4
22µF1
C3
22µF1
GND
R5
NS
R1
140kΩ
C6
68pF
R4
0Ω
C2
10µF1
COMP SS AGND PADDLE NC
5
OUTPUT VOLTAGE = 1.8V, 2A
VOUT
2
1 MURATA
X5R 0805
10μF: GRM21BR61A106KE19L
22μF: GRM21BR60J226ME39L
2 2μH INDUCTOR D62LCB TOKO
C5
1nF
NC = NO CONNECT
06079-044
R2
100kΩ
Figure 53. Evaluation Board Schematic of the ADP2107-1.8 (Bold Traces are High Current Paths)
RECOMMENDED PCB LAYOUT (EVALUATION BOARD LAYOUT)
JUMPER TO ENABLE
ENABLE
GROUND
VIN
100kΩ PULL-DOWN
GROUND
INPUT
INPUT CAPACITOR
POWER GROUND
PLANE
PLACE THE FEEDBACK RESISTORS AS
CLOSE TO THE FB PIN AS POSSIBLE.
RTOP RBOT
CONNECT THE GROUND RETURN OF
ALL POWER COMPONENTS SUCH AS
INPUT AND OUTPUT CAPACITORS TO
THE POWER GROUND PLANE.
OUTPUT CAPACITOR
CIN
COUT
LX
OUTPUT
PGND
ADP2105/ADP2106/ADP2107
VOUT
LX
RCOMP
CIN
CCOMP
PLACE THE COMPENSATION
COMPONENTS AS CLOSE TO
THE COMP PIN AS POSSIBLE.
INDUCTOR (L)
COUT
OUTPUT CAPACITOR
CSS
ANALOG GROUND PLANE
POWER GROUND
INPUT CAPACITOR
06079-045
CONNECT THE GROUND RETURN OF ALL
SENSITIVE ANALOG CIRCUITRY SUCH AS
COMPENSATION AND OUTPUT VOLTAGE
DIVIDER TO THE ANALOG GROUND PLANE.
Figure 54. Recommended Layout of Top Layer of ADP2105/ADP2106/ADP2107
Rev. E | Page 30 of 36
Data Sheet
ADP2105/ADP2106/ADP2107
ENABLE
VIN
GND
GND
ANALOG GROUND PLANE
POWER GROUND PLANE
INPUT VOLTAGE PLANE
CONNECTING THE TWO
PWIN PINS AS CLOSE
AS POSSIBLE.
VIN
CONNECT THE EXPOSED PAD OF
THE ADP2105/ADP2106/ADP2107
TO A LARGE GROUND PLANE TO
AID POWER DISSIPATION.
VOUT
FEEDBACK TRACE: THIS TRACE CONNECTS THE TOP OF THE
RESISTIVE VOLTAGE DIVIDER ON THE FB PIN TO THE OUTPUT.
PLACE THIS TRACE AS FAR AWAY FROM THE LX NODE AND HIGH
CURRENT TRACES AS POSSIBLE TO PREVENT NOISE PICKUP.
Figure 55. Recommended Layout of Bottom Layer of ADP2105/ADP2106/ADP2107
Rev. E | Page 31 of 36
06079-046
CONNECT THE PGND PIN
TO THE POWER GROUND
PLANE AS CLOSE TO THE
ADP2105/ADP2106/ADP2107
AS POSSIBLE.
ADP2105/ADP2106/ADP2107
Data Sheet
APPLICATION CIRCUITS
0.1μF
10Ω
VIN
INPUT VOLTAGE = 5V
10μF1
VOUT
OFF
13
14
16
15
FB
GND IN
PWIN1
LX2 12
1
EN
2
GND
2.5μH2
PGND 11
ADP2107-3.3
3
GND
LX1 10
4
GND
PWIN2 9
COMP
SS
5
6
10μF1
8
1nF
70kΩ
OUTPUT VOLTAGE = 3.3V
4.7μF1
LOAD
0A TO 2A
VIN
AGND NC
7
VOUT
10μF1
1 MURATA
X5R 0805
10μF: GRM21BR61A106KE19L
4.7μF: GRM21BR61A475KA73L
2 SUMIDA CDRH5D28: 2.5μH
NOTES
1. NC = NO CONNECT.
2. EXTERNAL COMPONENTS WERE
CHOSEN FOR A 10% OVERSHOOT
FOR A 1A LOAD TRANSIENT.
120pF
06079-047
ON
Figure 56. Application Circuit—VIN = 5 V, VOUT = 3.3 V, Load = 0 A to 2 A
0.1μF
10Ω
VIN
INPUT VOLTAGE = 3.6V
10μF1
VOUT
16
15
FB
GND IN
14
13
PWIN1
LX2 12
1 EN
OFF
1.5μH2
PGND 11
2 GND
ADP2107-1.5
3 GND
LX1 10
4 GND
PWIN2 9
COMP
SS
5
6
10μF1
8
LOAD
0A TO 2A
1 MURATA X5R 0805
10μF: GRM21BR61A106KE19L
22μF: GRM21BR60J226ME39L
2 TOKO D62LCB OR COILCRAFT LPS4012
1nF
140kΩ
OUTPUT VOLTAGE = 1.5V
22μF1
VIN
AGND NC
7
VOUT
22μF1
NOTES
1. NC = NO CONNECT.
2. EXTERNAL COMPONENTS WERE
CHOSEN FOR A 5% OVERSHOOT
FOR A 1A LOAD TRANSIENT.
68pF
06079-048
ON
Figure 57. Application Circuit—VIN = 3.6 V, VOUT = 1.5 V, Load = 0 A to 2 A
0.1μF
10Ω
VIN
INPUT VOLTAGE = 2.7V TO 4.2V
4.7μF1
VOUT
OFF
16
15
FB
GND IN
14
13
PWIN1
LX2 12
1
EN
2
GND
2.7μH2
PGND 11
ADP2105-1.8
3
GND
LX1 10
4
GND
PWIN2 9
COMP
SS
5
6
270kΩ
39pF
AGND NC
1nF
7
VOUT
22μF1
8
OUTPUT VOLTAGE = 1.8V
22μF1
LOAD
0A TO 1A
VIN
4.7μF1
1 MURATA
X5R 0805
4.7μF: GRM21BR61A475KA73L
22μF: GRM21BR60J226ME39L
2 TOKO 1098AS-DE2812: 2.7μH
NOTES
1. NC = NO CONNECT.
2. EXTERNAL COMPONENTS WERE
CHOSEN FOR A 5% OVERSHOOT
FOR A 1A LOAD TRANSIENT.
Figure 58. Application Circuit—VIN = Li-Ion Battery, VOUT = 1.8 V, Load = 0 A to 1 A
Rev. E | Page 32 of 36
06079-049
ON
Data Sheet
ADP2105/ADP2106/ADP2107
0.1μF
10Ω
VIN
INPUT VOLTAGE = 2.7V TO 4.2V
4.7μF1
VOUT
16
15
FB
GND IN
14
13
PWIN1
LX2 12
1 EN
OFF
2.4μH2
VOUT
PGND 11
2 GND
22μF1
ADP2105-1.2
3 GND
LX1 10
4 GND
PWIN2 9
COMP
SS
5
6
4.7μF1
1 MURATA X5R 0805
4.7μF: GRM21BR61A475KA73L
22μF: GRM21BR60J226ME39L
8
2 TOKO 1069AS-DB3018HCT OR
1nF
135kΩ
LOAD
0A TO 1A
VIN
AGND NC
7
OUTPUT VOLTAGE = 1.2V
4.7μF1
TOKO 1070AS-DB3020HCT
82pF
NOTES
1. NC = NO CONNECT.
2. EXTERNAL COMPONENTS WERE
CHOSEN FOR A 10% OVERSHOOT
FOR A 1A LOAD TRANSIENT.
06079-050
ON
Figure 59. Application Circuit—VIN = Li-Ion Battery, VOUT = 1.2 V, Load = 0 A to 1 A
0.1μF
10Ω
VIN
INPUT VOLTAGE = 5V
10μF1
FB
OFF
16
15
14
13
FB
GND
IN
PWIN1
LX2 12
1
EN
2
GND
2.5μH2
85kΩ
ADP2106-ADJ
3
GND
LX1 10
4
GND
PWIN2 9
COMP SS
5
180kΩ
56pF
OUTPUT VOLTAGE = 2.5V
PGND 11
AGND NC
6
1nF
7
10μF1
22μF1
LOAD
0A TO 1.5A
FB
VIN
40kΩ
4.7μF1
8
1 MURATA
X5R 0805
4.7μF: GRM21BR61A475KA73L
10μF: GRM21BR61A106KE19L
22μF: GRM21BR60J226ME39L
2 COILTRONICS SD14: 2.5μH
NOTES
1. NC = NO CONNECT.
2. EXTERNAL COMPONENTS WERE
CHOSEN FOR A 5% OVERSHOOT
FOR A 1A LOAD TRANSIENT.
Figure 60. Application Circuit—VIN = 5 V, VOUT = 2.5 V, Load = 0 A to 1.5 A
Rev. E | Page 33 of 36
06079-051
ON
ADP2105/ADP2106/ADP2107
Data Sheet
OUTLINE DIMENSIONS
PIN 1
INDICATOR
4.10
4.00 SQ
3.90
0.35
0.30
0.25
0.65
BSC
PIN 1
INDICATOR
16
13
1
12
*2.40
2.35 SQ
2.30
EXPOSED
PAD
9
0.80
0.75
0.70
0.25 MIN
BOTTOM VIEW
0.05 MAX
0.02 NOM
COPLANARITY
0.08
0.20 REF
SEATING
PLANE
PKG-000000
4
5
8
FOR PROPER CONNECTION OF
THE EXPOSED PAD, REFER TO
THE PIN CONFIGURATION AND
FUNCTION DESCRIPTIONS
SECTION OF THIS DATA SHEET.
07-21-2015-B
TOP VIEW
0.50
0.40
0.30
*COMPLIANT TO JEDEC STANDARDS MO-220-WGGC-3
WITH EXCEPTION TO THE EXPOSED PAD.
Figure 61. 16-Lead Lead Frame Chip Scale Package [LFCSP]
4 mm × 4 mm Body and 0.75 mm Package Height
(CP-16-20)
Dimensions shown in millimeters
ORDERING GUIDE
Model1
ADP2105ACPZ-1.2-R7
ADP2105ACPZ-1.5-R7
ADP2105ACPZ-1.8-R7
ADP2105ACPZ-3.3-R7
ADP2105ACPZ-R7
ADP2106ACPZ-1.2-R7
ADP2106ACPZ-1.5-R7
ADP2106ACPZ-1.8-R7
ADP2106ACPZ-3.3-R7
ADP2106ACPZ-R7
ADP2107ACPZ-1.2-R7
ADP2107ACPZ-1.5-R7
ADP2107ACPZ-1.8-R7
ADP2107ACPZ-3.3-R7
ADP2107ACPZ-R7
ADP2105-1.8-EVALZ
ADP2105-EVALZ
ADP2106-1.8-EVALZ
ADP2106-EVALZ
ADP2107-1.8-EVALZ
ADP2107-EVALZ
1
Output
Current
1A
1A
1A
1A
1A
1.5 A
1.5 A
1.5 A
1.5 A
1.5 A
2A
2A
2A
2A
2A
Temperature
Range
−40°C to +125°C
−40°C to +125°C
−40°C to +125°C
−40°C to +125°C
−40°C to +125°C
−40°C to +125°C
−40°C to +125°C
−40°C to +125°C
−40°C to +125°C
−40°C to +125°C
−40°C to +125°C
−40°C to +125°C
−40°C to +125°C
−40°C to +125°C
−40°C to +125°C
Output Voltage
1.2 V
1.5 V
1.8 V
3.3 V
ADJ
1.2 V
1.5 V
1.8 V
3.3 V
ADJ
1.2 V
1.5 V
1.8 V
3.3 V
ADJ
1.8 V
Adjustable, but set to 2.5 V
1.8 V
Adjustable, but set to 2.5 V
1.8 V
Adjustable, but set to 2.5 V
Z = RoHS Compliant Part.
Rev. E | Page 34 of 36
Package Description
16-Lead LFCSP
16-Lead LFCSP
16-Lead LFCSP
16-Lead LFCSP
16-Lead LFCSP
16-Lead LFCSP
16-Lead LFCSP
16-Lead LFCSP
16-Lead LFCSP
16-Lead LFCSP
16-Lead LFCSP
16-Lead LFCSP
16-Lead LFCSP
16-Lead LFCSP
16-Lead LFCSP
Evaluation Board
Evaluation Board
Evaluation Board
Evaluation Board
Evaluation Board
Evaluation Board
Package Option
CP-16-20
CP-16-20
CP-16-20
CP-16-20
CP-16-20
CP-16-20
CP-16-20
CP-16-20
CP-16-20
CP-16-20
CP-16-20
CP-16-20
CP-16-20
CP-16-20
CP-16-20
Data Sheet
ADP2105/ADP2106/ADP2107
NOTES
Rev. E | Page 35 of 36
ADP2105/ADP2106/ADP2107
Data Sheet
NOTES
©2006–2016 Analog Devices, Inc. All rights reserved. Trademarks and
registered trademarks are the property of their respective owners.
D06079-0-3/16(E)
Rev. E | Page 36 of 36
工商网监
湘ICP备2023018690号
