User's Guide
SNVA129B – October 2005 – Revised April 2013
AN-1410 LM2696 Demonstration Board
1
Introduction
The LM2696 is a constant on-time, buck regulator capable of delivering up to 3A into a load.
The LM2696 is capable of switching frequencies in the range of 100 kHz to 500 kHz and accepts input
voltages from 4.5 V to 24 V. An internal soft-start and power-good flag are also provided to allow for
simple sequencing between multiple regulators.
The operating conditions for the evaluation board are the following:
VIN = 6 V to 24 V
VOUT = 2.5 V
IOUT = 0A to 3A
fSW = 250 kHz
LM2696
VPGOOD
PGOOD
VSD
EXTVCC
SD
CVCC
CSD
RON
CBOOT
RON
VIN
CIN CBY CAVIN CSS
CBOOT
AVIN
SW
PVIN
GND
L
VOUT
RFB1
DSW
SS
COUT
FB
RFB2
Figure 1. Evaluation Board Schematic
Table 1. Bill of Materials (BOM)
ID
Part Number
U1
LM2696
L
MSS1260-682MX
Type
Size
3A Constant ontime Regulator
HTSSOP-16
Parameters
Qty
Vendor
1
TI
Coilcraft
Inductor
MSS1260
6.8 µH, 4.9A ISAT
1
CIN
EEUFC1V181
Capacitor
8 x 11.5
180 µF, 35 V
1
Sanyo
CBY
VJ0805Y104KXAM
Capacitor
0805
0.1 µF
1
Vishay
CSS
VJ080JY103KXX
Capacitor
0805
0.01 µF
1
Vishay
CVCC
VJ0805Y105JXACW1BC
Capacitor
0805
1 µF
1
Vishay
CBOOT
VJ0805Y104KXAM
Capacitor
0805
0.1 µF
1
Vishay
CAVIN
VJ0805Y105JXACW1BC
Capacitor
0805
1 µF
1
Vishay
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1
Performance
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Table 1. Bill of Materials (BOM) (continued)
ID
2
Type
Size
Parameters
Qty
Vendor
COUT
Part Number
TPSW476M010R0150
Capacitor
W
47 µF, 10 V, 150
mΩ
1
AVX
CSD
VJ0805Y102KXXA
Capacitor
0805
1 nF
1
Vishay
RFB1
CRCW08051001F
Resistor
0805
1 kΩ
1
Vishay
RFB2
CRCW08051001F
Resistor
0805
1 kΩ
1
Vishay
RON
CRCW08051433F
Resistor
0805
143 kΩ
1
Vishay
DSW
CMSH3-40M-NST
Schottky Diode
SMB
40 V @ 3A diode,
VF = 0.55 V
1
Central
Semiconductor
160-1026-02
-05-00
Solder Terminals
7
Wearnes
Terminals for
VIN, GND and
VOUT
Performance
Benchmark data has been taken from the evaluation board using the LM2696. Figure 2 shows an
efficiency measurement taken with VIN at 12 V.
Figure 2. Efficiency with VIN = 12 V
The advantage of the evaluation board is the ability to examine performance tradeoffs through substitution
of parts. By careful selection of the components used, it is possible to optimize the application circuit for a
given parameter. For instance, the inductor footprint has been designed to accommodate DO-3316 and
MSS-1278 packages. The inductor selection would then be determined by the design constraints.
3
Frequency Selection
The resistor connected to the RON pin sets the switching frequency of the LM2696. This resistor controls
the current flowing into the RON pin and is directly related to the on-time pulse. Connecting a resistor from
this pin to PVIN allows the switching frequency to remain constant as the input voltage changes. In normal
operation this pin is approximately 0.65 V above GND. In shutdown, this pin becomes a high impedance
node to prevent current flow.
The value of RON may be expressed as:
RON =
(VIN ± VD) x VOUT
kON x fSW x VIN
106
(1)
Where RON is in kΩ, fSW is in kHz, and kON is in µA • µs
2
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Inductor Selection
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Under no condition should a bypass capacitor be connected to the RON pin. Doing so couples any AC
perturbations into the pin and prevents proper operation.
For this demo board, RON is calculated as :
RON =
4
(12V ± 0.65V) x 2.5V
6
66 PA x Ps x 250 kHz x 12V
10 = 143 k:
(2)
Inductor Selection
Typically an inductor is selected such that the maximum peak-to-peak ripple current is less than 30% of
the maximum load current. The inductor current ripple (ΔIL) may be expressed as:
(VIN - VOUT) D
'IL =
L fSW
(3)
The inductor for this demo board was calculated as shown in Equation 4:
L=
(12V ± 2.5V) x 0.21V
3
10 = 6.8 PH
(40% x 3A) x 250 kHz
(4)
A standard value of 10 µH may be chosen.
The other characteristics of the inductor that should be taken into account are saturation current and core
material. A shielded inductor or low profile unshielded inductor is recommended to reduce EMI.
Physical orientation of the inductor effects the parts stability. The inductor should be oriented such that the
magnetic flux flows down through the center of the inductor and returns through the ground plane. Simply
put, the inductor should be oriented such that terminal associated with the dot or label is connected to the
switchnode.
5
Output Capacitor
The output capacitor size and ESR have a direct affect on the stability of the loop. This is because the
constant on-time control scheme works by sensing the output voltage ripple and switching appropriately.
The ripple voltage necessary at the feedback pin may be estimated using the following relationship:
ΔVFB ≥ 0.057 x fSW + 35
(5)
Where fSW is in kHz and ΔVFB is in mV.
This minimum ripple voltage is necessary in order for the comparator to initiate switching.
The ripple at the output may be calculated by multiplying the feedback ripple voltage by the gain seen
through the feedback resistors. This gain H may be expressed as:
VOUT
H=
VFB
VOUT
=
1.25V
(6)
For this demo board, the ripple necessary at the feedback pin is calculated as:
ΔVFB 21 mV ≥ 0.057 x 250 kHz + 35
(7)
Therefore, the ripple at the output is:
'VOUT = 42 mV = 21 mV x
2.5V
1.25V
(8)
Since the ripple current is calculated as 798 mA, the output capacitor must have an ESR not less than:
ESR = 36 m: =
Ripple_Voltage
Ripple_Current
=
42 mV
1200 mA
(9)
Typically the best performance is obtained using POSCAPs, SP CAPs, tantalum, Niobium Oxide, or
similar chemistry type capacitors. Low ESR ceramic capacitors may be used in conjunction with the RC
feed forward scheme; however, the feed forward voltage at the feedback pin must greater than 30 mV. For
more information, see Section 6.
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Ripple Feed Forward
6
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Ripple Feed Forward
An RC network may be used to eliminate the need for high ESR capacitors. Such a network is connected
as shown in Figure 3.
L
SW
VOUT
Rff
RFB1
FB
COUT
Cff
RFB2
Figure 3. RC Feed Forward Network
The value of Rff should be large in order to prevent any potential offset in VOUT. Typically the value of Rff is
on the order of 1MΩ and the value of RFB1 should be less than 10kΩ. The large difference in resistor
values minimizes output voltage offset errors in DCM. The value of the capacitor may be selected using
the following relationship:
(VIN_MIN - VFB) TON_MIN
Cff_MAX =
0.03V Rff
(10)
Where the on-time (TON_MIN) is in µs, and the resistance (Rff) is in MΩ.
If a ceramic output capacitor is used with this demo board, Cff_MAX is calculated as:
Cff_MAX =
(6V ± 1.25V) x 0.42 Ps
0.03V x 1 M:
= 67 pF
(11)
A standard value of 270 pF may be chosen.
7
Feedback Resistors
In order to reduce noise at the feedback pin, RFB2 is typically on the order of 1kΩ. To calculate the value of
RFB1, one may use the relationship:
RFB1 = RFB2
§ VOUT
¨ VFB
©
·
¹
- 1¸
(12)
Where VFB is the internal reference voltage (1.255 V typical).
The output voltage value can be set in a precise manner by taking into account the fact that the reference
voltage is regulating the bottom of the output ripple as opposed to the average value. This relationship is
shown in Figure 4.
4
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Soft-Start Capacitor
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VOUT
VOUT_AVG
'VOUT
VREF
Time
Figure 4. Average and Ripple Output Voltages
One should note that for high output voltages (>5 V), a load of approximately 15mA may be required for
the output voltage to reach the desired value.
The resistors for this demo board were selected as: RFB2 = 1kΩ
RFB1 = 1 k:
8
§ 2.5V - 1· = 1 k:
©1.25V ¹
(13)
Soft-Start Capacitor
The SS capacitor is used to slowly ramp the reference from 0 V to its final value of 1.25 V. The startup
time may be calculated using Equation 14:
tSS =
1.25V x CSS
ISS
x 103
(14)
or conversely, capacitance as a function of startup time:
CSS = ISS
tSS
1.25V
x 10-3
(15)
Where ISS is the soft-start pin source current (1µA typical) in µA, CSS is in µF, and tSS is in ms.
The soft-start capacitor was selected such that the soft start time would be approximately 12.5 ms. The
capacitor value was calculated as:
CSS = 0.01 PF = 1 PA
9
12.5 ms
x 10-3
1.25V
(16)
Shutdown
The state of the shutdown pin enables the device or places it in a sleep state. This pin has an internal pullup and may be left floating or connected to a high logic level. Connecting this pin to GND will shutdown
the part. This pin must be bypassed with a 1nF ceramic capacitor to ensure proper logic thresholds.
10
Layout Guidelines
Good layout for DC-DC converters can be implemented by following a few simple design guidelines:
1. Place the power components (catch diode, inductor, and filter capacitors) close together. Make the
traces between them as short and wide as possible.
2. Use wide traces between the power components and for power connections to the DC-DC converter
circuit.
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PCB Layouts
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3. Connect the ground pins of the input and output filter capacitors and catch diode as close as possible
using generous component-side copper fill as a pseudo-ground plane. Then, connect this to the ground
plane through several vias.
4. Arrange the power components so that the switching loops curl in the same direction.
5. Separate noise sensitive traces, such as the voltage feedback path, from noisy traces associated with
the power components.
6. Ensure a low-impedance ground for the converter IC.
7. Place the supporting components for the converter IC, including frequency selection components as
close to the converter IC as possible, but away from noisy traces and the power components. Make
their connections to the converter IC and its pseudoground plane as short as possible.
8. Place noise sensitive circuitry such as radio or modem blocks away from the DC-DC converter.
11
PCB Layouts
Figure 5. Top Layer
Figure 6. Bottom Layer
6
AN-1410 LM2696 Demonstration Board
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Alternate Application Circuit
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12
Alternate Application Circuit
LM2696
VPGOOD
PGOOD
VSD
EXTVCC
SD
CVCC
CSD
RON
CBOOT
RON
VIN
CIN CBY CAVIN CSS
CBOOT
AVIN
SW
PVIN
GND
L
VOUT
RFB1
DSW
SS
COUT
FB
RFB2
Figure 7. 5 V to 2.5 V Voltage Applications Circuit
ID
Part Number
Type
Size
Parameters
Qty
Vendor
U1
LM2696
3A Constant ontime Regulator
HTSSOP-16
1
NSC
L
MSS1260-103MX
Inductor
MSS1260
10 µH, 4.0A ISAT
1
Coilcraft
CIN
EEUFC1V181
Capacitor
10 x 12.5
180 µF, 35 V, 90
mΩ
1
Panasonic
CBY
VJ0805Y104KXAM
Capacitor
CSS
VJ080JY103KXX
Capacitor
0805
0.1 µF
1
Vishay
0805
0.01 µF
1
Vishay
CVCC
VJ0805Y105JXACW1BC
Capacitor
0805
1 µF
1
Vishay
CBOOT
VJ0805Y104KXAM
Capacitor
0805
0.1 µF
1
Vishay
CAVIN
VJ0805Y105JXACW1BC
Capacitor
0805
1 µF
1
Vishay
COUT
TPSC107M006R0075
Capacitor
C
100 µF, 6 V, 75
mΩ
1
AVX
CSD
VJ0805Y102KXXA
Capacitor
0805
1 nF
1
Vishay
RFB1
CRCW08051651F
Resistor
0805
1.65 kΩ
1
Vishay
RFB2
CRCW08051001F
Resistor
0805
1 kΩ
1
Vishay
RON
CRCW08051543F
Resistor
0805
154 kΩ
1
Vishay
DSW
CMSH3-40M-NST
Schottky Diode
SMB
40 V @ 3A diode,
VF = 0.55 V
1
Central
Semiconduct
or
160-1026-02-0500
Solder Terminals
7
Wearnes
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Terminals for
VIN, GND and
VOUT
AN-1410 LM2696 Demonstration Board
Copyright © 2005–2013, Texas Instruments Incorporated
7
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