LMH6553
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SNOSB07H – SEPTEMBER 2008 – REVISED MARCH 2013
LMH6553 900 MHz Fully Differential Amplifier With Output Limiting Clamp
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FEATURES
DESCRIPTION
1
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The LMH6553 is a 900 MHz differential amplifier with
an integrated adjustable output limiting clamp. The
clamp increases system performance and provides
transient over-voltage protection to following stages.
The internal clamp feature of the LMH6553 reduces
or eliminates the need for external discrete overload
protection networks. When used to drive ADCs, the
amplifier's output clamp allows low voltage ADC
inputs to be protected from being overdriven and
damaged by large input signals appearing at the
system input. Fast overdrive recovery of 600 ps
ensures the amplifier output rapidly recovers from a
clamping event and quickly resumes to follow the
input signal. The LMH6553 delivers exceptional
bandwidth, distortion, and noise performance ideal for
driving ADCs up to 14-bits. The LMH6553 could also
be used for automotive, communication, medical, test
and measurement, video, and LIDAR applications.
900 MHz −3 dB Small Signal
Bandwidth @ AV = 1
670 MHz −3 dB Large Signal
Bandwidth @ AV = 1
−79 dB THD @ 20 MHz
−92 dB IMD3 @ fc = 20 MHz
10 ns Settling Time to 0.1%
600 ps Clamp Overdrive Recovery Time
40 mV Clamp Accuracy with 100% Overdrive
−0.1 mV/°C Clamp Temperature Drift
4.5 to 12 Supply Voltage Operation
APPLICATIONS
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Differential ADC Driver
Video Over Twisted Pair
Differential Line Driver
Single End to Differential Converter
High Speed Differential Signaling
IF/RF Amplifier
SAW Filter Buffer/Driver
CCD Output Limiting Amplifier
Automotive Safety Applications
With external gain set resistors and integrated
common mode feedback, the LMH6553 can be
configured as either a differential input to differential
output or single ended input to differential output gain
block. The LMH6553 can be AC or DC coupled at the
input which makes it suitable for a wide range of
applications including communication systems and
high speed oscilloscope front ends. The LMH6553 is
available in 8-pin SO PowerPAD and 8-pin WSON
packages, and is part of our LMH™ high speed
amplifier family.
Typical Application
275:
V
255:
59:
255:
49.9:
ADC
+
50:
Single-Ended
AC-Coupled
Source
VCM
RO
VIN+
+
LMH6553
+
-
VIN-
-
V
59:
0.1PF
C
8 to14 Bit
275:
RO
+
-
VCM
VCLAMP
Figure 1. Single-Ended Input Differential Output ADC Driver
1
2
3
Please be aware that an important notice concerning availability, standard warranty, and use in critical applications of
Texas Instruments semiconductor products and disclaimers thereto appears at the end of this data sheet.
LMH is a trademark of Texas Instruments.
All other trademarks are the property of their respective owners.
PRODUCTION DATA information is current as of publication date.
Products conform to specifications per the terms of the Texas
Instruments standard warranty. Production processing does not
necessarily include testing of all parameters.
Copyright © 2008–2013, Texas Instruments Incorporated
LMH6553
SNOSB07H – SEPTEMBER 2008 – REVISED MARCH 2013
www.ti.com
These devices have limited built-in ESD protection. The leads should be shorted together or the device placed in conductive foam
during storage or handling to prevent electrostatic damage to the MOS gates.
Absolute Maximum Ratings
ESD Tolerance
(1) (2)
(3)
Human Body Model
4000V
Machine Model
350V
Supply Voltage
13.2V
Common Mode Input Voltage
±VS
Maximum Input Current (pins 1, 2, 7, 8)
30 mA
(4)
Maximum Output Current (pins 4, 5)
Maximum Junction Temperature
150°C
For soldering specifications
see product folder at http://www.ti.com and
http://www.ti.com/lit/SNOA549
(1)
(2)
(3)
(4)
Absolute Maximum Ratings indicate limits beyond which damage to the device may occur. Operating Ratings indicate conditions for
which the device is intended to be functional, but specific performance is not ensured. For ensured specifications, see the Electrical
Characteristics tables.
If Military/Aerospace specified devices are required, please contact the Texas Instruments Sales Office/ Distributors for availability and
specifications.
Human Body Model, applicable std. MIL-STD-883, Method 30157. Machine Model, applicable std. JESD22-A115-A (ESD MM std. of
JEDEC). Field-Induced Charge-Device Model, applicable std. JESD22-C101-C (ESD FICDM std. of JEDEC).
The maximum output current (IOUT) is determined by device power dissipation limitations. See POWER DISSIPATION of Application
Information for more details.
Operating Ratings
(1)
Operating Temperature Range
(2)
−40°C to +125°C
−65°C to +150°C
Storage Temperature Range
Total Supply Voltage
4.5V to 12V
Package Thermal Resistance (θJA)
8-Pin SO PowerPAD
59°C/W
8-Pin WSON
58°C/W
(1)
(2)
2
Absolute Maximum Ratings indicate limits beyond which damage to the device may occur. Operating Ratings indicate conditions for
which the device is intended to be functional, but specific performance is not ensured. For ensured specifications, see the Electrical
Characteristics tables.
The maximum power dissipation is a function of TJ(MAX), θJA. The maximum allowable power dissipation at any ambient temperature is
PD = (TJ(MAX)– TA) / θJA. All numbers apply for packages soldered directly onto a PC Board.
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SNOSB07H – SEPTEMBER 2008 – REVISED MARCH 2013
VS = ±5V Electrical Characteristics
(1)
Unless otherwise specified, all limits are ensured for TA = 25°C, VS = ±5V, AV = 1, VCM = 0V, VCLAMP = 3V, RF = RG = 275Ω,
RL = 200Ω, for single-ended in, differential out. Boldface limits apply at the temperature extremes.
Symbol
Parameter
Conditions
Min
(2)
Typ
(3)
Max
(2)
Units
AC Performance (Differential)
SSBW
LSBW
Small Signal −3 dB Bandwidth
(2)
Large Signal −3 dB Bandwidth
VOUT = 0.2 VPP, AV = 1, RL = 1 kΩ
900
VOUT = 0.2 VPP, AV = 1
720
VOUT = 0.2 VPP, AV = 2
680
VOUT = 0.2 VPP, AV = 4
630
VOUT = 0.2 VPP, AV = 8, (RF = 400Ω, RG =
50Ω)
350
VOUT = 2 VPP, AV = 1, RL = 1 kΩ
670
VOUT = 2 VPP, AV = 1
540
VOUT = 2 VPP, AV = 2
530
VOUT = 2 VPP, AV = 4
490
VOUT = 2 VPP, AV = 8, (RF = 400Ω, RG = 50Ω)
350
MHz
MHz
0.1 dB Bandwidth
VOUT = 0.2 VPP, AV = 1
50
MHz
0.5 dB Bandwidth
VOUT = 0.2 VPP, AV = 1
525
MHz
Slew Rate
4V Step, AV = 1
2300
V/μs
Rise/Fall Time, 10%-90%
2V Step
690
ps
0.1% Settling Time
2V Step
10
ns
1.0% Settling Time
2V Step
6
ns
Distortion and Noise Response
HD2
HD3
IMD3
2nd Harmonic Distortion
VOUT = 2 VPP, f = 20 MHz, RL = 800Ω
−79
VOUT = 2 VPP, f = 70 MHz, RL = 800Ω
−78
VOUT = 2 VPP, f = 20 MHz, RL = 800Ω
−90
VOUT = 2 VPP, f = 70 MHz, RL = 800Ω
−71
fc = 20 MHz, , VOUT = 2 VPP Composite,
RL = 200Ω
−92
fc = 150 MHz, , VOUT = 2 VPP Composite,
RL = 200Ω
−76
Input Noise Voltage
f = 100 kHz
1.2
nV/√Hz
Input Noise Current
f = 100 kHz
13.6
pA/√Hz
Noise Figure (See Figure 58)
50Ω System, AV = 9, 10 MHz
10.3
dB
3rd Harmonic Distortion
3rd-Order Two-Tone
Intermodulation
dBc
dBc
dBc
Input Characteristics
IBI
Input Bias Current
(4)
(3)
IBoffset
Input Bias Current Differential
CMRR
Common Mode Rejection Ratio
RIN
(3)
VCM = 0V, VID = 0V, IBoffset = (IB - IB )/2
−
+
−95
50
95
−18
2.5
18
µA
µA
DC, VCM = 0V, VID = 0V
82
dBc
Input Resistance
Differential
15
Ω
CIN
Input Capacitance
Differential
0.5
pF
CMVR
Input Common Mode Voltage
Range
CMRR > 38 dB
±3.6
V
(1)
(2)
(3)
(4)
±3.3
Electrical Table values apply only for factory testing conditions at the temperature indicated. Factory testing conditions result in very
limited self-heating of the device such that TJ = TA. No specification of parametric performance is indicated in the electrical tables under
conditions of internal self-heating where TJ > TA. See Application Information for information on temperature de-rating of this device."
Min/Max ratings are based on product characterization and simulation. Individual parameters are tested as noted.
Limits are 100% production tested at 25°C. Limits over the operating temperature range are specified through correlation using
Statistical Quality Control (SQC) methods.
Typical values represent the most likely parametric norm as determined at the time of characterization. Actual typical values may vary
over time and will also depend on the application and configuration. The typical values are not tested and are not ensured on shipped
production material.
Exceeding limits could result in excessive device current.
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SNOSB07H – SEPTEMBER 2008 – REVISED MARCH 2013
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VS = ±5V Electrical Characteristics (1) (continued)
Unless otherwise specified, all limits are ensured for TA = 25°C, VS = ±5V, AV = 1, VCM = 0V, VCLAMP = 3V, RF = RG = 275Ω,
RL = 200Ω, for single-ended in, differential out. Boldface limits apply at the temperature extremes.
Symbol
Parameter
Conditions
Min
(2)
Typ
(3)
Max
(2)
Units
Output Performance
(5)
Output Voltage Level
IOUT
Linear Output Current
ISC
Short Circuit Current
(5)
Single-Ended Output
−3.7
±3.78
VOUT = 0V
±100
±120
mA
±150
mA
One Output Shorted to Ground VIN = 2V
Single-Ended (6)
+3.7
V
Clamp Performance
VCLAMP
VCLAMP Voltage Range
VCLAMP Peak Voltage
Continuous Operation
(7)
VCM
VCM +
2.0
(8)
VCM +
3.0
Default VCLAMP Voltage
VCLAMP Floating
0.92
1.0
1.08
Upper Clamp Level Accuracy
VCLAMP = 2V, VCM = 1.5V, VO = 2V, 100%
Overdrive
−53
−40
+53
Lower Clamp Level Accuracy
VCLAMP = 2V, VCM = 1.5V, VO = 1V, 100%
Overdrive
−30
−8
+30
VIN = 0V, VCLAMP(MIN) = −3.1 V
−200
−175
−0.1
Clamp Accuracy Temperature Drift
Clamp Pin Bias Current
VIN = 0V, VCLAMP(MAX) = +4.5V
150
Clamp Pin Bias Drift
Linear to Clamped Operation
Clamp Pin Input Impedance
V
mV
mV/°C
175
0.3
Diff Amp Input Bias Shift
V
µA
µA/°C
60
µA
30
1
KΩ/pF
Clamp Pin Feedthrough
f = 10 MHz
−60
dB
Clamp Bandwidth
0.5VDC + 40 mVPP, SE VIN = 2V
140
MHz
Clamp Slew Rate
100% Overdrive
64
V/µs
Clamp Overshoot
VIN = 2V Step, AV = 2 V/V, VCLAMP = 0.5V,
VCM = 0V, 100% Overdrive
125
mV
Clamp Overshoot
VIN = 2V Step, AV = 2 V/V, VCLAMP = 2V,
VCM = 1.5V, 100% Overdrive
250
mV
Clamp Overshoot Width
(9)
650
ps
VIN = 2V Step, AV = 2 V/V, VCLAMP = 0.5V,
VCM = 0V, 50% Output Crossing
600
ps
f = 75 MHz, VOD = 2 VPP, RL = 800, SFDR
Down 3 dB
22
mV
Common Mode Small Signal
Bandwidth
VIN+ = VIN− = 0
220
MHz
Slew Rate
VIN+ = VIN− = 0
Output Common Mode Error
Common Mode, VIN = Float, VCM = 0
Clamp Overdrive Recovery Time
Linearity Guardband
(10)
Output Common Mode Control Circuit
VOSCM
340
−25
1
V/μs
25
mV
(5)
Typical values represent the most likely parametric norm as determined at the time of characterization. Actual typical values may vary
over time and will also depend on the application and configuration. The typical values are not tested and are not ensured on shipped
production material.
(6) Short circuit current should be limited in duration to no more than 10 seconds. See POWER DISSIPATION in Application Information for
more details.
(7) Exceeding limits could result in excessive device current.
(8) This parameter is ensured by design and/or characterization and is not tested in production. The condition of VCLAMP = 3V is not
intended for continuous operation; continuous operation with VCLAMP = 3V may incur permanent damage to the device.
(9) Clamp Overshoot Width is the duration of overshoot in a 100% overdrive condition.
(10) Linearity Guardband is defined for an output sinusoid (f = 75 MHz, VOD = 2 VPP). It is the difference between the VCLAMP level and the
peak output voltage where the SFDR is decreased by 3 dB.
4
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SNOSB07H – SEPTEMBER 2008 – REVISED MARCH 2013
VS = ±5V Electrical Characteristics (1) (continued)
Unless otherwise specified, all limits are ensured for TA = 25°C, VS = ±5V, AV = 1, VCM = 0V, VCLAMP = 3V, RF = RG = 275Ω,
RL = 200Ω, for single-ended in, differential out. Boldface limits apply at the temperature extremes.
Symbol
Parameter
Conditions
Input Bias Current
VCM(TYPICAL) = 0,
(11)
VCM(MIN) = −3.2 V,
(11)
VCM(MAX) = +3.2V,
(11)
Voltage Range
Min
(2)
(3)
−8
−3.5
−9
−4.5
−2.5
±3.14
CMRR
Typ
Measure VOD, VID = 0V
Input Resistance
Max
(2)
µA
2
±3.18
V
80
dB
200
ΔVO,CM/ΔVCM
Gain
0.995
Units
1
1.00
kΩ
1.008
V/V
Miscellaneous Performance
ZT
Open Loop Transimpedance
Differential
112
PSRR
Power Supply Rejection Ratio
DC, ΔVS = ±1V
87
IS
Supply Current
RL = ∞
25
dBΩ
dB
29.1
33
37
mA
(11) Negative current implies current flowing out of the device.
VS = ±2.5V Electrical Characteristics
(1)
Unless otherwise specified, all limits are ensured for TA = 25°C, VS = ±2.5V, AV = 1, VCM = 0V, VCLAMP = 2V, RF = RG = 275Ω,
RL = 200Ω, for single-ended in, differential out. Boldface limits apply at the temperature extremes.
Symbol
Parameter
Conditions
Min
(2)
Typ
(3)
Max
(2)
Units
AC Performance (Differential)
SSBW
LSBW
Small Signal −3 dB Bandwidth
Large Signal −3 dB Bandwidth
(2)
VOUT = 0.2 VPP, AV = 1, RL = 1 kΩ
875
VOUT = 0.2 VPP, AV = 1
630
VOUT = 0.2 VPP, AV = 2
580
VOUT = 0.2 VPP, AV = 4
540
VOUT = 0.2 VPP, AV = 8 , (RF = 400Ω, RG =
50Ω)
315
VOUT = 2 VPP, AV = 1, RL = 1 kΩ
640
VOUT = 2 VPP, AV = 1
485
VOUT = 2 VPP, AV = 2
435
VOUT = 2 VPP, AV = 4
420
VOUT = 2 VPP, AV = 8, (RF = 400Ω, RG = 50Ω)
405
MHz
MHz
0.1 dB Bandwidth
VOUT = 0.2 VPP, AV = 1
60
MHz
0.5 dB Bandwidth
VOUT = 0.2 VPP, AV = 1
236
MHz
Slew Rate
2V Step, AV = 1
1350
V/μs
Rise/Fall Time, 10%-90%
2V Step
860
ps
0.1% Settling Time
2V Step
10
ns
1.0% Settling Time
2V Step
6
ns
Distortion and Noise Response
HD2
(1)
(2)
(3)
2nd Harmonic Distortion
VOUT = 2 VPP, f = 20 MHz, RL = 800Ω
−80
VOUT = 2 VPP, f = 70 MHz, RL = 800Ω
−72
dBc
Electrical Table values apply only for factory testing conditions at the temperature indicated. Factory testing conditions result in very
limited self-heating of the device such that TJ = TA. No specification of parametric performance is indicated in the electrical tables under
conditions of internal self-heating where TJ > TA. See Application Information for information on temperature de-rating of this device."
Min/Max ratings are based on product characterization and simulation. Individual parameters are tested as noted.
Limits are 100% production tested at 25°C. Limits over the operating temperature range are specified through correlation using
Statistical Quality Control (SQC) methods.
Typical values represent the most likely parametric norm as determined at the time of characterization. Actual typical values may vary
over time and will also depend on the application and configuration. The typical values are not tested and are not ensured on shipped
production material.
Submit Documentation Feedback
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LMH6553
SNOSB07H – SEPTEMBER 2008 – REVISED MARCH 2013
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VS = ±2.5V Electrical Characteristics (1) (continued)
Unless otherwise specified, all limits are ensured for TA = 25°C, VS = ±2.5V, AV = 1, VCM = 0V, VCLAMP = 2V, RF = RG = 275Ω,
RL = 200Ω, for single-ended in, differential out. Boldface limits apply at the temperature extremes.
Symbol
HD3
IMD3
Parameter
Conditions
rd
3 Harmonic Distortion
3rd-Order Two-Tone
Intermodulation
Min
(2)
Typ
(3)
VOUT = 2 VPP, f = 20 MHz, RL = 800Ω
−78
VOUT = 2 VPP, f = 70 MHz, RL = 800Ω
−66
fc = 20 MHz, VOUT = 2 VPP Composite,
RL = 200Ω
−87
fc = 150 MHz, VOUT = 2 VPP Composite,
RL = 200Ω
−68
Max
(2)
Units
dBc
dBc
Input Noise Voltage
f = 100 kHz
1.1
nV/√Hz
Input Noise Current
f = 100 kHz
13.6
pA/√Hz
Noise Figure (See Figure 58)
50Ω System, AV = 9, 10 MHz
10.3
dB
Input Characteristics
(4) (5)
IBI
Input Bias Current
IBoffset
Input Bias Current Differential
(3)
(3)
(5)
−90
45
90
µA
VCM = 0V, VID = 0V, IBoffset = (IB− - IB+)/2
−24
2
24
µA
CMRR
Common Mode Rejection Ratio
DC, VCM = 0V, VID = 0V
80
RIN
Input Resistance
Differential
15
dBc
Ω
CIN
Input Capacitance
Differential
0.5
pF
CMVR
Input Common Mode Voltage
Range
CMRR > 38 dB
±1.0
±1.2
V
Output Performance
Output Voltage Swing
(3)
Differential Output
5.32
5.47
VPP
IOUT
Linear Output Current
(3)
VOUT = 0V
±75
±95
mA
ISC
Short Circuit Current
±140
mA
One Output Shorted to Ground VIN = 2V
Single-Ended (6)
Clamp Performance
VCLAMP
VCLAMP Voltage Range
VCLAMP Peak Voltage
Continuous Operation
(7)
VCLAMP Floating
0.42
0.48
0.54
Upper Clamp Level Accuracy
VIN = 0V, VCLAMP = +0.5V, VCM = 0, VO =
+0.5V,
100% Overdrive
−39
−30
+39
Lower Clamp Level Accuracy
VIN = 0V, VCLAMP = +0.5V, VCM = 0, VO =
−0.5V,
100% Overdrive
−18
6
+18
VIN = 0V, VCLAMP = 1V, VCM = 0
Clamp Pin Bias Drift
Diff Amp Input Bias Shift
Linear to Clamped Operation
Clamp Pin Input Impedance
6
V
VCM +
3.0
Default VCLAMP Voltage
Clamp Pin Bias Current
(7)
(8)
VCM +
2.0
(8)
Clamp Accuracy Temperature Drift
(4)
(5)
(6)
VCM
V
mV
−0.1
mV/°C
23.5
µA
0.3
µA/°C
50
µA
30
1
kΩ/pF
Clamp Pin Feedthrough
f = 10 MHz
−60
dB
Clamp Bandwidth
0.5VDC + 40 mVPP, SE VIN = 2V
125
MHz
Clamp Slew Rate
100% Overdrive
52
V/µs
Exceeding limits could result in excessive device current.
IBI is referred to a differential output offset voltage by the following relationship: VOD(offset) = IBI*2RF
Short circuit current should be limited in duration to no more than 10 seconds. See POWER DISSIPATION in Application Information for
more details.
Exceeding limits could result in excessive device current.
This parameter is ensured by design and/or characterization and is not tested in production. The condition of VCLAMP = 3V is not
intended for continuous operation; continuous operation with VCLAMP = 3V may incur permanent damage to the device.
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SNOSB07H – SEPTEMBER 2008 – REVISED MARCH 2013
VS = ±2.5V Electrical Characteristics (1) (continued)
Unless otherwise specified, all limits are ensured for TA = 25°C, VS = ±2.5V, AV = 1, VCM = 0V, VCLAMP = 2V, RF = RG = 275Ω,
RL = 200Ω, for single-ended in, differential out. Boldface limits apply at the temperature extremes.
Symbol
Parameter
Conditions
Min
(2)
Typ
(3)
Max
(2)
Units
Clamp Overshoot
VIN = 1V Step, AV = 2 V/V, VCLAMP = 0.5V,
VCM= 0V, 100% Overdrive
105
mV
Clamp Overshoot
VIN = 1V Step, AV= 2 V/V, VCLAMP = 1V,
VCM = 0.5V, 100% Overdrive
105
mV
650
ps
VIN = 2V Step, AV = 2 V/V, VCLAMP = 0.5V,
VCM = 0V, 50% Output Crossing
600
ps
f = 75 MHz, VOD = 2 VPP, RL = 800, SFDR
Down 3 dB
40
mV
Common Mode Small Signal
Bandwidth
VIN+ = VIN− = 0
130
MHz
Slew Rate
VIN+ = VIN− = 0
Output Common Mode Error
Common Mode, VIN = float, VCM = 0
Input Bias Current
VCM = 0,
(9)
Clamp Overshoot Width
Clamp Overdrive Recovery Time
Linearity Guardband
(10)
Output Common Mode Control Circuit
VOSCM
(11)
Voltage Range
CMRR
186
−20
V/μs
20
−3.5
±0.75
Measure VOD, VID = 0V
Input Resistance
Gain
2
µA
±0.81
V
84
dB
200
ΔVO,CM/ΔVCM
0.995
mV
1.00
kΩ
1.008
V/V
Miscellaneous Performance
ZT
Open Loop Transimpedance
Differential
105
dBΩ
PSRR
Power Supply Rejection Ratio
DC, ΔVS = ±1V
85
dB
IS
Supply Current
RL = ∞
23
26.5
30
34
mA
(9) Clamp Overshoot Width is the duration of overshoot in a 100% overdrive condition.
(10) Linearity Guardband is defined for an output sinusoid (f = 75 MHz, VOD = 2 VPP). It is the difference between the VCLAMP level and the
peak output voltage where the SFDR is decreased by 3 dB.
(11) Negative current implies current flowing out of the device.
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CONNECTION DIAGRAM
-IN
VCM
V+
+OUT
1
8
2
-
+
7
+IN
VCLAMP
6
3
V-
5
4
-OUT
DAP
Figure 2. 8-Pin SO PowerPAD
Top View
-IN
1
8
+IN
VCM
2
7
VCLAMP
V+
3
6
V-
+OUT
4
5
-OUT
DAP
Figure 3. 8-Pin WSON
Top View
8
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PIN DESCRIPTIONS
Pin No.
Pin Name
Description
1
-IN
Negative Input
2
VCM
Output Common Mode Control
3
V+
Positive Supply
4
+OUT
Positive Output
5
-OUT
Negative Output
6
V-
Negative Supply
7
VCLAMP
Output Voltage Clamp Control
8
+IN
Positive Input
DAP
DAP
Die Attach Pad (See THERMAL
PERFORMANCE for more information)
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Typical Performance Characteristics VS = ±5V
(TA = 25°C, RF = RG = 275Ω, RL = 200Ω, AV = 1, for single ended in, differential out, unless specified).
Frequency Response vs. Gain
1
AV = 1
0
-3
AV = 8
-4
-1
NORMALIZED GAIN (dB)
AV = 4
-2
-5
-6
-7
-3
-5
-6
-7
NORMALIZED GAIN (dB)
1000
-9
1
10000
10
100
FREQUENCY (MHz)
Figure 5.
Frequency Response vs. VOUT
-9
VO = 0.5 VPP
VOD = 0.5 VPP
-8
VO = 2 VPP
VO = 4 VPP
-4
-5
-6
-7 VS = +5V
-8 AV = 2V/V
DIFFERENTIAL INPUT
-9
1
10
100
1000
FREQUENCY (MHz)
10000
-7
VOD = 2 VPP
-6
-5
VOD = 4 VPP
-4
-3
-2
-1 VS = +5V
0 AV = 2V/V
SINGLE-ENDED INPUT
1
1
10
100
1000
FREQUENCY (MHz)
0
2
1
-1
-2
VS = +2.5V
-4
RL = 200Ö
-5
RF = 275Ö
-6
-7 VOD = 0.2 VPP
-8 AV = 1 V/V
DIFFERENTIAL INPUT
-9
1
10
100
3
RL = 200Ö
RF = 275Ö
-3
Frequency Response vs. Supply Voltage (RL = 1 kΩ)
VS = +5V
NORMALIZED GAIN (dB)
NORMALIZED GAIN (dB)
1
10000
Figure 7.
Frequency Response vs. Supply Voltage (RL = 200Ω)
2
10000
Frequency Response vs. VOUT
Figure 6.
10
1000
Figure 4.
-2
-3
VOUT = 0.2 VPP
SINGLE-ENDED INPUT
-8
FREQUENCY (MHz)
0
-1
AV = 8
-4
NORMALIZED GAIN (dB)
1
AV = 4
-2
-8
VOUT = 0.2 VPP
-9 DIFFERENTIAL INPUT
-10
1
10
100
AV = 1
AV = 2
0
AV = 2
-1
NORMALIZED GAIN (dB)
Frequency Response vs. Gain
1
0
-1
VS = +2.5V
-2
RL = 1 kÖ
-3
RF = 225Ö
-4
VS = +5V
-5
RL = 1 kÖ
-7
-8
1000
10000
RF = 225Ö
-6
-9
1
VOD = 0.2 VPP
AV = 1 V/V
DIFFERENTIAL INPUT
FREQUENCY (MHz)
10
100
1000
FREQUENCY (MHz)
Figure 8.
Figure 9.
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Typical Performance Characteristics VS = ±5V (continued)
(TA = 25°C, RF = RG = 275Ω, RL = 200Ω, AV = 1, for single ended in, differential out, unless specified).
Frequency Response vs. Capacitive Load
Suggested RO vs. Capacitive Load
-9
60
CL = 82 pF, RO =16Ö
-7
50
SUGGESTED RO (Ö)
NORMALIZED GAIN (dB)
-8
CL = 39 pF, RO = 21Ö
-6
-5
CL = 15 pF, RO = 30Ö
-4
CL = 5.6 pF, RO = 40Ö
-3
-2 VOD = 200 mVPP
-1 AV = 1 V/V
0
1
40
30
20
10
LOAD = (CL || 1 kÖ) IN
1
10
VS = +5V
LOAD = 1 kÖ || CAP LOAD
SERIES WITH 2 ROUTS
0
100
1
1000
10
Figure 10.
Figure 11.
Frequency Response vs. Resistive Load
Frequency Response vs. Resistive Load
3
3
2
RL = 1 kÖ, RF = 400Ö
RL = 800Ö
1
0
NORMALIZED GAIN (dB)
NORMALIZED GAIN (dB)
RL = 1 kÖ, RF = 400Ö
2
1
RL = 500Ö
-1
-2
-3
RL = 200Ö
-4
-5
VS = +5V
-6
AV = 1V/V
-7
RF = 275Ö
RL = 800Ö
0
-1
RL = 500Ö
-2
-3
RL = 200Ö
-4
-5
-6
-7
VOUT = 0.2 VPP
-8
SINGLE-ENDED INPUT
-9
1
10
100
1000
FREQUENCY (MHz)
VS = +5V
AV = 1V/V
RF = 275Ö
VOUT = 2 VPP
-8
SINGLE-ENDED INPUT
-9
1
10
100
1000
FREQUENCY (MHz)
10000
Figure 12.
10000
Figure 13.
Frequency Response vs. RF
1 VPP Pulse Response Single-Ended Input
-0.8
3
2
100
CAPACITIVE LOAD (pF)
FREQUENCY (MHz)
RF = 200Ö
-0.6
-0.4
0
-1
-2
-3
-0.2
RF = 275Ö
VOD (V)
NORMALIZED GAIN (dB)
1
RF = 350Ö
-4
0
VS = +2.5V
0.2
-5
RL = 200Ö
-6 AV = 1 V/V
-7 VOUT = 2 VPP
RL = 1 kÖ
-8
DIFFERENTIAL INPUT
-9
1
10
100
0.4
RF = 275Ö
0.6
VCLAMP = 3V
VCM = 0V
0.8
1000
10000
FREQUENCY (MHz)
Figure 14.
0
5
10
15 20 25
TIME (ns)
30
35
40
Figure 15.
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Typical Performance Characteristics VS = ±5V (continued)
(TA = 25°C, RF = RG = 275Ω, RL = 200Ω, AV = 1, for single ended in, differential out, unless specified).
2 VPP Pulse Response Single-Ended Input
4 VPP Pulse Response Single-Ended Input
-2.5
1.5
-2.0
1.0
-1.5
-1.0
0.0
VS = +5V
-0.5
-0.5
VOD (V)
0.0
RL = 200Ö
RF = 275Ö
-1.0
VS = +5V
1.0
RL = 200Ö
RF = 275Ö
1.5
VCLAMP = 3V
VCLAMP = 3V
2.0
VCM = 0V
-1.5
VCM = 0V
2.5
0
5
10
15
20
25
30
35
40
0
1.5
10
3.0
VOD (V)
2.0
0
VS = +5V
1.0
AV = 2V/V
RL = 200Ö
0.5
RL = 200Ö
VCM = 1.5V
VCM = 0V
0
0
10 15 20 25 30 35 40 45 50
5
TIME (ns)
10 15 20 25 30 35 40 45 50
TIME (ns)
Figure 18.
Figure 19.
Overdrive Recovery with VS = ±5V
2.0
4.8
8
1.6
6
1.2
OUTPUT VOLTAGE (VOD)
INPUT
0.8
2
0.4
0
0
-2
-0.4
-4
-0.8
-6
-1.2
-10
-12
0
OUTPUT
VCLAMP = 3V
200
400
600
VS = +5V
AV = 5 V/V -1.6
RF = 275Ö -2.0
RL = 200Ö
-2.4
800
1000
OUTPUT VOLTAGE (VOD)
10
INPUT VOLTAGE (V)
6.0
-8
12
Overdrive Recovery with VS = ±2.5V
2.4
OUTPUT
VCLAMP = 0.5V
40
100% Overdrive
VCLAMP = 2V
0% Overdrive
VCLAMP = 2.5V
AV = 2V/V
4
35
1.5
VS = +5V
12
30
Pulse Response with 0% and 100% Overdrive
100% Overdrive
VCLAMP = 0.5V
0.5
5
25
Figure 17.
2.5
-1.5
0
20
Figure 16.
1.0
-1.0
15
TIME (ns)
0% Overdrive
VCLAMP = 1V
-0.5
5
TIME (ns)
Pulse Response with 0% and 100% Overdrive
VOD (V)
0.5
INPUT
1.2
0.8
3.6
OUTPUT
VCLAMP = 0.5V
2.4
1.2
0.4
0
0
-1.2
-0.4
-2.4
-3.6
-4.8
-6.0
0
OUTPUT
VCLAMP = 3V
200
400
600
TIME (ns)
TIME (ns)
Figure 20.
Figure 21.
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VS = +2.5V
AV = 5 V/V -0.8
RF = 275Ö
RL = 200Ö
-1.2
800
1000
INPUT VOLTAGE (V)
VOD (V)
0.5
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Typical Performance Characteristics VS = ±5V (continued)
(TA = 25°C, RF = RG = 275Ω, RL = 200Ω, AV = 1, for single ended in, differential out, unless specified).
Output Common Mode Pulse Response
-50
-45
-40
-50
-30
-55
DISTORTION (dBc)
COMMON MODE VOUT (mV)
Distortion vs. Frequency Single-Ended Input (RL=800Ω)
-40
-60
-20
-10
0
10
20
VS = +5V
30
RL = 200Ö
40
RF = 275Ö
50
VOD = 2VPP
5
-60
-65
-70
VS = +5V
-75
RL = 800Ö
-80
VOD = 2VPP
HD2
-85
RF = 275Ö
-90
VCLAMP = 3V
-95
VCM = 0V
-100
10 30 50 70 90 110 130 150 170 190
FREQUENCY (MHz)
60
0
HD3
10 15 20 25 30 35 40 45 50
TIME (ns)
Figure 22.
Figure 23.
Distortion vs. Supply Voltage (fc=20Mhz, RL=800Ω)
Distortion vs. Supply Voltage (fc=75Mhz, RL=800Ω)
-50
-40
RL = 800Ö
VOD = 2 VPP
VCLAMP = 3V
VCM = 0
fc = 20 MHz
DISTORTION (dBc)
-60
-65
-50
-70
HD2
-75
-80
-85
-95
4
-55
-65
-70
-75
-80
HD2
-90
5
-10
6
7
8
9
10
11
-95
4
12
6
7
8
9
10
11
TOTAL SUPPLY VOLTAGE (V)
Figure 24.
Figure 25.
Distortion vs.
VCM (fc=20Mhz, RL=800Ω)
Distortion vs.
VCM (fc=75Mhz, RL=800Ω)
-10
12
VS = +5V
-20
VOD = 2VPP
-40
VCLAMP = 3V
DISTORTION (dBc)
RL = 800Ö
-30
HD3
fc = 20 MHz
-50
5
TOTAL SUPPLY VOLTAGE (V)
VS = +5V
-20
DISTORTION (dBc)
HD3
-60
-85
HD3
-90
RL = 800Ö
VOD = 2 VPP
VCLAMP = 3V
VCM = 0
fc = 75 MHz
-45
DISTORTION (dBc)
-55
-60
-70
HD2
-30
RL = 800Ö
VOD = 2VPP
VCLAMP = 3V
-40
fc = 75 MHz
-50
HD3
-60
-70
-80
-90
-80
-100
-90
0
HD2
0
0.5
1
1.5
2
2.5
3
0.5
1
1.5
VCM (V)
VCM (V)
Figure 26.
Figure 27.
2
2.5
3
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Typical Performance Characteristics VS = ±5V (continued)
(TA = 25°C, RF = RG = 275Ω, RL = 200Ω, AV = 1, for single ended in, differential out, unless specified).
Distortion vs.
Frequency Single-Ended Input (RL=200Ω)
Distortion vs.
Supply Voltage (fc=20Mhz, RL=200Ω)
-35
-50
-40
-55
-45
DISTORTION (dBc)
DISTORTION (dBc)
-60
HD3
-50
-55
-60
-65
-70
-75
VS = ±5V
RL = 200Ö
VOD = 2VPP
RF = 275Ö
VCLAMP = 3V
VCM = 0V
-80
-85
HD2
-90
-95
-65
-70
-75
HD2
-80
-85
-90
-95
HD3
-100
-105
4
-100
10 30 50 70 90 110 130 150 170 190 200
5
6
7
8
9
10
11
FREQUENCY (MHz)
TOTAL SUPPLY VOLTAGE (V)
Figure 28.
Figure 29.
Distortion vs.
Supply Voltage (fc=75Mhz, RL=200Ω)
Distortion vs.
VCM (fc=20Mhz, RL=200Ω)
-40
12
-10
-50
-55
DISTORTION (dBc)
RL = 200Ö
VOD = 2VPP
VCLAMP = 3V
VCM = 0V
fc = 75 MHz
-45
DISTORTION (dBc)
RL = 200Ö
VOD = 2VPP
VCLAMP = 3V
VCM = 0V
fc = 20 MHz
-60
-65
HD3
-70
HD2
VS = ±5V
-20 RL = 200Ö
VOD = 2 VPP
-30 VCLAMP = 3V
fc = 20MHz
-40
HD3
-50
-60
HD2
-70
-75
-80
-80
-90
-85
4
-100
0
HD3
14
5
6
7
8
9
10
11
12
0.5
1
1.5
2
TOTAL SUPPLY VOLTAGE (V)
VCM (V)
Figure 30.
Figure 31.
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3
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Typical Performance Characteristics VS = ±5V (continued)
(TA = 25°C, RF = RG = 275Ω, RL = 200Ω, AV = 1, for single ended in, differential out, unless specified).
Distortion vs.
VCM (fc=75Mhz, RL=200Ω)
Maximum VOUT vs.
IOUT
4.5
VS = ±5V
R = 200Ö
-20.0 L
VOD = 2 VPP
V
= 3V
-30.0 CLAMP
fc = 75MHz
HD2
4
MAXIMUM VOUT (V)
DISTORTION (dBc)
-10.0
-40.0
-50.0
HD3
-60.0
-70.0
3.5
3 VS = +5V
RF = 275Ö
VCM = 3V
2.5
VCLAMP = 5V
-80.0
VIN = 3.5V SINGLE-ENDED INPUT
HD2
2
-90.0
0
0.5
1
1.5
2
2.5
0
3
20
40
VCM (V)
Figure 32.
80
Figure 33.
Minimum VOUT vs.
IOUT
Closed Loop Output Impedance
-2
1000
VS = +5V
RF = 275Ö
100
-2.5 VCM = -3V
VCLAMP = -1V
VS = +5V
VIN = 0V
AV = 1 V/V
10
VIN = -3.5V SINGLE-ENDED INPUT
1
Z (:)
MINIMUM VOUT (V)
60
OUTPUT CURRENT (mA)
-3
0.1
0.01
-3.5
0.001
0.0001
0.01
-4
0
20
40
60
OUTPUT CURRENT (mA)
80
1000
Figure 35.
Closed Loop Output Impedance
Open Loop Transimpedance
1000
120
VS = +2.5V
VIN = 0V
AV = 1 V/V
1
0.1
0.01
0.001
0.0001
0.01
MAGNITUDE
100
90
0
80
PHASE
70
PHASE (°)
MAGNITUDE, |Z| (dB Ö)
110
10
Z (:)
100
FREQUENCY (MHz)
Figure 34.
100
10
1
0.1
-45
-90
60
-135
50
VS = +5V
0.1
1
10
100
1000
40
0.01
FREQUENCY (MHz)
0.1
1
10
100
-180
1000
FREQUENCY (MHz)
Figure 36.
Figure 37.
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Typical Performance Characteristics VS = ±5V (continued)
(TA = 25°C, RF = RG = 275Ω, RL = 200Ω, AV = 1, for single ended in, differential out, unless specified).
Open Loop Transimpedance
PSRR
120
100
90
100
90
0
80
PHASE
70
-45
-90
60
PSRR (dBc DIFFERENTIAL)
MAGNITUDE
PHASE (°)
MAGNITUDE, |Z| (dB Ö)
110
-135
50
VS = +2.5V
40
0.01
0.1
1
10
100
-180
1000
80
-PSRR
70
60
50
+PSRR
40
30 AV = 2 V/V
20 RL = 200Ö
VIN = 0V
10 VCM = 0V
VCLAMP = 3V
0
0.1
1
10
100
FREQUENCY (MHz)
FREQUENCY (MHz)
Figure 38.
Figure 39.
PSRR
1000
CMRR
80
90.0
-PSRR
80.0
60
50
70.0
+PSRR
CMRR (dB)
PSRR (dBc DIFFERENTIAL)
70
40
30
20
60.0
50.0
40.0
AV = 2 V/V
RL = 200Ö
VOUT = 1.0 VPP
VCM = 0V
VCLAMP = 3V
30.0
AV = 2 V/V
RL = 200Ö
10 V = 0V
IN
VCM = 0V
0
0.1
1
20.0
10
100
10.0
1.0e-1
1000
FREQUENCY (MHz)
1.0
1.0e1
1.0e2
1.0e3
FREQUENCY (MHz)
Figure 40.
Figure 41.
Balance Error
Noise Figure
-15
14
-20
VS = +2.5V
13
-30
NOISE FIGURE (dB)
BALANCE ERROR (dBc)
-25
-35
-40
VS = +5V
-45
-50
-55
-60
RL = 200Ö
RF = 274Ö
AV = 1 V/V
-65
-70
1
10
100
12
11
10
1000
FREQUENCY (MHz)
20 40 60 80 100 120 140 160 180 200
FREQUENCY (MHz)
Figure 42.
16
9
0
AV = 9 V/V
RF = 275Ö
VCM = 0V
VCLAMP = 3V
50Ö SYSTEM
Figure 43.
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Typical Performance Characteristics VS = ±5V (continued)
(TA = 25°C, RF = RG = 275Ω, RL = 200Ω, AV = 1, for single ended in, differential out, unless specified).
Noise Figure
Differential S-Parameter Magnitude vs. Frequency
10
AV = 9 V/V
RF = 275Ö
13 VCM = 0V
VCLAMP = 3V
50Ö SYSTEM
0
S21
-10
MAGNITUDE (dB)
NOISE FIGURE (dB)
14
12
11
10
S11
-20 (SINGLE-ENDED
INPUT)
-30
-40
-50
S22
S11
-60
-70
9
0
-90
10
20 40 60 80 100 120 140 160 180 200
Figure 44.
Figure 45.
3rd Order Intermodulation Products vs. VOUT
-50
VS = ±5V
-55 RF = 324Ö
A = 2 V/V
-60 V
VCM = 0V
-65 VCLAMP = 3V
S22
100
50
IMD3 (dBc)
PHASE (°)
S21
-50
S12
S11
-150
S11
-200
(SINGLE-ENDED
INPUT)
-250
VS = +5V
-300 AV = 1 V/V
50: SYSTEM
-350
10
100
RL = 800Ö
-70
RL = 200Ö
-75
-80
-85
-90
fc = 75 MHz (2MHz SPACING)
SINGLE-ENDED INPUT
-95
-100
1
1000
2
3
4
5
6
FREQUENCY (MHz)
DIFFERENTIAL VOUT (VPP)
Figure 46.
Figure 47.
3rd Order Intermodulation Products vs. VOUT
3rd Order Intermodulation Products vs. Center Frequency
-30
-50
VS = ±2.5V
RF = 324Ö
-40 AV = 2 V/V
VCM = 0V
-50 VCLAMP = 3V
RL = 200Ö
IMD3 (dBc)
IMD3 (dBc)
1000
FREQUENCY (MHz)
Differential S-Parameter Phase vs. Frequency
-100
100
FREQUENCY (MHz)
150
0
VS = +5V
AV = 1 V/V
50: SYSTEM
S12
-80
-60
-70
RL = 800Ö
VS = ±5V
-55 RL = 200Ö
RF = 324Ö
-60
AV = 2 V/V
-65 VOD = 2 VPP
VCLAMP = 3V
-70
VCM = 1.5V
-75
-80
VCM = 0V
-85
-80
-90
-90
-100
1
fc = 75 MHz (2MHz SPACING)
SINGLE-ENDED INPUT
2
3
4
SINGLE-ENDED INPUT
2MHz SPACING
-95
5
-100
25
50
75
100
125
DIFFERENTIAL VOUT (VPP)
CENTER FREQUENCY (MHz)
Figure 48.
Figure 49.
150
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Typical Performance Characteristics VS = ±5V (continued)
(TA = 25°C, RF = RG = 275Ω, RL = 200Ω, AV = 1, for single ended in, differential out, unless specified).
3rd Order Intermodulation Products vs. Center Frequency
3rd Order Intermodulation Products vs. Center Frequency
-30
VS = ±5V
-55 RF = 324Ö
RL = 800Ö
-60 AV = 2 V/V
V = 2 VPP
-65 OD
VCLAMP = 3V
-70
VS = ±2.5V
RL = 200Ö
-40 RF = 324Ö
AV = 2 V/V
-50 VOD = 2 VPP
VCLAMP = 2V
VCM = 1.5V
IMD3 (dBc)
IMD3 (dBc)
-50
-75
-80
-60
-70
VCM = 0V
-85
VCM = 1.5V
VCM = 0V
-80
-90
-100
25
-90
SINGLE-ENDED INPUT
2MHz SPACING
-95
50
75
100
125
150
-100
25
SINGLE-ENDED INPUT
2 MHz SPACING
50
75
100
125
150
CENTER FREQUENCY (MHz)
CENTER FREQUENCY (MHz)
Figure 50.
Figure 51.
3rd Order Intermodulation Products vs. Center Frequency
3rd Order Intermodulation Products vs. VCLAMP
-30
-30
VS = ±5V
VCM = 1.5V
RL = 200Ö
-50
-60
-70
VCM = 0V
fc = 150 Mhz
VOD = 2 VPP
-60
-70
AV = 2 V/V
VCM = 0V
fc = 50 Mhz
-80
-80
-90
-90
-100
25
RF = 324Ö
-40
IMD3 (dBc)
IMD3 (dBc)
VS = ±2.5V
RL = 800Ö
-40 RF = 324Ö
AV = 2V/V
-50 VOD = 2VPP
VCLAMP = 2V
SINGLE-ENDED INPUT
2 MHz SPACING
50
75
100
125
150
SINGLE-ENDED INPUT
2 MHz SPACING
-100
0.5
1.0
1.5
2.0
VCLAMP (V)
2.5
3.0
CENTER FREQUENCY (MHz)
Figure 52.
18
Figure 53.
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APPLICATION INFORMATION
The LMH6553, a fully differential current feedback amplifier with integrated output common mode control and
output limiting clamp, is designed to provide protection of following input stages. The common mode feedback
circuit sets the output common mode voltage independent of the input common mode, as well as forcing the
outputs to be equal in magnitude and opposite in phase, even when only one of the inputs is driven as in single
ended to differential conversion.
The proprietary current feedback architecture of the LMH6553 offers gain and bandwidth independence even at
high values of gain, simply with the appropriate choice of RF1 and RF2. Generally RF1 is set equal to RF2, and RG1
equal to RG2, so that the gain is set by the ratio RF/RG. Matching of these resistors greatly affects CMRR, DC
offset error, and output balance. Resistors with 0.1% tolerances are recommended for optimal performance, and
the amplifier is internally compensated to operate with optimum gain flatness with values of RF between 250Ω
and 350Ω depending on package selection, PCB layout, and load resistance.
The output common mode voltage is set by the VCM pin with a fixed gain of 1 V/V. This pin should be driven by a
low impedance source and should be bypassed to ground with a 0.1 µF ceramic capacitor. Any unwanted signal
coupling into the VCM pin will be passed along to the outputs, reducing the performance of the amplifier. This pin
must not be left floating.
The LMH6553 can be operated with either a single 5V supply or split +5V and −5V supplies. Operation on a
single 5V supply, depending on gain, is limited by the input common mode range; therefore, AC coupling may be
required. For example, in a DC coupled input application on a single 5V supply, with a VCM of 1.5V, the input
common voltage at a gain of 1 will be 0.75V which is outside the minimum 1.5V to 3.5V input common mode
range of the amplifier. The minimum VCM for this application should be greater than 1.5V depending on output
signal swing. Alternatively, AC coupling of the inputs in this example results in equal input and output common
mode voltages, so a 1.5V input common mode would result. Split supplies allow much less restricted AC and DC
coupled operation with optimum distortion performance.
The LMH6553 has a VCLAMP input which allows control of the maximum amplifier output swing to prevent
overdriving of following stages such as sensitive ADC inputs and also provides fast recovery from transients that
would otherwise saturate the signal path.
RECOMMENDED FEEDBACK RESISTOR
The LMH6553 is available in both an 8-pin WSON and SO PowerPAD package. The recommended feedback
resistor, RF, for the WSON package is 275Ω and 325Ω for the SO PowerPAD to give a flat frequency response
with minimal peaking.
FULLY DIFFERENTIAL OPERATION
The LMH6553 is ideal for a fully differential configuration. The circuit shown in Figure 54 is a typical fully
differential application circuit as might be used to drive an analog to digital converter (ADC). In this circuit the
closed loop gain AV = VOUT/ VIN = RF/RG, where the feedback is symmetric. The series output resistors, RO, are
optional and help keep the amplifier stable when presented with a capacitive load. Refer to DRIVING
CAPACITIVE LOADS for details.
RO
RF
RG
VIN
+
a
CL
VCM
RL
VO
RG
VCLAMP
RF
RO
Figure 54. Typical Application
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When driven from a differential source, the LMH6553 provides low distortion, excellent balance, and common
mode rejection. This is true provided the resistors RF, RG and RO are well matched and strict symmetry is
observed in board layout.
275:
50:
61:
RS = 50:
VIN
275:
+
VCM
a
RL
RS = 50:
61:
275:
VCLAMP
50:
275:
Figure 55. Differential S-Parameter Test Circuit
The circuit configuration shown in Figure 55 was used to measure differential S parameters in a 50Ω
environment at a gain of 1 V/V. Refer to Figure 45 and Figure 46 in Typical Performance Characteristics for
measurement results.
SINGLE-ENDED INPUT TO DIFFERENTIAL OUTPUT OPERATION
In many applications, it is required to drive a differential input ADC from a single-ended source. Traditionally,
transformers have been used to provide single to differential conversion, but these are inherently bandpass by
nature and cannot be used for DC coupled applications. The LMH6553 provides excellent performance as a
single-to-differential converter down to DC. Figure 56 shows a typical application circuit where an LMH6553 is
used to produce a differential signal from a single ended source.
RF
AV, RIN
V
RS
VIN
+
RO
RG
+
a
VCM
RT
+
RM
RG
+
-
-
VCLAMP
+
-
§ RG + R M
E2 = ¨¨R + R + R
F
M
© G
§
¨
¨
©
§
¨
¨
©
§
¨
¨
©
§ 2RG + RM (1-E2)
¨
¨
1 + E2
©
§ RG
E1 = ¨R + R
¨ G
F
©
§
¨
¨
©
RIN =
ADC
IN+
RO
V
RF
§ 2(1 - E1)
AV = ¨¨
© E1 + E2
IN-
VOUT
LMH6553
RS = RT || RIN
RM = RT || RS
Figure 56. Single-Ended Input with Differential Output
When using the LMH6553 in single-to-differential mode, the complementary output is forced to a phase inverted
replica of the driven output by the common mode feedback circuit as opposed to being driven by its own
complementary input. Consequently, as the driven input changes, the common mode feedback action results in a
varying common mode voltage at the amplifier's inputs, proportional to the driving signal. Due to the non-ideal
common mode rejection of the amplifier's input stage, a small common mode signal appears at the outputs which
is superimposed on the differential output signal. The ratio of the change in output common mode voltage to
output differential voltage is commonly referred to as output balance error. The output balance error response of
the LMH6553 over frequency is shown in the Typical Performance Characteristics.
20
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To match the input impedance of the circuit in Figure 56 to a specified source resistance, RS, requires that RT ||
RIN = RS. The equations governing RIN and AV for single-to-differential operation are also provided in Figure 56.
These equations, along with the source matching condition, must be solved iteratively to achieve the desired gain
with the proper input termination. Component values for several common gain configurations in a 50Ω
environment are given in Table 1.
Table 1. Gain Component Values for 50Ω System
WSON Package
Gain
RF
RG
RT
RM
0 dB
275Ω
255Ω
59Ω
26.7Ω
6 dB
275Ω
127Ω
68.1Ω
28.7Ω
12 dB
275Ω
54.9Ω
107Ω
34Ω
Table 2. Gain Component Values for 50Ω System
SO PowerPAD Package
Gain
RF
RG
RT
RM
0 dB
325Ω
316Ω
56.2Ω
26.7Ω
6 dB
325Ω
150Ω
64.9Ω
28Ω
12 dB
325Ω
68.1Ω
88.7Ω
31.6Ω
275:
50:
255:
RS = 50:
VIN
a
VCM
59:
+
RL
255:
26.7:
VCLAMP
50:
275:
Figure 57. Single Ended Input S-Parameter Test Circuit (50Ω System)
The circuit shown in Figure 57 was used to measure S-parameters for a single-to-differential configuration.
Figure 45 and Figure 46 in Typical Performance Characteristics are taken using the recommended component
values for 0 dB gain.
SINGLE SUPPLY OPERATION
Single supply operation is possible on supplies from 5V to 10V; however, as discussed earlier, AC input coupling
is recommended for low supplies due to input common mode limitations. An example of an AC coupled, single
supply, single-to-differential circuit is shown in Figure 58. Note that when AC coupling, both inputs need to be AC
coupled irrespective of single-to-differential or differential-to-differential configuration. For higher supply voltages,
DC coupling of the inputs may be possible provided that the output common mode DC level is set high enough
so that the amplifier's inputs and outputs are within their specified operating ranges.
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RF
RG
RS
RO
VO1
VI1
-
+
VIN
a
RT
CL
VCM
RL
+
RG
RM
VOUT
VI2
VO2
RF
RO
VCLAMP
*VCM =
VO1 + VO2
2
*BY DESIGN
VICM = VOCM
VICM =
VI1 + VI2
2
Figure 58. AC Coupled for Single Supply Operation
SPLIT SUPPLY OPERATION
For optimum performance, split supply operation is recommended using +5V and −5V supplies; however,
operation is possible on split supplies as low as +2.25V and −2.25V and as high as +6V and −6V. Provided the
total supply voltage does not exceed the 4.5V to 12V operating specification, asymmetric supply operation is also
possible and in some cases advantageous. For example, if 5V DC coupled operation is required for low power
dissipation but the amplifier input common mode range prevents this operation, it is still possible with split
supplies of (V+) and (V−). Where (V+) - (V−) = 5V and V+ and V− are selected to set the amplifier input common
mode voltage to suit the application.
CLAMP OPERATION
The output clamp allows control of the maximum amplifier output swing to prevent overdriving of following stages
such as sensitive ADC inputs and provide fast recovery from signal transients that would otherwise saturate the
signal path. Figure 59 shows the relationship between VCLAMP and the +OUT and −OUT outputs. The example
circuit shown has a single ended input and is set for a gain of 2 V/V. For proper operation VCM < VCLAMP < VCM +
2.0V and the upper single ended output voltage is limited to the voltage level set at the VCLAMP input. The output
common mode control loop forces the lower single ended voltage to be limited to 2*VCM - VCLAMP. The maximum
clamped single ended output swing is therefore equal to 2*(VCLAMP - VCM) and the maximum differential output
swing is therefore equal to 4*(VCLAMP - VCM). In the example of Figure 59 with VCLAMP set to 2V and VCM set to
1.5V, the maximum single ended output is therefore 1 VPP centered at 1.5V and the maximum differential output
is 2 VPP. This is shown for the case of a 2 VPP input sine wave which for a gain of 2 V/V in unclamped operation
would provide single ended outputs at +OUT and -OUT of 2 VPP but is shown being clamp limited to 1 VPP.
22
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V
VON_SE
2.5
VCLAMP
2.0
VCM = 1.5
1 VPP
2*VCM ± VCLAMP
1.0
0.5
SE Unclampled output
0
RF
t
RG
VIN = 2VPP
0V
+
VCM = 1.5V
VCM VCLAMP
Differential Output
VON-VOP = 2VPP
RG
RF
V
Vclamp = 2.0V
VOP_SE
2.5
VCLAMP
1 VPP
2.0
VCM = 1.5
1.0
2*VCM ± VCLAMP
0.5
SE Unclampled output
0
t
Figure 59. Clamp Operation
CLAMP PERFORMANCE
Key clamp performance specifications are listed in the electrical characteristics section. Figure 60 illustrates the
clamp overdrive recovery time which is defined as the difference in input to output propagation delay due to a
step change at the input for a clamped output versus a normal linear unclamped, non-saturated output.
Clamp Overdrive
Recovery Time
V
50%
Response to step
from clamped state
Normal Linear
response to step
Time
Figure 60. Clamp Overdrive Recovery Time
MAXIMUM OUTPUT LEVEL
The maximum unclamped output swing in normal operation is 4VPP single ended or 8 VPP differential due to the
requirement that VCLAMP < VCM + 2.0V. For split supply operation of +5V and −5V, the maximum output voltage is
limited by the output stage's ability to swing close to either supply (VOUT < ±3.7V). As shown in Figure 61, if
VCLAMP is set > 3.7V, the amplifier output will saturate at the positive supply before the clamp can operate and
similarly if 2*VCM - VCLAMP < −3.7V, the amplifier output will saturate at the negative supply.
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VOUT(MAX)
+V
VCLAMP
5
SE Unclamped output
4
VOUT(MAX) = + 3.7V
VCM = 3
2
1
2*VCM ± VCLAMP
0
t
VOUT(MIN)
t
0
-1
VCLAMP
-2
VCM = -3
VOUT(MIN) = -3.7V
-4
SE Unclamped output
2*VCM ± VCLAMP
-5
-V
Figure 61. Split Supply VOUT(MAX) and VOUT(MIN) Output Levels
OUTPUT NOISE PERFORMANCE AND MEASUREMENT
Unlike differential amplifiers based on voltage feedback architectures, noise sources internal to the LMH6553
refer to the inputs largely as current sources, hence the low input referred voltage noise and relatively higher
input referred current noise. The output noise is therefore more strongly coupled to the value of the feedback
resistor and not to the closed loop gain, as would be the case with a voltage feedback differential amplifier. This
allows operation of the LMH6553 at much higher gain without incurring a substantial noise performance penalty,
simply by choosing a suitable feedback resistor.
Figure 62 shows a circuit configuration used to measure noise figure for the LMH6553 in a 50Ω system. An RF
value of 275Ω is chosen for the SO PowerPAD package to minimize output noise while simultaneously allowing
both high gain (9 V/V) and proper 50Ω input termination. Refer to SINGLE-ENDED INPUT TO DIFFERENTIAL
OUTPUT OPERATION for calculation of resistor and gain values. Noise figure values at various frequencies are
shown in Figure 43 in Typical Performance Characteristics.
275:
V
RS = 50:
VIN
1 PF
10:
VCM
a
+
+
VO
LMH6553
50:
+
50:
2:1 (TURNS)
-
10:
1 PF
V
-
275:
AV = 9 V/V
Figure 62. Noise Figure Circuit Configuration
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DRIVING ANALOG TO DIGITAL CONVERTERS
Analog-to-digital converters present challenging load conditions. They typically have high impedance inputs with
large and often variable capacitive components. As well, there are usually current spikes associated with
switched capacitor or sample and hold circuits. Figure 63 shows the LMH6553 driving the ADC14C105. The
amplifier is configured to provide a gain of 2 V/V in a single-to-differential mode. The LMH6553 common mode
voltage is set by the ADC14C105. The 0.1 µF capacitor, in series with the 49.9Ω resistor, is inserted to ground
across the 68.1Ω resistor to balance the amplifier inputs. The circuit in Figure 63 has a 2nd order lowpass LC
filter formed by the 620 nH inductors along with the 22 pF capacitor across the differential inputs of the
ADC14C105. The filter has a pole frequency of about 50 MHz. The two 100Ω resistors serve to isolate the
capacitive loading of the ADC from the amplifier and ensure stability. For switched capacitor input ADCs, the
input capacitance will vary based on the clock cycle, as the ADC switches between the sample and hold mode.
See your particular ADC's datasheet for details.
274:
50:
Single-Ended
AC-Coupled
Source
V
127:
-
+
VCM
68.1:
ADC14C105
100: 620 nH
+
-
+
127:
49.9:
V
-
100: 620 nH
VREF
+ V
CLAMP
68.1:
0.1PF
14-Bit
105 MSPS
22 pF
LMH6553
274:
Figure 63. Driving a 14-bit ADC
Figure 64 shows the SFDR and SNR performance vs. frequency for the LMH6553 and ADC14C105 combination
circuit with the ADC input signal level at −1 dBFS. The ADC14C105 is a single channel 14-bit ADC with
maximum sampling rate of 105 MSPS. The amplifier is configured to provide a gain of 2 V/V in single to
differential mode. An external bandpass filter is inserted in series between the input signal source and the
amplifier to reduce harmonics and noise from the signal generator. In order to properly match the input
impedance seen at the LMH6553 amplifier inputs, RM is chosen to match ZS || RT for proper input balance.
100
95
90
SFDR (dBc)
85
(dB)
80
75
70
SNR (dBFs)
65
60
55
50
0
5
10
15
20
25
30
35
40
INPUT FREQUENCY (MHz)
Figure 64. LMH6553/ADC14C105 SFDR and SNR Performance vs. Frequency
The amplifier and ADC should be located as close together as possible. Both devices require that the filter
components be in close proximity to them. The amplifier needs to have minimal parasitic loading on it's outputs
and the ADC is sensitive to high frequency noise that may couple in on its inputs. Some high performance ADCs
have an input stage that has a bandwidth of several times its sample rate. The sampling process results in all
input signals presented to the input stage mixing down into the first Nyquist zone (DC to Fs/2).
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The LMH6553 is capable of driving a variety of Texas Instruments Analog-to-Digital Converters. This is shown in
Table 3, which offers a list of possible signal path ADC and amplifier combinations. The use of the LMH6553 to
drive an ADC is determined by the application and the desired sampling process (Nyquist operation, subsampling or over-sampling). See application note AN-236 (SNAA079) for more details on the sampling processes
and application note AN-1393, Using High Speed Differential Amplifiers to Drive ADCs (SNOA461). For more
information regarding a particular ADC, refer to the particular ADC datasheet for details.
Table 3. DIFFERENTIAL INPUT ADCs COMPATIBLE WITH LMH6553 DRIVER
Product Number
Max Sampling Rate (MSPS)
Resolution
Channels
ADC1173
15
8
SINGLE
ADC1175
20
8
SINGLE
ADC08351
42
8
SINGLE
ADC1175-50
50
8
SINGLE
ADC08060
60
8
SINGLE
ADC08L060
60
8
SINGLE
ADC08100
100
8
SINGLE
ADC08200
200
8
SINGLE
ADC08500
500
8
SINGLE
ADC081000
1000
8
SINGLE
ADC08D1000
1000
8
DUAL
ADC10321
20
10
SINGLE
ADC10D020
20
10
DUAL
ADC10030
27
10
SINGLE
ADC10040
40
10
DUAL
ADC10065
65
10
SINGLE
ADC10DL065
65
10
DUAL
ADC10080
80
10
SINGLE
ADC11DL066
66
11
DUAL
ADC11L066
66
11
SINGLE
ADC11C125
125
11
SINGLE
ADC11C170
170
11
SINGLE
ADC12010
10
12
SINGLE
ADC12020
20
12
SINGLE
ADC12040
40
12
SINGLE
ADC12D040
40
12
DUAL
ADC12DL040
40
12
DUAL
ADC12DL065
65
12
DUAL
ADC12DL066
66
12
DUAL
ADC12L063
63
12
SINGLE
ADC12C080
80
12
SINGLE
ADC12DS080
80
12
DUAL
ADC12L080
80
12
SINGLE
ADC12C105
105
12
SINGLE
ADC12DS105
105
12
DUAL
ADC12C170
170
12
SINGLE
ADC14L020
20
14
SINGLE
ADC14L040
40
14
SINGLE
ADC14C080
80
14
SINGLE
ADC14DS080
80
14
DUAL
ADC14C105
105
14
SINGLE
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Table 3. DIFFERENTIAL INPUT ADCs COMPATIBLE WITH LMH6553 DRIVER (continued)
Product Number
Max Sampling Rate (MSPS)
Resolution
Channels
ADC14DS105
105
14
DUAL
ADC14155
155
14
SINGLE
DRIVING CAPACITIVE LOADS
As noted previously, capacitive loads should be isolated from the amplifier outputs with small valued resistors.
This is particularly the case when the load has a resistive component that is 500Ω or higher. A typical ADC has
capacitive components of around 10 pF and the resistive component could be 1000Ω or higher. If driving a
transmission line, such as 50Ω coaxial or 100Ω twisted pair, using matching resistors will be sufficient to isolate
any subsequent capacitance.
BALANCED CABLE DRIVER
With up to 8 VPP differential output voltage swing and 100 mA of linear drive current the LMH6553 makes an
excellent cable driver as shown in Figure 65. The LMH6553 is also suitable for driving differential cables from a
single ended source.
275:
50:
100:
TWISTED PAIR
127:
RS = 50:
+
VIN
a
VCM
61.8:
-
2 VPP
127:
28.7:
VCLAMP
50:
275:
AV = 2 V/V
Figure 65. Fully Differential Cable Driver
POWER SUPPLY BYPASSING
The LMH6553 requires supply bypassing capacitors as shown in Figure 66 and Figure 67. The 0.01 µF and 0.1
µF capacitors should be leadless SMT ceramic capacitors and should be no more than 3 mm from the supply
pins. These capacitors should be star routed with a dedicated ground return plane or trace for best harmonic
distortion performance. A small capacitor, ~0.01 µF, placed across the supply rails, and as close to the chip's
supply pins as possible, can further improve HD2 performance. Narrow traces or small vias will reduce the
effectiveness of bypass capacitors. Also shown in both figures is a capacitor from the VCM and VCLAMP pins to
ground. These inputs are high impedance and can provide a coupling path into the amplifier for external noise
sources, possibly resulting in loss of dynamic range, degraded CMRR, degraded balance and higher distortion.
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+
V
10 PF
0.1 PF
+
VCM
0.01 PF
-
VCLAMP
0.1 PF
0.1 PF
10 PF
-
V
0.1 PF
Figure 66. Split Supply Bypassing Capacitors
V+
0.1 PF
10 PF
0.01 PF
+
VCM
0.1 PF
VCLAMP
0.01 PF
Figure 67. Single Supply Bypassing Capacitors
POWER DISSIPATION
The LMH6553 is optimized for maximum speed and performance in the small form factor of the standard WSON
package. To ensure maximum output drive and highest performance, thermal shutdown is not provided.
Therefore, it is of utmost importance to make sure that the TJMAX of 150°C is never exceeded.
Follow these steps to determine the maximum power dissipation for the LMH6553:
1. Calculate the quiescent (no-load) power:
PAMP = ICC* VS
where
•
VS = V+ - V−. (Be sure to include any current through the feedback network if VCM is not mid-rail.)
(1)
2. Calculate the RMS power dissipated in each of the output stages:
PD (rms) = rms ((VS - V+OUT) * I+OUT) + rms ((VS − V−OUT) * I−OUT)
where
•
VOUT and IOUT are the voltage and the current measured at the output pins of the differential amplifier as if they were
single ended amplifiers and VS is the total supply voltage
(2)
3. Calculate the total RMS power:
PT = PAMP + PD
28
(3)
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The maximum power that the LMH6553 package can dissipate at a given temperature can be derived with the
following equation:
PMAX = (150° – TAMB)/ θJA
where
•
•
•
•
TAMB = Ambient temperature (°C)
θJA = Thermal resistance, from junction to ambient, for a given package (°C/W)
For the SO PowerPAD package θJA is 59°C/W
For WSON package θJA is 58°C/W
(4)
Note: If VCM is not mid-rail, then there will be quiescent current flowing in the feedback network. This current
should be included in the thermal calculations and added into the quiescent power dissipation of the amplifier.
THERMAL PERFORMANCE
The LMH6553 is available in both the SO PowerPAD and WSON packages. Both packages are designed for
enhanced thermal performance and features an exposed die attach pad (DAP) at the bottom center of the
package that creates a direct path to the PCB for maximum power dissipation. The DAP is floating and is not
electrically connected to internal circuitry.
The thermal advantage of the two packages is fully realized only when the exposed die attach pad is soldered
down to a thermal land on the PCB board with thermal vias planted underneath the thermal land. The thermal
land can be connected to any power or ground plane within the allowable supply voltage range of the device.
The junction-to-ambient thermal resistance (θJA) of the LMH6553 can be significantly lowered, as opposed to an
alternative with no direct soldering to a thermal land. Based on thermal analysis of the WSON package, the
junction-to-ambient thermal resistance (θJA) can be improved by a factor of two when the die attach pad of the
WSON package is soldered directly onto the PCB with thermal land and thermal vias are 1.27 mm and 0.33 mm
respectively. Typical copper via barrel plating is 1 oz, although thicker copper may be used to further improve
thermal performance.
For more information on board layout techniques for the WSON package, refer to Application Note 1187
(literature number SNOA401). This application note also discusses package handling, solder stencil and the
assembly process.
ESD PROTECTION
The LMH6553 is protected against electrostatic discharge (ESD) on all pins. The LMH6553 will survive 4000V
Human Body model and 350V Machine model events. Under normal operation the ESD diodes have no effect on
circuit performance. The current that flows through the ESD diodes will either exit the chip through the supply
pins or through the device, hence it is possible to power up a chip with a large signal applied to the input pins.
BOARD LAYOUT
The LMH6553 is a very high performance amplifier. In order to get maximum benefit from the differential circuit
architecture, board layout and component selection are very critical. The circuit board should have a low
inductance ground plane and well bypassed wide supply lines. External components should be leadless surface
mount types. The feedback network and output matching resistors should be composed of short traces and
precision resistors (0.1%). The output matching resistors should be placed within 3 or 4 mm of the amplifier as
should the supply bypass capacitors. Refer to POWER SUPPLY BYPASSING for recommendations on bypass
circuit layout. Evaluation boards are available free of charge through the product folder on TI’s web site.
By design, the LMH6553 is relatively insensitive to parasitic capacitance at its inputs. Nonetheless, ground and
power plane metal should be removed from beneath the amplifier and from beneath RF and RG for best
performance at high frequency.
With any differential signal path, symmetry is very important. Even small amounts of asymmetry can contribute to
distortion and balance errors.
EVALUATION BOARD
See the LMH6553 Product Folder for evaluation board availability and ordering information.
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Copyright © 2008–2013, Texas Instruments Incorporated
Product Folder Links: LMH6553
29
LMH6553
SNOSB07H – SEPTEMBER 2008 – REVISED MARCH 2013
www.ti.com
REVISION HISTORY
Changes from Revision G (March 2013) to Revision H
•
30
Page
Changed layout of National Data Sheet to TI format .......................................................................................................... 29
Submit Documentation Feedback
Copyright © 2008–2013, Texas Instruments Incorporated
Product Folder Links: LMH6553
PACKAGE OPTION ADDENDUM
www.ti.com
10-Dec-2020
PACKAGING INFORMATION
Orderable Device
Status
(1)
Package Type Package Pins Package
Drawing
Qty
Eco Plan
(2)
Lead finish/
Ball material
MSL Peak Temp
Op Temp (°C)
Device Marking
(3)
(4/5)
(6)
LMH6553MR/NOPB
ACTIVE SO PowerPAD
DDA
8
95
RoHS & Green
SN
Level-3-260C-168 HR
-40 to 125
LMH65
53MR
LMH6553MRE/NOPB
ACTIVE SO PowerPAD
DDA
8
250
RoHS & Green
SN
Level-3-260C-168 HR
-40 to 125
LMH65
53MR
LMH6553MRX/NOPB
ACTIVE SO PowerPAD
DDA
8
2500
RoHS & Green
SN
Level-3-260C-168 HR
-40 to 125
LMH65
53MR
LMH6553SD/NOPB
ACTIVE
WSON
NGS
8
1000
RoHS & Green
SN
Level-1-260C-UNLIM
-40 to 125
6553
LMH6553SDE/NOPB
ACTIVE
WSON
NGS
8
250
RoHS & Green
SN
Level-1-260C-UNLIM
-40 to 125
6553
(1)
The marketing status values are defined as follows:
ACTIVE: Product device recommended for new designs.
LIFEBUY: TI has announced that the device will be discontinued, and a lifetime-buy period is in effect.
NRND: Not recommended for new designs. Device is in production to support existing customers, but TI does not recommend using this part in a new design.
PREVIEW: Device has been announced but is not in production. Samples may or may not be available.
OBSOLETE: TI has discontinued the production of the device.
(2)
RoHS: TI defines "RoHS" to mean semiconductor products that are compliant with the current EU RoHS requirements for all 10 RoHS substances, including the requirement that RoHS substance
do not exceed 0.1% by weight in homogeneous materials. Where designed to be soldered at high temperatures, "RoHS" products are suitable for use in specified lead-free processes. TI may
reference these types of products as "Pb-Free".
RoHS Exempt: TI defines "RoHS Exempt" to mean products that contain lead but are compliant with EU RoHS pursuant to a specific EU RoHS exemption.
Green: TI defines "Green" to mean the content of Chlorine (Cl) and Bromine (Br) based flame retardants meet JS709B low halogen requirements of
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