3.3V 1:12 LVCMOS PLL Clock Generator
MPC9772
DATA SHEET
PRODUCT DISCONTINUATION NOTICE - LAST TIME BUY EXPIRES SEPTEMBER 7, 2016
The MPC9772 is a 3.3 V compatible, 1:12 PLL based clock generator targeted
for high performance low-skew clock distribution in mid-range to
high-performance networking, computing and telecom applications. With output
frequencies up to 240 MHz and output skews less than 250 ps the device meets
the needs of the most demanding clock applications.
MPC9772
Features
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1:12 PLL Based Low-Voltage Clock Generator
3.3 V Power Supply
Internal Power-On Reset
Generates Cock Signals Up to 240 MHz
Maximum Output Skew of 250 ps
On-Chip Crystal Oscillator Clock Reference
Two LVCMOS PLL Reference Clock Inputs
External PLL Feedback Supports Zero-Delay Capability
Various Feedback and Output Dividers (See Applications Information
Section)
Supports Up to Three Individual Generated Output Clock Frequencies
Synchronous Output Clock Stop Circuitry for Each Individual Output for
Power Down Support
Drives Up to 24 Clock Lines
Ambient Temperature Range 0C to +70C
Pin and Function Compatible To the MPC972
52-Lead Pb-Free Package
For drop in replacement use 87972DYI-147
3.3 V 1:12 LVCMOS
PLL CLOCK GENERATOR
AE SUFFIX
52-LEAD LQFP PACKAGE
Pb-FREE PACKAGE
CASE 848D-03
Functional Description
The MPC9772 utilizes PLL technology to frequency lock its outputs onto an input reference clock. Normal operation of the
MPC9772 requires the connection of the PLL feedback output QFB to feedback input FB_IN to close the PLL feedback path. The
reference clock frequency and the divider for the feedback path determine the VCO frequency. Both must be selected to match
the VCO frequency range. The MPC9772 features an extensive level of frequency programmability between the 12 outputs as
well as the output to input relationships, for instance 1:1, 2:1, 3:1, 3:2, 4:1, 4:3, 5:1, 5:2, 5:3, 5:4, 5:6, 6:1, 8:1, and 8:3.
The QSYNC output will indicate when the coincident rising edges of the above relationships will occur. The selectability of the
feedback frequency is independent of the output frequencies. This allows for very flexible programming of the input reference
versus output frequency relationship. The output frequencies can be either odd or even multiples of the input reference. In addition the output frequency can be less than the input frequency for applications where a frequency needs to be reduced by a nonbinary factor. The MPC9772 also supports the 180 phase shift of one of its output banks with respect to the other output banks.
The QSYNC outputs reflects the phase relationship between the QA and QC outputs and can be used for the generation of system baseline timing signals.
The REF_SEL pin selects the internal crystal oscillator or the LVCMOS compatible inputs as the reference clock signal. Two
alternative LVCMOS compatible clock inputs are provided for clock redundancy support. The PLL_EN control selects the PLL
bypass configuration for test and diagnosis. In this configuration, the selected input reference clock is routed directly to the output
dividers bypassing the PLL. The PLL bypass is fully static and the minimum clock frequency specification and all other PLL characteristics do not apply.
The outputs can be individually disabled (stopped in logic low state) by programming the serial CLOCK_STOP interface of the
MPC9772. The MPC9772 has an internal power-on reset.
The MPC9772 is fully 3.3 V compatible and requires no external loop filter components. All inputs (except XTAL) accept
LVCMOS signals while the outputs provide LVCMOS compatible levels with the capability to drive terminated 50 transmission
lines. For series terminated transmission lines, each of the MPC9772 outputs can drive one or two traces giving the devices an
effective fanout of 1:24. The device is pin and function compatible to the MPC972 and is packaged in a 52-lead LQFP package.
MPC9772 REVISION 8 3/16/16
1
©2016 Integrated Device Technology, Inc.
MPC9772 DATA SHEET
QA0
All input resistors have a value of 25k
XTAL_IN
XTAL_OUT
XTAL
1
VCC
CCLK0
0
CCLK1
1
CCLK_SEL
Bank A
Ref
0
VCO
2
0
1
1
0
4, 6, 8, 12
1
4, 6, 8, 10
CLK
Stop
4, 6, 8, 10
12, 16, 20
VCC
QB0
Bank B
SYNC PULSE
REF_SEL
FB_IN
CLK
Stop
FB
Bank C
VCC
QB2
FSEL_B[0:1]
FSEL_C[0:1]
FSEL_FB[0:2]
QC0
CLK
Stop
2
2
2
3
FSEL_A[0:1]
0
1
CLK
Stop
Power-On Reset
CLK
Stop
Clock Stop
QC1
QC2
QC3
QFB
INV_CLK
STOP_DATA
STOP_CLK
MR/OE
QB1
QB3
VCO_SEL
PLL_EN
VCC
QA2
QA3
2, 4, 6, 8
PLL
QA1
QSYNC
12
GND
QB0
VCC
QB1
GND
QB2
VCC
QB3
FB_IN
GND
QFB
VCC
FSEL_FB0
Figure 1. Logic Diagram
FSEL_FB1
QSYNC
GND
QC0
VCC
QC1
FSEL_C0
FSEL_C1
QC2
VCC
QC3
GND
INV_CLK
XTAL_IN
XTAL_OUT
VCC_PLL
39 38 37 36 35 34 33 32 31 30 29 28 27
26
40
25
41
24
42
23
43
22
44
21
45
20
46
MPC9772
19
47
18
48
17
49
16
50
15
51
14
52
1 2 3 4 5 6 7 8 9 10 11 12 13
GND
MR/OE
STOP_CLK
STOP_DATA
FSEL_FB2
PLL_EN
REF_SEL
CCLK_SEL
CCLK0
CCLK1
FSEL_B1
FSEL_B0
FSEL_A1
FSEL_A0
QA3
VCC
QA2
GND
QA1
VCC
QA0
GND
VCO_SEL
Figure 2. MPC9772 52-Lead Package Pinout (Top View)
REVISION 8 3/16/16
2
©2016 Integrated Device Technology, Inc.
MPC9772 DATA SHEET
Table 1. Pin Configuration
Pin
I/O
Type
Function
CCLK0
Input
LVCMOS PLL reference clock
CCLK1
Input
LVCMOS Alternative PLL reference clock
XTAL_IN, XTAL_OUT
Analog
Crystal oscillator interface
FB_IN
Input
LVCMOS PLL feedback signal input, connect to an QFB
CCLK_SEL
Input
LVCMOS LVCMOS clock reference select
REF_SEL
Input
LVCMOS LVCMOS/PECL reference clock select
VCO_SEL
Input
LVCMOS VCO operating frequency select
PLL_EN
Input
LVCMOS PLL enable/PLL bypass mode select
MR/OE
Input
LVCMOS Output enable/disable (high-impedance tristate) and device reset
FSEL_A[0:1]
Input
LVCMOS Frequency divider select for bank A outputs
FSEL_B[0:1]
Input
LVCMOS Frequency divider select for bank B outputs
FSEL_C[0:1]
Input
LVCMOS Frequency divider select for bank C outputs
FSEL_FB[0:2]
Input
LVCMOS Frequency divider select for the QFB output
INV_CLK
Input
LVCMOS Clock phase selection for outputs QC2 and QC3
STOP_CLK
Input
LVCMOS Clock input for clock stop circuitry
STOP_DATA
Input
LVCMOS Configuration data input for clock stop circuitry
QA[0-3]
Output
LVCMOS Clock outputs (Bank A)
QB[0-3]
Output
LVCMOS Clock outputs (Bank B)
QC[0-3]
Output
LVCMOS Clock outputs (Bank C)
QFB
Output
LVCMOS PLL feedback output. Connect to FB_IN.
QSYNC
Output
LVCMOS Synchronization pulse output
GND
Supply
Ground
VCC_PLL
Supply
VCC
PLL positive power supply (analog power supply). It is recommended to use an external RC
filter for the analog power supply pin VCC_PLL. Please see applications section for details.
VCC
Supply
VCC
Positive power supply for I/O and core. All VCC pins must be connected to the positive power
supply for correct operation
REVISION 8 3/16/16
Negative power supply
3
©2016 INTEGRATED DEVICE TECHNOLOGY, INC.
MPC9772 DATA SHEET
Table 2. Function Table (Configuration Controls)
Control
Default
0
1
REF_SEL
1
Selects CCLKx as the PLL reference clock
Selects the crystal oscillator as the PLL
reference clock
CCLK_SEL
1
Selects CCLK0
Selects CCLK1
VCO_SEL
1
Selects VCO2. The VCO frequency is scaled by a factor of 2 (low VCO Selects VCO1. (high VCO frequency range)
frequency range).
PLL_EN
1
Test mode with the PLL bypassed. The reference clock is substituted for the Normal operation mode with PLL enabled.
internal VCO output. MPC9772 is fully static and no minimum frequency
limit applies. All PLL related AC characteristics are not applicable.
INV_CLK
1
QC2 and QC3 are in phase with QC0 and QC1
MR/OE
1
Outputs disabled (high-impedance state) and device is reset. During
Outputs enabled (active)
reset/output disable the PLL feedback loop is open and the internal VCO
is tied to its lowest frequency. The MPC9772 requires reset after any loss
of PLL lock. Loss of PLL lock may occur when the external feedback path
is interrupted. The length of the reset pulse should be greater than one
reference clock cycle (CCLKx). The device is reset by the internal poweron reset (POR) circuitry during power-up.
QC2 and QC3 are inverted (180 phase shift)
with respect to QC0 and QC1
VCO_SEL, FSEL_A[0:1], FSEL_B[0:1], FSEL_C[0:1], FSEL_FB[0:2] control the operating PLL frequency range and input/output frequency
ratios. See Table 3 to Table 6 and the Applications Information for supported frequency ranges and output to input frequency ratios.
Table 3. Output Divider Bank A (NA)
VCO_SEL
FSEL_A1
FSEL_A0
0
0
0
QA[0:3]
VCO8
0
0
1
VCO12
0
1
0
VCO16
0
1
1
VCO24
1
0
0
VCO4
1
0
1
VCO6
1
1
0
VCO8
1
1
1
VCO12
VCO_SEL
FSEL_B1
FSEL_B0
QB[0:3]
0
0
0
VCO8
0
0
1
VCO12
0
1
0
VCO16
0
1
1
VCO20
1
0
0
VCO4
1
0
1
VCO6
1
1
0
VCO8
1
1
1
VCO10
VCO_SEL
FSEL_C1
FSEL_C0
QC[0:3]
0
0
0
VCO4
0
0
1
VCO8
0
1
0
VCO12
0
1
1
VCO16
1
0
0
VCO2
Table 4. Output Divider Bank B (NB)
Table 5. Output Divider Bank C (NC)
REVISION 8 3/16/16
4
©2016 Integrated Device Technology, Inc.
MPC9772 DATA SHEET
Table 5. Output Divider Bank C (NC)
VCO_SEL
FSEL_C1
FSEL_C0
QC[0:3]
1
0
1
VCO4
1
1
0
VCO6
1
1
1
VCO8
Table 6. Output Divider PLL Feedback (M)
VCO_SEL
FSEL_FB2
FSEL_FB1
FSEL_FB0
QFB
0
0
0
0
VCO8
0
0
0
1
VCO12
0
0
1
0
VCO16
0
0
1
1
VCO20
0
1
0
0
VCO16
0
1
0
1
VCO24
0
1
1
0
VCO32
0
1
1
1
VCO40
1
0
0
0
VCO4
1
0
0
1
VCO6
1
0
1
0
VCO8
1
0
1
1
VCO10
1
1
0
0
VCO8
1
1
0
1
VCO12
1
1
1
0
VCO16
1
1
1
1
VCO20
Table 7. General Specifications
Symbol
Characteristics
Min
Typ
Max
VCC 2
Unit
Condition
VTT
Output Termination Voltage
V
MM
ESD Protection (Machine Model)
200
V
HBM
ESD Protection (Human Body Model)
2000
V
LU
Latch-Up Immunity
200
mA
CPD
Power Dissipation Capacitance
12
pF
Per output
CIN
Input Capacitance
4.0
pF
Inputs
Table 8. Absolute Maximum Ratings(1)
Symbol
Characteristics
Min
Max
Unit
VCC
Supply Voltage
–0.3
3.9
V
VIN
DC Input Voltage
–0.3
VCC+0.3
V
DC Output Voltage
–0.3
VCC+0.3
V
DC Input Current
20
mA
DC Output Current
50
mA
125
C
VOUT
IIN
IOUT
TS
Storage Temperature
–65
Condition
1. Absolute maximum continuous ratings are those maximum values beyond which damage to the device may occur. Exposure to these
conditions or conditions beyond those indicated may adversely affect device reliability. Functional operation at absolute-maximum-rated
conditions is not implied.
REVISION 8 3/16/16
5
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MPC9772 DATA SHEET
Table 9. DC Characteristics (VCC = 3.3 V ± 5%, TA = -40° to 85°C)
Symbol
Characteristics
Min
Typ
Max
Unit
Condition
VCC_PLL
PLL Supply Voltage
3.0
VCC
V
LVCMOS
VIH
Input High Voltage
2.0
VCC + 0.3
V
LVCMOS
VIL
Input Low Voltage
0.8
V
LVCMOS
VOH
Output High Voltage
V
IOH = –24 mA(1)
VOL
Output Low Voltage
V
V
IOL = 24 mA
IOL = 12 mA
ZOUT
Output Impedance
IIN
ICC_PLL
ICCQ
2.4
0.55
0.30
14 – 17
Input Current(2)
Maximum PLL Supply Current
200
A
VIN = VCC or
GND
5.0
mA
VCC_PLL Pin
15
mA
All VCC Pins
3.0
Maximum Quiescent Supply Current
1. The MPC9772 is capable of driving 50 transmission lines on the incident edge. Each output drives one 50 parallel terminated
transmission line to a termination voltage of VTT. Alternatively, the device drives up to two 50 series terminated transmission lines.
2. Inputs have pull-down resistors affecting the input current.
Table 10. AC Characteristics (VCC = 3.3 V ± 5%, TA = –40° to +85°C)(1), (2), continued on next page
Max
Symbol
fREF
Characteristics
Input reference frequency
Min
4 feedback
6 feedback
8 feedback
10 feedback
12 feedback
16 feedback
20 feedback
24 feedback
32 feedback
40 feedback
50.0
33.3
25.0
20.0
16.6
12.5
10.0
8.33
6.25
5.00
Input reference frequency in PLL bypass mode(3)
fVCO
VCO frequency range(4)
200
fXTAL
Crystal interface frequency range(4)
10
fMAX
Output Frequency
2 output
4 output
6 output
8 output
10 output
12 output
16 output
20 output
24 output
100.0
50.0
33.3
25.0
20.0
16.6
12.5
10.0
8.33
fSTOP_CLK Serial interface clock frequency
tPW,MIN
Input Reference Pulse Width(5)
tR, tF
CCLKx Input Rise/Fall Time(6)
REVISION 8 3/16/16
Typ
Condition
TA = 0°C TA = –40°C
to +70°C to +85°C
120.0
80.0
60.0
48.0
40.0
30.0
24.0
20.0
15.0
12.0
115.00
76.67
57.50
46.00
38.33
28.75
23.00
19.16
14.37
11.50
MHz
MHz
MHz
MHz
MHz
MHz
MHz
MHz
MHz
MHz
PLL locked
250
250
MHz
PLL bypass
480
460
MHz
25
240.0
120.0
80.0
60.0
48.0
40.0
30.0
24.0
20.0
MHz
230.00
115.00
76.67
57.50
46.00
38.33
28.75
23.00
19.16
20
2.0
MHz
MHz
MHz
MHz
MHz
MHz
MHz
MHz
MHz
PLL locked
MHz
ns
1.0
6
Unit
ns
0.8 to 2.0 V
©2016 Integrated Device Technology, Inc.
MPC9772 DATA SHEET
Table 10. AC Characteristics (VCC = 3.3 V ± 5%, TA = –40° to +85°C)(1), (2), continued on next page
Max
Symbol
Characteristics
Min
t()
Propagation Delay (static phase offset)(7)
CCLK to FB_IN
6.25 MHz < fREF < 65.0 MHz
65.0 MHz < fREF < 125 MHz
fREF=50 MHz and feedback=8
–3
–4
–166
tSK(O)
Output-to-output Skew(8)
Typ
Unit
TA = 0°C TA = –40°C
to +70°C to +85°C
PLL locked
within QA outputs
within QB outputs
within QC outputs
all outputs
T 2
+3
+4
+166
ps
100
100
100
250
ps
ps
ps
ps
(T2) + 200
ps
1.0
ns
DC
Output Duty Cycle(9)
(T2) – 200
tR, tF
Output Rise/Fall Time
0.1
tPLZ, HZ
Output Disable Time
8
ns
tPZL, LZ
Output Enable Time
8
ns
200
ps
150
ps
11
86
13
88
16
19
21
22
27
30
ps
ps
ps
ps
ps
ps
ps
ps
ps
ps
tJIT(CC)
Cycle-to-cycle Jitter
tJIT(PER)
Period Jitter(11)
5.
6.
7.
8.
9.
10.
11.
12.
13.
150
I/O Phase Jitter RMS (1 )(12)
4 feedback
6 feedback
8 feedback
10 feedback
12 feedback
16 feedback
20 feedback
24 feedback
32 feedback
40 feedback
BW
PLL closed loop bandwidth(13)
4 feedback
6 feedback
8 feedback
10 feedback
12 feedback
16 feedback
20 feedback
24 feedback
32 feedback
40 feedback
tLOCK
1.
2.
3.
4.
(10)
tJIT()
Condition
1.20 – 3.50
0.70 – 2.50
0.50 – 1.80
0.45 – 1.20
0.30 – 1.00
0.25 – 0.70
0.20 – 0.55
0.17 – 0.40
0.12 – 0.30
0.11 – 0.28
Maximum PLL Lock Time
0.55 to 2.4 V
(VCO=400 MHz)
MHz
MHz
MHz
MHz
MHz
MHz
MHz
MHz
MHz
MHz
10
ms
AC characteristics apply for parallel output termination of 50 to VTT.
In bypass mode, the MPC9772 divides the input reference clock.
The input reference frequency must match the VCO lock range divided by the total feedback divider ratio: fREF= fVCO (M Þ VCO_SEL).
The crystal frequency range must both meet the interface frequency range and VCO lock range divided by the feedback divider ratio:
fXTAL(min, max) = fVCO(min, max) (M VCO_SEL) and 10 MHz fXTAL 25 MHz.
Calculation of reference duty cycle limits: DCREF,MIN = tPW,MIN fREF 100% and DCREF,MAX = 100% – DCREF, MIN.
The MPC9772 will operate with input rise/fall times up to 3.0 ns, but the A.C. characteristics, specifically t(), tPW,MIN, DC and fMAX can only
be guaranteed if tR, tF are within the specified range.
Static phase offset depends on the reference frequency. t() [s] = t() [] (fREF 360).
Excluding QSYNC output. See application section for part-to-part skew calculation.
Output duty cycle is DC = (0.5 200 ps fOUT) 100%. E.g. the DC range at fOUT = 100 MHz is 48% < DC < 52%. T = output period.
Cycle jitter is valid for all outputs in the same divider configuration. See Applications Information section for more details.
Period jitter is valid for all outputs in the same divider configuration. See Applications Information section for more details.
I/O jitter is valid for a VCO frequency of 400 MHz. See Applications Information section for I/O jitter vs. VCO frequency.
–3 dB point of PLL transfer characteristics.
REVISION 8 3/16/16
7
©2016 INTEGRATED DEVICE TECHNOLOGY, INC.
MPC9772 DATA SHEET
APPLICATIONS INFORMATION
MPC9772 Configurations
Configuring the MPC9772 amounts to properly configuring
the internal dividers to produce the desired output
frequencies. The output frequency can be represented by
this formula:
the specified frequency range. This divider is controlled by
the VCO_SEL pin. VCO_SEL effectively extends the usable
input frequency range while it has no effect on the output to
reference frequency ratio.
The output frequency for each bank can be derived from
the VCO frequency and output divider:
fOUT = fREF M N
fREF
PLL
VCO_SEL
fQA[0:3] = fVCO (VCO_SEL NA)
N
fQB[0:3] = fVCO (VCO_SEL NB)
fQC[0:3] = fVCO (VCO_SEL NC)
fOUT
Table 11. MPC9772 Divider
M
where fREF is the reference frequency of the selected input
clock source (CCLKO, CCLK1 or XTAL interface), M is the
PLL feedback divider and N is a output divider. The PLL
feedback divider is configured by the FSEL_FB[2:0] and the
output dividers are individually configured for each output
bank by the FSEL_A[1:0], FSEL_B[1:0] and FSEL_C[1:0]
inputs.
The reference frequency fREF and the selection of the
feedback-divider M is limited by the specified VCO frequency
range. fREF and M must be configured to match the VCO
frequency range of 200 to 480 MHz in order to achieve stable
PLL operation:
Function
VCO_SEL
Values
M
PLL feedback
FSEL_FB[0:3]
1
4, 6, 8, 10, 12, 16
2
8, 12, 16, 20, 24, 32, 40
Bank A Output
Divider
FSEL_A[0:1]
1
4, 6, 8, 12
2
8, 12, 16, 24
Bank B Output
Divider
FSEL_B[0:1]
1
4, 6, 8, 10
2
8, 12, 16, 20
Bank C Output
Divider
FSEL_C[0:1]
1
2, 4, 6, 8
2
4, 8, 12, 16
NA
NB
NC
fVCO,MIN (fREF VCO_SEL M) fVCO,MAX
Table 11 shows the various PLL feedback and output
dividers and Figure 3 and Figure 4 display example
configurations for the MPC9772:
The PLL post-divider VCO_SEL is either a divide-by-one
or a divide-by-two and can be used to situate the VCO into
REVISION 8 3/16/16
Divider
8
©2016 Integrated Device Technology, Inc.
MPC9772 DATA SHEET
CCLK0
CCLK1
CCLK_SEL
fref = 33.3 MHz
1 VCO_SEL
FB_IN
11
00
00
101
FSEL_A[1:0]
FSEL_B[1:0]
FSEL_C[1:0]
FSEL_FB[2:0]
QA[3:0]
33.3 MHz
QB[3:0]
100 MHz
QC[3:0]
200 MHz
CCLK0
CCLK1
CCLK_SEL
fref = 25 MHz
1 VCO_SEL
FB_IN
00
00
00
011
QFB
FSEL_A[1:0]
FSEL_B[1:0]
FSEL_C[1:0]
FSEL_FB[2:0]
MPC9772
QA[3:0]
62.5 MHz
QB[3:0]
62.5 MHz
QC[3:0]
125 MHz
QFB
MPC9772
33.3 MHz (Feedback)
25 MHz (Feedback)
MPC9772 example configuration (feedback of QFB = 33.3 MHz,
fVCO=400 MHz, VCO_SEL=1, M=12, NA=12, NB=4, NC=2).
MPC9772 example configuration (feedback of QFB = 25 MHz,
fVCO=250 MHz, VCO_SEL=1, M=10, NA=4, NB=4, NC=2).
Frequency Range
TA = 0°C to +70°C
TA = –40°C to +85°C
Frequency Range
Input
16.6 – 40 MHz
16.6 – 38.33 MHz
Input
20 – 48 MHz
20 – 46 MHz
QA Outputs
16.6 – 40 MHz
16.6 – 38.33 MHz
QA Outputs
50 – 120 MHz
50 – 115 MHz
QA Outputs
50 – 120 MHz
50 – 115 MHz
QA Outputs
50 – 120 MHz
50 – 115 MHz
QC Outputs
100 – 240 MHz
100 – 230 MHz
QC Outputs
100 – 240 MHz
100 – 230 MHz
Figure 3. Example Configuration
TA = 0°C to +70°C TA = –40°C to +85°C
Figure 4. Example Configuration
MPC9772 Individual Output Disable
(Clock Stop) Circuitry
The individual clock stop (output enable) control of the
MPC9772 allows designers, under software control, to
implement power management into the clock distribution
design. A simple serial interface and a clock stop control logic
provides a mechanism through which the MPC9772 clock
outputs can be individually stopped in the logic ‘0’ state: The
clock stop mechanism allows serial loading of a 12-bit serial
input register. This register contains one programmable clock
stop bit for 12 of the 14 output clocks. The QC0 and QFB
outputs cannot be stopped (disabled) with the serial port.
The user can program an output clock to stop (disable) by
writing logic ‘0’ to the respective stop enable bit. Likewise, the
user may programmably enable an output clock by writing
logic ‘1’ to the respective enable bit. The clock stop logic
enables or disables clock outputs during the time when the
output would be in normally in logic low state, eliminating the
possibility of short or ‘runt’ clock pulses.
The user can write to the serial input register through the
STOP_DATA input by supplying a logic ‘0’ start bit followed
serially by 12 NRZ disable/enable bits. The period of each
STOP_DATA bit equals the period of the free—running
STOP_CLK signal. The STOP_DATA serial transmission
should be timed so the MPC9772 can sample each
STOP_DATA bit with the rising edge of the free—running
STOP_CLK signal. (See Figure 5.)
STOP_CLK
STOP_DATA
START
QA0
QA1
QA2
QA3
QB0
QB1
QB2
QB3
QC1
QC2
QC3
QSYNC
Figure 5. Clock Stop Circuit Programming
SYNC Output Description
The MPC9772 has a system synchronization pulse output
QSYNC. In configurations with the output frequency
relationships are not integer multiples of each other QSYNC
provides a signal for system synchronization purposes. The
MPC9772 monitors the relationship between the A bank and
the B bank of outputs. The QSYNC output is asserted (logic
low) one period in duration and one period prior to the
REVISION 8 3/16/16
coincident rising edges of the QA and QC outputs. The
duration and the placement of the pulse is dependent QA and
QC output frequencies: the QSYNC pulse width is equal to
the period of the higher of the QA and QC output frequencies.
Figure 6 shows various waveforms for the QSYNC output.
The QSYNC output is defined for all possible combinations of
the bank A and bank C outputs.
9
©2016 INTEGRATED DEVICE TECHNOLOGY, INC.
MPC9772 DATA SHEET
fVCO
1:1 Mode
QA
QC
QSYNC
2:1 Mode
QA
QC
QSYNC
3:1 Mode
QC(2)
QA(6)
QSYNC
3:2 Mode
QA(4)
QC(6)
QSYNC
4:1 Mode
QC(2)
QA(8)
QSYNC
4:3 Mode
QA(6)
QC(8)
QSYNC
6:1 Mode
QA(12)
QC(2)
QSYNC
Figure 6. QSYNC Timing Diagram
REVISION 8 3/16/16
10
©2016 Integrated Device Technology, Inc.
MPC9772 DATA SHEET
Power Supply Filtering
The MPC9772 is a mixed analog/digital product. Its analog
circuitry is naturally susceptible to random noise, especially if
this noise is seen on the power supply pins. Random noise
on the VCC_PLL power supply impacts the device
characteristics, for instance I/O jitter. The MPC9772 provides
separate power supplies for the output buffers (VCC) and the
phase-locked loop (VCC_PLL) of the device. The purpose of
this design technique is to isolate the high switching noise
digital outputs from the relatively sensitive internal analog
phase-locked loop. In a digital system environment where it
is more difficult to minimize noise on the power supplies a
second level of isolation may be required. The simple but
effective form of isolation is a power supply filter on the
VCCA_PLL pin for the MPC9772. Figure 7 illustrates a typical
power supply filter scheme. The MPC9772 frequency and
phase stability is most susceptible to noise with spectral
content in the 100 kHz to 20 MHz range. Therefore the filter
should be designed to target this range. The key parameter
that needs to be met in the final filter design is the DC voltage
drop across the series filter resistor RF. From the data sheet
the ICC_PLL current (the current sourced through the VCC_PLL
pin) is typically 3 mA (5 mA maximum), assuming that a
minimum of 3.0 V must be maintained on the VCC_PLL pin.
The resistor RF shown in Figure 7 must have a resistance of
5-10 to meet the voltage drop criteria.
Using the MPC9772 in Zero-Delay Applications
Nested clock trees are typical applications for the
MPC9772. Designs using the MPC9772 as LVCMOS PLL
fanout buffer with zero insertion delay will show significantly
lower clock skew than clock distributions developed from
CMOS fanout buffers. The external feedback option of the
MPC9772 clock driver allows for its use as a zero delay
buffer. The PLL aligns the feedback clock output edge with
the clock input reference edge resulting a near zero delay
through the device (the propagation delay through the device
is virtually eliminated). The maximum insertion delay of the
device in zero-delay applications is measured between the
reference clock input and any output. This effective delay
consists of the static phase offset, I/O jitter (phase or
long-term jitter), feedback path delay and the
output-to-output skew error relative to the feedback output.
Calculation of Part-to-Part Skew
The MPC9772 zero delay buffer supports applications
where critical clock signal timing can be maintained across
several devices. If the reference clock inputs of two or more
MPC9772 are connected together, the maximum overall
timing uncertainty from the common CCLKx input to any
output is:
tSK(PP) = t() + tSK(O) + tPD, LINE(FB) + tJIT() CF
CF = 22 F
RF = 5–10
RF
VCC
this section should be adequate to eliminate power supply
noise related problems in most designs.
This maximum timing uncertainty consist of 4 components:
static phase offset, output skew, feedback board trace delay
and I/O (phase) jitter:
VCC_PLL
CF
10 nF
MPC9772
VCC
CCLKCommon
33...100 nF
QFBDevice 1
Figure 7. VCC_PLL Power Supply Filter
The minimum values for RF and the filter capacitor CF are
defined by the required filter characteristics: the RC filter
should provide an attenuation greater than 40 dB for noise
whose spectral content is above 100 kHz. In the example RC
filter shown in Figure 7, the filter cut-off frequency is around
4.5 kHz and the noise attenuation at 100 kHz is better than
42 dB.
As the noise frequency crosses the series resonant point
of an individual capacitor its overall impedance begins to look
inductive and thus increases with increasing frequency. The
parallel capacitor combination shown ensures that a low
impedance path to ground exists for frequencies well above
the bandwidth of the PLL. Although the MPC9772 has
several design features to minimize the susceptibility to
power supply noise (isolated power and grounds and fully
differential PLL) there still may be applications in which
overall performance is being degraded due to system power
supply noise. The power supply filter schemes discussed in
REVISION 8 3/16/16
tPD,LINE(FB)
–t()
tJIT()
Any QDevice 1
+tSK(O)
+t()
QFBDevice2
Any QDevice 2
Max. skew
tJIT()
+tSK(O)
tSK(PP)
Figure 8. MPC9772 Maximum
Device-to-Device Skew
11
©2016 INTEGRATED DEVICE TECHNOLOGY, INC.
MPC9772 DATA SHEET
Due to the statistical nature of I/O jitter a RMS value (1 )
is specified. I/O jitter numbers for other confidence factors
(CF) can be derived from Table 12.
Max. I/O Phase Jitter versus Frequency
Parameter: PLL Feedback Divider FB
120
Table 12. Confidence Factor CF
Probability of Clock Edge
within the Distribution
1
0.68268948
2
0.95449988
3
0.99730007
4
0.99993663
5
0.99999943
6
0.99999999
tjit() [ps] RMS
100
CF
FB=6
FB=24
40
0
200
FB=12
250
300
350
400
VCO Frequency [MHz]
450
480
Figure 10. MPC9772 I/O Jitter
Max. I/O Phase Jitter versus Frequency
Parameter: PLL Feedback Divider FB
tjit() [ps] RMS
140
120
450
FB=40
60
40
FB=20
250
300
350
400
VCO Frequency [MHz]
450
480
Figure 11. MPC9772 I/O Jitter
Driving Transmission Lines
The MPC9772 clock driver was designed to drive high
speed signals in a terminated transmission line environment.
To provide the optimum flexibility to the user the output
drivers were designed to exhibit the lowest impedance
possible. With an output impedance of less than 20 the
drivers can drive either parallel or series terminated
transmission lines. For more information on transmission
lines the reader is referred to Freescale Semiconductor
application note AN1091. In most high performance clock
networks point-to-point distribution of signals is the method of
choice. In a point-to-point scheme either series terminated or
parallel terminated transmission lines can be used. The
parallel technique terminates the signal at the end of the line
with a 50 resistance to VCC2.
This technique draws a fairly high level of DC current and
thus only a single terminated line can be driven by each
output of the MPC9772 clock driver. For the series terminated
case however there is no DC current draw, thus the outputs
can drive multiple series terminated lines. Figure 12
illustrates an output driving a single series terminated line
versus two series terminated lines in parallel. When taken to
its extreme the fanout of the MPC9772 clock driver is
effectively doubled due to its capability to drive multiple lines.
Max. I/O Phase Jitter versus Frequency
Parameter: PLL Feedback Divider FB
160
140
FB=32
120
100
FB=16
80
FB=8
60
40
20
FB=4
0
200
250
300
350
400
VCO Frequency [MHz]
FB=10
100
80
20
0
200
tSK(PP) = [-166ps...166ps] + [-250ps...250ps] +
[(13ps @ –3)...(13ps @ 3)] + tPD, LINE(FB)
tSK(PP) = [-455ps...455ps] + tPD, LINE(FB)
tjit() [ps] RMS
60
20
The feedback trace delay is determined by the board
layout and can be used to fine-tune the effective delay
through each device.
Due to the frequency dependence of the static phase
offset and I/O jitter, using Figure 9 to Figure 11 to predict a
maximum I/O jitter and the specified t( parameter relative to
the input reference frequency results in a precise timing
performance analysis.
In the following example calculation an I/O jitter confidence
factor of 99.7% ( 3) is assumed, resulting in a worst case
timing uncertainty from the common input reference clock to
any output of –455 ps to +455 ps relative to CCLK (PLL
feedback = 8, reference frequency = 50 MHz, VCO
frequency = 400 MHz, I/O jitter = 13 ps rms max., static
phase offset t() = 166 ps):
480
Figure 9. MPC9772 I/O Jitter
REVISION 8 3/16/16
80
12
©2016 Integrated Device Technology, Inc.
MPC9772 DATA SHEET
towards the quiescent 3.0 V in steps separated by one round
trip delay (in this case 4.0 ns).
MPC9772
Output
Buffer
14
MPC9772
Output
Buffer
In
ZO = 50
OutA
OutA
tD = 3.8956
2.5
OutB
tD = 3.9386
2.0
RS = 36
ZO = 50
RS = 36
ZO = 50
In
OutB0
Voltage (V)
In
3.0
RS = 36
14
1.5
1.0
OutB1
0.5
0
Figure 12. Single versus Dual Transmission Lines
2
The waveform plots in Figure 13 show the simulation
results of an output driving a single line versus two lines. In
both cases the drive capability of the MPC9772 output buffer
is more than sufficient to drive 50 transmission lines on the
incident edge. Note from the delay measurements in the
simulations a delta of only 43 ps exists between the two
differently loaded outputs. This suggests the dual line driving
need not be used exclusively to maintain the tight
output-to-output skew of the MPC9772. The output waveform
in Figure 13 shows a step in the waveform, this step is
caused by the impedance mismatch seen looking into the
driver. The parallel combination of the 36 series resistor
plus the output impedance does not match the parallel
combination of the line impedances. The voltage wave
launched down the two lines will equal:
4
6
8
Time (ns)
10
12
14
Figure 13. Single versus Dual Waveforms
Since this step is well above the threshold region it will not
cause any false clock triggering, however designers may be
uncomfortable with unwanted reflections on the line. To better
match the impedances when driving multiple lines the
situation in Figure 14 should be used. In this case the series
terminating resistors are reduced such that when the parallel
combination is added to the output buffer impedance the line
impedance is perfectly matched.
MPC9772
Output
Buffer
VL = VS (Z0 (RS+R0 +Z0))
Z0 = 50 || 50
RS = 22
ZO = 50
RS = 22
ZO = 50
14
RS = 36 || 36
R0 = 14
VL = 3.0 (25 (18+17+25)
14 + 22 || 22 = 50 || 50
25 = 25
= 1.31 V
At the load end the voltage will double, due to the near
unity reflection coefficient, to 2.6 V. It will then increment
Figure 14. Optimized Dual Line Termination
MPC9772 DUT
Pulse
Generator
Z = 50
ZO = 50
ZO = 50
RT = 50
RT = 50
VTT
VTT
Figure 15. CCLK MPC9772 AC Test Reference
REVISION 8 3/16/16
13
©2016 INTEGRATED DEVICE TECHNOLOGY, INC.
MPC9772 DATA SHEET
VCC
VCC2
VCC
GND
VCC2
CCLKx
VCC
VCC2
GND
GND
VCC
VCC2
FB_IN
tSK(O)
GND
t()
The pin-to-pin skew is defined as the worst case difference in
propagation delay between any similar delay path within a single
device
Figure 16. Output-to-Output Skew tSK(O)
Figure 17. Propagation Delay (t(), Static Phase
Offset) Test Reference
VCC
VCC2
CCLKx
GND
tP
FB_IN
T0
DC = tP/T0 x 100%
TJIT() = |T0-T1mean|
The deviation in t0 for a controlled edge with respect to a t0 mean in a
random sample of cycles
The time from the PLL controlled edge to the non controlled
edge, divided by the time between PLL controlled edges,
expressed as a percentage
Figure 19. I/O Jitter
Figure 18. Output Duty Cycle (DC)
TN
TN+1
TJIT(CC) = |TN-TN+1|
TJIT(PER) = |TN-1/f0|
T0
The variation in cycle time of a signal between adjacent cycles, over a
random sample of adjacent cycle pairs
The deviation in cycle time of a signal with respect to the ideal period over a
random sample of cycles
Figure 20. Cycle-to-Cycle Jitter
Figure 21. Period Jitter
VCC=3.3 V
2.4
0.55
tR
tF
Figure 22. Output Transition Time Test Reference
REVISION 8 3/16/16
14
©2016 Integrated Device Technology, Inc.
MPC9772 DATA SHEET
3.3V 1:12 LVCMOS PLL CLOCK GENERATOR
4X
4X 13 TIPS
0.20 (0.008) H L-M N
0.20 (0.008) T L-M N
-XX=L, M, N
52
40
1
CL
39
AB
G
3X VIEW Y
-L-
-M-
AB
B
B1
13
V
VIEW Y
BASE METAL
F
PLATING
V1
27
14
J
26
U
-N-
A1
D
0.13 (0.005)
M
T L-M
S
N
S
S1
SECTION AB-AB
A
ROTATED 90˚ CLOCKWISE
S
4X θ2
C
0.10 (0.004) T
-H-T-
4X θ3
SEATING
PLANE
VIEW AA
0.05 (0.002)
S
W
2X R
θ1
R1
0.25 (0.010)
C2
θ
GAGE PLANE
K
C1
E
Z
VIEW AA
NOTES:
1. CONTROLLING DIMENSIONS: MILLIMETER.
2. DIMENSIONING AND TOLERANCING PER ANSI
Y14.5M, 1982.
3. DATUM PLANE -H- IS LOCATED AT BOTTOM OF
LEAD AND IS COINCIDENT WITH THE LEAD
WHERE THE LEAD EXITS THE PLASTIC BODY AT
THE BOTTOM OF THE PARTING LINE.
4. DATUMS -L-, -M- AND -N- TO BE DETERMINED
AT DATUM PLANE -H-.
5. DIMENSIONS S AND V TO BE DETERMINED AT
SEATING PLANE -T-.
6. DIMENSIONS A AND B DO NOT INCLUDE MOLD
PROTRUSION. ALLOWABLE PROTRUSION IS
0.25 (0.010) PER SIDE. DIMENSIONS A AND B
DO INCLUDE MOLD MISMATCH AND ARE
DETERMINED AT DATUM PLANE -H-.
7. DIMENSION D DOES NOT INCLUDE DAMBAR
PROTRUSION. DAMBAR PROTRUSION SHALL
NOT CAUSE THE LEAD WIDTH TO EXCEED 0.46
(0.018). MINIMUM SPACE BETWEEN
PROTRUSION AND ADJACENT LEAD OR
PROTRUSTION 0.07 (0.003).
DIM
A
A1
B
B1
C
C1
C2
D
E
F
G
J
K
R1
S
S1
U
V
V1
W
Z
θ
θ1
θ2
θ3
MILLIMETERS
MIN
MAX
10.00 BSC
5.00 BSC
10.00 BSC
5.00 BSC
--1.70
0.05
0.20
1.50
1.30
0.40
0.20
0.45
0.75
0.22
0.35
0.65 BSC
0.07
0.20
0.50 REF
0.08
0.20
12.00 BSC
6.00 BSC
0.09
0.16
12.00 BSC
6.00 BSC
0.20 REF
1.00 REF
0˚
7˚
--0˚
12˚ REF
12˚ REF
INCHES
MIN
MAX
0.394 BSC
0.197 BSC
0.394 BSC
0.197 BSC
--0.067
0.002
0.008
0.051
0.059
0.008
0.016
0.018
0.030
0.009
0.014
0.026 BSC
0.003
0.008
0.020 REF
0.003
0.008
0.472 BSC
0.236 BSC
0.004
0.006
0.472 BSC
0.236 BSC
0.008 REF
0.039 REF
7˚
0˚
--0˚
12˚ REF
12˚ REF
CASE 848D-03
ISSUE D
52-LEAD LQFP PACKAGE
REVISION 8 3/16/16
15
©2016 Integrated Device Technology, Inc.
MPC9772 DATA SHEET
Revision History Sheet
Rev
Table
7
Page
1
8
8
REVISION 8 3/16/16
1
Description of Change
Date
NRND – Not Recommend for New Designs
1/8/13
Removed NRND and updated data sheet format
3/18/15
Product Discontinuation Notice - Last time buy expires September 7, 2016.
PDN N-16-02
3/16/16
16
©2016 Integrated Device Technology, Inc.
Corporate Headquarters
Sales
Tech Support
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1-800-345-7015 or 408-284-8200
Fax: 408-284-2775
www.IDT.com
email: clocks@idt.com
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