Single 2A High-Speed,
Low-Side Gate Driver
FAN3100T, FAN3100C
Description
The FAN3100 2 A gate driver is designed to drive an N−channel
enhancement−mode MOSFET in low−side switching applications by
providing high peak current pulses during the short switching
intervals. The driver is available with either TTL (FAN3100T)
or CMOS (FAN3100C) input thresholds. Internal circuitry provides
an under−voltage lockout function by holding the output LOW until
the supply voltage is within the operating range. The FAN3100
delivers fast MOSFET switching performance, which helps maximize
efficiency in high−frequency power converter designs.
FAN3100 drivers incorporate MillerDrive t architecture
for the final output stage. This bipolar−MOSFET combination
provides high peak current during the Miller plateau stage
of the MOSFET turn−on / turn−off process to minimize switching
loss, while providing rail−to−rail voltage swing and reverse current
capability.
The FAN3100 also offers dual inputs that can be configured
to operate in non−inverting or inverting mode and allow
implementation of an enable function. If one or both inputs are left
unconnected, internal resistors bias the inputs such that the output is
pulled LOW to hold the power MOSFET off.
The FAN3100 is available in a lead−free finish, 2x2 mm, 6−lead,
Molded Leadless Package (MLP) for the smallest size with excellent
thermal performance; or industry−standard, 5−pin, SOT23.
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WDFN6 2x2, 065P
CASE 511CY
PIN ASSIGNMENT
•
•
•
•
•
•
•
•
3 A Peak Sink/Source at VDD = 12 V
4.5 to 18 V Operating Range
2.5 A Sink/1.8 A Source at VOUT = 6 V
Dual−Logic Inputs Allow Configuration as Non−Inverting or
Inverting with Enable Function
Internal Resistors Turn Driver Off If No Inputs
13 ns Typical Rise Time and 9 ns Typical Fall−Time with 1 nF Load
Choice of TTL or CMOS Input Thresholds
MillerDrive Technology
Typical Propagation Delay Time Under 20 ns with Input Falling or
Rising
6−Lead, 2x2 mm MLP or 5−Pin, SOT23 Packages
Rated from –40°C to 125°C Ambient
These Devices are Pb−Free and Halogen Free
Applications
•
•
•
•
•
© Semiconductor Components Industries, LLC, 2007
February, 2021 − Rev. 3
1
6
IN−
AGND
2
5
PGND
VDD
3
4
OUT
VDD
1
GND
2
IN+
3
5
OUT
4
IN*
SOT23−5 (Top View)
MARKING DIAGRAM
&E&E&Y
&O100X&C
&.&O&E&V
&E
&Y
&O
100X
&C
&.
&V
Switch−Mode Power Supplies (SMPS)
High−Efficiency MOSFET Switching
Synchronous Rectifier Circuits
DC−to−DC Converters
Motor Control
IN+
6−Lead MLP (Top View)
Features
•
•
•
•
SOT23−5
CASE 527AH
= Designates Space
= Binary Calendar Year Coding Scheme
= Plant Code identifier
= Device Specific Code
X = T or C
= Single digit Die Run Code
= Pin One Dot
= Eight−Week Binary Datecoding Scheme
ORDERING INFORMATION
See detailed ordering and shipping information on page 17 of
this data sheet.
1
Publication Order Number:
FAN3100T/D
FAN3100T, FAN3100C
BLOCK DIAGRAMS
THERMAL CHARACTERISTICS (Note 1)
QJL
(Note 2)
QJT
(Note 3)
QJA
(Note 4)
YJB
(Note 5)
YJT
(Note 6)
Unit
6−Lead, 2x2 mm Molded Leadless Package (MLP)
2.7
133
58
2.8
42
°C/W
SOT23, 5−Lead
56
99
157
51
5
°C/W
Package
1. Estimates derived from thermal simulation; actual values depend on the application.
2. Theta_JL (QJL): Thermal resistance between the semiconductor junction and the bottom surface of all the leads (including any thermal pad)
that are typically soldered to a PCB.
3. Theta_JT (QJT): Thermal resistance between the semiconductor junction and the top surface of the package, assuming it is held at a uniform
temperature by a top−side heatsink.
4. Theta_JA (QJA): Thermal resistance between junction and ambient, dependent on the PCB design, heat sinking, and airflow. The value given
is for natural convection with no heatsink using a 2S2P board, as specified in JEDEC standards JESD51−2, JESD51−5, and JESD51−7,
as appropriate.
5. Psi_JB (YJB): Thermal characterization parameter providing correlation between semiconductor junction temperature and an application
circuit board reference point for the thermal environment defined in Note 4. For the MLP−6 package, the board reference is defined as the
PCB copper connected to the thermal pad and protruding from either end of the package. For the SOT23−5 package, the board reference
is defined as the PCB copper adjacent to pin 2.
6. Psi_JT (YJT): Thermal characterization parameter providing correlation between the semiconductor junction temperature and the center of
the top of the package for the thermal environment defined in Note 4.
PIN DEFINITIONS
SOT23 Pin
Number
MLP Pin
Number
Name
1
3
VDD
2
AGND
ÁÁÁÁÁ
ÁÁÁÁÁ
ÁÁÁÁÁ
ÁÁÁÁÁ
ÁÁÁÁÁ
ÁÁÁÁÁ
ÁÁÁÁÁ
ÁÁÁÁÁ
ÁÁÁÁÁ
ÁÁÁÁÁ
ÁÁÁÁÁ
2
GND
Description
Supply Voltage. Provides power to the IC.
Analog ground for input signals (MLP only). Connect to PGND underneath the IC.
Ground (SOT−23 only). Common ground reference for input and output circuits.
3
1
IN+
Non−Inverting Input. Connect to VDD to enable output.
4
6
IN−
Inverting Input. Connect to AGND or PGND to enable output.
5
4
OUT
Gate Drive Output: Held LOW unless required inputs are present and VDD is above
UVLO threshold.
Pad
P1
5
PGND
Thermal Pad (MLP only). Exposed metal on the bottom of the package, which is
electrically connected to pin 5.
Power Ground (MLP only). For output drive circuit; separates switching noise from
inputs.
OUTPUT LOGIC
IN+
IN−
OUT
0 (Note 7)
0
0
0 (Note 7)
1 (Note 7)
0
1
0
1
1
1 (Note 7)
0
7. Default input signal if no external connection is made.
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2
FAN3100T, FAN3100C
BLOCK DIAGRAMS
1
VDD
5
OUT
2
GND
3
VDD
4
OUT
5
PGND
UVLO
100 kW
IN+
VDD_OK
3
100 kW
100 kW
IN−
4
Figure 1. Simplified Block Diagram (SOT23 Pin−out)
UVLO
100 kW
IN+
VDD_OK
1
100 kW
100 kW
IN−
AGND
6
2
0.4 W
Figure 2. Simplified Block Diagram (MLP Pin−out)
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3
FAN3100T, FAN3100C
ABSOLUTE MAXIMUM RATINGS
Symbol
Parameter
Min
Max
Unit
−0.3
20.0
V
Voltage on IN+ and IN− to GND, AGND or PGND
GND −0.3
VDD + 0.3
V
Voltage on OUT to GND, AGND or PGND
GND −0.3
VDD + 0.3
V
GND −2
VDD + 0.3
V
+260
°C
VDD
VDD to GND
VIN
VOUT
Repetitive Voltage on OUT to GND, AGND or PGND (TPULSE < 300 ns)
(Note 8)
TL
Lead Soldering Temperature (10 Seconds)
TJ
Junction Temperature
−55
+150
°C
TSTG
Storage Temperature
−65
+150
°C
Stresses exceeding those listed in the Maximum Ratings table may damage the device. If any of these limits are exceeded, device functionality
should not be assumed, damage may occur and reliability may be affected.
8. Restricted by thermal dissipation. (< Max TJ)
RECOMMENDED OPERATING CONDITIONS
Symbol
Parameter
Min
Max
Unit
VDD
Supply Voltage Range
4.5
18.0
V
VIN
Input Voltage IN+, IN−
0
VDD
V
TA
Operating Ambient Temperature
−40
+125
°C
Functional operation above the stresses listed in the Recommended Operating Ranges is not implied. Extended exposure to stresses beyond
the Recommended Operating Ranges limits may affect device reliability.
ELECTRICAL CHARACTERISTICS (VDD = 12 V, TJ = −40°C to +125°C unless otherwise noted. Currents are defined as positive
into the device and negative out of the device.)
Symbol
Parameter
Test Condition
Min
Typ
Max
Unit
18.0
V
SUPPLY
VDD
Operating Range
IDD
Supply Current
Inputs/EN Not Connected
4.5
FAN3100C (Note 9)
0.20
0.35
mA
FAN3100T
0.50
0.80
mA
VON
Turn−On Voltage
3.5
3.9
4.3
V
VOFF
Turn−Off Voltage
3.3
3.7
4.1
V
INPUTS (FAN3100T)
VINL_T
IN+, IN− Logic Low−Voltage, Maximum
VINH_T
IN+, IN− Logic High−Voltage, Minimum
0.8
V
2.0
V
IIN+
Non−inverting Input
IN from 0 to VDD
−1
175
mA
IIN−
Inverting Input
IN from 0 to VDD
−175
1
mA
0.8
V
VHYS
IN+, IN− Logic Hysteresis Voltage
0.2
0.4
INPUTS (FAN3100C)
VINL_C
IN+, IN− Logic Low Voltage
VINH_C
IN+, IN− Logic High Voltage
30
%VDD
70
%VDD
IINL
IN Current, Low
IN from 0 to VDD
−1
175
mA
IINH
IN Current, High
IN from 0 to VDD
−175
1
mA
VHYS_C
IN+, IN− Logic Hysteresis Voltage
17
%VDD
OUT Current, Mid−Voltage, Sinking (Note 10) OUT at VDD/2, CLOAD = 0.1 mF,
f = 1 kHz
2.5
A
OUTPUT
ISINK
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4
FAN3100T, FAN3100C
ELECTRICAL CHARACTERISTICS (VDD = 12 V, TJ = −40°C to +125°C unless otherwise noted. Currents are defined as positive
into the device and negative out of the device.)
Symbol
Parameter
Test Condition
Min
Typ
Max
Unit
OUTPUT
ISOURCE
OUT Current, Mid−Voltage, Sourcing
(Note 10)
OUT at VDD/2, CLOAD = 0.1 mF,
f = 1 kHz
IPK_SINK
OUT Current, Peak, Sinking (Note 10)
IPK_SOURCE OUT Current, Peak, Sourcing (Note 10)
−1.8
A
CLOAD = 0.1 mF, f = 1kHz
3
A
CLOAD = 0.1 mF, f = 1 kHz
−3
A
13
20
ns
tRISE
Output Rise Time (Note 11)
CLOAD = 1000 pF
tFALL
Output Fall Time (Note 11)
CLOAD = 1000 pF
9
14
ns
tD1, tD2
Output Prop. Delay, CMOS Inputs (Note 11)
0−12 VIN, 1 V/ns Slew Rate
7
15
28
ns
tD1, tD2
Output Prop. Delay, TTL Inputs (Note 11)
0−5 VIN, 1 V/ns Slew Rate
9
16
30
ns
IRVS
Output Reverse Current Withstand (Note 10)
500
9. Lower supply current due to inactive TTL circuitry.
10. Not tested in production.
11. See Timing Diagrams of Figure 3 and Figure 4.
TIMING DIAGRAMS
90%
90%
Output
Output
10%
Input
10%
VINH
Input
VINL
tD1
tD2
tRISE
tFALL
VINH
VINL
tD1
tFALL
Figure 3. Non−Inverting
tD2
tRISE
Figure 4. Inverting
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5
mA
FAN3100T, FAN3100C
TYPICAL PERFORMANCE CHARACTERISTICS
(Typical characteristics are provided at 25°C and VDD = 12 V unless otherwise noted)
Figure 5. IDD (Static) vs. Supply Voltage
Figure 6. IDD (Static) vs. Supply Voltage
Figure 7. IDD (No−Load) vs. Frequency
Figure 8. IDD (No−Load) vs. Frequency
Figure 10. IDD (1 nF Load) vs. Frequency
Figure 9. IDD (1 nF Load) vs. Frequency
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FAN3100T, FAN3100C
TYPICAL PERFORMANCE CHARACTERISTICS (continued)
(Typical characteristics are provided at 25°C and VDD = 12 V unless otherwise noted)
Figure 11. IDD (Static) vs. Temperature
Figure 12. IDD (Static) vs. Temperature
Figure 13. Input Thresholds vs. Supply Voltage
Figure 14. Input Thresholds vs. Supply Voltage
Figure 15. Input Thresholds % vs. Supply Voltage
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FAN3100T, FAN3100C
TYPICAL PERFORMANCE CHARACTERISTICS (continued)
(Typical characteristics are provided at 25°C and VDD = 12 V unless otherwise noted)
Figure 17. TTL Input Thresholds vs. Temperature
Figure 16. CMOS Input Thresholds vs. Temperature
Figure 18. UVLO Thresholds vs. Temperature
Figure 19. UVLO Hysteresis vs. Temperature
Figure 21. Propagation Delay vs. Supply Voltage
Figure 20. Propagation Delay vs. Supply Voltage
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FAN3100T, FAN3100C
TYPICAL PERFORMANCE CHARACTERISTICS (continued)
(Typical characteristics are provided at 25°C and VDD = 12 V unless otherwise noted)
Figure 23. Propagation Delay vs. Supply Voltage
Figure 22. Propagation Delay vs. Supply Voltage
Figure 24. Propagation Delay vs. Temperature
Figure 25. Propagation Delay vs. Temperature
Figure 26. Propagation Delay vs. Temperature
Figure 27. Propagation Delay vs. Temperature
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FAN3100T, FAN3100C
TYPICAL PERFORMANCE CHARACTERISTICS (continued)
(Typical characteristics are provided at 25°C and VDD = 12 V unless otherwise noted)
Figure 29. Rise Time vs. Supply Voltage
Figure 28. Fall Time vs. Supply Voltage
Figure 30. Rise and Fall Time vs. Temperature
Figure 32. Rise / Fall Waveforms with 10 nF Load
Figure 31. Rise / Fall Waveforms with 1 nF Load
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FAN3100T, FAN3100C
TYPICAL PERFORMANCE CHARACTERISTICS (continued)
(Typical characteristics are provided at 25°C and VDD = 12 V unless otherwise noted)
Figure 33. Quasi−Static Source Current with VDD = 12 V
Figure 34. Quasi−Static Sink Current with VDD = 12 V
Figure 35. Quasi−Static Source Current with VDD = 8 V
Figure 36. Quasi−Static Sink Current with VDD = 8 V
VDD
4.7 mF
Ceramic
470 mF
Al. El.
Current Probe
LECROY AP015
IOUT
IN
1 kHz
1 mF
Ceramic
VOUT
CLOAD
1 mF
Figure 37. Quasi−Static IOUT / VOUT Test Circuit
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FAN3100T, FAN3100C
APPLICATIONS INFORMATION
Input Threshold
situation often occurs in synchronous rectifier applications
because the body diode is generally conducting before the
MOSFET is switched on. The output pin slew rate is
determined by VDD voltage and the load on the output. It is
not user adjustable, but if a slower rise or fall time at the
MOSFET gate is needed, a series resistor can be added.
The FAN3100 offers TTL or CMOS input thresholds. In
the FAN3100T, the input thresholds meet industry−standard
TTL logic thresholds, independent of the VDD voltage, and
there is a hysteresis voltage of approximately 0.4 V. These
levels permit the inputs to be driven from a range of input
logic signal levels for which a voltage over 2 V is considered
logic HIGH. The driving signal for the TTL inputs should
have fast rising and falling edges with a slew rate of 6 V/ms
or faster, so the rise time from 0 to 3.3 V should be 550 ns
or less. With reduced slew rate, circuit noise could cause
the driver input voltage to exceed the hysteresis voltage and
retrigger the driver input, causing erratic operation. In the
FAN3100C, the logic input thresholds are dependent on
the VDD level and, with VDD of 12 V, the logic rising edge
threshold is approximately 55% of VDD and the input falling
edge threshold is approximately 38% of VDD. The CMOS
input configuration offers a hysteresis voltage of
approximately 17% of VDD. The CMOS inputs can be used
with relatively slow edges (approaching DC) if good
decoupling and bypass techniques are incorporated in
the system design to prevent noise from violating the input
voltage hysteresis window. This allows setting precise
timing intervals by fitting an R−C circuit between
the controlling signal and the IN pin of the driver. The slow
rising edge at the IN pin of the driver introduces a delay
between the controlling signal and the OUT pin of the driver.
VDD
Input
stage
VOUT
Figure 38. MillerDrivet Output Architecture
Under−Voltage Lockout
In the IDD (static) typical performance graphs
(Figure 5 − Figure 6 and Figure 11 − Figure 12), the curve is
produced with all inputs floating (OUT is LOW) and
indicates the lowest static IDD current for the tested
configuration. For other states, additional current flows
through the 100 kW resistors on the inputs and outputs
shown in the block diagrams (Figure 1 − Figure 2). In these
cases, the actual static IDD current is the value obtained from
the curves plus this additional current.
The FAN3100 start−up logic is optimized to drive ground
referenced N−channel MOSFETs with a under−voltage
lockout (UVLO) function to ensure that the IC starts up in
an orderly fashion. When VDD is rising, yet below the 3.9 V
operational level, this circuit holds the output LOW,
regardless of the status of the input pins. After the part is
active, the supply voltage must drop 0.2 V before the part
shuts down. This hysteresis helps prevent chatter when low
VDD supply voltages have noise from the power switching.
This configuration is not suitable for driving high−side
P−channel MOSFETs because the low output voltage of the
driver would turn the P−channel MOSFET on with VDD
below 3.9 V.
MillerDrivet Gate Drive Technology
VDD Bypass Capacitor Guidelines
Static Supply Current
FAN3100 drivers incorporate the MillerDrive
architecture shown in Figure 38 for the output stage, a
combination of bipolar and MOS devices capable of
providing large currents over a wide range of supply voltage
and temperature variations. The bipolar devices carry the
bulk of the current as OUT swings between 1/3 to 2/3 VDD
and the MOS devices pull the output to the high or low rail.
The purpose of the MillerDrive architecture is to speed up
switching by providing the highest current during the Miller
plateau region when the gate−drain capacitance of the
MOSFET is being charged or discharged as part of the
turn−on / turn−off process. For applications that have zero
voltage switching during the MOSFET turn−on or turn−off
interval, the driver supplies high peak current for fast
switching even though the Miller plateau is not present. This
To enable this IC to turn a power device on quickly, a local,
high−frequency, bypass capacitor CBYP with low ESR and
ESL should be connected between the VDD and GND pins
with minimal trace length. This capacitor is in addition to
bulk electrolytic capacitance of 10 mF to 47 mF often found
on driver and controller bias circuits.
A typical criterion for choosing the value of CBYP is to
keep the ripple voltage on the VDD supply ≤ 5%. Often this
is achieved with a value ≥ 20 times the equivalent load
capacitance CEQV, defined here as Qgate/VDD. Ceramic
capacitors of 0.1 mF to 1 mF or larger are common choices,
as are dielectrics, such as X5R and X7R, which have good
temperature characteristics and high pulse current
capability.
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FAN3100T, FAN3100C
If circuit noise affects normal operation, the value of CBYP
may be increased to 50−100 times the CEQV, or CBYP may
be split into two capacitors. One should be a larger value,
based on equivalent load capacitance, and the other a smaller
value, such as 1−10 nF, mounted closest to the VDD and
GND pins to carry the higher−frequency components of
the current pulses.
VDD
VDS
CBYP
FAN3100
PWM
Layout and Connection Guidelines
The FAN3100 incorporates fast−reacting input circuits,
short propagation delays, and powerful output stages
capable of delivering current peaks over 2 A to facilitate
voltage transition times from under 10 ns to over 100 ns.
The following layout and connection guidelines are strongly
recommended:
• Keep high−current output and power ground paths
separate from logic input signals and signal ground
paths. This is especially critical when dealing with
TTL−level logic thresholds.
• Keep the driver as close to the load as possible to
minimize the length of high−current traces. This
reduces the series inductance to improve high−speed
switching, while reducing the loop area that can radiate
EMI to the driver inputs and other surrounding
circuitry.
• The FAN3100 is available in two packages with
slightly different pinouts, offering similar performance.
In the 6−pin MLP package, Pin 2 is internally
connected to the input analog ground and should be
connected to power ground, Pin 5, through a short
direct path underneath the IC. In the 5−pin SOT23, the
internal analog and power ground connections are made
through separate, individual bond wires to Pin 2, which
should be used as the common ground point for power
and control signals.
• Many high−speed power circuits can be susceptible to
noise injected from their own output or other external
sources, possibly causing output re−triggering. These
effects can be especially obvious if the circuit is tested
in breadboard or non−optimal circuit layouts with long
input, enable, or output leads. For best results, make
connections to all pins as short and direct as possible.
• The turn−on and turn−off current paths should be
minimized as discussed in the following sections.
Figure 39 shows the pulsed gate drive current path when
the gate driver is supplying gate charge to turn the MOSFET
on. The current is supplied from the local bypass capacitor,
CBYP, and flows through the driver to the MOSFET gate and
to ground. To reach the high peak currents possible, the
resistance and inductance in the path should be minimized.
The localized CBYP acts to contain the high peak current
pulses within this driver−MOSFET circuit, preventing them
from disturbing the sensitive analog circuitry in the PWM
controller.
Figure 39. Current Path for MOSFET Turn−On
Figure 40 shows the current path when the gate driver
turns the MOSFET off. Ideally, the driver shunts the current
directly to the source of the MOSFET in a small circuit loop.
For fast turn−off times, the resistance and inductance in this
path should be minimized.
VDS
VDD
CBYP
FAN3100
PWM
Figure 40. Current Path for MOSFET Turn−Off
Truth Table of Logic Operation
The truth table indicates the operational states using the
dual−input configuration. In a non−inverting driver
configuration, the IN− pin should be a logic LOW signal. If
the IN− pin is connected to logic HIGH, a disable function
is realized, and the driver output remains LOW regardless of
the state of the IN+ pin.
Table 1. FAN3100 TRUTH TABLE
IN+
IN−
OUT
0
0
0
0
1
0
1
0
1
1
1
0
In the non−inverting driver configuration in Figure 41, the
IN− pin is tied to ground and the input signal (PWM) is
applied to IN+ pin. The IN− pin can be connected to logic
HIGH to disable the driver and the output remains LOW,
regardless of the state of the IN+ pin.
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FAN3100T, FAN3100C
and the input signal applied to IN–, the OUT pulses are
inverted with respect to the input. At power up, the inverted
output remains LOW until the VDD voltage reaches the
turn−on threshold, then it follows the input with inverted
phase.
VDD
PWM
IN+
IN−
FAN 3100
OUT
GND
Turn−on Threshold
VDD
Figure 41. Dual−Input Driver Enabled,
Non−Inverting Configuration
IN−
In the inverting driver application shown in Figure 42, the
IN+ pin is tied HIGH. Pulling the IN+ pin to GND forces the
output LOW, regardless of the state of the IN− pin.
IN+
(VDD)
VDD
OUT
Figure 44. Inverting Start−Up Waveforms
IN+
PWM
IN−
FAN3100
OUT
GND
Thermal Guidelines
Gate drivers used to switch MOSFETs and IGBTs at high
frequencies can dissipate significant amounts of power. It is
important to determine the driver power dissipation and the
resulting junction temperature in the application to ensure
that the part is operating within acceptable temperature
limits.
The total power dissipation in a gate driver is the sum of
two components; PGATE and PDYNAMIC:
Figure 42. Dual−Input Driver Enabled, Inverting
Configuration
Operational Waveforms
At power up, the driver output remains LOW until the
VDD voltage reaches the turn−on threshold. The magnitude
of the OUT pulses rises with VDD until steady−state VDD is
reached. The non−inverting operation illustrated in
Figure 43 shows that the output remains LOW until the
UVLO threshold is reached, then the output is in−phase with
the input.
VDD
P TOTAL + P GATE ) P DYNAMIC
(eq. 1)
Gate Driving Loss: The most significant power loss
results from supplying gate current (charge per unit time) to
switch the load MOSFET on and off at the switching
frequency. The power dissipation that results from driving
a MOSFET at a specified gate−source voltage, VGS, with
gate charge, QG, at switching frequency, fSW, is determined
by:
Turn−on Threshold
P GATE + Q G @ V GS @ f SW
IN−
(eq. 2)
Dynamic Pre−drive / Shoot−through Current: A power
loss resulting from internal current consumption under
dynamic operating conditions, including pin pull−up /
pull−down resistors, can be obtained using the IDD
(no−Load) vs. Frequency graphs in Typical Performance
Characteristics to determine the current IDYNAMIC drawn
from VDD under actual operating conditions:
IN+
OUT
Figure 43. Non−Inverting Start−Up Waveforms
P DYNAMIC + I DYNAMIC @ V DD
For the inverting configuration of Figure 42, start−up
waveforms are shown in Figure 44. With IN+ tied to VDD
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14
(eq. 3)
FAN3100T, FAN3100C
Once the power dissipated in the driver is determined, the
driver junction rise with respect to circuit board can be
evaluated using the following thermal equation, assuming
YJB was determined for a similar thermal design (heat
sinking and air flow):
T J + P TOTAL @ Y JB ) T B
where:
TJ
The 5−pin SOT23 has a junction−to−lead thermal
characterization parameter YJB = 51°C/W.
In a system application, the localized temperature around
the device is a function of the layout and construction of the
PCB along with airflow across the surfaces. To ensure
reliable operation, the maximum junction temperature of the
device must be prevented from exceeding the maximum
rating of 150°C; with 80% derating, TJ would be limited to
120°C. Rearranging Equation 4 determines the board
temperature required to maintain the junction temperature
below 120°C:
(eq. 4)
= driver junction temperature;
= (psi) thermal;
YJB
characterization parameter relating temperature rise to total
power dissipation;
TB
= board temperature in location defined in
the Thermal Characteristics table
T B,MAX + T J * P TOTAL @ Y JB
T B,MAX + 120°C * 0.24W @ 51°CńW + 108°C (eq. 9)
For comparison purposes, replace the 5−pin SOT23 used
in the previous example with the 6−pin MLP package with
YJB = 2.8°C/W. The 6−pin MLP package can operate at a
PCB temperature of 119°C, while maintaining the junction
temperature below 120°C. This illustrates that the
physically smaller MLP package with thermal pad offers a
more conductive path to remove the heat from the driver.
Consider the tradeoffs between reducing overall circuit size
with junction temperature reduction for increased
reliability.
In a typical forward converter application with 48 V input,
as shown in Figure 45, the FDS2672 would be a potential
MOSFET selection. The typical gate charge would be 32 nC
with VGS = VDD = 10 V. Using a TTL input driver at
a switching frequency of 500 kHz, the total power
dissipation can be calculated as:
P GATE + 32nC @ 10V @ 500kHz + 0.160W
(eq. 5)
P DYNAMIC + 8mA @ 10V + 0.080W
(eq. 6)
P TOTAL + 0.24W
(eq. 7)
(eq. 8)
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15
FAN3100T, FAN3100C
TYPICAL APPLICATION DIAGRAMS
VIN
ENABLE
Active LOW
FAN3100
PWM
IN+
AGND
VDD
IN−
1
6
2
5
3
4
PGND
OUT
Figure 45. Forward Converter, Primary−Side Gate Drive (MLP Package Show)
Q1
VIN
T2
T1
D1
VDD
D2
FAN3100
Q2
CC
PWM
VSEC
0.1 μF
Figure 46. Driver for Two−Transistor Forward Converter Gate Transformer
VIN
Q1
T1
D1
PWM
Control/
Isolation
L
VSEC
D2
VOUT
Q5
Q3
Q2
SR
VDRV
ISOLATION
FAN3100
Figure 47. Secondary Synchronous Rectifier Driver
VDD
R
IN
FAN3100C
OUT
C
Delay
IN
OUT
Figure 48. Programmable Delay Using CMOS Input
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16
FAN3100T, FAN3100C
ORDERING INFORMATION
Input Threshold
Package
Shipping†
FAN3100CMPX
CMOS
6−Lead, 2x2 mm MLP
3,000 / Tape & Reel
FAN3100CSX
CMOS
5−Pin SOT23
3,000 / Tape & Reel
FAN3100TMPX
TTL
6−Lead, 2x2 mm MLP
3,000 / Tape & Reel
FAN3100TSX
TTL
5−Pin SOT23
3,000 / Tape & Reel
Part Number
†For information on tape and reel specifications, including part orientation and tape sizes, please refer to our Tape and Reel Packaging
Specifications Brochure, BRD8011/D.
Table 2. RELATED PRODUCTS
Part
Number
Type
Gate Drive
(Note 12)
(Sink/Src)
Input
Threshold
Logic
Package
FAN3100T
Single 2 A
+2.5 A/−1.8 A
TTL
Single Channel of Two−Input/One−Output
SOT23−5, MLP6
FAN3100C
Single 2 A
+2.5 A/−1.8A
CMOS
Single Channel of Two−Input/One−Output
SOT23−5, MLP6
FAN3226C
Dual 2 A
+2.4 A/−1.6 A
CMOS
Dual Inverting Channels + Dual Enable
SOIC8, MLP8
FAN3226T
Dual 2 A
+2.4 A/−1.6 A
TTL
Dual Inverting Channels + Dual Enable
SOIC8, MLP8
FAN3227C
Dual 2 A
+2.4 A/−1.6 A
CMOS
Dual Non−Inverting Channels + Dual Enable
SOIC8, MLP8
FAN3227T
Dual 2 A
+2.4 A/−1.6 A
TTL
Dual Non−Inverting Channels + Dual Enable
SOIC8, MLP8
FAN3228C
Dual 2 A
+2.4 A/−1.6 A
CMOS
Dual Channels of Two−Input/One−Output,
Pin Config. 1
SOIC8, MLP8
FAN3228T
Dual 2 A
+2.4 A/−1.6 A
TTL
Dual Channels of Two−Input/One−Output,
Pin Config. 1
SOIC8, MLP8
FAN3229C
Dual 2 A
+2.4 A/−1.6 A
CMOS
Dual Channels of Two−Input/One−Output,
Pin Config. 2
SOIC8, MLP8
FAN3229T
Dual 2 A
+2.4 A/−1.6 A
TTL
Dual Channels of Two−Input/One−Output,
Pin Config. 2
SOIC8, MLP8
FAN3223C
Dual 4 A
+4.3 A/−2.8 A
CMOS
Dual Inverting Channels + Dual Enable
SOIC8, MLP8
FAN3223T
Dual 4 A
+4.3 A/−2.8 A
TTL
Dual Inverting Channels + Dual Enable
SOIC8, MLP8
FAN3224C
Dual 4 A
+4.3 A/−2.8 A
CMOS
Dual Non−Inverting Channels + Dual Enable
SOIC8, MLP8
FAN3224T
Dual 4 A
+4.3 A/−2.8 A
TTL
Dual Non−Inverting Channels + Dual Enable
SOIC8, MLP8
FAN3225C
Dual 4 A
+4.3 A/−2.8 A
CMOS
Dual Channels of Two−Input/One−Output
SOIC8, MLP8
FAN3225T
Dual 4 A
+4.3 A/−2.8 A
TTL
Dual Channels of Two−Input/One−Output
SOIC8, MLP8
12. Typical currents with OUT at 6 V and VDD = 12 V.
MillerDrive is trademark of Semiconductor Components Industries, LLC (SCILLC) or its subsidiaries in the United States and/or other countries.
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17
MECHANICAL CASE OUTLINE
PACKAGE DIMENSIONS
WDFN6 2x2, 0.65P
CASE 511CY
ISSUE O
0.05
C
2.0
DATE 31 JUL 2016
A
1.72
2X
1.68
B
6
4
0.15
2.0
1.21
0.90
2.25
0.52(6X)
0.05
PIN#1 IDENT
TOP VIEW
C
1
2X
3
0.42(6X)
0.65
RECOMMENDED
LAND PATTERN
0.75±0.05
0.10
C
0.20±0.05
0.08
NOTES:
C
SIDE VIEW
0.025±0.025
C
A. PACKAGE DOES NOT FULLY CONFORM
TO JEDEC MO−229 REGISTRATION
SEATING
PLANE
B. DIMENSIONS ARE IN MILLIMETERS.
2.00±0.05
C. DIMENSIONS AND TOLERANCES PER
ASME Y14.5M, 2009.
1.40±0.05
(0.70)
(0.20)4X
PIN #1 IDENT
1
0.32±0.05
D. LAND PATTERN RECOMMENDATION IS
EXISTING INDUSTRY LAND PATTERN.
3
(0.40)
(6X)
0.80±0.05
(0.60)
6
4
0.30±0.05
0.65
1.30
BOTTOM VIEW
DOCUMENT NUMBER:
DESCRIPTION:
98AON13613G
WDFN6 2X2, 0.65P
(6X)
0.10
C
0.05
C
A
B
Electronic versions are uncontrolled except when accessed directly from the Document Repository.
Printed versions are uncontrolled except when stamped “CONTROLLED COPY” in red.
PAGE 1 OF 1
ON Semiconductor and
are trademarks of Semiconductor Components Industries, LLC dba ON Semiconductor or its subsidiaries in the United States and/or other countries.
ON Semiconductor reserves the right to make changes without further notice to any products herein. ON Semiconductor makes no warranty, representation or guarantee regarding
the suitability of its products for any particular purpose, nor does ON Semiconductor assume any liability arising out of the application or use of any product or circuit, and specifically
disclaims any and all liability, including without limitation special, consequential or incidental damages. ON Semiconductor does not convey any license under its patent rights nor the
rights of others.
© Semiconductor Components Industries, LLC, 2019
www.onsemi.com
MECHANICAL CASE OUTLINE
PACKAGE DIMENSIONS
SOT−23, 5 Lead
CASE 527AH−01
ISSUE O
D
DATE 19 DEC 2008
SYMBOL
E1
MIN
NOM
A
0.90
1.45
A1
0.00
0.15
A2
0.90
b
0.30
0.50
c
0.08
0.22
E
1.15
D
2.90 BSC
E
2.80 BSC
E1
1.60 BSC
L
1.30
0.95 BSC
e
e
0.45
0.30
L1
PIN #1 IDENTIFICATION
MAX
0.60
0.60 REF
L2
0.25 REF
θ
0°
4°
8°
θ1
5°
10°
15°
θ2
5°
10°
15°
TOP VIEW
θ1
A2
A
b
θ2
A1
SIDE VIEW
θ
L1
L2
L
c
END VIEW
Notes:
(1) All dimensions in millimeters. Angles in degrees.
(2) Complies with JEDEC standard MO-178.
DOCUMENT NUMBER:
DESCRIPTION:
98AON34320E
SOT−23, 5 LEAD
Electronic versions are uncontrolled except when accessed directly from the Document Repository.
Printed versions are uncontrolled except when stamped “CONTROLLED COPY” in red.
PAGE 1 OF 1
ON Semiconductor and
are trademarks of Semiconductor Components Industries, LLC dba ON Semiconductor or its subsidiaries in the United States and/or other countries.
ON Semiconductor reserves the right to make changes without further notice to any products herein. ON Semiconductor makes no warranty, representation or guarantee regarding
the suitability of its products for any particular purpose, nor does ON Semiconductor assume any liability arising out of the application or use of any product or circuit, and specifically
disclaims any and all liability, including without limitation special, consequential or incidental damages. ON Semiconductor does not convey any license under its patent rights nor the
rights of others.
© Semiconductor Components Industries, LLC, 2019
www.onsemi.com
ON Semiconductor and
are trademarks of Semiconductor Components Industries, LLC dba ON Semiconductor or its subsidiaries in the United States and/or other countries.
ON Semiconductor owns the rights to a number of patents, trademarks, copyrights, trade secrets, and other intellectual property. A listing of ON Semiconductor’s product/patent
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