FAN8811MNTXG

High-Frequency, High Side and Low Side Gate Driver FAN8811 www.onsemi.com WDFN10 4x4, 0.8P CASE 511DU MARKING DIAGRAM HI NC LI VSS LO The FAN8811 is high side and low side gate−drive IC designed for high−voltage, high−speed, driving MOSFETs operating up to 80 V. The FAN8811 integrates a driver IC and a bootstrap diode. The driver IC features low delay time and matched PWM input propagation delays, which further enhance the performance of the part. The high speed dual gate drivers are designed to drive both the high−side and low−side of N−Channel MOSFETs in a half bridge or synchronous buck configuration. The floating high−side driver is capable of operating with supply voltages of up to 80 V. In the dual gate driver, the high side and low side each have independent inputs to allow maximum flexibility of input control signals in the application. The PWM input signal (high level) can be 3.3 V, 5 V or up to VDD logic input to cover all possible applications. The bootstrap diode for the high−side driver bias supply is integrated in the chip. The high−side driver is referenced to the switch node (HS) which is typically the source pin of the high−side MOSFET and drain pin of the low−side MOSFET. The low−side driver is referenced to VSS which is typically ground. The functions contained are the input stages, UVLO protection, level shift, bootstrap diode, and output driver stages. ZXYTT FAN8811T MPX Features NC HS HO HB • • • • • Drives two N−Channel MOSFETs in High & Low Side Integrated Bootstrap Diode for High Side Gate Drive Bootstrap Supply Voltage Range up to 100 V 3 A Source, 6 A Sink Output Current Capability Drives 1 nF Load with Typical Rise/Fall Times of 6 ns/4 ns TTL Compatible Input Thresholds Wide Supply Voltage Range 7.5 V to 16 V (Absolute Maximum 18 V) Fast Propagation Delay Times (Typ. 30 ns) 2 ns Delay Matching (Typical) Under−Voltage Lockout (UVLO) Protection for Drive Voltage Operating Junction Temperature Range of −40°C to 125°C These Devices are Pb−Free, Halogen Free/BFR Free and are RoHS Compliant VDD • • • • • • • FAN8811T= Specific Device Code Z = Plant Code X = 1−Digit Year Code Y = 1−Digit Week Code TT = 2−Digit Die Run Code MP = Package Type X = Reel Package ORDERING INFORMATION See detailed ordering and shipping information in the package dimensions section on page 13 of this data sheet. Typical Applications • • • • • Power Supplies for Telecom and Datacom Half−Bridge and Full−Bridge Converters Synchronous−Buck Converters Two−Switch Forward Converters Class−D Audio Amplifiers © Semiconductor Components Industries, LLC, 2018 July, 2021 − Rev. 4 1 Publication Order Number: FAN8811/D FAN8811 TYPICAL APPLICATIONS L VDC Supply Voltage L COUT RLGATE RHGATE CIN V DD LO HB V SS O A D CHB HO LI FAN8811 HS HI NC NC PWM Controller FEEDBACK Figure 1. Application Schematic − Synchronous Buck Converter VDC SECONDARY SIDE CIRCUIT RHGATE PWM Controller NC NC HI HS LI FAN8811 HO CHB HB LO V DD CIN Supply Voltage VSS RLGATE ISOLATION AND FEEDBACK Figure 2. Application Schematic − Half Bridge Converter www.onsemi.com 2 FAN8811 BLOCK DIAGRAM VDD 1 UVLO HI LI 2 HB 3 HO 4 HS LEVEL SHIFT 7 8 UVLO 10 LO VSS 9 NC 5 6 Figure 3. Simplified Block Diagram PIN CONNECTIONS V DD LO HB V SS FAN8811 HO LI HS HI NC NC Figure 4. Pin Assignments − 10 Lead MLP (Top View) Table 1. PIN DESCRIPTION Pin No. Pin Name Description 1 VDD Logic and low−side gate driver power supply voltage 2 HB High−side floating supply 3 HO High−side driver output 4 HS High−voltage floating supply return 5 NC No Connection 6 NC No Connection 7 HI Logic input for High−side gate driver output 8 LI Logic input for Low−side gate driver output 9 VSS Logic Ground 10 LO Low−side driver output www.onsemi.com 3 NC FAN8811 Table 2. MAXIMUM RATINGS All voltage parameters are referenced to VSS, unless otherwise noted. Symbol Parameter Min. Max. Units −0.3 18 V −1 100 V −(24 – VDD) 100 V −0.3 VDD + 0.3 V −2 VDD + 0.3 V VHS – 0.3 VHB + 0.3 V VHS – 2 VHB + 0.3 V Logic Input Voltage −0.3 VDD + 0.3 V High−Side Floating Supply Voltage −0.3 100 V VHS to VHB Supply Voltage −0.3 18 V Operating Junction Temperature −55 150 °C VDD Low−Side and Logic Fixed Supply Voltage VHS High−Side Floating Supply Offset Voltage(Note 1) Repetitive Pulse (< 100 ns)(Note 2) VLO Low−Side Output Voltage, LO Pin Repetitive Pulse (< 100 ns)(Note 2) VHO High−Side Floating Output Voltage, HO Pin Repetitive Pulse (< 100 ns)(Note 2) VLI, VHI VHB VHB – VHS TJ, Stresses exceeding those listed in the Maximum Ratings table may damage the device. If any of these limits are exceeded, device functionality should not be assumed, damage may occur and reliability may be affected. 1. The VHS negative voltage capability can be calculated using (VHB –VHS)−18 V base on VHB, due to its dependence on VDD voltage level. 2. Verified at bench characterization. Table 3. ESD AND MSL Symbol ESDHBM Parameters Electrostatic Discharge Capability ESDCDM Value Unit.s Human Body Model,per AEC Q100−002 2000 V Charged Device Model, AEC Q100−011 1000 Table 4. THERMAL INFORMATION Symbol Parameters PD Power Dissipation (Note 3) qJA Thermal Resistance Junction−Air 1S0P with thermal vias (Note 4) Value Unit.s 0.6 W 1S2P with thermal vias (Note 5) 2.4 1S0P with thermal vias (Note 4) 163 1S2P with thermal vias (Note 5) 41 °C/W 3. JEDEC standard: JESD51−2, JESD51−3. Mounted on 76.2 x 114.3 x1.6 mm PCB (FR−4 glass epoxy material) 4. 1S0P with thermal via: one signal layer with zero power plane and thermal via 5. 1S2P with thermal via: one signal layer with two power planes and thermal via Table 5. RECOMMENDED OPERATING RANGES All voltage parameters are referenced to VSS Symbol Parameters VDD Supply Voltage VHS High Side Floating Return VHB dVSW/dt TJ Test Condition Min. Max. Units DC 7.5 16 V DC −1 80 V Repetitive Pulse (< 100 ns) −(24 – VDD) 100 V DC VHS + 7.5 VHS + 16 V 50 V/ns 125 °C Voltage on HB Voltage Slew Rate on SW Operating Temperature −40 Functional operation above the stresses listed in the Recommended Operating Ranges is not implied. Extended exposure to stresses beyond the Recommended Operating Ranges limits may affect device reliability. www.onsemi.com 4 FAN8811 Table 6. ELECTRICAL CHARACTERISTICS VDD = VHB = 12 V, VHS = VSS = 0 V, TA = TJ = −40°C to 125°C, no load on HO or LO, unless otherwise noted. Symbol Parameters Test Condition Min. Typ. Max. Units Power Supply Section IDD VDD Quiescent Current VHI = 0 V; VLI = 0 V 0.17 0.3 mA IDDO VDD Operating Current fSW = 500 kHz 1.5 3.0 mA IHB HB Quiescent Current VHI = 0 V; VLI = 0 V 0.1 0.2 mA IHBO HB Operating Current fSW = 500 kHz 1.9 3.0 mA IHBS HB to VSS Quiescent Current VHS = VHB = 80 V IHBSO HB to VSS Operating Current fSW = 500 kHz VDDR VDD UVLO Threshold VDD Rising 6.2 VDDH VDD UVLO Hysteresis VHBR HB UVLO Threshold HB Rising 5.5 VHBH HB UVLO Hysteresis 0 10 mA 0.3 1.0 mA 6.8 7.4 V 0.6 6.3 V 7.2 0.4 V V Input Logic Section VIH High Level Input Voltage Threshold 1.80 2.2 2.50 V VIL Low Level Input Voltage Threshold 1.3 1.7 2.0 V VIHYS RIN Input Logic Voltage Hysteresis 0.5 V Input Pull−down Resistance 100 kW Bootstrap Diode VFL Forward Voltage @ Low Current IVDD−HB = 100 mA 0.55 0.8 V VFH Forward Voltage @ High Current IVDD−HB = 100 mA 0.8 1.0 V RD Dynamic Resistance IVDD−HB = 100 mA 0.7 1.5 W tBS (Note 6) Diode Turn−off Time IF = 20 mA, IREV = 0.5 A 20 VOLL Low Level Output Voltage ILO = 100 mA 0.06 0.15 V VOHL High Level Output Voltage ILO = −100 mA, VOHL = VDD − VLO 0.16 0.28 V IOHL (Note 6) Peak Pull−up Current VLO = 0 V 3 IOLL (Note 6) ns Low Side Driver A Peak Pull−down Current VLO = 12 V 6 A tR_LO LO Rise Time 10% to 90%, CLOAD = 1 nF 6 ns tF_LO LO Fall Time 90% to 10%, CLOAD = 1 nF 4 tR_LO1 LO Rise Time 3 V to 9 V, CLOAD = 100 nF 300 500 ns ns tF_LO1 LO Fall Time 9 V to 3 V, CLOAD = 100 nF 140 300 ns tLPHL LI = Low Propagation Delay VLI Falling to VLO Falling, CLOAD = 0 28 43 ns tLPLH LI = High Propagation Delay VLI Rising to VLO Rising, CLOAD = 0 30 45 ns VOLH Low Level Output Voltage IHO = 100 mA 0.06 0.15 V VOHH High Level Output Voltage IHO = −100 mA, VOHH = VHB − VHO 0.16 0.28 V IOHH (Note 6) Peak Pull−up Current VHO = 0 V 3 A IOLH (Note 6) Peak Pull−down Current VHO = 12 V 6 A tR_HO HO Rise Time 10% to 90%, CLOAD = 1 nF 6 ns tF_HO HO Fall Time 90% to 10%, CLOAD = 1 nF 4 ns tR_HO1 HO Rise Time 3 V to 9 V, CLOAD = 100 nF 300 500 ns tF_HO1 HO Fall Time 9 V to 3 V, CLOAD = 100 nF 140 300 ns tHPHL HI = Low Propagation Delay VHI Falling to VHO Falling, CLOAD = 0 28 43 ns tHPLH HI = High Propagation Delay VHI Rising to VHO Rising, CLOAD = 0 30 45 ns High Side Driver www.onsemi.com 5 FAN8811 Table 6. ELECTRICAL CHARACTERISTICS VDD = VHB = 12 V, VHS = VSS = 0 V, TA = TJ = −40°C to 125°C, no load on HO or LO, unless otherwise noted. Symbol Parameters Test Condition Min. Typ. Max. Units Delay Matching tMON HI Turn−OFF to LI Turn−ON 2 10 ns tMOFF LI Turn−OFF to HI Turn−ON 2 10 ns 50 ns Minimum Pulse Width tPW Minimum Pulse Width for HI and LI (Note 6) Product parametric performance is indicated in the Electrical Characteristics for the listed test conditions, unless otherwise noted. Product performance may not be indicated by the Electrical Characteristics if operated under different conditions. 6. These parameters are guaranteed by design. TYPICAL CHARACTERISTICS Typical characteristics are provided at 25°C and VDD, VHB = 12 V unless otherwise noted. Figure 5. Quiescent Current vs. Temperature Figure 6. Quiescent Current vs. VDD (VHB) Figure 7. Operating Current vs. Temperature Figure 8. IDD Operating Current vs. Frequency www.onsemi.com 6 FAN8811 TYPICAL CHARACTERISTICS Figure 9. IHB Operating Current vs. Frequency Figure 10. Input Threshold vs. Temperature Figure 11. Input Threshold vs. VDD Figure 12. VDD UVLO Threshold vs. Temperature Figure 13. VHB UVLO Threshold vs. Temperature Figure 14. Bootstrap Diode VF vs. Temperature www.onsemi.com 7 FAN8811 TYPICAL CHARACTERISTICS Figure 16. VOH, VOL Voltage vs. VDD (VHB) Figure 15. VOH, VOL Voltage vs. Temperature Figure 17. Low Side Propagation Delay vs. Temperature Figure 18. High Side Propagation Delay vs. Temperature Figure 19. Low Side Propagation Delay vs. VDD Figure 20. High Side Propagation Delay vs. VHB www.onsemi.com 8 FAN8811 TYPICAL CHARACTERISTICS Figure 21. HO, LO Peak Source Current vs. Supply Voltage Figure 22. HO, LO Peak Sink Current vs. Supply Voltage Figure 23. Bootstrap Diode Forward Voltage vs. Temperature www.onsemi.com 9 FAN8811 Switching Time Definitions Figure 23 shows the switching time waveforms definitions of the turn on and off propagation delay times. HIN (LIN) 50% 50% tHPLH tLPLH tHPHL tLPHL 90% LIN HIN 90% LO 50% HO (LO) 50% 10% 10% HO tF tR tMON tMOFF Figure 24. Timing Diagrams Input to Output Definitions Figure 24 shows an input to output timing diagram for overall operation. VDD UVLO period VDD VDD UVLO threshold voltage : Typ. 6.8 V VDD UVLO Hysteresis HB UVLO period HB HI HB UVLO threshold voltage : Typ. 6.3 V VDD UVLO Hysteresis PWM Input Threshold PWM Input Threshold LI HO LO Figure 25. Overall Operation Timing Diagram www.onsemi.com 10 FAN8811 APPLICATIONS INFORMATION differential voltage is below the specified threshold. The HB UVLO rise threshold is 6.3 V with 0.4 V hysteresis. The FAN8811 is designed to drive high side and the low side N−channel power MOSFETs in a half bridge or synchronous buck. The driver IC integrates a bootstrap diode for the high side driver bias supply. High side and Low side outputs are independently controlled by each of input control signals with TTL or logic compatibility. The floating high side driver can operate with supply voltage up to 80 V. The FAN8811 functions consist of the input stage, level shift, bootstrap diode, Under−Voltage Lockout (UVLO) protection and output stage. The UVLO function is included in both the high−and low side. Output Stage The FAN8811 output stage is able to Sink/Source 3.0 A /6.0 A typical which can effectively charge and discharge a 1 nF load in few ns. High speed switching, low resistance and high current capability of both high side and low side drivers allow for efficient switching operation. The low side driver is referenced from VDD to VSS and the high side is referenced from HB to HS. The device logic status shows as below. Input Stage Table 7. DEVICE LOGIC STATUS The input pins (HI,LI) of gate driver devices are based on a TTL compatible input threshold logic that is independent of the VDD supply voltage. The PWM input signal (high level) can be 3.3 V, 5 V or up to VDD logic input to accommodate all possible applications. The input impedance of the FAN8811 is 100 kW nominal. The 100 kW is a pull−down resistance to ground (GND). The logic level compatible input provides a 2.2 V rising threshold and a 1.7 V falling threshold. Status Level Shift HI LI HO LO L L L L L H L H H L H L H H H H X X L L Select Bootstrap Capacitor The level shift circuit is the interface from the high side input to the high side driver stage which is referenced to the switch node (HS). The level shift allows control of the HO output referenced to the HS pin and provides excellent delay matching with the low side driver. To control the high side output drive utilizes a widely used technique for high side level shifter circuit so−called pulsed latch level translators. The maximum allowable voltage drop across the bootstrap capacitor to ensure enough gate−source voltage is highly dependent to the internal under−voltage Lockout level of the gate drive IC, and the voltage level at the source connection of switching node HS. The maximum allowable drop voltage can be obtained by (eq.1) DV HB + V DD * V f * V HB,UVLO (eq. 1) Where: Bootstrap Diode • VDD: Gate drive IC supply voltage • Vf : Static forward voltage drop of bootstrap diode • VHB,UVLO: HB Under−Voltage Lockout level The FAN8811 integrates a high voltage bootstrap diode to generate the high side bias. It is provided to charge high side gate drive bootstrap capacitor. The diode anode is connected to VDD and cathode connected to HB. The boot capacitor should be connected externally to HB and the HS pins, the HB capacitor charge is refreshed every switching cycle when HS transitions to Ground. The bootstrap diode provides fast recovery times, and a low resistance value of 0.7 W typ. The total charge (Qbs) required by the bootstrap capacitor can be calculated by summing the Qg of the MOSFET and the charge required for the level shifter in the gate drive IC which is negligible quantity to compared Qg of the MOSFET. Q BS + Q g ) (I HBS Under−Voltage Lockout (UVLO) Both high side and low side drivers have independent UVLO protections which monitor the VDD supply voltage and HB bootstrap voltage. The function of the UVLO circuits is to ensure that there is enough supply voltages (VDD and HB) to correctly bias high side and low side circuits. This also ensures that the gate of external MOSFETs are driven at an optimum voltage. The VDD UVLO disables both high side and low side drivers when VDD is below the specified threshold. The rise VDD threshold is 6.8 V with 0.6 V hysteresis. The HB UVLO disables only the high side driver when the HB to HS • • • • T ON) (eq. 2) Where: QBS: Total gate charge of bootstrap capacitor Qg: Gate charge of the MOSFET IHBS: Quiescent current in High side gate drive IC. TON: Turning on of MOSFET The guiding criteria for calculating the minimum required bootstrap capacitance can be obtained through (eq.4). C BOOT.MIN w www.onsemi.com 11 Q BS DV HB (eq. 3) FAN8811 Select External Bootstrap Series Resistor The FAN8811 utilizes high speed gate driving for synchronous buck and half bridge applications. In these applications, voltage ringing can be generated by parasitic inductance of the primary power path, consisting of the input capacitor and switching MOSFETs (Coss). To reduce this ringing phenomenon, the first step is to optimize the PCB layout to reduce parasitic components of the power path. The second step is to add a series resistor with the bootstrap capacitor to slow down the turn−on transition of the high side MOSFET. Bias Supply Input Supply HB RB Bootstrap Diode HS Driver • • • • • • • • • LHS− D CIN HO LHS− S HS L LCIN LHS− D LS Driver LS COSS GND VOUT L O A D I OLH + V DD * V f * V OLH R gate I OHL + V DD * V OHL R gate I OLL + V DD * V OLL R gate (eq. 5) Where: IOHH: High side peak source current IOLH: High side peak sink current IOHL: Low side peak source current IOLL: Low side peak sink current Vf : Bootstrap diode forward voltage drop VOHH: High level output voltage drop (high side) VOLH: Low level output voltage drop (high side) VOHL: High level output voltage drop (low side) VOLL: Low level output voltage drop (low side) The total power dissipation is the sum of the gate driver losses and the bootstrap diode losses. The gate driver losses are: • The static and dynamic losses related to the switching frequency • Output load capacitance losses on high and low side drivers • Internal consumption supply voltage, VDD The static losses are due to the quiescent current from the voltage supplies VDD and ground in low side driver and the leakage current in the level shifting stage in high side driver, which are dependent on the voltage supplied on the HS pin and proportional to the duty cycle when only the high side power device is turned on. The quiescent current is consumed by the device through all internal circuits such as input stage, reference voltage, logic circuits, protections, and also any current associated with switching of internal devices when the driver output changes state. The effect of the static losses within the gate driver can be safely assumed to be negligible thanks to the FAN8811 low 0.17 mA quiescent current. The dynamic losses are defined as follows: In the low side driver, the dynamic losses are due to two different sources. One is due to whenever a load capacitor is charged or discharged through a gate resistor, half of the energy that Figure 26 shows the synchronous buck with the parasitic component at the power path. Each of parasitic inductance and low side COSS of MOSFET made up the ringing phenomenon at the HS node, when the high side turns on. When the bootstrap series resistor RB installed with bootstrap capacitor, the bootstrap resistor limits the current available to charge the gate of the high side MOSFET, increasing the time needed to turn the high side MOSFET on. The increased switching time slows the HS node rate of rising and can have a significant impact on the peak voltage on the HS node. We recommend selecting less than 10 W for RB. V DD * V f RB V DD * V f * V OHH R gate Gate Driver Power Dissipation LHS− S Figure 26. Application Circuit with Parasitic Components I BOOT(PEAK) + I OHH + (eq. 4) Select Gate Resistor The gate resistor is also sized to reduce a ringing voltage of the HS node by parasitic inductances and capacitances. But, it limits the current capability of the gate driver output by the resistance value. The limited current capability value by the gate resistor can be obtained (eq.5). www.onsemi.com 12 FAN8811 • The gate driver should be located as close as possible of goes into the capacitance is dissipated in the resistor. The losses in the gate driver resistance, internal and external to the gate driver, and the switching losses of the internal CMOS circuitry. The dynamic losses of the high side driver also have two different sources. One is due to the level shifting circuit and one due to the charging and discharging of the capacitance of the high side. The static losses are neglected here because the total IC power dissipation is mainly dynamic losses of gate drive IC and can be estimated as: P DGATE + 2 CL fS • • • 2 V DD [W] • (eq. 6) The bootstrap circuit power dissipation is the sum of the bootstrap diode losses and the bootstrap resistor losses if any exist. The bootstrap diode loss is the sum of the forward bias power loss that occurs while charging the bootstrap capacitor and the reverse bias power loss that occurs during reverse recovery. Since each of these events happens once per cycle, the diode power loss is proportional to switching frequency. Larger capacitive loads require more current to recharge the bootstrap capacitor, resulting in more losses. switching MOSFET. The VDD capacitor and bootstrap capacitor should be located as near as possible to the device. In order to reduce a ringing voltage of the HS node, the space between high side source and low side drain of the MOSFET should be as small as possible. The exposed pad should be connected to GND plane and use at least four or more vias for improved thermal performance. Avoid driver input pulse signal close to the HS node. One of recommendation layout pattern for the driver is shown in Figure 27. PCB Layout Guideline FAN8811 is a high speed and high current high side and low side driver. To avoid any device malfunction during device operation, it is very important that there is very low parasitic inductance in the current switching path. It is very important that the best layout practices are followed for the PCB layout of the FAN8811. The following should be considered before beginning a PCB layout using the FAN8811. Figure 27. Layout Recommendation ORDERING INFORMATION Output Configuration Temperature Range (5C) Package Shipping† FAN8811TMPX High−Side and Low−Side −40 to 125 WDFN10 4x4, 0.8P (Pb−Free) Tape & Reel (Pin 1 upper left near sprocket holes) FAN8811MNTXG High−Side and Low−Side −40 to 125 WDFN10 4x4, 0.8P (Pb−Free) Tape & Reel (Pin 1 upper right near sprocket holes) Device †For information on tape and reel specifications, including part orientation and tape sizes, please refer to our Tape and Reel Packaging Specifications Brochure, BRD8011/D www.onsemi.com 13 MECHANICAL CASE OUTLINE PACKAGE DIMENSIONS WDFN10 4x4, 0.8P CASE 511DU ISSUE O DOCUMENT NUMBER: DESCRIPTION: 98AON13715G WDFN10 4x4, 0.8P DATE 28 FEB 2017 Electronic versions are uncontrolled except when accessed directly from the Document Repository. Printed versions are uncontrolled except when stamped “CONTROLLED COPY” in red. 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