TNY253PN

This product is not recommended for new designs. TNY253/254/255 TinySwitch Family Energy Efficient, Low Power Off-line Switchers Product Highlights Lowest Cost, Low Power Switcher Solution • Lower cost than RCC, discrete PWM and other integrated/hybrid solutions • Cost effective replacement for bulky linear adapters • Lowest component count • Simple ON/OFF control – no loop compensation devices • No bias winding – simpler, lower cost transformer • Allows simple RC type EMI filter for up to 2 W from universal input or 4 W from 115 VAC input Extremely Energy Efficient • Consumes only 30/60 mW at 115/230 VAC with no load • Meets Blue Angel, Energy Star, Energy 2000 and 200 mW European cell phone requirements for standby • Saves $1 to $4 per year in energy costs (at $0.12/kWHr) compared to bulky linear adapters • Ideal for cellular phone chargers, standby power supplies for PC, TV and VCR, utility meters, and cordless phones. High Performance at Low Cost • High-voltage powered – ideal for charger applications • Very high loop bandwidth provides excellent transient response and fast turn on with practically no overshoot • Current limit operation rejects line frequency ripple • Glitch free output when input is removed • Built-in current limit and thermal protection • 44 kHz operation (TNY253/4) with snubber clamp reduces EMI and video noise in TVs and VCRs • Operates with optocoupler or bias winding feedback Description The TinySwitch™ family uses a breakthrough design to provide the lowest cost, high efficiency, off-line switcher solution in the 0 to 10 W range. These devices integrate a 700 V power MOSFET, oscillator, high-voltage switched current source, current limit and thermal shutdown circuitry. They start-up and run on power derived from the DRAIN voltage, eliminating the need for a transformer bias winding and the associated circuitry. And yet, they consume only about 80 mW at no load, from 265 VAC input. A simple ON/OFF control scheme also eliminates the need for loop compensation. + Wide-Range High-Voltage DC Input + DC Output – D TinySwitch EN BP S – PI-2178-022699 Figure 1. Typical Standby Application. TinySwitch Selection Guide Recommended Range for Lowest System Cost* ORDER PART NUMBER PACKAGE TNY253P DIP-8 TNY253G SMD-8 TNY254P DIP-8 TNY254G SMD-8 TNY255P DIP-8 TNY255G SMD-8 230 VAC or 115 VAC w/Doubler 85-265 VAC 0-4 W 0-2 W 2-5 W 1-4 W 4-10 W 3.5-6.5 W Table 1. *Please refer to the Key Application Considerations section for details. The TNY253 and TNY254 switch at 44 kHz to minimize EMI and to allow a simple snubber clamp to limit DRAIN spike voltage. At the same time, they allow use of low cost EE16 core transformers to deliver up to 5 W. The TNY253 is identical to TNY254 except for its lower current limit, which reduces output short-circuit current for applications under 2.5  W. TNY255 uses higher switching rate of 130 kHz to deliver up to 10 W from the same low cost EE16 core for applications such as PC standby supply. An EE13 or EF13 core with safety spaced bobbin can be used for applications under 2.5 W. Absence of a bias winding eliminates the need for taping/margins in most applications, when triple insulated wire is used for the secondary. This simplifies the transformer construction and reduces cost. August 2016 TNY253/254/255 REGULATOR 5.8 V BYPASS DRAIN UNDERVOLTAGE OSCILLATOR 5.8 V 5.1 V + + - - VI LIMIT CLOCK 50 μA DCMAX THERMAL SHUTDOWN S Q R Q LEADING EDGE BLANKING 1.5 V + VTH SOURCE ENABLE PI-2197-061898 Figure 2. Functional Block Diagram. Pin Functional Description DRAIN (D) Pin: Power MOSFET drain connection. Provides internal operating current for both start-up and steady-state operation. BYPASS (BP) Pin: Connection point for an external bypass capacitor for the internally generated 5.8 V supply. Bypass pin is not intended for sourcing supply current to external circuitry. ENABLE (EN) Pin: The power MOSFET switching can be terminated by pulling this pin low. The I-V characteristic of this pin is equivalent to a voltage source of approximately 1.5 V with a source current clamp of 50 µA. SOURCE (S) Pin: Power MOSFET source connection. Primary return. TinySwitch Functional Description TinySwitch is intended for low power off-line applications. It combines a high-voltage power MOSFET switch with a power supply controller in one device. Unlike a conventional PWM (Pulse Width Modulator) controller, the TinySwitch uses a simple ON/OFF control to regulate the output voltage. The TinySwitch controller consists of an Oscillator, Enable (Sense and Logic) circuit, 5.8 V Regulator, Undervoltage circuit, BYPASS 1 8 SOURCE SOURCE 2 7 SOURCE SOURCE 3 6 SOURCE ENABLE 4 5 DRAIN P Package (DIP-8) G Package (SMD-8) PI-2199-031501 Figure 3. Pin Configuration. Hysteretic Over Temperature Protection, Current Limit circuit, Leading Edge Blanking, and a 700 V power MOSFET. Figure 2 shows a functional block diagram with the most important features. Oscillator The oscillator frequency is internally set at 44 kHz (130 kHz for the TNY255). The two signals of interest are the Maximum Duty Cycle signal (DMAX) which runs at typically 67% duty cycle and the Clock signal that indicates the beginning of each cycle. When cycles are skipped (see below), the oscillator frequency doubles (except for TNY255 which remains at 130 kHz). This increases the sampling rate at the ENABLE pin for faster loop response. Enable (Sense and Logic) The ENABLE pin circuit has a source follower input stage set at 1.5 V. The input current is clamped by a current source set at 50 µA with 10 µA hysteresis. The output of the enable sense 2 Rev. F 08/16 www.power.com TNY253/254/255 circuit is sampled at the rising edge of the oscillator Clock signal (at the beginning of each cycle). If it is high, then the power MOSFET is turned on (enabled) for that cycle, otherwise the power MOSFET remains in the off state (cycle skipped). Since the sampling is done only once at the beginning of each cycle, any subsequent changes at the ENABLE pin during the cycle are ignored. 5.8 V Regulator The 5.8 V regulator charges the bypass capacitor connected to the BYPASS pin to 5.8 V by drawing a current from the voltage on the DRAIN, whenever the MOSFET is off. The BYPASS pin is the internal supply voltage node for the TinySwitch. When the MOSFET is on, the TinySwitch runs off of the energy stored in the bypass capacitor. Extremely low power consumption of the internal circuitry allows the TinySwitch to operate continuously from the current drawn from the DRAIN pin. A bypass capacitor value of 0.1 µF is sufficient for both high frequency de-coupling and energy storage. Undervoltage The undervoltage circuitry disables the power MOSFET when the BYPASS pin voltage drops below 5.1 V. Once the BYPASS pin voltage drops below 5.1 V, it has to rise back to 5.8 V to enable (turn-on) the power MOSFET. Hysteretic Over Temperature Protection The thermal shutdown circuitry senses the die junction temperature. The threshold is set at 135 °C with 70 °C hysteresis. When the junction temperature rises above this threshold (135 °C) the power MOSFET is disabled and remains disabled until the die junction temperature falls by 70 °C, at which point it is re-enabled. Current Limit The current limit circuit senses the current in the power MOSFET. When this current exceeds the internal threshold (ILIMIT), the power MOSFET is turned off for the remainder of that cycle. The leading edge blanking circuit inhibits the current limit comparator for a short time (tLEB) after the power MOSFET is turned on. This leading edge blanking time has been set so that current spikes caused by primary-side capacitance and secondary-side rectifier reverse recovery time will not cause premature termination of the switching pulse. TinySwitch Operation TinySwitch is intended to operate in the current limit mode. When enabled, the oscillator turns the power MOSFET on at the beginning of each cycle. The MOSFET is turned off when the current ramps up to the current limit. The maximum on-time of the MOSFET is limited to DCMAX by the oscillator. Since the current limit and frequency of a given TinySwitch device are constant, the power delivered is proportional to the primary inductance of the transformer and is relatively independent of the input voltage. Therefore, the design of the power supply involves calculating the primary inductance of the transformer for the maximum power required. As long as the TinySwitch device chosen is rated for the power level at the lowest input voltage, the calculated inductance will ramp up the current to the current limit before the DCMAX limit is reached. Enable Function The TinySwitch senses the ENABLE pin to determine whether or not to proceed with the next switch cycle as described earlier. Once a cycle is started TinySwitch always completes the cycle (even when the ENABLE pin changes state half way through the cycle). This operation results in a power supply whose output voltage ripple is determined by the output capacitor, amount of energy per switch cycle and the delay of the ENABLE feedback. The ENABLE signal is generated on the secondary by comparing the power supply output voltage with a reference voltage. The ENABLE signal is high when the power supply output voltage is less than the reference voltage. In a typical implementation, the ENABLE pin is driven by an optocoupler. The collector of the optocoupler transistor is connected to the ENABLE pin and the emitter is connected to the SOURCE pin. The optocoupler LED is connected in series with a Zener across the DC output voltage to be regulated. When the output voltage exceeds the target regulation voltage level (optocoupler diode voltage drop plus Zener voltage), the optocoupler diode will start to conduct, pulling the ENABLE pin low. The Zener could be replaced by a TL431 device for improved accuracy. The ENABLE pin pull-down current threshold is nominally 50 µA, but is set to 40 µA the instant the threshold is exceeded. This is reset to 50 µA when the ENABLE pull-down current drops below the current threshold of 40 µA. ON/OFF Control The internal clock of the TinySwitch runs all the time. At the beginning of each clock cycle the TinySwitch samples the ENABLE pin to decide whether or not to implement a switch cycle. If the ENABLE pin is high (< 40 µA), then a switching cycle takes place. If the ENABLE pin is low (greater than 50 µA) then no switching cycle occurs, and the ENABLE pin status is sampled again at the start of the subsequent clock cycle. At full load TinySwitch will conduct during the majority of its clock cycles (Figure 4). At loads less than full load, the TinySwitch will “skip” more cycles in order to maintain voltage regulation at the secondary output (Figure 5). At light load or no load, almost all cycles will be skipped (Figure 6). A small percentage of cycles will conduct to support the power consumption of the power supply. 3 www.power.com Rev. F 08/16 TNY253/254/255 V EN V EN CLOCK CLOCK DC DC MAX MAX IDRAIN IDRAIN VDRAIN VDRAIN PI-2259-061298 PI-2255-061298 Figure 4. TinySwitch Operation at Heavy Load. Figure 5. TinySwitch Operation at Medium Load. The response time of TinySwitch ON/OFF control scheme is very fast compared to normal PWM control. This provides high line ripple rejection and excellent transient response. rejection and relatively constant power delivery independent of the input voltage. Power Up/Down TinySwitch requires only a 0.1 µF capacitor on the BYPASS pin. Because of the small size of this capacitor, the power-up delay is kept to an absolute minimum, typically 0.3 ms (Figure 7). Due to the fast nature of the ON/OFF feedback, there is no overshoot at the power supply output. During power-down, the power MOSFET will switch until the rectified line voltage drops to approximately 12 V. The power MOSFET will then remain off without any glitches (Figure 8). Bias Winding Eliminated TinySwitch does not require a bias winding to provide power to the chip. Instead it draws the power directly from the DRAIN pin (see Functional Description above). This has two main benefits. First for a nominal application, this eliminates the cost of an extra bias winding and associated components. Secondly, for charger applications, the current-voltage characteristic often allows the output voltage to fall to low values while still delivering power. This type of application normally requires a forward-bias winding which has many more associated components, none of which are necessary with TinySwitch. Current Limit Operation Each switching cycle is terminated when the DRAIN current reaches the current limit of the TinySwitch. For a given primary inductance and input voltage, the duty cycle is constant. However, duty cycle does change inversely with the input voltage providing “voltage feed-forward” advantages: good line ripple 44 kHz Switching Frequency (TNY253/254) Switching frequency (with no cycle skipping) is set at 44 kHz. This provides several advantages. At higher switching frequencies, the capacitive switching losses are a significant proportion of the power losses in a power supply. At higher frequencies, the preferred snubbing schemes are RCD or diode-Zener clamps. However, due to the lower switching frequency of TinySwitch , it is possible to use a simple RC snubber (and even just a capacitor alone in 115 VAC applications at powers levels below 4 W). Secondly, a low switching frequency also reduces EMI filtering requirements. At 44 kHz, the first, second and third harmonics are all below 150 kHz where the EMI limits are not very restrictive. For power levels below 4 W it is possible to meet worldwide EMI requirements with only resistive and capacitive filter elements (no inductors or chokes). This significantly reduces EMI filter costs. Finally, if the application requires stringent noise emissions (such as video applications), then the TNY253/254 will allow more effective use of diode snubbing (and other secondary snubbing techniques). The lower switching frequency allows RC snubbers to be used to reduce noise, without significantly impacting the efficiency of the supply. 130 kHz Switching Frequency (TNY255) The switching frequency (with no cycle skipping) is set at 130 kHz. This allows the TNY255 to deliver 10 W while still using the same size, low cost transformer (EE16) as used by the TNY253/254 for lower power applications. 4 Rev. F 08/16 www.power.com PI–2253-062398 TNY253/254/255 V EN CLOCK DC V IN MAX IDRAIN 0V VDRAIN 0V 0 .2 .4 .6 .8 1 Time (ms) VDRAIN PI-2261-061198 Figure 6. TinySwitch Operation at Light Load. PI–2251-062398 Figure 7. TinySwitch Power-Up Timing Diagram. V IN BYPASS Pin Capacitor The BYPASS pin uses a small 0.1 µF ceramic capacitor for decoupling the internal power supply of the TinySwitch. Application Examples 12 V 0V VDRAIN Television Standby TinySwitch is an ideal solution for low cost, high efficiency standby power supplies used in consumer electronic products such as TVs. Figure 9 shows a 7.5 V, 1.3 W flyback circuit that uses TNY253 for implementing a TV standby supply. The circuit operates from the DC high-voltage already available from the main power supply. This input voltage can range from 120 to 375 VDC depending on the input AC voltage range that the TV is rated for. Capacitor C1 filters the high-voltage DC supply, and is necessary only if there is a long trace length from the source of the DC supply to the inputs of the TV standby circuit. The high-voltage DC bus is applied to the series combination of the primary winding of T1 and the integrated high-voltage MOSFET inside the TNY253. The low operating frequency of the TNY253 (44 kHz), allows a low cost snubber circuit C2 and R1 to be used in place of a primary clamp circuit. In addition to limiting the DRAIN turn off voltage spike to a safe value, the RC snubber also reduces radiated video noise by lowering the dv/dt of the DRAIN waveform, which is critical for video applications such as TV and VCR. On fixed frequency PWM and RCC circuits, use of a snubber will result in an undesirable fixed AC switching loss that is independent of load. The ON/OFF control on the TinySwitch eliminates this problem by scaling the effective switching frequency and therefore, 12 V 0V 0 100 200 300 400 500 Time (ms) Figure 8. TinySwitch Power Down Timing Diagram. switching loss linearly with load. Thus the efficiency of the supply stays relatively constant down to a fraction of a watt of output loading. The secondary winding is rectified and filtered by D1 and C4 to create the 7.5 V output. L1 and C5 provide additional filtering. The output voltage is determined by the sum of the optocoupler U2 LED forward drop (~ 1 V) and Zener diode VR1 voltage. The resistor R2, maintains a bias current through the Zener to improve its voltage tolerance. 10 W Standby The TNY255 is ideal for standby applications that require up to 10 W of power from 230 VAC or 100/115 VAC with doubler circuit. The TNY255 operates at 130 kHz as opposed to 44 kHz for TNY253/254. The higher frequency operation allows the 5 www.power.com Rev. F 08/16 TNY253/254/255 1 + T1 D1 1N4934 L1 15 μH 10 + 7.5 V C5 47 μF 10 V C4 330 μF 10 V 8 4 Optional DC IN 120 - 375 VDC C1 0.01 μF 1 kV R1 100 Ω 1/2 W TinySwitch U1 TNY253P D RTN U2 SFH615-2 EN BP R2 1 kΩ S C3 0.1 μF C2 56 pF 1 kV – VR1 1N5235B C6 680 pF Y1 Safety PI-2246-082898 Figure 9. 1.3 W TV Standby Circuit using TNY253. 1 R1 150 kΩ 1W 240 - 375 VDC C1 0.01 μF 1 kV 10 D2 SB540 TinySwitch U1 TNY255P L1 10 μH C4 2700 μF 6.3 V C2 4700 pF 1 kV 4 D1 1N4937 Optional T1 D +5V C5 220 μF 10 V 8 RTN EN BP R2 68 Ω U2 LTV817 S C3 0.1 μF VR1 1N5229B PI-2242-082898 Figure 10. 10 W Standby Supply Circuit. use of a low cost EE16 core transformer up to the 10 W level. Figure 10 shows a 5 V, 10 W circuit for such an application. The circuit operates from the high-voltage DC supply already available from the main power supply. Capacitor C1 filters the high-voltage DC supply, and is necessary only if there is a long trace length from the source of the DC supply to the inputs of the standby circuit. The high-voltage DC bus is applied to the primary winding of T1 in series with the integrated high-voltage MOSFET inside the TNY255. The diode D1, capacitor C2 and resistor R1 comprise the clamp circuit that limits the turn-off voltage spike on the TinySwitch DRAIN pin to a safe value. The secondary winding is rectified and filtered by D2 and C4 to provide the 5 V ouput. Additional filtering is provided by L1 and C5. The output voltage is determined by the sum of the optocoupler U2 LED forward drop (~ 1 V) and Zener diode VR1 voltage. The resistor R2, maintains a bias current through the Zener to improve its voltage tolerance. For tighter tolerance, a TL431 precision reference IC feedback circuit may be used. Cellular Phone Charger The TinySwitch is well suited for applications that require a constant voltage and constant current output. TinySwitch is always powered from the input high-voltage, therefore it does not require bias winding for power. Consequently, its operation is not dependent on the level of the output voltage. This allows for constant current charger designs that work down to zero volts on the output. 6 Rev. F 08/16 www.power.com TNY253/254/255 T1 1 D1 1N4005 85 - 265 VAC R2 100 kΩ 1W D2 1N4005 C1 6.8 μF 400 V RF1 10 Ω D5 FR201 C5 220 μF 25 V D EN U2 LTV817 BP R7 100 Ω R9 47 Ω Q1 2N3904 C3 0.1 μF R1 1.2 kΩ D4 1N4005 RTN R8 820 Ω S L1 560 μH + 5.2 V C6 220 μF 16 V 5 2 D6 1N4937 Fusible D3 1N4005 L2 3.3 μH C4 2200 pF TinySwitch U1 TNY254P C2 4.7 μF 400 V 10 R3 22 Ω VR1 1N5230B 4.7 V R5 18 Ω 1/8 W R4 1Ω 1W C8 2.2 nF Y1 Safety R6 0.82 Ω 1/2 W PI-2244-082898 Figure 11. 3.6 W Constant Voltage-Constant Current Cellular Phone Charger Circuit. T1 1 10 D3 1N3934 D1 1N4004 6 5 C1 2.2 μF 200 V 115 VAC ± 15% RF1 1.8 Ω +9V C6 100 μF 16V D2 1N4004 C2 2.2 μF 200 V C4 68 pF 1 KV TinySwitch U1 TNY253P R2 100 Ω D VR1 1N5239B RTN EN BP S C3 0.1 μF C5 2.2 nF Y1 Safety Fusible PI-2190-031501 Figure 12. 0.5 W Open Loop AC Adapter Circuit. Figure 11 shows a 5.2 V, 3.6 W cellular phone charger circuit that uses the TNY254 and provides constant voltage and constant current output over an universal input (85 to 265 VAC) range. The AC input is rectified and filtered by D1 - D4, C1 and C2 to create a high-voltage DC bus connected to T1 in series with the high-voltage MOSFET inside the TNY254. The inductor L1 forms a π-filter in conjunction with C1 and C2. The resistor R1 damps resonances in the inductor L1. The low frequency of operation of TNY254 (44 kHz) allows use of the simple π-filter described above in combination with a single Y1-capacitor C8 to meet worldwide conducted EMI standards. The diode D6, capacitor C4 and resistor R2 comprise the clamp circuit that limits the turn-off voltage spike on the TinySwitch DRAIN pin to a safe value. The secondary winding is rectified and filtered by D5 and C5 to provide the 5.2 V output. Additional filtering is provided by L2 and C6. The output voltage is determined by the sum of the optocoupler U2 LED forward drop (~ 1 V) and Zener diode VR1 voltage. The resistor R8, maintains a bias current through the Zener to improve its voltage tolerance. A simple constant current circuit is implemented using the VBE of transistor Q1 to sense the voltage across the current sense resistor R4, which can be made up of one or more resistors to 7 www.power.com Rev. F 08/16 TNY253/254/255 achieve the appropriate value. R3 is a base current limiting resistor. When the drop across R4 exceeds the VBE of transistor Q1, it turns on and takes over the control of the loop by driving the optocoupler LED. R6 drops an additional voltage to keep the control loop in operation down to zero volts on the output. With the output shorted, the drop across R4 and R6 (~ 1.5 V) is sufficient to keep the Q1 and LED circuit active. Resistors R7 and R9 limit the forward current that could be drawn through VR1 by Q1 under output short-circuit conditions, due to the voltage drop across R6 and R4. AC Adapter Many consumer electronic products utilize low power 50/60 Hz transformer based AC adapters. The TinySwitch can cost effectively replace these linear adapters with a solution that is lighter, smaller and more energy efficient . Figure 12 shows a 9 V, 0.5 W AC adapter circuit using the TNY253. This circuit operates from a 115 VAC input. To save cost, this circuit runs without any feedback, in discontinuous conduction mode to deliver constant power output relatively independent of input voltage. The output voltage is determined by the voltage drop across Zener diode VR1. The primary inductance of the transformer is chosen to deliver a power that is in excess of the required output power by at least 50% to allow for component tolerances and to maintain some current through the Zener VR1 at full load. At no load, all of the power is delivered to the Zener which should be rated and heat sinked accordingly. In spite of a constant power consumption from the mains input, this solution is still significantly more efficient than linear adapters up to output power levels of approximately 1 W. The AC input is rectified by diodes D1 and D2. D2 is used to reduce conducted EMI by only allowing noise onto the neutral line during diode conduction. The rectified AC is then filtered by capacitors C1 and C2 to generate a high-voltage DC bus, which is applied to the series combination of the primary winding of T1 and the high-voltage MOSFET inside the TNY253. The resistor R2 along with capacitors C1 and C2 form a π-filter which is sufficient for meeting EMI conducted emissions at these power levels. C5 is a Y capacitor which is used to reduce common mode EMI. Due to the 700 V rating of the TinySwitch MOSFET, a simple capacitive snubber (C4) is adequate to limit the leakage inductance spike in 115 VAC applications, at low power levels. The secondary winding is rectified and filtered by D3 and C6. Key Application Considerations For the most up to date information visit our Web site at: www.powerint.com Design Output Power Range The power levels shown in the TinySwitch Selection Guide (Table 1) are approximate, recommended output power ranges that will provide a cost optimum design and are based on following assumptions: 1. The minimum DC input voltage is 90 V or higher for 85 VAC input or 240 V or higher for 230 VAC input or 115 VAC input with a voltage doubler. 2. The TinySwitch is not thermally limited - the source pins are soldered to sufficient copper area to keep the die temperature at or below 100 °C. This limitation does not usually apply to TNY253 and TNY254. The maximum power capability of a TinySwitch depends on the thermal environment, transformer core size and design (continuous or discontinuous), efficiency required, minimum specified input voltage, input storage capacitance, output voltage, output diode forward drop, etc., and can be different from the values shown in the selection guide. Audible Noise At loads other than maximum load, the cycle skipping mode operation used in TinySwitch can generate audio frequency components in the transformer. This can cause the transformer to produce audio noise. Transformer audible noise can be reduced by utilizing appropriate transformer construction techniques and decreasing the peak flux density. For more information on audio suppression techniques, please check the Application Notes section on our Web site at www.powerint.com. Ceramic capacitors that use dielectrics such as Z5U, when used in clamp and snubber circuits, can also generate audio noise due to electrostriction and piezo-electric effects. If this is the case, replacing them with a capacitor having a different type of dielectric is the simplest solution. Polyester film capacitor is a good alternative. Short-Circuit Current The TinySwitch does not have an auto-restart feature. As a result, TinySwitch will continue to deliver power to the load during output short-circuit conditions. In the worst case, peak short-circuit current is equal to the primary current limit (ILIMIT) multiplied by the turns ratio of the transformer (Np/Ns). In a typical design the average current is 25 to 50% lower than this peak value. At the power levels of TinySwitch this is 8 Rev. F 08/16 www.power.com TNY253/254/255 Safety Spacing Input Filter Capacitor Output Filter Capacitor Transformer + HV SEC PRI – S D TOP VIEW Y1Capacitor TinySwitch CBP Optocoupler BP S EN – DC + OUT Maximize hatched copper areas ( ) for optimum heat sinking PI-2176-071398 Figure 13. Recommended PC Layout for the TinySwitch. easily accommodated by rating the output diode to handle the short-circuit current. The short-circuit current can be minimized by choosing the smallest (lowest current limit) TinySwitch for the required power. Layout Single Point Grounding Use a single point ground connection at the SOURCE pin for the BYPASS pin capacitor and the Input Filter Capacitor (see Figure 13). Primary Loop Area The area of the primary loop that connects the input filter capacitor, transformer primary and TinySwitch together, should be kept as small as possible. Primary Clamp Circuit A clamp or snubber circuit is used to minimize peak voltage and ringing on the DRAIN pin at turn-off. This can be achieved by using an RC snubber for less than 3 W or an RCD clamp as shown in Figure 13 for higher power. A Zener and diode clamp across the primary or a single 550 V Zener clamp from DRAIN to SOURCE can also be used. In all cases care should be taken to minimize the circuit path from the snubber/clamp components to the transformer and TinySwitch. Thermal Considerations Copper underneath the TinySwitch acts not only as a single point ground, but also as a heatsink. The hatched area shown in Figure  13 should be maximized for good heat-sinking of TinySwitch and output diode. Y Capacitor The placement of the Y capacitor should be directly from the primary single point ground to the common/return terminal on the secondary side. Such placement will maximize the EMI benefit of the Y capacitor. Optocoupler It is important to maintain the minimum circuit path from the optocoupler transistor to the TinySwitch ENABLE and SOURCE pins to minimize noise coupling. Output Diode For best performance, the area of the loop connecting the secondary winding, the Output Diode and the Output Filter Capacitor, should be minimized. See Figure 13 for optimized layout. In addition, sufficient copper area should be provided at the anode and cathode terminals of the diode to adequately heatsink the diode under output short-circuit conditions. Input and Output Filter Capacitors There are constrictions in the traces connected to the input and output filter capacitors. These constrictions are present for two reasons. The first is to force all the high frequency currents to flow through the capacitor (if the trace were wide then it could flow around the capacitor). Secondly, the constrictions minimize the heat transferred from the TinySwitch to the input filter capacitor and from the secondary diode to the output filter capacitor. The common/return (the negative output terminal in Figure 13) terminal of the output filter capacitor should be connected with a short, low resistance path to the secondary winding. In addition, the common/return output connection should be taken directly from the secondary winding pin and not from the Y capacitor connection point. 9 www.power.com Rev. F 08/16 TNY253/254/255 ABSOLUTE MAXIMUM RATINGS(1) DRAIN Voltage........................................... -0.3 V to 700 V Peak DRAIN Current (TNY253/4).............400 (500) mA(6) Peak DRAIN Current (TNY255)................530 (660) mA(6) ENABLE Voltage............................................ -0.3 V to 9 V ENABLE Current.................................................... 100 mA BYPASS Voltage............................................. -0.3 V to 9 V 1. All voltages referenced to SOURCE, TA = 25 °C. 2. Normally limited by internal circuitry. 3. 1/16" from case for 5 seconds. Storage Temperature....................................... -65 to 150 °C Operating Junction Temperature(2) ................. -40 to 150 °C Lead Temperature(3) ..................................................260 °C Thermal Impedance (θJA)...................70 °C/W(4), 55 °C/W(5) Thermal Impedance (θJC)........................................ 11 °C/W 4. Soldered to 0.36 sq. inch (232 mm2), 2 oz. (610 gm/m2) copper clad. 5. Soldered to 1 sq. inch (645 mm2), 2 oz. (610 gm/m2) copper clad. 6. The higher peak drain current is allowed while the drain voltage is simultaneously less than 400 V. Conditions Parameter SOURCE = 0 V; TJ = -40 to 125 °C See Figure 14 (Unless Otherwise Specified) Symbol fOSC Maximum Duty Cycle DCMAX ENABLE Pin Turnoff Threshold Current IDIS ENABLE Pin Hysteresis Current IHYS ENABLE Pin Voltage VEN ENABLE ShortCircuit Current IENSC DRAIN Supply Current IS2 ICH1 BYPASS Pin Charge Current BYPASS Pin Voltage BYPASS Hysteresis TJ = 25 °C S1 Open IS1 ICH2 Max Units TNY253 TNY254 TNY255 TNY253 TNY254 TNY255 TJ = -40 °C to 125 °C 40 44 48 kHz 130 115 140 66 68 71 % 64 69 67 TJ = 125 °C -68 -68 -50 -30 -45 -52 See Note A -15 -10 -5 µA µA 1.10 1.45 1.80 V VEN = 0 V, TJ = -40 °C to 125 °C -58 -42 -25 µA VEN = 0 V, TJ = 125 °C -58 -45 -38 TNY253 160 200 VEN = 0 V TNY254 µA (MOSFET Not Switching) 170 215 TNY255 See Note B TNY253 ENABLE Open 140 180 TNY254 (MOSFET Switching) µA See Note B, C TNY255 215 265 TNY253 -2.0 -3.5 VBP = 0 V, TJ = 25 °C TNY254 -5.0 mA See Note D, E -6.0 -3.0 TNY255 -4.5 TNY253 -1.0 -2.5 VBP = 4 V, TJ = 25 °C See TNY254 -4.0 mA Note D, E TNY255 -4.8 -1.8 -3.3 IEN = -25 µA VBP VBPH Typ CONTROL FUNCTIONS Output Frequency Min See Note D 5.6 5.8 6.1 V 0.60 0.72 0.85 V 10 Rev. F 08/16 www.power.com  Conditions Parameter Symbol SOURCE = 0 V; TJ = -40 to 125 °C See Figure 14 (Unless Otherwise Specified) TNY253/254/255 Min Typ Max Units CIRCUIT PROTECTION Current Limit ILIMIT Note F di/dt = 12.5 mA/µs TJ = 25 °C TNY253 135 150 165 di/dt = 25 mA/µs TJ = 25 °C TNY254 230 255 280 di/dt = 80 mA/µs TJ = 25 °C TNY255 255 280 310 Initial Current IINIT Limit Leading Edge Blanking Time See Figure 17 TJ = 25 °C TJ = 25 °C tLEB Current Limit Delay Thermal Shutdown Temperature tILD TJ = 25 °C See Note G TNY253 TNY254 TNY255 TNY253 TNY254 TNY255 Thermal Shutdown Hysteresis mA 0.65 x mA I LIMIT(MIN) 170 240 ns 170 215 200 250 100 150 ns 125 135 145 °C °C 70 OUTPUT ON-State RDS(ON) Resistance OFF-State Drain IDSS Leakage Current Breakdown BVDSS Voltage Rise Time Fall Time TNY253/TNY254 ID = 25 mA TNY255 ID = 33 mA TJ = 25 °C TJ = 100 °C TJ = 25 °C TJ = 100 °C VBP = 6.2 V, VEN = 0 V, VDS = 560 V, TJ = 125 °C VBP = 6.2 V, VEN = 0 V, IDS = 100 µA, TJ = 25 °C tR tF Measured with Figure 10 Schematic. 31 36 50 60 Ω 23 27 37 45 µA 50 V 700 50 50 ns ns 11 www.power.com Rev. F 08/16 TNY253/254/255 Conditions Parameter Symbol SOURCE = 0 V; TJ = -40 to 125 °C See Figure 14 (Unless Otherwise Specified) Min Typ Max Units OUTPUT (cont.) DRAIN Supply Voltage Output Enable Delay tEN Output Disable Setup Time tDST TNY253 TNY254 TNY255 50 V 14 µs 10 0.5 µs NOTES: A. For a threshold with a negative value, negative hysteresis is a decrease in magnitude of the corresponding threshold. B. Total current consumption is the sum of IS1 and IDSS when ENABLE pin is shorted to ground (MOSFET not switching) and the sum of IS2 and IDSS when ENABLE pin is open (MOSFET switching). C. Since the output MOSFET is switching, it is difficult to isolate the switching current from the supply current at the DRAIN. An alternative is to measure the BYPASS pin current at 6.2 V. D. BYPASS pin is not intended for sourcing supply current to external circuitry. E. See typical performance characteristics section for BYPASS pin start-up charging waveform. F. For current limit at other di/dt values, refer to current limit vs. di/dt curve under typical performance characteristics. G. This parameter is derived from the change in current limit measured at 5X and 10X of the di/dt shown in the ILIMIT specification. 470 Ω 5W S2 470 Ω D EN S S S S S BP S1 50 V 10 V 0.1 μF NOTE: This test circuit is not applicable for current limit or output characteristic measurements. PI-2211-061898 Figure 14. TinySwitch General Test Circuit. 12 Rev. F 08/16 www.power.com TNY253/254/255 DCMAX t2 HV 90% tP t1 90% DRAIN VOLTAGE ENABLE tEN t D= 1 t2 1 tP = for TNY253/254 2fOSC 10% 0V t = P PI-2048-033001 PI-2194-062398 Figure 16. TinySwitch Output Enable Timing. PI-2248-090198 DRAIN Current (normalized) Figure 15. TinySwitch Duty Cycle Measurement. 1 for TNY255 fOSC tLEB (Blanking Time) 1.3 1.2 1.1 1.0 0.9 0.8 0.7 0.6 0.5 0.4 0.3 0.2 0.1 IINIT(MIN) ILIMIT(MAX) @ 25 °C ILIMIT(MIN) @ 25 °C 0 0 1 2 3 4 5 6 7 8 Time (μs) Figure 17. Current Limit Envelope. Typical Performance Characteristics BREAKDOWN vs. TEMPERATURE 1.2 PI-2238-033001 PI-2213-040901 1.1 FREQUENCY vs. TEMPERATURE 1.0 0.8 0.6 1.0 0.4 0.2 0 0.9 -50 -25 0 25 50 75 100 125 150 -50 -25 0 25 50 75 100 125 13 www.power.com Rev. F 08/16 TNY253/254/255 Typical Performance Characteristics (Continued) TNY253 CURRENT LIMIT vs. di/dt CURRENT LIMIT vs. TEMPERATURE 1.0 0.8 0.6 0.4 0.2 1.2 1.0 0.8 0.6 0.4 0.2 0.0 -50 -25 0 25 50 75 PI-2230-082798 1.2 1.4 Current Limit (Normalized to 12.5 mA/s) PI-2236-033001 1.4 0.0 100 125 0 12.5 25 37.5 50 62.5 75 87.5 100 di/dt in mA/s TNY255 CURRENT LIMIT vs. di/dt TNY254 CURRENT LIMIT vs. di/dt 1.0 0.8 0.6 0.4 0.2 PI-2234-082798 1.2 1.4 Current Limit (Normalized to 80 mA/s) PI-2232-082798 Current Limit (Normalized to 25 mA/s) 1.4 1.2 1.0 0.8 0.6 0.4 0.2 0.0 0.0 0 50 100 150 200 0 250 160 480 640 800 di/dt in mA/s di/dt in mA/s OUTPUT CHARACTERISTIC BYPASS PIN START-UP WAVEFORM 5 4 3 2 1 PI-2221-033001 6 300 250 Drain Current (mA) PI-2240-082898 7 BYPASS Pin Voltage (V) 320 200 150 100 Scaling Factors: TNY253 1.00 TNY254 1.00 TNY255 1.33 50 0 0 0 0.2 0.4 0.6 Time (ms) 0.8 1.0 0 2 4 6 8 10 DRAIN Voltage (V) 14 Rev. F 08/16 www.power.com TNY253/254/255 Typical Performance Characteristics (Continued) COSS vs. DRAIN VOLTAGE DRAIN CAPACITANCE POWER Scaling Factors: TNY253 1.00 TNY254 1.00 TNY255 1.33 40 Power (mW) Scaling Factors: TNY253 1.00 TNY254 1.00 TNY255 1.33 10 PI-2225-033001 50 PI-2223-033001 DRAIN Capacitance (pF) 100 30 20 10 1 0 200 0 600 400 0 DRAIN Voltage (V) 200 400 600 DRAIN Voltage (V) PDIP-8 (P Package) DIM Inches mm A B C G H J1 J2 K L M N P Q 0.356-0.387 0.240-0.260 0.125-0.145 0.015-0.040 0.118-0.140 0.057-0.068 0.014-0.022 0.008-0.015 0.100 BSC 0.030 (MIN) 0.300-0.320 0.300-0.390 0.300 BSC 9.05-9.83 6.10-6.60 3.18-3.68 0.38-1.02 3.00-3.56 1.45-1.73 0.36-0.56 0.20-0.38 2.54 BSC 0.76 (MIN) 7.62-8.13 7.62-9.91 7.62 BSC D S .004 (.10) 8 5 -E- B 1 4 M Notes: 1. Package dimensions conform to JEDEC specification MS-001-AB for standard dual in-line (DIP) package .300 inch row spacing (PLASTIC) 8 leads (issue B, 7/85). 2. Controlling dimensions are inches. 3. Dimensions shown do not include mold flash or other protrusions. Mold flash or protrusions G shall not exceed .006 (.15) on any side. 4. D, E and F are reference datums on the molded body. L -D- A J1 N C -FH J2 K Q P P08A PI-2076-081716 15 www.power.com Rev. F 08/16 TNY253/254/255 SMD-8 (G Package) D S .004 (.10) -E- 8 5 1 .420 .046 .060 .060 .046 .080 Pin 1 4 L .086 .186 -D- A M E S .010 (.25) P B Inches mm A B C G H J1 J2 J3 J4 K L M P α 0.356-0.387 0.240-0.260 0.125-0.145 0.004-0.012 0.036-0.044 0.057-0.068 0.048-0.053 0.032-0.037 0.007-0.011 0.010-0.012 0.100 BSC 0.030 (MIN) 0.372-0.388 0-8° 9.05-9.83 6.10-6.60 3.18-3.68 0.10-0.30 0.91-1.12 1.45-1.73 1.22-1.35 0.81-0.94 0.18-0.28 0.25-0.30 2.54 BSC 0.76 (MIN) 9.45-9.86 0-8° .286 Solder Pad Dimensions J1 C K -FJ3 G08A DIM J4 J2 .010 (.25) M A S .004 (.10) α G H Notes: 1. Package dimensions conform to JEDEC specification MS-001-AB (issue B, 7/85) except for lead shape and size. 2. Controlling dimensions are inches. 3. Dimensions shown do not include mold flash or other protrusions. Mold flash or protrusions shall not exceed .006 (.15) on any side. 4. D, E and F are reference datums on the molded body. PI-2077-081716 16 Rev. F 08/16 www.power.com TNY253/254/255 Revision Notes Date A - 02/98 B 1. Leading edge blanking time (tLEB) typical and minimum values increased to improve design flexibility. 2. Minimum DRAIN supply current (IS1, IS2) eliminated as it has no design revelance. 02/99 C 1. Updated package reference. 2. Corrected VR1 in Figure 12. 3. Corrected storage temperature, θJA and θJC and updated nomenclature in parameter table. 4. Corrected spacing and font sizes in figures. 07/01 D 1. Corrected θJA for P/G package. 2. Updated DIP-8 and SMD-8 Package Drawings. 3. Figure 10 caption and text description modified. 04/03 E 1. Changed SOA limit. 02/12 F Updated PDIP-8 (P Package) and SMD-8 (G Package) per PCN-16232. 08/16 17 www.power.com Rev. F 08/16 For the latest updates, visit our website: www.power.com Power Integrations reserves the right to make changes to its products at any time to improve reliability or manufacturability. Power Integrations does not assume any liability arising from the use of any device or circuit described herein. POWER INTEGRATIONS MAKES NO WARRANTY HEREIN AND SPECIFICALLY DISCLAIMS ALL WARRANTIES INCLUDING, WITHOUT LIMITATION, THE IMPLIED WARRANTIES OF MERCHANTABILITY, FITNESS FOR A PARTICULAR PURPOSE, AND NON-INFRINGEMENT OF THIRD PARTY RIGHTS. Patent Information The products and applications illustrated herein (including transformer construction and circuits external to the products) may be covered by one or more U.S. and foreign patents, or potentially by pending U.S. and foreign patent applications assigned to Power Integrations. A complete list of Power Integrations patents may be found at www.power.com. Power Integrations grants its customers a license under certain patent rights as set forth at http://www.power.com/ip.htm. Life Support Policy POWER INTEGRATIONS PRODUCTS ARE NOT AUTHORIZED FOR USE AS CRITICAL COMPONENTS IN LIFE SUPPORT DEVICES OR SYSTEMS WITHOUT THE EXPRESS WRITTEN APPROVAL OF THE PRESIDENT OF POWER INTEGRATIONS. As used herein: 1. A Life support device or system is one which, (i) is intended for surgical implant into the body, or (ii) supports or sustains life, and (iii) whose failure to perform, when properly used in accordance with instructions for use, can be reasonably expected to result in significant injury or death to the user. 2. A critical component is any component of a life support device or system whose failure to perform can be reasonably expected to cause the failure of the life support device or system, or to affect its safety or effectiveness. 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