AOZ1280CI

AOZ1280 EZBuck™ 1.2 A Simple Buck Regulator General Description Features The AOZ1280 is a high efficiency, simple to use, 1.2 A buck regulator which is flexible enough to be optimized for a variety of applications. The AOZ1280 operates from a 3 V to 26 V input voltage range, and provides up to 1.2 A of continuous output current. The output voltage is adjustable down to 0.8 V. The fixed 1.5 MHz PWM switching frequency reduces inductor size.  3 V to 26 V operating input voltage range The AOZ1280 comes in a SOT23-6L package and is rated over a -40 °C to +85 °C operating ambient temperature range.  Internal soft start  240 mΩ internal NMOS  High efficiency: up to 95 %  Internal compensation  1.2 A continuous output current  Fixed 1.5 MHz PWM operation  Output voltage adjustable down to 0.8 V  Cycle-by-cycle current limit  Short-circuit protection  Thermal shutdown  Small size SOT23-6L Applications  Point of load DC/DC conversion  Set top boxes  DVD drives and HDD  LCD Monitors & TVs  Cable modems  Telecom/Networking/Datacom equipment Typical Application VIN C3 C1 4.7µF VIN L1 2.2µH EN AOZ1280 VOUT LX R1 FB GND C2 10µF R2 Figure 1. 1.2 A Buck Regulator Rev. 1.1 August 2011 www.aosmd.com Page 1 of 13 AOZ1280 Ordering Information Part Number Ambient Temperature Range Package Environmental AOZ1280CI -40 °C to +85 °C SOT23-6L Green Product RoHS Compliant AOS Green Products use reduced levels of Halogens, and are also RoHS compliant. Please visit www.aosmd.com/media/AOSGreenPolicy.pdf for additional information. Pin Configuration BST 1 6 LX GND 2 5 VIN FB 3 4 EN SOT23-6L (Top View) Pin Description Pin Number Pin Name 1 BST Bootstrap voltage input. High side driver supply. Connected to 10 nF capacitor between BST and LX. 2 GND Ground. 3 FB Feedback input. It is regulated to 0.8 V. The FB pin is used to determine the PWM output voltage via a resistor divider between the output and GND. 4 EN Enable pin. The enable pin is active high. Connect EN pin to VIN through current limiting resistor. Do not leave the EN pin floating. 5 VIN Supply voltage input. Input range from 3 V to 26 V. When VIN rises above the UVLO threshold the device starts up. 6 LX PWM output connection to inductor. Rev. 1.1 August 2011 Pin Function www.aosmd.com Page 2 of 13 AOZ1280 Absolute Maximum Ratings Recommended Operating Conditions Exceeding the Absolute Maximum Ratings may damage the device. The device is not guaranteed to operate beyond the Recommended Operating Conditions. Parameter Rating Supply Voltage (VIN) Parameter 30 V LX to GND -0.7 V to VVIN+ 2 V EN to GND -0.3 V to 26 V FB to GND -0.3 V to 6 V Junction Temperature (TJ) +150 °C Storage Temperature (TS) -65 °C to +150 °C ESD Rating (1) Supply Voltage (VIN) 3.0 V to 26 V Output Voltage Range 0.8 V to VVIN Ambient Temperature (TA) -40 °C to +85 °C Package Thermal Resistance (JA) SOT23-6L VLX + 6 V BST to AGND Rating 220 °C/W 2 kV Note: 1. Devices are inherently ESD sensitive, handling precautions are required. Human body model rating: 1.5 kΩ in series with 100 pF. Electrical Characteristics TA = 25 °C, VVIN = VEN = 12 V. Specifications in BOLD indicate a temperature range of -40 °C to +85 °C. These specifications are guaranteed by design. Symbol VVIN VUVLO Parameter Conditions Supply Voltage Input Under-Voltage Lockout Threshold Min. 3 VVIN Rising VVIN Falling 2.3 UVLO Hysteresis Max. Units 26 V 2.9 V V 200 IVIN Supply Current (Quiescent) IOUT = 0, VFB = 1 V, VEN > 1.2 V IOFF Shutdown Supply Current VEN = 0 V VFB Feedback Voltage TA = 25 ºC VFB_LOAD Load Regulation Typ. 1 784 800 mV 1.5 mA 8 A 816 mV 120 mA < Load < 1.08 A 0.5 % Line Regulation Load = 600 mA 0.03 %/V Feedback Voltage Input Current VFB = 800 mV 500 nA VEN_OFF VEN_ON EN Input Threshold Off Threshold On Threshold VEN_HYS EN Input Hysteresis IEN Enable Input Current VFB_LINE IFB ENABLE 0.4 1.2 200 V V mV 3 A 1.8 MHz MODULATOR fO DMAX TON_MIN ILIM Frequency Maximum Duty Cycle Minimum On Time Current Limit Over-Temperature Shutdown Limit TSS 1.2 1.5 TJ Rising TJ Falling Soft Start Interval 1.5 87 % 100 ns 2 A 150 110 °C °C 400 s mΩ POWER STATE OUTPUT RDS(ON) NMOS On-Resistance VIN = 12 V 240 RDS(ON) NMOS On-Resistance VIN = 3.3 V 380 ILEAKAGE NMOS Leakage VEN = 0 V, VLX = 0 V Rev. 1.1 August 2011 www.aosmd.com mΩ 10 A Page 3 of 13 AOZ1280 Block Diagram VIN Regulator EN Enable Detect + Current Sense Ramp Generator OC BST LDO BST Softstart OSC FB CLK – PWM Logic Driver – 0.8V + Error Amplifier + LX PWM Comparator GND Rev. 1.1 August 2011 www.aosmd.com Page 4 of 13 AOZ1280 Typical Performance Characteristics Circuit of Figure 1. VIN = 12 V, VOUT = 3.3 V, L = 4.7 H, C1 = 10 F, C2 = 22 F, TA = 25 °C, unless otherwise specified. Load Transient Test Steady State Test (IOUT = 0.2A to 0.8A) (IOUT = 0.5A) Vo ripple 20V/div Vo ripple 50mV/div Vlx 10V/div IL 1A/div IL 500mA/div Io 1A/div 200μs/div 500ns/div Short Circuit Protection Short Circuit Recovery Vlx 10V/div Vlx 10V/div Vo 1V/div Vo 1V/div lL 1A/div lL 1A/div 2ms/div 2ms/div Start-up Through Enable No Load Start-up Through Enable with IOUT = 1A Resistive Load Ven 5V/div Ven 5V/div Vo 2V/div Vo 2/div Vlx 10V/div Vlx 10V/div IL 1A/div IL 1A/div 1ms/div Rev. 1.1 August 2011 1ms/div www.aosmd.com Page 5 of 13 AOZ1280 Typical Performance Characteristics (Continued) Circuit of Figure 1. VIN = 12 V, VOUT = 3.3 V, L = 4.7 H, C1 = 10 F, C2 = 22 F, TA = 25 °C, unless otherwise specified. Shut-down Through Enable with IOUT = 1A Resistive Load Shut-down Through Enable No Load Ven 5V/div Ven 5V/div Vo 2/div Vo 2/div Vlx 10V/div Vlx 10V/div IL 1A/div IL 1A/div 1ms/div 1ms/div Efficiency Efficiency (VIN = 12V) vs. Load Current 100 5.0V OUTPUT 90 Efficiency (VIN = 24V) vs. Load Current 100 90 5.0V OUTPUT 80 Efficieny (%) Efficieny (%) 3.3V OUTPUT 70 80 70 60 60 50 50 40 0 0.2 0.4 0.6 0.8 1.0 40 1.2 3.3V OUTPUT 0 0.2 0.4 Load Current (A) 0.6 0.8 1.0 1.2 Load Current (A) Efficiency (VIN = 5V) vs. Load Current 100 5.0V OUTPUT 90 Efficieny (%) 3.3V OUTPUT 80 70 60 50 40 0 0.2 0.4 0.6 0.8 1.0 1.2 Load Current (A) Rev. 1.1 August 2011 www.aosmd.com Page 6 of 13 AOZ1280 Detailed Description The AOZ1280 is a current-mode step down regulator with integrated high side NMOS switch. It operates from a 3 V to 26 V input voltage range and supplies up to 1.2 A of load current. Features include: enable control, under voltage lock-out, internal soft-start, output over-voltage protection, over-current protection, and thermal shut down. The AOZ1280 is available in SOT23-6L package. Enable and Soft Start The AOZ1280 has an internal soft start feature to limit in-rush current and ensure the output voltage ramps up smoothly to regulation voltage. A soft start process begins when the input voltage rises to a voltage higher than UVLO and the voltage level on the EN pin is HIGH. In the soft start process, the output voltage is typically ramped to regulation voltage in 400 s. The 400 s soft start time is set internally. The EN pin of the AOZ1280 is active high. Connect the EN pin to VIN if the enable function is not used. Pulling EN to ground will disable the AOZ1280. Do not leave EN open. The voltage on the EN pin must be above 1.2 V to enable the AOZ1280. When voltage on the EN pin falls below 0.4 V, the AOZ1280 is disabled. Switching Frequency The AOZ1280 switching frequency is fixed and set by an internal oscillator. The switching frequency is set internally 1.5 MHz. Output Voltage Programming Output voltage can be set by feeding back the output to the FB pin with a resistor divider network. In the application circuit shown in Figure 1. The resistor divider network includes R1 and R2. Usually, a design is started by picking a fixed R2 value and calculating the required R1 with equation below. R 1  V O = 0.8   1 + ------- R 2  Some standard values of R1 and R2 for the most commonly used output voltage values are listed in Table 1. Table 1. Vo (V) Steady-State Operation Under steady-state conditions, the converter operates in fixed frequency and Continuous-Conduction Mode (CCM). The AOZ1280 integrates an internal NMOS as the high-side switch. Inductor current is sensed by amplifying the voltage drop across the drain to the source of the high-side power MOSFET. Output voltage is divided down by the external voltage divider at the FB pin. The difference of the FB pin voltage and reference voltage is amplified by the internal transconductance error amplifier. The error voltage is compared against the current signal, which is sum of inductor current signal plus ramp compensation signal, at the PWM comparator input. If the current signal is less than the error voltage, the internal high-side switch is on. The inductor current flows from the input through the inductor to the output. When the current signal exceeds the error voltage, the high-side switch is off. The inductor current is freewheeling through the external Schottky diode to output. Rev. 1.1 August 2011 R1 (kΩ) R2 (kΩ) 1.8 80.6 64.2 2.5 49.9 23.4 3.3 49.9 15.8 5.0 49.9 9.53 The combination of R1 and R2 should be large enough to avoid drawing excessive current from the output, which will cause power loss. Protection Features The AOZ1280 has multiple protection features to prevent system circuit damage under abnormal conditions. Over Current Protection (OCP) The sensed inductor current signal is also used for over current protection. The cycle-by-cycle current limit threshold is set normal value of 2 A. When the load current reaches the current limit threshold, the cycle-by-cycle current limit circuit immediately turns off the high-side switch to terminate the current duty cycle. The inductor current stop rising. The cycle-by-cycle current limit protection directly limits inductor peak current. The average inductor current is also limited due to the limitation on peak inductor current. When cycle-by-cycle current limit circuit is triggered, the output voltage drops as the duty cycle decreasing. www.aosmd.com Page 7 of 13 AOZ1280 The AOZ1280 has internal short circuit protection to protect itself from catastrophic failure under output short circuit conditions. The FB pin voltage is proportional to the output voltage. Whenever the FB pin voltage is below 0.2 V, the short circuit protection circuit is triggered. As a result, the converter is shut down and hiccups. The converter will start up via a soft start once the short circuit condition is resolved. In the short circuit protection mode, the inductor average current is greatly reduced. Under Voltage Lock Out (UVLO) An UVLO circuit monitors the input voltage. When the input voltage exceeds 2.9 V, the converter starts operation. When input voltage falls below 2.3 V, the converter will stop switching. The relationship between the input capacitor RMS current and voltage conversion ratio is calculated and shown in Figure 2. It can be seen that when VO is half of VIN, CIN is under the worst current stress. The worst current stress on CIN is 0.5 x IO. 0.5 0.4 ICIN_RMS(m) 0.3 IO 0.2 0.1 Thermal Protection 0 An internal temperature sensor monitors the junction temperature. The sensor shuts down the internal control circuit and high side NMOS if the junction temperature exceeds 150 °C. The regulator will restart automatically under the control of soft-start circuit when the junction temperature decreases to 100 °C. Application Information The basic AOZ1280 application circuit is shown in Figure 1. Component selection is explained below. Input Capacitor The input capacitor must be connected to the VIN pin and the GND pin of the AOZ1280 to maintain steady input voltage and filter out the pulsing input current. The voltage rating of the input capacitor must be greater than maximum input voltage plus ripple voltage. The input ripple voltage can be approximated by equation below: Since the input current is discontinuous in a buck converter, the current stress on the input capacitor is another concern when selecting the capacitor. For a buck circuit, the RMS value of input capacitor current can be calculated by: if we let m equal the conversion ratio: VO -------- = m V IN Rev. 1.1 August 2011 0.5 m 1 Figure 2. ICIN vs. Voltage Conversion Ratio For reliable operation and best performance, the input capacitors must have a current rating higher than ICIN_RMS at the worst operating conditions. Ceramic capacitors are preferred for use as input capacitors because of their low ESR and high ripple current rating. Depending on the application circuits, other low ESR tantalum capacitor or aluminum electrolytic capacitor may be used. When selecting ceramic capacitors, X5R or X7R type dielectric ceramic capacitors are preferred for their better temperature and voltage characteristics. Note that the ripple current rating from capacitor manufactures are based on a fixed life time. Further derating may be necessary for practical design requirement. Inductor VO  VO IO  V IN = -----------------   1 – ---------  --------f  C IN  V IN V IN VO  VO  -  1 – -------- I CIN_RMS = I O  -------V IN  V IN 0 The inductor is used to supply constant current to output when it is driven by a switching voltage. For given input and output voltage, inductance and switching frequency together decide the inductor ripple current, which is: VO  VO  - I L = -----------   1 – -------fL  V IN The peak inductor current is: I L I Lpeak = I O + -------2 High inductance provides a low inductor ripple current but requires larger size inductor to avoid saturation. Low ripple current reduces inductor core losses and also www.aosmd.com Page 8 of 13 AOZ1280 reduces RMS current through inductor and switches. This results in less conduction loss. When selecting the inductor, make sure it is able to handle the peak current without saturation at the highest operating temperature. The inductor takes the highest current in a buck circuit. The conduction loss on inductor needs to be checked for thermal and efficiency requirements. Surface mount inductors in different shape and styles are available from Coilcraft, Elytone and Murata. Shielded inductors are small and radiate less EMI noise but cost more than unshielded inductors. The choice depends on EMI requirement, price and size. Output Capacitor The output capacitor is selected based on the DC output voltage rating, output ripple voltage specification and ripple current rating. The selected output capacitor must have a higher rated voltage specification than the maximum desired output voltage including ripple. De-rating needs to be considered for long term reliability. Output ripple voltage specification is another important factor for selecting the output capacitor. In a buck converter circuit, output ripple voltage is determined by inductor value, switching frequency, output capacitor value and ESR. It can be calculated by the equation below: 1 V O = I L   ESR CO + -------------------------  8fC  O where, CO is output capacitor value, and ESRCO is the equivalent series resistance of the output capacitor. When low ESR ceramic capacitor is used as output capacitor, the impedance of the capacitor at the switching frequency dominates. Output ripple is mainly caused by capacitor value and inductor ripple current. The output ripple voltage calculation can be simplified to: 1 V O = I L   ------------------------- 8  f  C  O If the impedance of ESR at switching frequency dominates, the output ripple voltage is mainly decided by capacitor ESR and inductor ripple current. The output ripple voltage calculation can be further simplified to: V O = I L  ESR CO Rev. 1.1 August 2011 For lower output ripple voltage across the entire operating temperature range, X5R or X7R dielectric type of ceramic, or other low ESR tantalum capacitor or aluminum electrolytic capacitor may also be used as output capacitors. In a buck converter, output capacitor current is continuous. The RMS current of output capacitor is decided by the peak to peak inductor ripple current. It can be calculated by: I L I CO_RMS = ---------12 Usually, the ripple current rating of the output capacitor is a smaller issue because of the low current stress. When the buck inductor is selected to be very small and inductor ripple current is high, output capacitor could be overstressed. Schottky Diode Selection The external freewheeling diode supplies the current to the inductor when the high side NMOS switch is off. To reduce the losses due to the forward voltage drop and recovery of diode, a Schottky diode is recommended. The maximum reverse voltage rating of the Schottky diode should be greater than the maximum input voltage, and the current rating should be greater than the maximum load current. Thermal Management and Layout Consideration In the AOZ1280 buck regulator circuit, high pulsing current flows through two circuit loops. The first loop starts from the input capacitors, to the VIN pin, to the LX pin, to the filter inductor, to the output capacitor and load, and then returns to the input capacitor through ground. Current flows in the first loop when the high side switch is on. The second loop starts from inductor, to the output capacitors and load, to the anode of Schottky diode, to the cathode of Schottky diode. Current flows in the second loop when the low side diode is on. In PCB layout, minimizing the area of the two loops will reduce the noise of this circuit and improves efficiency. A ground plane is strongly recommended to connect the input capacitor, the output capacitor, and the GND pin of the AOZ1280. In the AOZ1280 buck regulator circuit, the major power dissipating components are the AOZ1280, the Schottky diode and the output inductor. The total power dissipation of converter circuit can be measured by input power minus output power. P total_loss =  V IN  I IN  –  V O  V IN  www.aosmd.com Page 9 of 13 AOZ1280 The power dissipation in Schottky can be approximated as: Several layout tips are listed below for the best electric and thermal performance. P diode_loss = I O   1 – D   V FW_Schottky 1. The input capacitor should be connected as close as possible to the VIN pin and the GND pin. where, 2. The inductor should be placed as close as possible to the LX pin and the output capacitor. VFW_Schottky is the Schottky diode forward voltage drop. The power dissipation of inductor can be approximately calculated by output current and DCR of inductor. P inductor_loss = IO2  R inductor  1.1 3. Keep the connection of the schottky diode between the LX pin and the GND pin as short and wide as possible. 4. Place the feedback resistors and compensation components as close to the chip as possible. The actual junction temperature can be calculated with power dissipation in the AOZ1280 and thermal impedance from junction to ambient. T junction =  P total_loss – P inductor_loss    JA + T amb The maximum junction temperature of AOZ1280 is 150 ºC, which limits the maximum load current capability. 5. Keep sensitive signal traces away from the LX pin. 6. Pour a maximized copper area to the VIN pin, the LX pin and especially the GND pin to help thermal dissipation. 7. Pour a copper plane on all unused board area and connect the plane to stable DC nodes, like VIN, GND or VOUT. The thermal performance of the AOZ1280 is strongly affected by the PCB layout. Extra care should be taken by users during design process to ensure that the IC will operate under the recommended environmental conditions. Rev. 1.1 August 2011 www.aosmd.com Page 10 of 13 AOZ1280 Package Dimensions, SOT23-6 Gauge Plane D e1 c Seating Plane 0.25mm L E E1 θ1 e b A2 A .010mm A1 Dimensions in millimeters RECOMMENDED LAND PATTERN 1.20 2.40 0.80 0.95 0.63 UNIT: mm Symbols A A1 A2 b c D E E1 e e1 L Min. 0.90 0.00 0.70 0.30 0.08 2.70 2.50 1.50 Nom. — — 1.10 0.40 0.13 2.90 2.80 1.60 0.95 BSC 1.90 BSC 0.30 — θ1 0° — Max. 1.25 0.15 1.20 0.50 0.20 3.10 3.10 1.70 Dimensions in inches Min. 0.035 0.00 0.028 0.012 0.003 0.106 0.098 0.059 0.60 Symbols A A1 A2 b c D E E1 e e1 L Nom. Max. — 0.049 — 0.006 0.043 0.047 0.016 0.020 0.005 0.008 0.114 0.122 0.110 0.122 0.063 0.067 0.037 BSC 0.075 BSC 0.012 — 0.024 8° θ1 0° — 8° Notes: 1. Package body sizes exclude mold flash and gate burrs. Mold flash at the non-lead sides should be less than 5 mils each. 2. Dimension “L” is measured in gauge plane. 3. Tolerance ±0.100 mm (4 mil) unless otherwise specified. 4. Followed from JEDEC MO-178C & MO-193C. 5. Controlling dimension is millimeter. Converted inch dimensions are not necessarily exact. Rev. 1.1 August 2011 www.aosmd.com Page 11 of 13 AOZ1280 Tape and Reel Dimensions, SOT23-6 Tape P1 P2 D1 T E1 E2 E B0 K0 D0 A0 P0 Feeding Direction Unit: mm Package A0 B0 K0 D0 D1 E E1 E2 P0 P1 P2 T SOT-23 3.15 ±0.10 3.27 ±0.10 1.34 ±0.10 1.10 ±0.01 1.50 ±0.10 8.00 ±0.20 1.75 ±0.10 3.50 ±0.05 4.00 ±0.10 4.00 ±0.10 2.00 ±0.10 0.25 ±0.05 Reel W1 S G N M V K R H W Unit: mm Tape Size Reel Size M N W W1 8 mm ø180 ø180.00 ±0.50 ø60.50 Min. 9.00 ±0.30 11.40 ±1.0 H K S ø13.00 10.60 2.00 +0.50 / -0.20 ±0.50 G ø9.00 R V 5.00 18.00 Leader/Trailer and Orientation Trailer Tape 300mm min. or 75 Empty Pockets Rev. 1.1 August 2011 Components Tape Orientation in Pocket www.aosmd.com Leader Tape 500mm min. or 125 Empty Pockets Page 12 of 13 AOZ1280 Part Marking AOZ1280CI AX 2D 11 (SOT23-6) Assembly Lot Code Week & Year Code Part Number Code Assembly Location Code LEGAL DISCLAIMER Applications or uses as critical components in life support devices or systems are not authorized. AOS does not assume any liability arising out of such applications or uses of its products. AOS reserves the right to make changes to product specifications without notice. It is the responsibility of the customer to evaluate suitability of the product for their intended application. Customer shall comply with applicable legal requirements, including all applicable export control rules, regulations and limitations. AOS' products are provided subject to AOS' terms and conditions of sale which are set forth at: http://www.aosmd.com/terms_and_conditions_of_sale LIFE SUPPORT POLICY ALPHA & OMEGA SEMICONDUCTOR PRODUCTS ARE NOT AUTHORIZED FOR USE AS CRITICAL COMPONENTS IN LIFE SUPPORT DEVICES OR SYSTEMS. As used herein: 1. Life support devices or systems are devices or systems which, (a) are intended for surgical implant into the body or (b) support or sustain life, and (c) whose failure to perform when properly used in accordance with instructions for use provided in the labeling, can be reasonably expected to result in a significant injury of the user. Rev. 1.1 August 2011 2. A critical component in any component of a life support, device, or system whose failure to perform can be reasonably expected to cause the failure of the life support device or system, or to affect its safety or effectiveness. www.aosmd.com Page 13 of 13