AOZ8105CI
Ultra-Low Capacitance TVS Diode
General Description
Features
The AOZ8105CI is a transient voltage suppressor array
designed to protect high speed data lines such as HDMI
and Gigabit Ethernet from damaging ESD events.
ESD protection for high-speed data lines:
This device incorporates eight surge rated, low
capacitance steering diodes and a TVS in a single
package. During transient conditions, the steering diodes
direct the transient to either the positive side of the power
supply line or to ground.
– IEC 61000-4-5 (Lightning) 3A (8/20µs)
The AOZ8105CI provides a typical line to line
capacitance of 0.35pF and low insertion loss up to 3GHz
providing greater signal integrity making it ideally suited
for HDMI 1.3 applications, such as Digital TVs, DVD
players, set-top boxes and mobile computing devices.
The AOZ8105CI comes in RoHS compliant, tiny
SOT-23-6 package and is rated -40°C to +85°C junction
temperature range.
– IEC 61000-4-2, level 4 (ESD) immunity test
– ±30kV (air discharge) and ±24kV (contact discharge)
– Human Body Model (HBM) ±24kV
Array of surge rated diodes with internal TVS diode
Small package saves board space
Protects four I/O lines
Low capacitance between I/O lines: 0.35pF
Low clamping voltage
Low operating voltage: 5.0V
Applications
HDMI ports
Monitors and flat panel displays
Set-top box
USB 2.0 power and data line protection
Video graphics cards
Digital Video Interface (DVI)
10/100/1000 Ethernet
Notebook computers
Typical Application
Vcc
I/O1
I/O2
I/O3
I/O4
Figure 1. HDMI Ports
Rev. 4.1 September 2021
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AOZ8105CI
Ordering Information
Part Number
Ambient Temperature Range
Package
Environmental
AOZ8105CI
-40°C to +85°C
SOT-23-6
Green Product
AOS Green Products use reduced levels of Halogens, and are also RoHS compliant.
Please visit www.aosmd.com/media/AOSGreenPolicy.pdf for additional information.
Pin Configuration
CH1
1
6
CH4
VN
2
5
VP
CH2
3
4
CH3
SOT23-6
(Top View)
Absolute Maximum Ratings
Exceeding the Absolute Maximum ratings may damage the device.
Parameter
Rating
Storage Temperature (TS)
-65°C to +150°C
ESD Rating per IEC61000-4-2, contact
(1)
±24kV
ESD Rating per IEC61000-4-2, air(1)
ESD Rating per Human Body Model
±30kV
(2)
±24kV
Notes:
1. IEC 61000-4-2 discharge with CDischarge = 150pF, RDischarge = 330.
2. Human Body Discharge per MIL-STD-883, Method 3015 CDischarge = 100pF, RDischarge = 1.5k.
Maximum Operating Ratings
Parameter
Rating
Junction Temperature (TJ)
Rev. 4.1 September 2021
-40°C to +125°C
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AOZ8105CI
Electrical Characteristics
TA = 25°C unless otherwise specified. Specifications in BOLD indicate a temperature range of -40°C to +85°C.
Symbol
VRWM
VBR
Parameter
Reverse Working Voltage
Conditions
Between VP and VN
Min.
(4)
Reverse Breakdown Voltage
IT = 1mA, between VP and VN
IR
Reverse Leakage Current
VRWM = 5V, between VP and VN
VF
Diode Forward Voltage
IF = 15mA
VCL
Cj
0.70
IPP = 1A, tp = 100ns, any I/O pin to Ground
Channel Clamp Voltage
Positive Transients
Negative Transient
IPP = 5A, tp = 100ns, any I/O pin to Ground(5)
VR = 0V, f = 1MHz, any I/O pin to
Ground(6)
VP = 5.0V, VR = 2.5V, f = 1MHz, any I/O pins
to Ground
Channel Input Capacitance
Matching
Units
5.5
V
V
0.85
1
µA
1
V
(5)
Channel Clamp Voltage
Positive Transients
Negative Transient
Channel Input Capacitance
Max.
6.6
VR = 0V, f = 1MHz, between I/O pins(6)
Cj
Typ.
(3)
VR = 0V, f = 1MHz, between I/O pins
12
-1.4
V
V
16.5
-2.8
V
V
0.35
pF
0.80
0.9
pF
0.43
0.5
pF
0.03
pF
Notes:
3. The working peak reverse voltage, VRWM, should be equal to or greater than the DC or continuous peak operating voltage level.
4. VBR is measured at the pulse test current IT.
5. Measurements performed using a 100ns Transmission Line Pulse (TLP) system.
6. Measure performed with no external capacitor on VP .
Rev. 4.1 September 2021
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AOZ8105CI
Typical Operating Characteristics
Negative Transmission Line Pulse
(tp = 100ns, tr = 0.2ns)
30
0
25
-5
20
-10
TLP Current (A)
TLP Current (A)
Positive Transmission Line Pulse
(tp = 100ns, tr = 0.2ns)
15
10
5
-20
-25
-30
0
-35
-14
-5
0
5
10
15
20
25
-12
-10
-8
-6
-4
-2
TLP Voltage (V)
TLP Voltage (V)
IEC61000-4-5 Positive Surge 8/20µs
IEC61000-4-5 Negative Surge 8/20µs
16
0
14
-1
Clamping Voltage (V)
Clamping Voltage (V)
-15
12
10
8
6
4
0
-2
-3
-4
-5
-6
2
-7
0
0
1.5
2
2.5
3
-3
IPP (A)
-2.5
-2
-1.5
-1
IPP (A)
Typical Variation of CIN vs. VR
(f = 1MHz, T = 25°C)
Normalized Input Capacitance
(pF)
1.2
1.0
0.8
0.6
0.4
0.2
0
0
1
2
3
4
5
Reverse Voltage (V)
Rev. 4.1 September 2021
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Page 4 of 11
AOZ8105CI
Application Information
VGA Ports
The AOZ8105CI TVS is designed to protect four high
speed data lines from ESD and transient over-voltage by
clamping them to a fixed voltage. When the voltages on
the protected lines exceed the limit, the internal steering
diode are forward bias will conduct the harmful transient
away from the sensitive circuitry. As system frequency
increases, printed circuit board layout becomes more
complex. A successful high speed board must integrate
the device and traces while avoiding signal transmission
problems associated with HDMI data speed.
With VGA ports back-drive current is a concern for system instability, start ups and power loss. The back-drive
current occurs when two systems are connected through
a cable and one system is OFF and another system is
ON. In this case the system that is ON is the monitor. The
monitor can inject current into the system that is turned
OFF via the cable. To inhibit the back-drive current from
happening, an integrated diode is designed into the
AOZ8105CI to prevent current from going into the system
that is turned OFF. Figure 2 shows the schematics where
the back-drive current is flowing in a system that is turned
OFF.
Mother Board
Video Monitor
VGA 5V+
6
System
5V
4
5
VGA
5V
BAV 70
1
2
3
Cable
100Ω
100kΩ
DDCA_SDA Scaler
DDCA_SDA
Figure 2. Back-Drive Current Path
ESD Protection
Sync
VGA 5V
Blue
6
5
4
Video Scaler
15 Pin DSUB
Connector
Red
Green
Blue
Sync
SCL
SDA
VSync
HSync
Dig Gnd
Red Gnd
Blue Gnd
Green Gnd
1
2
Red
3
Green
CLK
VGA 5V
SDA
6
5
4
1
2
VSYNC
Red
Green
Blue
Sync
SCL
SDA
VSync
HSync
3
HSYNC
Figure 3. ESD Design for VGA Ports in which Two AOZ8105CI are Used
Rev. 4.1 September 2021
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AOZ8105CI
PCB Layout Example for VGA Port
Figure 4 shows an example for a VGA port with two
AOZ8105CI being used. Place the AOZ8105CI device as
close to the connector as possible. Use ground plane
wherever to ensure maximum performance of the device.
possible traces. A short trace length equates to low
impedance, which ensures that the surge energy will be
dissipated by the AOZ8105CI device. Long signal traces
will act as antennas to receive energy from fields that are
produced by the ESD pulse. By keeping line lengths as
short as possible, the efficiency of the line to act as an
antenna for ESD related fields is reduced. Minimize
interconnecting line lengths by placing devices with the
most interconnect as close together as possible. The
protection circuits should shunt the surge voltage to
either the reference or chassis ground. Shunting the
surge voltage directly to the IC’s signal ground can cause
ground bounce. The clamping performance of TVS
diodes on a single ground PCB can be improved by
minimizing the impedance with relatively short and wide
ground traces. The PCB layout and IC package parasitic
inductances can cause significant overshoot to the TVS’s
clamping voltage. The inductance of the PCB can be
reduced by using short trace lengths and multiple layers
with separate ground and power planes. One effective
method to minimize loop problems is to incorporate a
ground plane in the PCB design.
The AOZ8105CI ultra-low capacitance TVS is designed
to protect four high speed data transmission lines from
transient over-voltages by clamping them to a fixed
reference. The low inductance and construction
minimizes voltage overshoot during high current surges.
When the voltage on the protected line exceeds the
reference voltage the internal steering diodes are forward
biased, conducting the transient current away from the
sensitive circuitry. The AOZ8105CI is designed for the
ease of PCB layout by allowing the traces to run
underneath the device. The pinout of the AOZ8105CI is
design to simply drop onto the IO lines of a High
Definition Multimedia Interface (HDMI) design without
having to divert the signal lines that may add more
parasitic inductance.
Figure 4. PCB Layout Example for VGA Port
High Speed HDMI PCB Layout Guidelines
Printed circuit board layout is the key to achieving the
highest level of surge immunity on power and data lines.
The location of the protection devices on the PCB is the
simplest and most important design rule to follow. The
AOZ8105CI devices should be located as close as
possible to the noise source. The placement of the
AOZ8105CI devices should be used on all data and
power lines that enter or exit the PCB at the I/O
connector. In most systems, surge pulses occur on data
and power lines that enter the PCB through the I/O
connector. Placing the AOZ8105CI devices as close as
possible to the noise source ensures that a surge voltage
will be clamped before the pulse can be coupled into
adjacent PCB traces. In addition, the PCB should use the
shortest
Rev. 4.1 September 2021
It is crucial that the layout is successful for a HDMI
design PCB board. Some of the problems associated
with high speed design are matching impedance of the
traces and to minimize the crosstalk between parallel
traces. This application note is to provide you as much
information to successfully design a high speed PCB
using Alpha & Omega devices.
The HDMI video signals are transmitted on a very high
speed pair of traces and any amount of capacitance,
inductance or even bends in a trace can cause the
impedance of a differential pair to drop as much as 40.
This is not desirable because HDMI ports must maintain
a 100 ±15% on each of the four pairs of its differential
lines per HDMI Compliance Test Specifications. The
HDMI CTS specifies that the impedance on the differential pair of a receiver must be measured using a Time
Domain Reflectometry method with a pulse rise time of
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AOZ8105CI
≤200pS. The TDR measurements of the PCB traces
allows to locate and model discontinuities cause by the
geometrical features of a bend and by the frequencydependant losses of the trace itself. These fast edge
rates can contribute to noise and crosstalk, depending on
the traces and PCB dielectric construction material.
Typical value of W = 12.6 mil, h = 10mils, D = 10mils,
t = 1.4mils and r = 4.0 with the equation below for a
microstrip impedance yields:
Material selection is another aspect that determines good
characteristic impedance in the lines. Different material
will give you different results. The dielectric material will
have the dielectric constant (r).
Zo = 61.73
Where Q1, Q2 = charges, r = distance between charges
(m), F = force(N), = permittivity of dielectric (F/m).
Q1 Q
F = --------------22
4r
5.98 h
87
Zo = -------------------------- = ln ----------------------
0.8W + t
r + 1.41
(3)
By solving for Zo you can calculate the differential
impedance with the equation below.
D
– 0.96 ----
h
Zdiff = 2 Zo 1 – 0.48e
Zdiff = 100.77
(4)
(1)
Each PCB substrate has a different relative dielectric
constant. The dielectric constant is the permittivity of a
relative that of empty space. Where r = dielectric
constant, = permittivity, and o = permittivity of empty
space.
r = ---o
(2)
The dielectric constant affects the impedance of a
transmission line and can propagate faster in materials
that have a lower r . The frequency in your design will
depend on the material being used. With equation 1 you
can determine the type of material to use. If higher
frequency is required other board material maybe
considered. GETEK is another material that can be used
in high speed boards. They have a typical r between 3.6
to 4.0. The most common type of dielectric material used
for PCB is FR-4. Typical dielectric constant for FR-4 is
between 4.0 to 4.5. Most PCB manufacture will be able to
give you the exact value of the FR-4 dielectric constant.
Once you determined the dielectric constant of the board
material you can start to calculate the impedance of each
trace. Below are the formulas for a microstrip layout. This
impedance is dependant on the width of the microstrip
(W) the thickness (t) of the trace and the height (h) of the
FR4 material, and (D) trace edge to edge spacing.
W
D
W
Adjust the trace width, height, distance between the
traces and FR4 thickness to obtain the desired 100
differential impedance. The general rule of thumb is to
route the traces as short as possible, use differential
routing strategies whenever feasible and match the
length and bends to each of the differential traces.
The graphs below show the differential impedance with
varying trace width without the package part on it. Each
of the graphs and board layout represent changing trace
width from 100 to 160 in increment of 20.
Figure 6. 100 Differential Impedance
Max 103, Min 97
t
Trace
εr
Dielectric Material
H
Ground
Figure 5. Dimensions of Microstrip Layout
Figure 7. 120 Differential Impedance
Max 110, Min 102
Rev. 4.1 September 2021
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AOZ8105CI
X
Zo = 61Ω
Zo = 61Ω
Z1
C(TVS)
Figure 11. Impedance Compensation
Figure 8. 140 Differential Impedance
Max 102, Min 92
Z
K = -----1Z2
(5)
Z 0 C TVS
K
X = --------------------- ----------------
2
K –1
(6)
Z0 is the normal 61 differential impedance on the trace.
Z1 is the need impedance to compensate for the added
C(TVS)
K is defined as the unloaded impedance of the adjusted
trace.
X is the length of the trace needed for the compensation.
Figure 9. 160 Differential Impedance
Max 123, Min 109
is the propagation delay time required for a signal to
travel from one point to another. This value should be
less than 200pS.
Differentail Impedance (Ω)
140
120
Max.
100
Min.
80
60
40
20
0
50
55
60
65
70
75
80
Common Mode Impedance (Ω)
Figure 10. Differential Impedance
By adding a TVS onto the traces it can have a large
effect on the impedance of the line. This addition of a
capacitance added to a 100 differential transmission
line without any compensation may decrease the
impedance as much as 20 or more. Below is a formula
to calculate the length for the compensation of C(TVS).
Rev. 4.1 September 2021
From the above method the designer should layout the
boards with a 50 common mode trace. The result
should give you approximately 100 differential impedance. Z1 is the impedance that you choose in order to
compensate the TVS capacitance. Based on Z1 value,
we can get the length of the segment from the above
equations. With the value of Z1 = 98, Zo = 61,
C(TVS) = 0.7 and = 180. The X(mils) equates to 250
mils.
Page 9 has a series of graph that represent changing
width and length of the trace from 100 to 160 in
increment of 20 with a package solder onto the board.
As you can observe from the graphs, a small incremental
capacitance that is added to the differential lines can
significantly decrease the differential impedance. Thus
violated the HDMI specification of 100±15%.
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AOZ8105CI
Figure 12. 100Ω Differential Impedance with Package on it
Max. 97Ω, Min. 80Ω
Figure 14. 140Ω Differential Impedance with Package on it
Max. 102Ω, Min. 92Ω
Figure 13. 120Ω Differential Impedance with Package on it
Max. 99Ω, Min. 86Ω
Figure 15. 160Ω Differential Impedance with Package on it
Max. 101Ω, Min. 95Ω
From Figure 15 we are able to get the best result from
using all of the equation above. With the value of
Z1 = 98, Z0 = 61, C(TVS) = 0.7, = 180. The X(mils)
equates to 250 mils to give the best compensated
Rev. 4.1 September 2021
differential impedance on the traces for the added capacitance from the AOZ8105CI.
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AOZ8105CI
Table 1. AOZ8105CI SOT-23-6 Evaluation Board
Specifications
Number of layers
100Ω
Differential
4
Copper Trace Thickness
1.4 mils
Dielectric Constant r
4
Overall Board Thickness
62 mils
Dielectric thickness between top and ground
layer
10 mils
Conclusion
160Ω
Differential
250 mils
Total Distance
Figure 16. Recommended Layout for SOT-23 Package
Rev. 4.1 September 2021
This application section discusses ESD protection while
maintaining the differential impedance of a HMDI sink
device. Since the TVS add capacitance we must design
the board to meet the HDMI requirements. This application note is a guideline to calculate and layout the PCB.
Different board manufacture and process will fluctuate
and will cause the final board to vary slightly. You must
carefully plan out a successful high speed HDMI PCB.
Factor such as PCB stack up, ground bounce, crosstalk
and signal reflection can interfere with a signal. The
layout, trace routing, board materials and impedance
calculation discussed in this application note can help
you design a more effective PCB.
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AOZ8105CI
LEGAL DISCLAIMER
Applications or uses as critical components in life support devices or systems are not authorized. Alpha and Omega
Semiconductor does not assume any liability arising out of such applications or uses of its products. AOS reserves
the right to make changes to product specifications without notice. It is the responsibility of the customer to evaluate
suitability of the product for their intended application. Customer shall comply with applicable legal requirements,
including all applicable export control rules, regulations and limitations
AOS' products are provided subject to AOS' terms and conditions of sale which are set forth at:
http://www.aosmd.com/terms_and_conditions_of_sale
LIFE SUPPORT POLICY
ALPHA AND OMEGA SEMICONDUCTOR PRODUCTS ARE NOT AUTHORIZED FOR USE AS CRITICAL
COMPONENTS IN LIFE SUPPORT DEVICES OR SYSTEMS.
As used herein:
1. Life support devices or systems are devices or
systems which, (a) are intended for surgical implant into
the body or (b) support or sustain life, and (c) whose
failure to perform when properly used in accordance
with instructions for use provided in the labeling, can be
reasonably expected to result in a significant injury of
the user.
Rev. 4.1 September 2021
2. A critical component in any component of a life
support, device, or system whose failure to perform can
be reasonably expected to cause the failure of the life
support device or system, or to affect its safety or
effectiveness.
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