CS5253-1

CS5253-1 CS5253-1 3A LDO 5-Pin Adjustable Linear Regulator Description This new very low dropout regulator is designed to power the next generation of advanced microprocessors. To achieve very low dropout, the internal pass transistor is powered separately from the control circuitry. Furthermore, with the control and power inputs tied together, this device can be used in single supply configuration and still offer a better dropout voltage than conventional PNP-NPN based LDO regulators. In this mode the dropout is determined by the minimum control voltage. It is supplied in a five-terminal D2PAK package, which allows for the implementation of a remotesense pin permitting very accurate regulation of output voltage directly at the load, where it counts, rather than at the regulator. This remote sensing feature virtually eliminates output voltage variations due to load changes and resistive voltage drops. Typical load regulation measured at the sense pin is less than 1mV for an output voltage of 2.5V with a load step of 10mA to 3A. The very fast transient loop response easily meets the needs of the latest microprocessors. In addition, a small capacitor on the Adjust pin will further improve the transient capabilities. Internal protection circuitry provides for Òbust-proofÓ operation, similar to three-terminal regulators. This circuitry, which includes overcurrent, short circuit, and over-temperature protection will self protect the regulator under all fault conditions. The CS5253-1 is ideal for generating a secondary 2-2.5V low voltage supply on a motherboard where both 5V and 3.3V are already available. Features s 1.25V to 5V VOUT at 3A s VPOWER Dropout < 0.40V @ 3A s VCONTROL Dropout < 1.05V @ 3A s 1% Trimmed Reference s Fast Transient Response s Remote Voltage Sensing s Thermal Shutdown s Current Limit s Short Circuit Protection s Drop-In Replacement for Semtech EZ1582 s Backwards Compatible with 3-pin Regulators Package Options 5 Lead D2PAK Applications Diagram 5.0V VCONTROL VOUT 2.5V @ 3A CS5253-1 3.3V VPOWER VSENSE Adjust 100mF 5V 0.1mF 5V 124 1% 124 Load 1% 300mF 5V 1 1. VSENSE 2. Adjust 3. VOUT 4. VCONTROL 5. VPOWER Tab = VOUT 10mF 10V Cherry Semiconductor Corporation 2000 South County Trail, East Greenwich, RI 02818 Tel: (401)885-3600 Fax: (401)885-5786 Email: info@cherry-semi.com Web Site: www.cherry-semi.com Rev. 5/6/99 1 A ¨ Company CS5253-1 Absolute Maximum Ratings VPOWER Input Voltage.......................................................................................................................................................................6V VCONTROL Input Voltage.................................................................................................................................................................13V Operating Junction Temperature Range ................................................................................................................0¡C ² TJ ² 150¡C Storage Temperature Range .....................................................................................................................................-65¡C to +150¡C Lead Temperature Soldering Reflow (SMD styles only) ......................................................................................60 sec. max above 183¡C, 230¡C peak ESD Damage Threshold............................................................................................................................................................2kV Electrical Characteristics: 0¡C²TA ² 70¡C, 0¡C²TJ ² 150¡C, VSENSE = VOUT and VAdj = 0V unless otherwise specified. PARAMETER TEST CONDITIONS MIN TYP MAX UNIT Reference Voltage Line Regulation Load Regulation VCONTROL=2.75V to 12V, VPOWER=2.05V to 5.5V, IOUT = 10mA to 3A VCONTROL = 2.5V to 12V, VPOWER = 1.75V to 5.5V, IOUT = 10mA VCONTROL = 2.75V, VPOWER = 2.05V, IOUT = 10mA to 3A, with remote sense VCONTROL = 5V, VPOWER = 3.3V, ÆVOUT = +1% VCONTROL = 2.75V, VPOWER = 2.05V, IOUT = 100mA VCONTROL = 2.75V, VPOWER = 2.05V, IOUT = 3A VCONTROL =2.75V, VPOWER = 2.05V, IOUT = 10mA VCONTROL = 2.75V, VPOWER = 2.05V, ÆVOUT = -1% VCONTROL = 2.75V, VPOWER = 2.05V, VOUT = 0V VCONTROL = VPOWER = 3.25V, VRIPPLE = 1VP-P@120Hz, IOUT = 4A, CADJ = 0.1µF 30ms Pulse, TA=25¡C VPOWER = 2.05V, IOUT = 100mA VPOWER = 2.05V, IOUT = 1A VPOWER = 2.05V, IOUT = 3A VCONTROL = 2.75V, IOUT = 100mA VCONTROL = 2.75V, IOUT = 1A VCONTROL = 2.75V, IOUT = 3A Freq = 10Hz to 10kHz, TA = 25¡C 1.237 (-1%) 1.250 .02 .04 1.263 (+1%) .20 .30 V % % Minimum Load Current (Note 1) Control Pin Current (Note 2) Adjust Pin Current Current Limit Short Circuit Current Ripple Rejection (Note 3) Thermal Regulation VCONTROL Dropout Voltage (Minimum VCONTROL-VOUT) (Note 4) VPOWER Dropout Voltage (Minimum VPOWER-VOUT) (Note 4) RMS Output Noise Temperature Stability Thermal Shutdown (Note 5) Thermal Shutdown Hysteresis VCONTROL Supply Only Output Current VPOWER Supply Only Output Current Note 1: Note 2: Note 3: Note 4: Note 5: 5 6 35 60 3.1 2.6 60 4.0 3.5 80 10 10 120 120 mA mA mA µA A A dB 0.002 0.90 1.00 1.05 .05 .15 .40 0.003 0.5 150 180 25 210 50 0.1 1.0 1.15 1.15 1.30 .15 .25 .60 %/W V V V V V V %VOUT % ¡C ¡C mA mA VCONTROL = 13V, VPOWER not connected, VADJUST = VOUT = VSENSE = 0V VPOWER = 6V, VCONTROL not connected, VADJUST = VOUT = VSENSE = 0V The minimum load current is the minimum current required to maintain regulation. Normally the current in the resistor divider used to set the output voltage is selected to meet the minimum load current requirement. The VCONTROL pin current is the drive current required for the output transistor. This current will track output current with roughly a 1:100 ratio. The minimum value is equal to the quiescent current of the device. This parameter is guaranteed by design and is not 100% production tested. Dropout is defined as either the minimum control voltage, (VCONTROL) or minimum power voltage (VPOWER) to output voltage differential required to maintain 1% regulation at a particular load current. This parameter is guaranteed by design, but not parametrically tested in production. However, a 100% thermal shutdown functional test is performed on each part. 2 CS5253-1 Package Pin Description PACKAGE PIN # PIN SYMBOL FUNCTION 5Lead D2 PAK 1 VSENSE This Kelvin sense pin allows for remote sensing of the output voltage at the load for improved regulation. It is internally connected to the positive input of the voltage sensing error amplifier. This pin is connected to the low side of the internally trimmed 1% bandgap reference voltage and carries a bias current of about 50µA. A resistor divider from Adj to VOUT and from Adj to ground sets the output voltage. Also, transient response can be improved by adding a small bypass capacitor from this pin to ground. This pin is connected to the emitter of the power pass transistor and provides a regulated voltage capable of sourcing 3A of current. This is the supply voltage for the regulator control circuitry. For the device to regulate, this voltage should be between 0.9V and 1.3V (depending on the output current) greater than the output voltage. The control pin current will be about 1% of the output current. This is the power input voltage. The pin is physically connected to the collector of the power pass transistor. For the device to regulate, this voltage should be between 0.1V and 0.6V greater than the output voltage, depending on output current. The output load current of 3A is supplied through this pin. 2 Adjust 3 VOUT 4 VCONTROL 5 VPOWER Block Diagram VPOWER VCONTROL BIAS and TSD VREF + EA IA + - VOUT VSENSE Adjust 3 CS5253-1 Typical Performance Characteristics Reference Voltage vs Junction Temperature 1.253 0.12 Load Regulation vs Output Current 1.252 0.10 Reference Voltage (V) 1.251 Load Regulation (%) 0.08 TJ = 120°C 0.06 TJ = 20°C 1.250 1.249 0.04 TJ = 0°C 0.02 1.248 1.247 0 20 40 60 80 100 120 0 0 0.5 1.0 1.5 2.0 2.5 3.0 Junction Temperature (C) Output Current (A) Transient Response 5.0 VCONTROL = 5.0V VPOWER = 3.3V VOUT = 2.5V CCONTROL = 10mF CPOWER = 100mF CADJ = 0.1mF COUT = 300mF Output Current vs VPOWER-VOUT Measured at DVOUT = -1% 4.5 4.0 3.5 Output Current (A) 3.0 2.5 2.0 1.5 1.0 0.5 0 0 1 2 3 4 5 6 VOUT ILOAD, 10mA to 3A VPOWER - VOUT (V) Adjust Pin Current vs Junction Temperature 85 Minimum Load Current vs VCONTROL-VOUT 1200 1150 Minimum Load Current (mA) VPOWER =3.3V D VOUT=+1% 80 1100 1050 1000 950 900 850 IADJ (mA) 75 70 65 60 0 20 40 60 80 100 120 140 800 1.0 2.0 3.0 4.0 Junction Temperature (C) 5.0 6.0 7.0 8.0 VCONTROL-VOUT (V) 9.0 10.0 11.0 4 CS5253-1 Typical Performance Characteristics Short Circuit Output Current vs Junction Temperature 3.9 Ripple Rejection vs Frequency 90.0 Short Circuit Output Current Limit (A) VCONTROL = 2.75V VPOWER = 2.05V 3.8 80.0 Ripple Rejection (dB) 70.0 60.0 50.0 40.00 30.0 VIN-VOUT=2V IOUT=4A VRIPPLE=1VP-P COUT=22mF CADJ=0.1mF 101 102 103 104 105 106 3.7 3.6 3.5 3.4 20.0 10.0 0 20 40 60 80 100 120 140 3.3 Junction Temperature (C) Frequency (Hz) VCONTROL Only Output Current vs Junction Temperature 12 1100 10 VCONTROL = 13V, VOUT = 0V, Vpower not connected VCONTROL Dropout Voltage vs Output Current Vcontrol Dropout Voltage (mV) TJ = 0°C 1000 8 6 TJ = 20°C 900 TJ = 120°C Iout (mA) 4 2 VPOWER = 2.05V 0 0 20 40 60 80 100 120 140 800 0.0 0.5 1.0 1.5 2.0 2.5 3.0 Junction Temperature (C) Output Current (A) VPOWER Dropout Voltage vs Output Current 916.4 916.3 Minimum Load Current vs VPOWER-VOUT 500 Vpower Dropout Voltage (V) Minimum Load Current (mA) 450 400 350 300 250 200 150 50 0 TJ = 120°C TJ = 20°C TJ = 0°C VCONTROL =5V D VOUT=+1% 916.2 916.1 916.0 915.9 915.8 915.7 915.6 915.5 915.4 0.50 1.50 2.50 VPOWER-VOUT (V) 3.50 4.50 0.0 0.5 1.0 1.5 2.0 2.5 3.0 Output Current (A) 5 CS5253-1 Typical Performance Characteristics: Continued VPOWER Only Output Current vs Junction Temperature 30 VPOWER = 6V VOUT = 0V VCONTROL not connected VCONTROL Supply Current vs Junction Temperature 40 VCONTROL = 2.75V VPOWER = 2.05V 35 30 25 20 15 ICONTROL (mA) IOUT (uA) 25 20 15 10 IOUT = 3A 10 5 5 0 0 IOUT = 1A IOUT = 100mA 0 20 40 60 80 100 120 140 0 20 40 60 80 100 120 140 Junction Temperature (C) Junction Temperature (C) Theory of Operation Design Guidelines The CS5253-1 linear regulator provides adjustable voltages from 1.26V to 5V at currents up to 3A. The regulator is protected against short circuits, and includes a thermal shutdown circuit with hysteresis. The output, which is current limited, consists of a PNP-NPN transistor pair and requires an output capacitor for stability. A detailed procedure for selecting this capacitor is included in the Stability Considerations section. VPOWER Function The CS5253-1 utilizes a two supply approach to maximize efficiency. The collector of the power device is brought out to the VPOWER pin to minimize internal power dissipation under high current loads. VCONTROL provides for the control circuitry and the drive for the output NPN transistor. VCONTROL should be at least 1V greater than the output voltage. Special care has been taken to ensure that there are no supply sequencing problems. The output voltage will not turn on until both supplies are operating. If the control voltage comes up first, the output current will be limited to about three milliamperes until the power input voltage comes up. If the power input voltage comes up first, the output will not turn on at all until the control voltage comes up. The output can never come up unregulated. The CS5253-1 can also be used as a single supply device with the control and power inputs tied together. In this mode, the dropout will be determined by the minimum control voltage. Output Voltage Sensing The CS5253-1 five terminal linear regulator includes a dedicated VSENSE function. This allows for true Kelvin sensing of the output voltage. This feature can virtually eliminate errors in the output voltage due to load regulation. Regulation will be optimized at the point where the sense pin is tied to the output. Adjustable Operation This LDO adjustable regulator has an output voltage range of 1.26V to 5V. An external resistor divider sets the output voltage as shown in Figure 1. The regulatorÕs voltage sensing error amplifier maintains a fixed 1.260V reference between the output pin and the adjust pin. A resistor divider network R1 and R2 causes a fixed current to flow to ground. This current creates a voltage across R2 that adds to the 1.260V across R1 and sets the overall output voltage. The adjust pin current (typically 50µA) also flows through R2 and adds a small error that should be taken into account if precise adjustment of VOUT is necessary. The output voltage is set according to the formula: R1+R2 R1 VOUT = 1.260V ´ + R2 ´ IADJ The term IADJ ´ R2 represents the error added by the adjust pin current. R1 is chosen so that the minimum load current is at least 10mA. R1 and R2 should be of the same composition for best tracking over temperature. The divider resistors should be placed physically as close to the load as possible. 5V VCONTROL VOUT 2.5V @3A R1 R2 CS5253-1 3.3V VPOWER VSENSE Adjust Figure 1: Typical application schematic. The resistor divider sets VOUT, with the internal 1.260V reference dropped across R1. 6 CS5253-1 Application Notes: continued While not required, a bypass capacitor connected between the adjust pin and ground will improve transient response and ripple rejection. A 0.1µF tantalum capacitor is recommended for Òfirst cutÓ design. Value and type may be varied to optimize performance vs. price. Other Adjustable Operation Considerations The CS5253-1 linear regulator has an absolute maximum specification of 6V for the voltage difference between VPOWER and VOUT. However, the IC may be used to regulate voltages in excess of 6V. The two main considerations in such a design are the sequencing of power supplies and short circuit capability. Power supply sequencing should be such that the VCONTROL supply is brought up coincidentally with or before the VPOWER supply. This allows the IC to begin charging the output capacitor as soon as the VPOWER to VOUT differential is large enough that the pass transistor conducts. As VPOWER increases, the pass transistor will remain in dropout, and current is passed to the load until VOUT is in regulation. Further increase in the supply voltage brings the pass transistor out of dropout. In this manner, any output voltage less than 13V may be regulated, provided the VPOWER to VOUT differential is less than 6V. In the case where VCONTROL and VPOWER are shorted, there is no theoretical limit to the regulated voltage as long as the VPOWER to VOUT differential of 6V is not exceeded. There is a possibility of damaging the IC when VPOWERVOUT is greater than 6V if a short circuit occurs. Short circuit conditions will result in the immediate operation of the pass transistor outside of its safe operating area. Overvoltage stresses will then cause destruction of the pass transistor before overcurrent or thermal shutdown circuitry can become active. Additional circuitry may be required to clamp the VPOWER to VOUT differential to less than 6V if fail safe operation is required. One possible clamp circuit is illustrated in Figure 2; however, the design of clamp circuitry must be done on an application by application basis. Care must be taken to ensure the clamp actually protects the design. Components used in the clamp design must be able to withstand the short circuit condition indefinitely while protecting the IC. External Supply Stability Considerations The output compensation capacitor helps determine three main characteristics of a linear regulator: start-up delay, load transient response, and loop stability. The capacitor value and type is based on cost, availability, size and temperature constraints. A tantalum or aluminum electrolytic capacitor is best, since a film or ceramic capacitor with almost zero ESR can cause instability. The aluminum electrolytic capacitor is the least expensive solution. However, when the circuit operates at low temperatures, both the value and ESR of the capacitor will vary considerably. The capacitor manufacturer's data sheet provides this information. A 300µF tantalum capacitor will work for most applications, but with high current regulators such as the CS5253-1 the transient response and stability improve with higher values of capacitor. The majority of applications for this regulator involve large changes in load current so the output capacitor must supply the instantaneous load current. The ESR of the output capacitor causes an immediate drop in output voltage given by: ÆV = ÆI ´ ESR. For microprocessor applications it is customary to use an output capacitor network consisting of several tantalum and ceramic capacitors in parallel. This reduces the overall ESR and reduces the instantaneous output voltage drop under transient load conditions. The output capacitor network should be as close to the load as possible for the best results. Protection Diodes When large external capacitors are used with a linear regulator, it is sometimes necessary to add protection diodes. If the input voltage of the regulator gets shorted, the output capacitor will discharge into the output of the regulator. The discharge current depends on the value of the capacitor, the output voltage, and the rate at which VCONTROL drops. In the CS5253-1 regulator, the discharge path is through a large junction and protection diodes are not usually needed. If the regulator is used with large values of output capacitance and the input voltage is instantaneously shorted to ground, damage can occur. In this case, a diode connected as shown in Figure 3 is recommended. External Supply VControl VPower VSENSE VOUT VCONTROL VOUT CS5253-1 VPOWER VSENSE Adjust VAdjust Figure 2: This circuit is an example of how the CS5253-1 can be shortcircuit-protected when operating with VOUT > 6V. Figure 3: Diode protection circuit. 7 CS5253-1 Application Notes: continued A rule of thumb useful in determining if a protection diode is required is to solve for current: I= C´V , T The thermal characteristics of an IC depend on the following four factors: junction temperature, ambient temperature, die power dissipation, and the thermal resistance from the die junction to ambient air. The maximum junction temperature can be determined by: TJ(max) = TA(max) + PD(max) ´ RQJA The maximum ambient temperature and the power dissipation are determined by the design while the maximum junction temperature and the thermal resistance depend on the manufacturer and the package type. The maximum power dissipation for a regulator is: PD(max) = (VIN(max) -VOUT(min))IOUT(max) + VIN(max) ´ IIN(max) A heat sink effectively increases the surface area of the package to improve the flow of heat away from the IC and into the surrounding air. Each material in the heat flow path between the IC and the outside environment has a thermal resistance which is measured in degrees per watt. Like series electrical resistances, these thermal resistances are summed to determine the total thermal resistance between the die junction and the surrounding air, RQJA. This total thermal resistance is comprised of three components. These resistive terms are measured from junction to case (RQJC), case to heat sink (RQCS), and heat sink to ambient air (RQSA). The equation is: RQJA = RQJC + RQCS + RQSA The value for RQJC is 2.5ûC/watt for the CS5253-1 in the D2 PAK package. For a high current regulator such as the CS5253-1 the majority of heat is generated in the power transistor section. The value for RQSA depends on the heat sink type, while the RQCS depends on factors such as package type, heat sink interface (is an insulator and thermal grease used?), and the contact area between the heat sink and the package. Once these calculations are complete, the maximum permissible value of RQJA can be calculated and the proper heat sink selected. For further discussion on heat sink selection, see our Cherry application note ÒThermal Management for Linear Regulators.Ó where I is the current flow out of the load capacitance when VCONTROL is shorted, C is the value of load capacitance V is the output voltage, and T is the time duration required for VCONTROL to transition from high to being shorted. If the calculated current is greater than or equal to the typical short circuit current value provided in the specifications, serious thought should be given to the use of a protection diode. Current Limit The internal current limit circuit limits the output current under excessive load conditions. Short Circuit Protection The device includes short circuit protection circuitry that clamps the output current at approximately 500mA less than its current limit value. This provides for a current foldback function, which reduces power dissipation under a direct shorted load. Thermal Shutdown The thermal shutdown circuitry is guaranteed by design to activate above a die junction temperature of approximately 150¡C and to shut down the regulator output. This circuitry has 25¡C of typical hysteresis, thereby allowing the regulator to recover from a thermal fault automatically. Calculating Power Dissipation and Heat Sink Requirements High power regulators such as the CS5253-1 usually operate at high junction temperatures. Therefore, it is important to calculate the power dissipation and junction temperatures accurately to ensure that an adequate heat sink is used. Since the package tab is connected to VOUT on the CS5253-1, electrical isolation may be required for some applications. Also, as with all high power packages, thermal compound in necessary to ensure proper heat flow. For added safety, this high current LDO includes an internal thermal shutdown circuit 8 CS5253-1 Package Specification PACKAGE DIMENSIONS IN mm (INCHES) PACKAGE THERMAL DATA Thermal Data RQJC RQJA typ typ 5Lead D2PAK 2.5 10-50* ûC/W ûC/W *Depending on thermal properties of substrate. RQJA = RQJC + RQCA 5 Lead D2PAK (DP) 10.31 (.406) 10.05 (.396) 1.40 (.055) 1.14 (.045) 1.68 (.066) 1.40 (.055) 8.53 (.336) 8.28 (.326) 15.75 (.620) 14.73 (.580) 2.74(.108) 2.49(.098) 0.91 (.036) 0.66 (.026) 2.79 (.110) 2.29 (.090) 1.70 (.067) REF .254 (.010) REF 4.57 (.180) 4.31 (.170) 0.10 (.004) 0.00 (.000) Ordering Information Part Number CS5253-1GDP5 CS5253-1GDPR5 Rev. 5/6/99 Description 5 Lead D2PAK 5 Lead D2PAK (tape & reel) 9 Cherry Semiconductor Corporation reserves the right to make changes to the specifications without notice. Please contact Cherry Semiconductor Corporation for the latest available information. © 1999 Cherry Semiconductor Corporation