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ADF4355-3BCPZ

ADF4355-3BCPZ

  • 厂商:

    AD(亚德诺)

  • 封装:

    WFQFN-32

  • 描述:

    IC INTEGRATED SYNTH/VCO 32LFCSP

  • 数据手册
  • 价格&库存
ADF4355-3BCPZ 数据手册
Microwave Wideband Synthesizer with Integrated VCO ADF4355-3 Data Sheet FEATURES GENERAL DESCRIPTION RF output frequency range: 51.5625 MHz to 6600 MHz Fractional-N synthesizer and integer-N synthesizer High resolution 38-bit modulus Low phase noise, voltage controlled oscillator (VCO) Programmable divide by 1, 2, 4, 8, 16, 32, or 64 output All power supplies: 3.3 V Logic compatibility: 1.8 V Programmable dual modulus prescaler of 4/5 or 8/9 Programmable output power level RF output mute function 3-wire serial interface Analog and digital lock detect The ADF4355-3 allows the implementation of fractional-N or integer-N phase-locked loop (PLL) frequency synthesizers when used with an external loop filter and an external reference frequency. A series of frequency dividers at the output provide operation from 51.5625 MHz to 6600 MHz. The ADF4355-3 has an integrated VCO with a fundamental output frequency ranging from 3300 MHz to 6600 MHz. In addition, the VCO frequency is connected to divide by 1, 2, 4, 8, 16, 32, or 64 circuits that allow the user to generate RF output frequencies as low as 51.5625 MHz. For applications that require isolation, the RF output stage can be muted. The mute function is both pin- and software-controllable. APPLICATIONS Control of all on-chip registers is through a simple 3-wire interface. The ADF4355-3 operates with analog, digital, charge pump, and VCO power supplies ranging from 3.1515 V to 3.4485 V. The ADF4355-3 also contains hardware and software power-down modes. Wireless infrastructure (W-CDMA, TD-SCDMA, WiMAX, GSM, PCS, DCS, DECT) Point to point/point to multipoint microwave links Satellites/VSATs Test equipment/instrumentation Clock generation FUNCTIONAL BLOCK DIAGRAM REF IN A REF IN B CLK DATA LE ×2 DOUBLER VVCO VRF AV DD MULTIPLEXER ÷2 DIVIDER 10-BIT R COUNTER RSET VP DV DD AV DD CE MUXOUT LOCK DETECT CREG 1 CREG 2 DATA REGISTER FUNCTION LATCH CHARGE PUMP CP OUT PHASE COMPARATOR VTUNE VREF INTEGER REG FRACTION REG VBIAS VCO CORE MODULUS REG VREGVCO 1/2/4/8 ÷ 16/32/64 THIRD-ORDER FRACTIONAL INTERPOLATOR OUTPUT STAGE RF OUTA+ RF OUTA– PDB RF OUTPUT STAGE MULTIPLEXER AGND CP GND AGNDRF SD GND ADF4355-3 AGNDVCO RF OUTB+ RF OUTB– 13345-001 N COUNTER Figure 1. Rev. B Document Feedback Information furnished by Analog Devices is believed to be accurate and reliable. However, no responsibility is assumed by Analog Devices for its use, nor for any infringements of patents or other rights of third parties that may result from its use. Specifications subject to change without notice. No license is granted by implication or otherwise under any patent or patent rights of Analog Devices. Trademarks and registered trademarks are the property of their respective owners. One Technology Way, P.O. Box 9106, Norwood, MA 02062-9106, U.S.A. Tel: 781.329.4700 ©2015–2017 Analog Devices, Inc. All rights reserved. Technical Support www.analog.com ADF4355-3 Data Sheet TABLE OF CONTENTS Features .............................................................................................. 1 Register 4 ..................................................................................... 22 Applications ....................................................................................... 1 Register 5 ..................................................................................... 23 General Description ......................................................................... 1 Register 6 ..................................................................................... 24 Functional Block Diagram .............................................................. 1 Register 7 ..................................................................................... 26 Revision History ............................................................................... 2 Register 8 ..................................................................................... 27 Specifications..................................................................................... 3 Register 9 ..................................................................................... 27 Timing Characteristics ................................................................ 5 Register 10 ................................................................................... 28 Absolute Maximum Ratings ............................................................ 6 Register 11 ................................................................................... 28 Transistor Count ........................................................................... 6 Register 12 ................................................................................... 29 ESD Caution .................................................................................. 6 Register Initialization Sequence ............................................... 29 Pin Configuration and Function Descriptions ............................. 7 Frequency Update Sequence ..................................................... 30 Typical Performance Characteristics ............................................. 9 RF Synthesizer—A Worked Example ...................................... 30 Theory of Operation ...................................................................... 12 Reference Doubler and Reference Divider ............................. 30 Reference Input Section ............................................................. 12 Spurious Optimization and Fast Lock ..................................... 31 RF N Divider ............................................................................... 12 Optimizing Jitter ......................................................................... 31 Phase Frequency Detector (PFD) and Charge Pump ............ 13 Spur Mechanisms ....................................................................... 31 MUXOUT and Lock Detect ...................................................... 13 Lock Time.................................................................................... 31 Input Shift Registers ................................................................... 13 Applications Information .............................................................. 32 Program Modes .......................................................................... 14 Direct Conversion Modulator .................................................. 32 VCO.............................................................................................. 14 Power Supplies ............................................................................ 33 Output Stage ................................................................................ 14 Loop Filter ................................................................................... 14 Printed Circuit Board (PCB) Design Guidelines for a ChipScale Package .............................................................................. 33 Register Maps .................................................................................. 16 Output Matching ........................................................................ 33 Register 0 ..................................................................................... 18 Outline Dimensions ....................................................................... 34 Register 1 ..................................................................................... 19 Ordering Guide .......................................................................... 34 Register 2 ..................................................................................... 20 Register 3 ..................................................................................... 21 REVISION HISTORY 8/2017—Rev. A to Rev. B Changes to Frequency Update Sequence .................................... 30 Updated Outline Dimensions ....................................................... 34 Changes to Ordering Guide .......................................................... 34 1/2016—Rev. 0 to Rev. A Change to Integrated RMS Jitter Parameter, Unit Column, Table 1 ................................................................................................ 4 Changes to Reference Input Section ............................................ 12 Changes to Table 6 .......................................................................... 15 Changes to Figure 25...................................................................... 17 Changes to Reference Mode Section ........................................... 23 Changes to Negative Bleed Section .............................................. 24 Changes to Charge Pump Bleed Current Section ...................... 25 Changes to Figure 34, Figure 35, and Register 8 Section .......... 27 Changes to Figure 37 and Register 11 Section ........................... 28 7/2015—Revision 0: Initial Version Rev. B | Page 2 of 34 Data Sheet ADF4355-3 SPECIFICATIONS AVDD = DVDD = VRF = VP = VVCO = VREGVCO = 3.3 V ± 4.5%, AGND = CPGND = AGNDVCO = SDGND = AGNDRF = 0 V, RSET = 5.1 kΩ, dBm referred to 50 Ω, TA = TMIN to TMAX, unless otherwise noted. Table 1. Parameter REFINA/REFINB CHARACTERISTICS Input Frequency Symbol Min Typ Differential Mode 250 600 100 MHz MHz MHz 0.4 AVDD V p-p 0.4 1.8 V p-p ±60 ±250 125 pF pF µA µA MHz Input Capacitance Single-Ended Mode Differential Mode Input Current Output Dividers VCO Supply Current RFOUTA±/RFOUTB± Supply Current Low Power Sleep Mode 6.9 1.4 ICP VINH VINL IINH/IINL CIN 1.5 VOH DVDD − 0.4 1.5 mA mA kΩ % % % DVDD 0.6 ±1 3.0 REFINA biased at AVDD/2; ac coupling ensures AVDD/2 bias LVDS and LVPECL compatible, REFINA/ REFINB biased at 2.1 V; ac coupling ensures 2.1 V bias Single-ended reference programmed Differential reference programmed 3.1515 Fixed 0.5 V ≤ VCP 1 ≤ VP − 0.5 V 0.5 V ≤ VCP1 ≤ VP − 0.5 V VCP1 = 2.5 V 1.8 V and 3.3 V compatible V V µA pF 0.4 500 V V V µA 3.3 V output selected 1.8 V output selected IOL 2 = 500 µA 3.3 AVDD 3.4485 V 3.3 V ± 4.5% Voltages must equal AVDD 3.1 66 5 75 mA mA 52 13/19/ 25/31 1500 1950 70 20/27/ 34/41 mA mA 1.8 VOL IOH IVCO IRFOUT x ± Doubler is set in Register 4, Bit DB26 RSET = 5.1 kΩ 4.8 0.3 5.1 3 3 1.5 AVDD DVDD, VRF, VP, VVCO IP Test Conditions/Comments For f < 10 MHz, ensure that the slew rate > 21 V/µs 10 10 Low Output High Current POWER SUPPLIES Analog Power Digital Power, RF Supply, Charge Pump, and VCO Supply Voltage Charge Pump Supply Current DIDD + AIDD 3 Unit REFIN Single-Ended Mode Differential Mode Doubler Enabled Input Sensitivity Single-Ended Mode Phase Detector Frequency CHARGE PUMP (CP) Charge Pump Current, Sink/Source High Low RSET Range Current Matching ICP vs. VCP1 ICP vs. Temperature LOGIC INPUTS Input Voltage High Low Input Current Input Capacitance LOGIC OUTPUTS Output Voltage High Max Rev. B | Page 3 of 34 µA µA Supply current drawn by DVDD plus supply current drawn by AVDD See Table 6 RF output stage is programmable; RFOUTB+/RFOUTB− powered off Hardware power-down Software power-down ADF4355-3 Parameter RF OUTPUT CHARACTERISTICS VCO Frequency Range RF Output Frequency VCO Sensitivity Frequency Pushing (Open-Loop) Frequency Pulling (Open-Loop) Harmonic Content Second Data Sheet Symbol fRF KV Third RF Output Power 4 RF Output Power Variation Over Frequency Level of Signal with Output Disabled NOISE CHARACTERISTICS Fundamental VCO Phase Noise Performance 3.3 GHz Carrier Typ Max Unit Test Conditions/Comments 6600 6600 Fundamental VCO range 63 22 0.54 MHz MHz MHz/V MHz/V MHz −27 −22 −20 −12 8 3 dBc dBc dBc dBc dBm dBm ±1 ±3 −60 −30 dB dB dBm dBm 3300 51.5625 Voltage standing wave ratio (VSWR) = 2:1 Fundamental VCO output (RFOUTA+) Divided VCO output (RFOUTA+) Fundamental VCO output (RFOUTA+) Divided VCO output (RFOUTA+) RFOUTA+ = 1 GHz. 7.5 nH inductor to VRF RFOUTA+/RFOUTA− = 4.4 GHz. 7.5 nH inductor to VRF RFOUTA+/RFOUTA− = 4.4 GHz RFOUTA+/RFOUTA− = 1 GHz to 4.4 GHz RFOUTA+/RFOUTA− = 1 GHz, VCO = 4 GHz RFOUTA+/RFOUTA− = 4.4 GHz, VCO = 4.4 GHz VCO noise in open-loop conditions 5.0 GHz Carrier 6.6 GHz Carrier Normalized In-Band Phase Noise Floor Fractional Channel 5 Integer Channel 6 Normalized 1/f Noise 7 Integrated RMS Jitter Spurious Signals due to Phase Frequency Detector (PFD) Frequency Min PN1_f −113 −133 −135 −153 −110 −130 −132 −151 −107 −127 −129 −148 dBc/Hz dBc/Hz dBc/Hz dBc/Hz dBc/Hz dBc/Hz dBc/Hz dBc/Hz dBc/Hz dBc/Hz dBc/Hz dBc/Hz 100 kHz offset from 3.3 GHz carrier 800 kHz offset from 3.3 GHz carrier 1 MHz offset from 3.3 GHz carrier 10 MHz offset from 3.3 GHz carrier 100 kHz offset from 5.0 GHz carrier 800 kHz offset from 5.0 GHz carrier 1 MHz offset from 5.0 GHz carrier 10 MHz offset from 5.0 GHz carrier 100 kHz offset from 6.6 GHz carrier 800 kHz offset from 6.6 GHz carrier 1 MHz offset from 6.6 GHz carrier 10 MHz offset from 6.6 GHz carrier −221 −223 −116 200 −85 dBc/Hz dBc/Hz dBc/Hz fs dBc 10 kHz offset, normalized to 1 GHz VCP is the voltage at the CPOUT pin. IOL is the output low current. 3 TA = 25°C; AVDD = DVDD = VRF = VVCO = VP = 3.3 V; prescaler = 4/5; fREFIN = 122.88 MHz; fPFD = 61.44 MHz; and fRF = 1650 MHz. 4 RF output power using the EV-ADF4355-3SD1Z evaluation board measured into a spectrum analyzer, with board and cable losses de-embedded. Unused RF output pins are terminated in 50 Ω. 5 Use this figure to calculate the phase noise for any application. To calculate in-band phase noise performance as seen at the VCO output, use the following formula: −221 + 10log(fPFD) + 20logN. The value given is the lowest noise mode for the fractional channel. 6 Use this figure to calculate the phase noise for any application. To calculate in-band phase noise performance as seen at the VCO output, use the following formula: −223 + 10log(fPFD) + 20logN. The value given is the lowest noise mode for the integer channel. 7 The PLL phase noise is composed of 1/f (flicker) noise plus the normalized PLL noise floor. The formula for calculating the 1/f noise contribution at an RF frequency (fRF) and at a frequency offset (f) is given by PN = P1_f + 10log(10 kHz/f) + 20log(fRF/1 GHz). Both the normalized phase noise floor and flicker noise are modeled in the ADIsimPLL™ design tool. 1 2 Rev. B | Page 4 of 34 Data Sheet ADF4355-3 TIMING CHARACTERISTICS AVDD = DVDD =VRF = VP = VVCO = 3.3 V ± 4.5%, AGND = CPGND = AGNDVCO = SDGND = AGNDRF = 0 V, RSET = 5.1 kΩ, dBm referred to 50 Ω, TA = TMIN to TMAX, unless otherwise noted. Table 2. Write Timing Parameter fCLK t1 t2 t3 t4 t5 t6 t7 Limit 50 10 5 5 10 10 5 20 or (2/fPFD), whichever is longer Unit MHz max ns min ns min ns min ns min ns min ns min ns min Description SPI CLK frequency LE setup time DATA to CLK setup time DATA to CLK hold time CLK high duration CLK low duration CLK to LE setup time LE pulse width Write Timing Diagram t4 t5 CLK t2 DATA DB31 (MSB) t3 DB30 DB3 (CONTROL BIT C4) DB2 (CONTROL BIT C3) DB1 (CONTROL BIT C2) DB0 (LSB) (CONTROL BIT C1) LE t1 t6 Figure 2. Write Timing Diagram Rev. B | Page 5 of 34 13345-002 t7 ADF4355-3 Data Sheet ABSOLUTE MAXIMUM RATINGS TA = 25°C, unless otherwise noted. Table 3. Parameter1 VRF, DVDD, AVDD to GND AVDD to DVDD VP, VVCO, VREGVCO to GND CPOUT to GND1 Digital Input/Output Voltage to GND Analog Input/Output Voltage to GND REFINA, REFINB to GND REFINA to REFINB Operating Temperature Range Storage Temperature Range Maximum Junction Temperature θJA, Thermal Impedance Pad Soldered to GND Reflow Soldering Peak Temperature Time at Peak Temperature Electrostatic Discharge (ESD) Charged Device Model Human Body Model 1 Rating −0.3 V to +3.6 V −0.3 V to +0.3 V −0.3 V to +3.6 V −0.3 V to VP + 0.3 V −0.3 V to DVDD + 0.3 V −0.3 V to AVDD + 0.3 V −0.3 V to AVDD + 0.3 V ±2.1 V −40°C to +105°C −65°C to +125°C 150°C 27.3°C/W Stresses at or above those listed under Absolute Maximum Ratings may cause permanent damage to the product. This is a stress rating only; functional operation of the product at these or any other conditions above those indicated in the operational section of this specification is not implied. Operation beyond the maximum operating conditions for extended periods may affect product reliability. The ADF4355-3 is a high performance RF integrated circuit with an ESD rating of 2500 V and is ESD sensitive. Take proper precautions for handling and assembly. TRANSISTOR COUNT The transistor count for the ADF4355-3 is 103,665 (CMOS) and 3214 (bipolar). ESD CAUTION 260°C 40 sec 500 V 2500 V GND = AGND = SDGND = AGNDRF = AGNDVCO = CPGND = 0 V. Rev. B | Page 6 of 34 Data Sheet ADF4355-3 32 31 30 29 28 27 26 25 CREG 2 SDGND MUXOUT REFINA REFINB DVDD PDBRF CREG 1 PIN CONFIGURATION AND FUNCTION DESCRIPTIONS CLK DATA LE CE AVDD VP CPOUT ADF4355-3 TOP VIEW (Not to Scale) 24 23 22 21 20 19 18 17 VBIAS VREF RSET AGNDVCO VTUNE VREGVCO AGNDVCO VVCO NOTES 1. THE EXPOSED PAD MUST BE CONNECTED TO AGND. 13345-003 AGND VRF RFOUTA+ RFOUTA− AGNDRF RFOUTB+ RFOUTB– AVDD 9 10 11 12 13 14 15 16 1 2 3 4 5 6 7 CPGND 8 Figure 3. Pin Configuration Table 4. Pin Function Descriptions Pin No. 1 Mnemonic CLK 2 DATA 3 LE 4 CE 5, 16 AVDD 6 VP 7 CPOUT 8 9 10 CPGND AGND VRF 11 12 RFOUTA+ RFOUTA− 13 14 AGNDRF RFOUTB+ 15 RFOUTB− 17 VVCO 18, 21 19 AGNDVCO VREGVCO 20 VTUNE Description Serial Clock Input. Data is clocked into the 32-bit shift register on the CLK rising edge. This input is a high impedance CMOS input. Serial Data Input. The serial data is loaded most significant bit (MSB) first with the four least significant bits (LSBs) as the control bits. This input is a high impedance CMOS input. Load Enable, CMOS Input. When LE goes high, the data stored in the shift register is loaded into the register that is selected by the four LSBs. Chip Enable. A logic low on this pin powers down the device and puts the charge pump into three-state mode. A logic high on this pin powers up the device, depending on the status of the power-down bits. Analog Power Supplies. These pins range from 3.1515 V to 3.4485 V. Connect decoupling capacitors to the analog ground plane as close to these pins as possible. AVDD must have the same value as DVDD. Charge Pump Power Supply. VP must have the same value as VVCO. Connect decoupling capacitors to the ground plane as close to this pin as possible. Charge Pump Output. When enabled, this output provides ±ICP to the external loop filter. The output of the loop filter is connected to VTUNE to drive the internal VCO. Charge Pump Ground. This output is the ground return pin for CPOUT. Analog Ground. Ground return pin for AVDD. Power Supply for the RF Output. Connect decoupling capacitors to the analog ground plane as close to this pin as possible. VRF must have the same value as AVDD. For optimum spurious performance, VRF and DVDD must originate from different regulators. VCO Output. The output level is programmable. The VCO fundamental output or a divided down version is available. Complementary VCO Output. The output level is programmable. The VCO fundamental output or a divided down version is available. RF Output Stage Ground. This pin is the ground return for the RF output stage. Auxiliary VCO Output. The output level is programmable. The VCO fundamental output or a divided down version is available. Complementary Auxiliary VCO Output. The output level is programmable. The VCO fundamental output or a divided down version is available. Power Supply for the VCO. The voltage on this pin ranges from 3.1515 V to 3.4485 V. Connect decoupling capacitors to the analog ground plane as close to this pin as possible. VCO Ground. This pin is the ground return path for the VCO. VCO Compensation Node. Connect decoupling capacitors to the ground plane as close to this pin as possible. Connect this pin directly to VVCO. Control Input to the VCO. This voltage determines the output frequency and is derived from filtering the CPOUT output voltage. The capacitance at this pin (VTUNE input capacitance) is 7 pF. Rev. B | Page 7 of 34 ADF4355-3 Pin No. 22 23 Mnemonic RSET VREF 24 VBIAS 25, 32 CREG1, CREG2 26 27 PDBRF DVDD 28 29 30 REFINB REFINA MUXOUT 31 SDGND EP Data Sheet Description Bias Current Resistor. Connecting a resistor between this pin and ground sets the charge pump output current. Internal Compensation Node. VREF is dc biased at half of the tuning range. Connect decoupling capacitors to the ground plane as close to this pin as possible. The recommended capacitor values are 10 pF, 1 nF, and 4.7 µF. Reference Voltage. Connect decoupling capacitors to the ground plane as close to this pin as possible. The recommended capacitor values are 10 pF, 1 nF, and 1 µF. Outputs from the LDO Regulator. Pin 25 and Pin 32 are the supply voltages to the digital circuits, and have a nominal voltage of 1.8 V. Decoupling capacitors of 100 nF connected to AGND are required for these pins. RF Power-Down. A logic low on this pin mutes the RF outputs. This mute function is also software-controllable. Digital Power Supply. This pin must be at the same voltage as AVDD. Place decoupling capacitors to the ground plane as close to this pin as possible. For optimum spurious performance, VRF and DVDD must originate from different regulators. Complementary Reference Input. If unused, ac-couple this pin to AGND. Reference Input. Multiplexer Output. The multiplexer output allows the digital lock detect, the analog lock detect, scaled RF, or the scaled reference frequency to be externally accessible. Digital Σ-Δ Modulator Ground. Pin 31 is the ground return path for the Σ-Δ modulator. Exposed Pad. The exposed pad must be connected to AGND. Rev. B | Page 8 of 34 Data Sheet ADF4355-3 –50 –50 –70 –70 PHASE NOISE (dBc/Hz) –90 –110 –130 –150 10k 100k 1M OFFSET FREQUENCY (Hz) 10M 100M –130 –170 1k –50 –70 –70 –90 –110 –130 1M 10M 100M ÷1 ÷2 ÷4 ÷8 ÷16 ÷32 ÷64 –90 –110 –130 10k 100k 1M OFFSET FREQUENCY (Hz) 10M 100M –170 13345-005 1k Figure 5. Open-Loop VCO Phase Noise, 5.0 GHz 1k 10k 100k 1M 10M 100M FREQUENCY (Hz) 13345-008 –150 –150 Figure 8. Closed-Loop Phase Noise, RFOUTA+, Fundamental VCO and Dividers, VCO = 5.0 GHz, fPFD = 61.44 MHz, Loop Bandwidth = 35 kHz –50 –70 –70 PHASE NOISE (dBc/Hz) –50 –90 –110 –130 –150 ÷1 ÷2 ÷4 ÷8 ÷16 ÷32 ÷64 –90 –110 –130 –150 1k 10k 100k 1M OFFSET FREQUENCY (Hz) 10M Figure 6. Open-Loop VCO Phase Noise, 6.6 GHz 100M –170 13345-006 –170 100k Figure 7. Closed-Loop Phase Noise, RFOUTA+, Fundamental VCO and Dividers, VCO = 3.3 GHz, fPFD = 61.44 MHz, Loop Bandwidth = 35 kHz –50 –170 10k FREQUENCY (Hz) PHASE NOISE (dBc/Hz) PHASE NOISE (dBc/Hz) –110 13345-007 1k Figure 4. Open-Loop VCO Phase Noise, 3.3 GHz PHASE NOISE (dBc/Hz) –90 –150 13345-004 –170 ÷1 ÷2 ÷4 ÷8 ÷16 ÷32 ÷64 1k 10k 100k 1M FREQUENCY (Hz) 10M 100M 13345-009 PHASE NOISE (dBc/Hz) TYPICAL PERFORMANCE CHARACTERISTICS Figure 9. Closed-Loop Phase Noise, RFOUTA+, Fundamental VCO and Dividers, VCO = 6.6 GHz, fPFD = 61.44 MHz, Loop Bandwidth = 35 kHz Rev. B | Page 9 of 34 Data Sheet –40 5 –50 WORST CASE PFD SPUR (dBc) 10 0 –5 –10 –15 –20 –40°C +25°C +105°C –30 0 1 2 3 4 5 6 Figure 10. Output Power vs. Frequency, RFOUTA+/RFOUTA− (7.5 nH Inductors, 10 pF Bypass Capacitors, Board Losses De-Embedded) –80 –90 0 1 2 3 4 5 6 FREQUENCY (GHz) Figure 13. Worst Case PFD Spur vs. Frequency, fPFD = 15.36 MHz, 30.72 MHz, and 61.44 MHz, Loop Filter = 35 kHz –80 SECOND HARMONIC THIRD HARMONIC 0 –90 PHASE NOISE (dBc/Hz) –10 –20 –30 –40 –50 –100 –110 –120 –130 –140 0 1 2 3 4 FREQUENCY (GHz) 5 6 7 Figure 11. RFOUTA+/RFOUTA− Harmonics vs. Frequency (7.5 nH Inductors, 10 pF Bypass Capacitors, Board Losses De-Embedded) 1.2 –160 1k 10k 100k 1M FREQUENCY (Hz) 10M 100M 13345-018 –150 13345-049 RFOUTA+/RFOUTA− HARMONICS (dBc) –70 –110 10 Figure 14. Spur Performance, GSM1800 Band, RFOUTA+ = 1550.2 MHz, REFIN = 122.88 MHz, fPFD = 61.44 MHz, Output Divide by 4 Selected, Loop Filter Bandwidth = 35 kHz, Channel Spacing = 20 kHz 1kHz - 20MHz 12kHz - 20MHz –80 1.0 –90 0.8 PHASE NOISE (dBc/Hz) RMS JITTER (ps) –60 –100 FREQUENCY (GHz) –60 PFD = 61.44MHz PFD = 30.72MHz PFD = 15.36MHz 13345-051 –25 13345-048 OUTPUT POWER (dBm) ADF4355-3 0.6 0.4 0.2 –100 –110 –120 –130 –140 1 2 3 4 5 OUTPUT FREQUENCY (GHz) 6 7 Figure 12. RMS Jitter vs. Output Frequency, fPFD = 61.44 MHz, Loop Filter = 35 kHz –160 1k 10k 100k 1M FREQUENCY (Hz) 10M 100M 13345-019 0 13345-050 –150 0 Figure 15. Spur Performance, W-CDMA Band, RFOUTA+ = 2113.5 MHz, REFIN = 122.88 MHz, fPFD = 61.44 MHz, Output Divide by 2 Selected, Loop Filter Bandwidth = 35 kHz, Channel Spacing = 20 kHz Rev. B | Page 10 of 34 Data Sheet ADF4355-3 –80 5 4 3 –100 FREQUENCY (MHz) –110 –120 –130 –140 1 0 –1 –2 –3 –150 –4 10k 100k 1M FREQUENCY (Hz) 10M 100M Figure 16. Spur Performance, RFOUTA+ = 2.591 GHz, REFIN = 122.88 MHz, fPFD = 61.44 MHz, Output Divide-by-2 Selected, Loop Filter Bandwidth = 35 kHz, Channel Spacing = 20 kHz –5 –150 13345-020 –160 1k 2 0 150 300 450 600 750 TIME (µs) 900 1050 1200 1350 13345-047 PHASE NOISE (dBc/Hz) –90 Figure 17. Lock Time for 100 MHz Jump from 3300 MHz to 6600 MHz, Loop Bandwidth = 3 kHz Rev. B | Page 11 of 34 ADF4355-3 Data Sheet THEORY OF OPERATION REFERENCE INPUT SECTION INT, FRACx, MODx, and R Counter Relationship Figure 18 shows the reference input section of the ADF4355-3. The reference input can accept both single-ended and differential signals. Use the reference mode bit (Register 4, Bit DB9) to select the signal. To use a differential signal on the reference input, program this bit high. In this case, SW1 and SW2 are open, SW3 and SW4 are closed, and the current source that drives the differential pair of transistors switches on. The differential signal is buffered, and it is provided to an emitter coupled logic (ECL) to a CMOS converter. When a single-ended signal is the reference, connect the reference signal to REFINA and program Bit DB9 in Register 4 to 0. In this case, SW1 and SW2 are closed, SW3 and SW4 are open, and the current source that drives the differential pair of transistors switches off. Single-ended mode results in lower integer boundary spurs. The INT, FRAC1, FRAC2, MOD1, and MOD2 values, in conjunction with the R counter, make it possible to generate output frequencies that are spaced by fractions of the PFD frequency (fPFD). For more information, see the RF Synthesizer— A Worked Example section. Calculate the RF VCO frequency (VCOOUT) by VCOOUT = fPFD × N where: VCOOUT is the output frequency of the VCO (without using the output divider). fPFD is the frequency of the phase frequency detector. N is the desired value of the feedback counter, N. Calculate fPFD by REFERENCE INPUT MODE fPFD = REFIN × ((1 + D)/(R × (1 + T))) BUFFER SW1 SW3 MULTIPLEXER TO R COUNTER AVDD N comprises ECL TO CMOS BUFFER REFINA N  INT  REFINB 2.5kΩ 2.5kΩ 13345-022 SW4 BIAS GENERATOR Figure 18. Reference Input Stage RF N DIVIDER The RF N divider allows a division ratio in the PLL feedback path. Determine the division ratio by the INT, FRAC1, FRAC2, and MOD2 values that this divider comprises. RF N COUNTER FRAC1 + N = INT + MOD2 TO PFD MOD1 FRAC1 REG FRAC2 VALUE 1. 2. 3. THIRD-ORDER FRACTIONAL INTERPOLATOR INT REG (3) Equation 3 results in a very fine frequency resolution with no residual frequency error. Apply this formula using the following steps: FRAC2 N COUNTER FRAC2 MOD2 MOD1 FRAC1  where: INT is the 16-bit integer value (23 to 32,767 for the 4/5 prescaler, and 75 to 65,535 for the 8/9 prescaler). FRAC1 is the numerator of the primary modulus (0 to 16,777,215). FRAC2 is the numerator of the 14-bit auxiliary modulus (0 to 16,383). MOD2 is the programmable, 14-bit auxiliary fractional modulus (2 to 16,383). MOD1 is a 24-bit primary modulus with a fixed value of 224 = 16,777,216. MOD2 VALUE 4. 13345-023 FROM VCO OUTPUT/ OUTPUT DIVIDERS (2) where: REFIN is the reference input frequency. D is the REFIN doubler bit. R is the preset divide ratio of the binary 10-bit programmable reference counter (1 to 1023). T is the REFIN divide by 2 bit (0 or 1). 85kΩ SW2 (1) Figure 19. RF N Divider Rev. B | Page 12 of 34 Calculate N by dividing VCOOUT/fPFD. The integer value of this number forms INT. Subtract the INT value from the full N value. Multiply the remainder by 224. The integer value of this number forms FRAC1. Calculate the MOD2 based on the channel spacing (fCHSP) by MOD2 = fPFD /GCD(fPFD, fCHSP) (4) where: fCHSP is the desired channel spacing. GCD(fPFD, fCHSP) is the greatest common divider of the PFD frequency and the channel spacing frequency. Data Sheet SDGND Calculate FRAC2 by the following equation: FRAC2 = ((N − INT) × 224 − FRAC1)) × MOD2 (5) THREE-STATE OUTPUT The FRAC2 and MOD2 fraction results in outputs with zero frequency error for channel spacings when SDGND DGND fPFD/GCD(fPFD/fCHSP) < 16,383 (6) R DIVIDER OUTPUT N DIVIDER OUTPUT where: fPFD is the frequency of the phase frequency detector. GCD is a greatest common divider function. fCHSP is the desired channel spacing. RESERVED INPUT SHIFT REGISTERS R Counter The 10-bit R counter allows the input reference frequency (REFIN) to be divided down to produce the reference clock to the PFD. Division ratios from 1 to 1023 are allowed. PHASE FREQUENCY DETECTOR (PFD) AND CHARGE PUMP The PFD takes inputs from the R counter and N counter and produces an output proportional to the phase and frequency difference between them. Figure 20 is a simplified schematic of the phase frequency detector. The PFD includes a fixed delay element that sets the width of the antibacklash pulse. This pulse ensures that there is no dead zone in the PFD transfer function and provides a consistent reference spur level. Set the phase detector polarity to positive on this device because of the positive tuning of the VCO. UP U1 CLR1 DELAY HIGH U3 CHARGE PUMP CP CLR2 DOWN D2 Q2 U2 –IN 13345-024 +IN DGND Figure 21. MUXOUT Block Diagram If negative bleed is enabled, lock detect is not reliable for low PFD frequencies. When FRAC1 and FRAC2 = 0, the synthesizer operates in integer-N mode. Q1 MUXOUT SDGND to DVDD INT N Mode D1 CONTROL DIGITAL LOCK DETECT If zero frequency error is not required, the MOD1 and MOD2 denominators operate together to create a 38-bit resolution modulus. HIGH MUX 13345-025 5. ADF4355-3 The ADF4355-3 digital section includes a 10-bit R counter, a 16-bit RF integer-N counter, a 24-bit FRAC1 counter, a 14-bit auxiliary fractional counter, and a 14-bit auxiliary modulus counter. Data clocks into the 32-bit shift register on each rising edge of CLK. The data clocks in MSB first. Data transfers from the shift register to one of 13 latches on the rising edge of LE. The state of the four control bits (C4, C3, C2, and C1) in the shift register determines the destination latch. As shown in Figure 2, the four least significant bits (LSBs) are DB3, DB2, DB1, and DB0. The truth table for these bits is shown in Table 5. Figure 24 and Figure 25 summarize the programing of the latches. Table 5. Truth Table for the C4, C3, C2, and C1 Control Bits C4 0 0 0 0 0 0 0 0 1 1 1 1 1 Figure 20. PFD Simplified Schematic MUXOUT AND LOCK DETECT The output multiplexer on the ADF4355-3 allows the user to access various internal points on the chip. The M3, M2, and M1 bits in Register 4 control the state of MUXOUT. Figure 21 shows the MUXOUT section in block diagram form. Rev. B | Page 13 of 34 C3 0 0 0 0 1 1 1 1 0 0 0 0 1 Control Bits C2 0 0 1 1 0 0 1 1 0 0 1 1 0 C1 0 1 0 1 0 1 0 1 0 1 0 1 0 Register Register 0 Register 1 Register 2 Register 3 Register 4 Register 5 Register 6 Register 7 Register 8 Register 9 Register 10 Register 11 Register 12 ADF4355-3 Data Sheet 130 PROGRAM MODES 120 Table 5 and Figure 24 through Figure 38 show the program modes that must be set up in the ADF4355-3. 110 100 VCO The VCO core in the ADF4355-3 consists of four separate VCOs, each of which uses 256 overlapping bands, which allows covering a wide frequency range without a large VCO sensitivity (KV) and without resulting poor phase noise and spurious performance. The correct VCO and band are chosen automatically by the VCO and band select logic when Register 0 is updated and autocalibration is enabled. The VCO VTUNE is disconnected from the output of the loop filter and is connected to an internal reference voltage. The R counter output is the clock for the band select logic. After band selection, normal PLL action resumes. The nominal value of KV is 63 MHz/V when the N divider is driven from the VCO output, or the KV value is divided by D. D is the output divider value if the N divider is driven from the RF output divider (chosen by programming Bits[D23:D21] in Register 6). 80 70 60 50 40 30 20 10 0 3.3 4.3 3.8 4.8 5.3 FREQUENCY (GHz) 5.8 6.3 13345-052 For example, to ensure that the modulus value loads correctly, every time the modulus value updates, Register 0 must be written to. The RF divider select in Register 6 is also double buffered, but only when DB14 of Register 4 is high. 90 KV (MHz/V) The following settings in the ADF4355-3 are double buffered: main fractional value (FRAC1), auxiliary modulus value (MOD2), auxiliary fractional value (FRAC2), reference doubler, reference divide by 2 (RDIV2), phase value, R counter value, and charge pump current setting. Two events must occur before the ADF4355-3 uses a new value for any of the double buffered settings. First, the new value must latch into the device by writing to the appropriate register, and second, a new write to Register 0 must be performed. Figure 22. KV vs. VCO Frequency OUTPUT STAGE The RFOUTA+ and RFOUTA− pins of the ADF4355-3 connect to the collectors of an NPN differential pair driven by buffered outputs of the VCO, as shown in Figure 23. In this scheme, the ADF4355-3 contains internal 50 Ω resistors connected to the VRF pin. To optimize the power dissipation vs. the output power requirements, the tail current of the differential pair is programmable using Bits[DB5:DB4] in Register 6. Four current levels can be set. These levels give the approximate output power levels of −4 dBm, −1 dBm, +2 dBm, and +5 dBm, respectively, using a 50 Ω resistor to VRF and ac coupling into a 50 Ω load. For accurate power levels, see the Typical Performance Characteristics section. Add an external shunt inductor to provide higher power levels; however, this is less wideband than the internal bias only. Terminate the unused complementary output with a similar circuit to the used output. VRF 50Ω The VCO shows the variation of KV as the tuning voltage, VTUNE, varies within the band and from band to band. For wideband applications covering a wide frequency range (and changing output dividers), a value of 63 MHz/V provides the most accurate KV, because this value is closest to the average value. Figure 22 shows how KV varies with fundamental VCO frequency along with an average value for the frequency band. Users may prefer this figure when using narrow-band designs. RFOUTA+ 50Ω RFOUTA– BUFFER/ DIVIDE BY 1/2/4/8/ 16/32/64 13345-027 VCO VRF Figure 23. Output Stage Another feature of the ADF4355-3 is that the supply current to the output stages can shut down until the ADF4355-3 achieves lock as measured by the digital lock detect circuitry. The mute until lock detect (MTLD) bit (Bit DB11) in Register 6 enables this function. The RFOUTB+/RFOUTB− pins are duplicate outputs that can be used independently or in addition to the RFOUTA+/RFOUTA− pins. LOOP FILTER Use only passive loop filters. For information on designing a loop filter, use the ADIsimPLL design tool. Rev. B | Page 14 of 34 Data Sheet ADF4355-3 Table 6. Total IDD (RFOUTA± Refers to RFOUTA+/RFOUTA−) Divide By IVCO and IP AIDD, DIDD, IRF 1 2 4 8 16 32 64 RFOUTA± Off 49.4 mA RFOUTA± = −4 dBm 49.4 mA RFOUTA± = −1 dBm 49.4 mA RFOUTA± = +2 dBm 49.4 mA RFOUTA± = +5 dBm 49.4 mA 91.8 mA 100.9 mA 110.8 mA 118.9 mA 124.0 mA 128.0 mA 130.4 mA 103.3 mA 113.6 mA 123.9 mA 132.1 mA 137.3 mA 141.4 mA 144.0 mA 106.5 mA 117.0 mA 127.5 mA 135.6 mA 140.8 mA 144.9 mA 147.4 mA 111.7 mA 122.8 mA 133.6 mA 141.8 mA 147.0 mA 151.1 mA 153.6 mA 116.9 mA 128.4 mA 139.8 mA 148.0 mA 153.3 mA 157.5 mA 160.0 mA Rev. B | Page 15 of 34 ADF4355-3 Data Sheet REGISTER MAPS RESERVED PRESCALER AUTOCAL REGISTER 0 CONTROL BITS 16-BIT INTEGER VALUE (INT) DB31 DB30 DB29 DB28 DB27 DB26 DB25 DB24 DB23 DB22 DB21 DB20 DB19 DB18 DB17 DB16 DB15 DB14 DB13 DB12 DB11 DB10 DB9 0 0 0 0 0 0 0 0 0 0 AC1 PR1 N15 N16 N14 N13 N12 N11 N10 N8 N9 N7 DB8 DB7 DB6 DB5 DB4 N5 N4 N3 N2 N1 N6 DB3 DB2 C4(0) C3(0) DB1 DB0 C2(0) C1(0) REGISTER 1 CONTROL BITS DBR 1 24-BIT MAIN FRACTIONAL VALUE (FRAC1) RESERVED DB31 DB30 DB29 DB28 DB27 DB26 DB25 DB24 DB23 DB22 DB21 DB20 DB19 DB18 DB17 DB16 DB15 DB14 DB13 DB12 DB11 DB10 DB9 DB8 0 0 0 F24 0 F23 F22 F21 F19 F20 F18 F17 F16 F15 F14 F13 F12 F11 F10 F9 F8 F7 F6 DB7 DB6 F5 F4 F3 DB2 DB1 DB0 DB5 DB4 DB3 F2 C4(0) C3(0) C2(0) C1(1) F1 REGISTER 2 14-BIT AUXILIARY FRACTIONAL VALUE (FRAC2) DBR 1 DB31 DB30 DB29 DB28 DB27 DB26 DB25 DB24 DB23 DB22 DB21 DB20 DB19 DB18 DB17 DB16 DB15 DB14 DB13 DB12 DB11 DB10 DB9 F14 F13 F11 F12 F10 F9 F8 F7 F6 F5 CONTROL BITS 14-BIT AUXILIARY MODULUS VALUE (MOD2) DBR 1 F4 F3 F2 M14 F1 M13 M12 M11 M10 M9 M8 M7 DB8 DB7 DB6 DB5 DB4 M5 M4 M3 M2 M1 M6 DB3 DB2 DB1 DB0 C4(0) C3(0) C2(1) C1(0) PHASE ADJUST PHASE RESYNC SD LOAD RESET RESERVED REGISTER 3 CONTROL BITS DBR 1 24-BIT PHASE VALUE (PHASE) P22 P21 P20 P19 P18 P17 P16 P15 P14 P13 P12 P11 P10 P9 P8 P7 DB5 DB4 DB3 P6 P5 P4 P3 P2 P1 C4(0) C3(0) C2(1) C1(1) COUNTER RESET P23 CP THREESTATE P24 POWER-DOWN PA1 PR1 PD POLARIT Y SD1 REF MODE 0 MUX LOGIC DB31 DB30 DB29 DB28 DB27 DB26 DB25 DB24 DB23 DB22 DB21 DB20 DB19 DB18 DB17 DB16 DB15 DB14 DB13 DB12 DB11 DB10 DB9 DB8 DB7 DB6 CONTROL BITS DB2 DB1 DB0 DBR 1 DOUBLE BUFF MUXOUT RDIV2 RESERVED REFERENCE DOUBLER DBR 1 REGISTER 4 DBR 1 10-BIT R COUNTER CURRENT SETTING DBR 1 DB31 DB30 DB29 DB28 DB27 DB26 DB25 DB24 DB23 DB22 DB21 DB20 DB19 DB18 DB17 DB16 DB15 DB14 DB13 DB12 DB11 DB10 DB9 DB8 0 0 M3 M2 M1 RD2 RD1 R10 R8 R9 R7 R6 R5 R4 R3 R2 CP4 D1 R1 CP3 CP2 CP1 U6 DB7 DB6 U5 U4 U3 DB5 DB4 DB3 U2 C4(0) C3(1) C2(0) C1(0) U1 DB2 DB1 DB0 REGISTER 5 CONTROL BITS DB31 DB30 DB29 DB28 DB27 DB26 0 0 0 0 0 DB25 DB24 DB23 DB22 DB21 DB20 DB19 DB18 DB17 DB16 DB15 DB14 DB13 DB12 DB11 DB10 0 0 0 1 0 0 0 0 0 0 0 0 0 0 0 0 DB9 DB8 DB7 DB6 DB5 DB4 0 0 0 0 1 0 RF OUTPUT ENABLE RESERVED RF OUTPUT POWER 0 DB3 DB2 DB1 DB0 C4(0) C3(1) C2(0) C1(1) AUX RF OUTPUT POWER CONTROL BITS DB31 DB30 DB29 DB28 DB27 DB26 DB25 DB24 DB23 DB22 DB21 DB20 DB19 DB18 DB17 DB16 DB15 DB14 DB13 DB12 DB11 DB10 DB9 DB8 DB7 DB6 DB5 DB4 DB3 0 1DBR 2DBB BL10 BL9 1 0 1 0 D13 D12 D11 D10 BL8 BL7 BL6 BL5 BL4 BL3 BL2 BL1 0 D8 = DOUBLE BUFFERED REGISTER—BUFFERED BY THE WRITE TO REGISTER 0. = DOUBLE BUFFERED BITS—BUFFERED BY A WRITE TO REGISTER 0 WHEN BIT DB14 OF REGISTER 4 IS HIGH. Figure 24. Register Summary (Register 0 to Register 6) Rev. B | Page 16 of 34 0 D6 D5 D4 D3 D2 D1 DB2 DB1 DB0 C4(0) C3(1) C2(1) C1(0) 13345-028 RESERVED CHARGE PUMP BLEED CURRENT AUX RF OUTPUT ENABLE RF DIVIDER SELECT2 MTLD RESERVED RESERVED FEEDBACK SELECT NEGATIVE BLEED GATED BLEED RESERVED REGISTER 6 Data Sheet ADF4355-3 LDO MODE LD CYCLE COUNT RESERVED FRAC-N LD PRECISION RESERVED LOL MODE LE SYNC REGISTER 7 DB31 DB30 DB29 DB28 DB27 DB26 DB25 DB24 DB23 DB22 DB21 DB20 DB19 DB18 DB17 DB16 DB15 DB14 DB13 DB12 DB11 DB10 DB9 DB8 DB7 DB6 DB5 DB4 0 0 0 1 0 0 LE 0 0 0 0 0 0 0 0 0 0 0 0 0 0 0 LD4 LD5 LOL LD3 CONTROL BITS DB3 DB2 DB1 DB0 LD2 LD1 C4(0) C3(1) C2(1) C1(1) REGISTER 8 CONTROL BITS RESERVED DB31 DB30 DB29 DB28 DB27 DB26 DB25 DB24 DB23 DB22 DB21 DB20 DB19 DB18 DB17 DB16 DB15 DB14 DB13 DB12 DB11 DB10 DB9 DB8 0 0 0 1 1 0 1 0 0 1 1 0 1 0 0 1 0 1 1 0 0 1 1 DB7 DB6 0 1 DB5 DB4 1 0 1 DB3 DB2 DB1 DB0 C4(1) C3(0) C2(0) C1(0) REGISTER 9 VCO BAND DIVISION SYNTHESIZER LOCK TIMEOUT RESERVED TIMEOUT DB31 DB30 DB29 DB28 DB27 DB26 DB25 DB24 DB23 DB22 DB21 DB20 DB19 DB18 DB17 DB16 DB15 DB14 DB13 DB12 DB11 DB10 DB9 DB8 VC8 VC7 VC6 VC5 VC4 VC3 VC2 VC1 TL10 TL9 TL8 TL7 TL6 TL5 TL4 TL3 TL2 TL1 1 1 1 1 1 SL5 CONTROL BITS DB7 DB6 DB5 DB4 SL4 SL2 SL3 DB3 DB2 DB1 DB0 SL1 C4(1) C3(0) C2(0) C1(1) ADC CLOCK DIVIDER RESERVED DB31 DB30 DB29 DB28 DB27 DB26 DB25 DB24 DB23 DB22 DB21 DB20 DB19 DB18 DB17 DB16 DB15 DB14 DB13 DB12 DB11 DB10 DB9 DB8 0 1 1 0 0 0 0 0 0 0 0 0 0 0 0 0 0 0 AD8 AD7 AD6 AD5 AD4 DB7 DB6 AD3 AD2 AD1 ADC ENABLE ADC CONVERSION REGISTER 10 DB5 DB4 CONTROL BITS DB3 DB2 DB1 DB0 AE2 AE1 C4(1) C3(0) C2(1) C1(0) REGISTER 11 CONTROL BITS RESERVED DB31 DB30 DB29 DB28 DB27 DB26 DB25 DB24 DB23 DB22 DB21 DB20 DB19 DB18 DB17 DB16 DB15 DB14 DB13 DB12 DB11 DB10 DB9 DB8 0 0 0 0 0 0 0 0 1 0 0 0 0 0 0 1 0 0 0 1 0 0 0 DB7 DB6 0 0 0 DB5 DB4 0 0 DB3 DB2 DB1 DB0 C4(1) C3(0) C2(1) C1(1) REGISTER 12 P15 P14 P13 P12 P11 P10 P9 P8 P7 P6 P5 P4 P3 P2 P1 0 0 0 0 0 1 Figure 25. Register Summary (Register 7 to Register 12) Rev. B | Page 17 of 34 DB9 DB8 DB7 DB6 DB5 DB4 0 1 0 0 0 0 DB3 DB2 DB1 DB0 C4(1) C3(1) C2(0) C1(0) 13345-029 DB31 DB30 DB29 DB28 DB27 DB26 DB25 DB24 DB23 DB22 DB21 DB20 DB19 DB18 DB17 DB16 DB15 DB14 DB13 DB12 DB11 DB10 P16 CONTROL BITS RESERVED RESYNC CLOCK DB31 DB30 DB29 DB28 DB27 DB26 DB25 DB24 DB23 DB22 DB21 DB20 DB19 DB18 DB17 DB16 DB15 DB14 DB13 DB12 DB11 DB10 DB9 0 0 0 0 0 0 0 0 0 0 AC1 PR1 CONTROL BITS 16-BIT INTEGER VALUE (INT) N16 N15 N14 N13 N12 N11 N10 N9 N8 N7 N6 DB8 DB7 DB6 DB5 DB4 N5 N4 N3 N2 N1 PR1 PRESCALER N16 N15 ... N5 N4 N3 N2 N1 0 4/5 0 0 ... 0 0 0 0 0 NOT ALLOWED 1 8/9 0 0 ... 0 0 0 0 1 NOT ALLOWED 0 0 ... 0 0 0 1 0 NOT ALLOWED . . ... . . . . . ... 0 0 ... 1 0 1 1 0 NOT ALLOWED DB2 DB1 DB0 INTEGER VALUE (INT) 0 0 ... 1 0 1 1 1 23 VCO AUTOCAL 0 0 ... 1 1 0 0 0 24 . . ... . . . . . ... 0 DISABLED 1 1 ... 1 1 1 0 1 65533 1 ENABLED 1 1 ... 1 1 1 1 0 65534 1 1 ... 1 1 1 1 1 65535 AC1 DB3 C4(0) C3(0) C2(0) C1(0) INTMIN = 75 WITH PRESCALER = 8/9 13345-030 RESERVED PRESCALER Data Sheet AUTOCAL ADF4355-3 Figure 26. Register 0 REGISTER 0 Prescaler Value Control Bits The dual modulus prescaler (P/P + 1), along with the INT, FRACx, and MODx counters, determines the overall division ratio from the VCO output to the PFD input. The PR1 bit (Bit DB20) in Register 0 sets the prescaler value. With Bits[C4:C1] set to 0000, Register 0 is programmed. Figure 26 shows the input data format for programming this register. Reserved Operating at CML levels, the prescaler takes the clock from the VCO output and divides it down for the counters. It is based on a synchronous 4/5 core. The prescaler limits the INT value; therefore, if P is 4/5, INTMIN is 23, and if P is 8/9, INTMIN is 75. Bits[DB31:DB22] are reserved and must be set to 0. Automatic Calibration (Autocal) Write to Register 0 to enact (by default) the VCO automatic calibration, and to choose the appropriate VCO and VCO subband. Write 1 to the AC1 bit (Bit DB21) to enable the automatic calibration, which is the recommended mode of operation. 16-Bit Integer Value Set the AC1 bit to 0 to disable the automatic calibration, which leaves the ADF4355-3 in the same band it is already in when Register 0 is updated. The 16 INT bits (Bits[DB19:DB4]) set the INT value, which determines the integer part of the feedback division factor. The INT value is used in Equation 3 (see the RF Synthesizer—A Worked Example section). All integer values from 23 to 32,767 are allowed for the 4/5 prescaler. For the 8/9 prescaler, the minimum integer value is 75, and the maximum value is 65,535. Disable the automatic calibration only for fixed frequency applications, phase adjust applications, or very small ( 100 MHz, disable bleed current using DB29. where: Floor() is a function to round down to the nearest integer value. Bleed Value is the value programmed to Bits[DB20:DB13]. fPFD is the PFD frequency. ICP is the value of charge pump current setting, Bits[DB13:DB10] of Register 4. Auxiliary RF Output Enable Bit DB9 enables or disables the auxiliary frequency RF output (RFOUTB+/RFOUTB−). When DB9 is set to 1, the auxiliary frequency RF output is enabled. When DB9 is set to 0, the auxiliary RF output is disabled. Auxiliary RF Output Power Bits[DB8:DB7] set the value of the auxiliary RF output power level. RF Output Enable Bit DB6 enables or disables the primary RF output (RFOUTA+/ RFOUTA−). When DB6 is set to 0, the primary RF output is disabled; when DB6 is set to 1, the primary RF output is enabled. Output Power Bits[DB5:DB4] set the value of the primary RF output power level. Reserved Bit DB12 is reserved and must be set to 0. Mute Till Lock Detect When D8 (Bit DB11) is set to 1, the supply current to the RF output stage is shut down until the device achieves lock, as determined by the digital lock detect circuitry. Rev. B | Page 25 of 34 LD MODE LD CYCLE COUNT RESERVED LOL MODE DB31 DB30 DB29 DB28 DB27 DB26 DB25 DB24 DB23 DB22 DB21 DB20 DB19 DB18 DB17 DB16 DB15 DB14 DB13 DB12 DB11 DB10 DB9 DB8 DB7 DB6 DB5 DB4 0 0 0 1 0 0 LE 0 0 0 0 0 0 0 0 0 0 0 0 0 0 0 LD5 LD4 LE SYNCHRONIZ ATION DB3 DB2 DB1 DB0 LD2 LD1 C4(0) C3(1) C2(1) C1(1) LOL LD3 LD1 LE CONTROL BITS LOCK DETECT MODE 0 FRACTIONAL-N 1 INTEGER-N (2.9ns) LD3 LD2 FRACTIONAL-N LD PRECISION 0 0 5.0ns 0 1 6.0ns 1 0 8.0ns 1 1 12.0ns LOL LOSS OF LOCK MODE 0 DISABLED 0 DISABLED 1 LE SYNCED TO REFIN 1 ENABLED LD5 LD4 LOCK DETECT CYCLE COUNT 0 0 1024 0 1 2048 1 0 4096 1 1 8192 13345-037 RESERVED FRAC-N LD PRECISION Data Sheet LE SYNC ADF4355-3 Figure 33. Register 7 REGISTER 7 Loss of Lock (LOL) Mode Control Bits Bits[DB31:DB29] and Bits[DB27:DB26] are reserved and must be set to 0. Bit DB28 is reserved and must be set to 1. Set LOL (Bit DB7) to 1 when the application is a fixed frequency application in which the reference (REFIN) is likely to be removed, such as a clocking application. The standard lock detect circuit assumes that REFIN is always present; however, this may not be the case with clocking applications. To enable this functionality, set Bit DB7 to 1. Loss of lock mode does not function reliably when using differential REFIN mode. LE Sync Fractional-N Lock Detect Precision (LDP) When set to 1, Bit DB25 ensures that the load enable (LE) edge is synchronized internally with the rising edge of the reference input frequency. This synchronization prevents the rare event of reference and RF dividers loading at the same time as a falling edge of reference frequency, which can lead to longer lock times. LD3 and LD2 (Bits[DB6:DB5]) set the precision of the lock detect circuitry in fractional-N mode. LDP is available at 5.0 ns, 6.0 ns, 8.0 ns, or 12.0 ns. If bleed currents are used, use 12.0 ns. With Bits[C4:C1] set to 0111, Register 7 is programmed. Figure 33 shows the input data format for programming this register. Reserved Reserved Bits[DB24:DB10] are reserved and must be set to 0. Fractional-N Lock Detect Count (LDC) LD5 and LD4 (Bits[DB9:DB8]) set the number of consecutive cycles counted by the lock detect circuitry before asserting lock detect high. See Figure 33 for details. Lock Detect Mode (LDM) If LD1 (Bit DB4) is set to 0, each reference cycle is set by the fractional-N lock detect precision as described in the Fractional-N Lock Detect Count (LDC) section. If DB4 is set to 1, each reference cycle is 2.9 ns long, which is more appropriate for integer-N applications. Rev. B | Page 26 of 34 Data Sheet ADF4355-3 DB31 DB30 DB29 DB28 DB27 DB26 DB25 DB24 DB23 DB22 DB21 DB20 DB19 DB18 DB17 DB16 DB15 DB14 DB13 DB12 DB11 DB10 DB9 DB8 0 0 1 0 1 0 1 0 0 1 1 0 1 0 0 1 0 1 1 0 0 1 1 0 DB7 DB6 1 DB5 DB4 1 0 1 DB3 DB2 DB1 DB0 C4(1) C3(0) C2(0) C1(0) 13345-038 CONTROL BITS RESERVED Figure 34. Register 8 (0x1A69A6B8) TIMEOUT VCO BAND DIVISION SYNTHESIZER LOCK TIMEOUT RESERVED DB31 DB30 DB29 DB28 DB27 DB26 DB25 DB24 DB23 DB22 DB21 DB20 DB19 DB18 DB17 DB16 DB15 DB14 DB13 DB12 DB11 DB10 DB9 DB8 VC8 VC7 VC5 VC6 VC4 VC3 VC2 VC1 TL10 TL9 TL8 TL7 TL6 TL5 TL4 TL3 TL2 TL1 1 1 1 1 .......... TL2 TL1 0 0 .......... 0 1 1 0 0 .......... 1 0 2 . . .......... . . . . . .......... . . . . . .......... . . . 1 1 .......... 0 0 1020 1 1 .......... 0 1 1021 1 1 .......... 1 0 1022 1 1 .......... 1 1 1023 .......... VC2 VC1 0 .......... 0 1 1 0 0 .......... 1 0 2 . . .......... . . . . . .......... . . . . . .......... . . . 1 1 .......... 0 0 252 1 1 .......... 0 1 253 1 1 .......... 1 0 254 1 1 .......... 1 1 255 DB7 DB6 DB5 DB4 SL4 SL3 SL2 DB3 DB2 DB1 DB0 SL1 C4(1) C3(0) C2(0) C1(1) SL4 .......... SL2 SL1 0 .......... 0 1 SLC WAIT 1 0 0 .......... 1 0 2 . . .......... . . . . . .......... . . . . . .......... . . . 1 1 .......... 0 0 28 1 1 .......... 0 1 29 1 1 .......... 1 0 30 1 1 .......... 1 1 31 VCO BAND DIV 13345-039 VC7 0 VC8 TIMEOUT SL5 0 SL5 TL9 TL10 1 CONTROL BITS Figure 35. Register 9 REGISTER 8 VCO Band Division The bits in this register are reserved and must be programmed as shown in Figure 34, using a hexadecimal word of 0x1A69A6B8. VC8 to VC1 (Bits[DB31:DB24]) set the value of the VCO band division clock. Determine the value of this clock by VCO Band Div = ceiling(fPFD/2,400,000) REGISTER 9 Timeout For a worked example and more information, see the Lock Time section. TL10 to TL1 (Bits[DB23:DB14]) set the timeout value for the VCO band selection. Control Bits With Bits[C4:C1] set to 1001, Register 9 is programmed. Figure 35 shows the input data format for programming this register. Reserved Bits Bits[DB13:DB9]) are reserved and must be set to 0b11111. Synthesizer Lock Timeout SL5 to SL1 (Bits[DB8:DB4]) set the synthesizer lock timeout value. This value allows the VTUNE force to settle on the VTUNE pin. The value must be 20 μs. Calculate the value using Equation 10: Synthesizer Lock Timeout > (20 μs × fPFD)/Timeout Rev. B | Page 27 of 34 (10) Data Sheet ADC CLOCK DIVIDER DB31 DB30 DB29 DB28 DB27 DB26 DB25 DB24 DB23 DB22 DB21 DB20 DB19 DB18 DB17 DB16 DB15 DB14 DB13 DB12 DB11 DB10 DB9 DB8 0 1 1 0 0 0 0 0 0 0 0 0 0 0 0 0 0 AD8 0 AD8 AD7 AD6 AD5 AD4 DB7 DB6 AD3 AD2 AD7 .......... AD2 0 0 .......... 0 1 1 0 0 .......... 1 0 2 . . .......... . . . . . .......... . . . . . .......... . . . 1 1 .......... 0 0 252 1 1 .......... 0 1 253 1 1 .......... 1 0 254 1 1 .......... 1 1 255 DB5 DB4 AD1 CONTROL BITS DB3 DB2 DB1 DB0 AE2 AE1 C4(1) C3(0) C2(1) C1(0) AE1 ADC 0 DISABLED 1 ENABLED AE2 ADC CONVERSION 0 DISABLED 1 ENABLED AD1 ADC CLK DIV 13345-040 RESERVED ADC ENABLE ADC CONVERSION ADF4355-3 Figure 36. Register 10 DB31 DB30 DB29 DB28 DB27 DB26 DB25 DB24 DB23 DB22 DB21 DB20 DB19 DB18 DB17 DB16 DB15 DB14 DB13 DB12 DB11 DB10 DB9 DB8 0 0 0 0 0 0 0 0 1 0 0 0 0 0 0 1 0 0 1 0 0 0 0 0 DB7 DB6 DB5 DB4 0 0 0 0 DB3 DB2 DB1 DB0 C4(1) C3(0) C2(1) C1(1) 13345-041 CONTROL BITS RESERVED Figure 37. Register 11 (0x0081200B) Choose the ADC_CLK_DIV value such that REGISTER 10 Control Bits ADC_CLK_DIV = ceiling(((fPFD/100,000) − 2)/4) With Bits[C4:C1] set to 1010, Register 10 is programmed. Figure 36 shows the input data format for programming this register. (11) where ceiling() is a function to round up to the nearest integer. For example, for fPFD = 61.44 MHz, set ADC_CLK_DIV = 154 so that the ADC clock frequency is 99.417 kHz. If ADC_CLK_DIV is greater than 255, set it to 255. Reserved Bits[DB31:DB14] are reserved. Bits[DB23:DB22] must be set to 11, and all other bits in this range must be set to 0. ADC Conversion Clock (ADC_CLK_DIV) An on-board analog-to-digital converter (ADC) is connected to a temperature sensor. It determines the VTUNE setpoint relative to the ambient temperature of the ADF4355-3 environment. The ADC ensures that the initial tuning voltage in any application is chosen correctly to avoid any temperature drift issues. The ADC uses a clock that is equal to the output of the R counter (or the PFD frequency) divided by ADC_CLK_DIV. AD8 to AD1 (Bits[DB13:DB6]) set the value of this divider. On power-up, the R counter is not programmed; however, in these power-up cases, it defaults to R = 1. ADC Conversion Enable AE2 (Bit DB5) ensures that the ADC performs a conversion when a write to Register 10 is performed. It is recommended to enable this mode. ADC Enable AE1 (Bit DB4), when set to 1, powers up the ADC for the temperature dependent VTUNE calibration. It is recommended to always use this function. REGISTER 11 The bits in this register are reserved and must be programmed as described in Figure 37, using a hexadecimal word of 0x0081200B. Rev. B | Page 28 of 34 Data Sheet ADF4355-3 DB31 DB30 DB29 DB28 DB27 DB26 DB25 DB24 DB23 DB22 DB21 DB20 DB19 DB18 DB17 DB16 DB15 DB14 DB13 DB12 DB11 DB10 P15 P14 P13 P12 P11 P10 P9 P8 P7 P6 P5 P4 P3 P2 P16 P15 ... P5 P4 P3 P2 P1 RESYNC CLOCK 0 0 ... 0 0 0 0 0 NOT ALLOWED 0 0 ... 0 0 0 0 1 1 0 0 ... 0 0 0 1 0 2 . . ... . . . . . ... 0 0 ... 1 0 1 1 0 22 0 0 ... 1 0 1 1 1 23 0 0 ... 1 1 0 0 0 24 . . ... . . . . . ... 1 1 ... 1 1 1 0 1 65533 1 1 ... 1 1 1 1 0 65534 1 1 ... 1 1 1 1 1 65535 P1 0 0 0 0 0 1 DB9 DB8 DB7 DB6 DB5 DB4 0 1 0 0 0 0 DB3 DB2 DB1 DB0 C4(1) C3(1) C2(0) C1(0) 13345-042 P16 CONTROL BITS RESERVED RESYNC CLOCK Figure 38. Register 12 REGISTER 12 14. Register 0. Control Bits For fPFD > 75 MHz (initially lock with halved fPFD), use the following sequence: With Bits[C4:C1] set to 1100, Register 12 is programmed. Figure 38 shows the input data format for programming this register. Phase Resync Clock Divider Value P16 to P1 (Bits[DB31:DB16]) set the timeout counter for activation of phase resync. This value must be set such that a the resync happens immediately after (and not before) the PLL achieves lock after reprogramming. Calculate the timeout value using the following equation: Timeout Value = Phase Resync Clock/fPFD (12) Reserved Bits[DB15:DB4] are reserved. Bit DB10 and Bit DB8 must be set to 1, but all other bits in this range must be set to 0. REGISTER INITIALIZATION SEQUENCE At initial power-up, after the correct application of voltages to the supply pins, the ADF4355-3 registers must be programmed in sequence. For f ≤ 75 MHz, use the following sequence: 1. 2. 3. 4. 5. 6. 7. 8. 9. 10. 11. 12. 13. Register 12. Register 11. Register 10. Register 9. Register 8. Register 7. Register 6. Register 5. Register 4. Register 3. Register 2. Register 1. Wait >16 ADC_CLK cycles. For example, if ADC_CLK = 99.417 kHz, wait 16/99,417 sec = 161 μs. See the Register 10 section for more information. 1. 2. 3. 4. 5. 6. 7. 8. 9. 10. 11. 12. 13. 14. 15. 16. 17. 18. 19. Rev. B | Page 29 of 34 Register 12. Register 11. Register 10. Register 4 (with the R divider doubled to halve fPFD). Register 9. Register 8. Register 7. Register 6. Register 5. Register 4 (with the R divider doubled to halve fPFD). Register 3. Register 2 (for halved fPFD). Register 1 (for halved fPFD). Wait >16 ADC_CLK cycles. For example, if ADC_CLK = 99.417 kHz, wait 16/99,417 sec = 161 μs. See the Register 10 section for more information. Register 0 (for halved fPFD; autocalibration enabled). Register 4 (with the R divider set for desired fPFD). Register 2 (for desired fPFD). Register 1 (for desired fPFD). Register 0 (for desired fPFD; autocalibration disabled). ADF4355-3 Data Sheet Frequency updates require updating the auxiliary modulator (MOD2) in Register 2, the fractional value (FRAC1) in Register 1, and the integer value (INT) in Register 0. It is recommended to perform a temperature dependent VTUNE calibration by updating Register 10 first. Therefore, for fPFD ≤ 75 MHz, the sequence must be as follows: 1. 2. 3. 4. 5. Register 10. Register 2. Register 1. Wait >16 ADC_CLK cycles. For example, if ADC_CLK = 99.417 kHz, wait 16/99,417 sec = 161 μs. See the Register 10 section for more information. Register 0. For example, in a universal mobile telecommunication system (UMTS) where 2112.8 MHz RF frequency output (RFOUT) is required, a 122.88 MHz reference frequency input (REFIN) is available. Note that the ADF4355-3 VCO operates in the frequency range of 3.3 GHz to 6.6 GHz. Therefore, RF divider of 2 must be used (VCO frequency = 4225.6 MHz, RFOUT = VCO frequency/RF divider = 4225.6 MHz/2 = 2112.8 MHz). The feedback path is also important. In this example, the VCO output is fed back before the output divider (see Figure 39). In this example, the 122.88 MHz reference signal is divided by 2 to generate an fPFD value of 61.44 MHz. The desired channel spacing is 200 kHz. fPFD PFD For fPFD > 75 MHz (initially lock with halved fPFD), the sequence must be as follows: 1. 2. 3. 4. 5. Register 10. Register 4 (RDivider doubled for halved fPFD). Register 2 (for halved fPFD). Register 1 (for halved fPFD). Wait >16 ADC_CLK cycles. For example, if ADC_CLK = 99.417 kHz, wait 16/99,417 sec = 161 μs. See the Register 10 section for more information. 6. Register 0 (for halved fPFD; autocalibration enabled). 7. Register 4 (RDivider set for desired fPFD). 8. Register 2 (for desired fPFD). 9. Register 1 (for desired fPFD). 10. Register 0 (for desired fPFD; autocalibration disabled). The worked example is as follows: • • • • • • • N = VCOOUT/fPFD = 4225.6 MHz/61.44 MHz = 68.7760416666666667 INT = int(VCO frequency/fPFD) = 68 FRAC = 0.7760416666666667 MOD1 = 16,777,216 FRAC1 = int(MOD1 × FRAC) = 13,019,817 Remainder = 0.6666666667 or 2/3 MOD2 = fPFD/GCD(fPFD/fCHSP) = 61.44 MHz/GCD(61.44 MHz/ 200 kHz) = 1536 FRAC2 = remainder × 1536 = 1024 RF SYNTHESIZER—A WORKED EXAMPLE From Equation 14, Use the following equations to program the ADF4355-3 synthesizer: where: RFOUT is the RF frequency output. INT is the integer division factor. FRAC1 is the fractionality. FRAC2 is the auxiliary fractionality. MOD2 is the auxiliary modulus. MOD1 is the fixed 24-bit modulus. RF Divider is the output divider that divides down the VCO frequency. fPFD = REFIN × ((1 + D)/(R × (1 + T))) where: REFIN is the reference frequency input. D is the RF REFIN doubler bit. R is the RF reference division factor. T is the reference divide by 2 bit (0 or 1). RFOUT Figure 39. Loop Closed Before Output Divider • (13) ÷2 N DIVIDER The frequency change occurs only when writing to Register 0. FRAC2 FRAC1 + MOD2 × (fPFD)/RF Divider RFOUT = INT + MOD1 VCO 13345-043 FREQUENCY UPDATE SEQUENCE fPFD = (122.88 MHz × (1 + 0)/2) = 61.44 MHz (15) 2112.8 MHz = 61.44 MHz × ((INT + (FRAC1 + FRAC2/MOD2)/224))/2 (16) where: INT = 68 FRAC1 = 13,019,817 FRAC2 = 1024 MOD2 = 1536 REFERENCE DOUBLER AND REFERENCE DIVIDER (14) The on-chip reference doubler allows the input reference signal to be doubled. The doubler is useful for increasing the PFD comparison frequency. To improve the noise performance of the system, increase the PFD frequency. Doubling the PFD frequency typically improves noise performance by 3 dB. The reference divide by 2 divides the reference signal by 2, resulting in a 50% duty cycle PFD frequency. Rev. B | Page 30 of 34 Data Sheet ADF4355-3 SPURIOUS OPTIMIZATION AND FAST LOCK LOCK TIME Narrow loop bandwidths can filter unwanted spurious signals, but these bandwidths usually have a long lock time. A wider loop bandwidth achieves faster lock times but may lead to increased spurious signals inside the loop bandwidth. The PLL lock time divides into a number of settings. All of these settings are modeled in the ADIsimPLL design tool. OPTIMIZING JITTER Synthesizer Lock Timeout For lowest jitter applications, use the highest possible PFD frequency to minimize the contribution of in-band noise from the PLL. Set the PLL filter bandwidth such that the in-band noise of the PLL intersects with the open-loop noise of the VCO, minimizing the contribution of both to the overall noise. The synthesizer lock timeout ensures that the VCO calibration DAC, which forces VTUNE, settles to a steady value for the band select circuitry. Use the ADIsimPLL design tool for this task. SPUR MECHANISMS This section describes the two different spur mechanisms that arise with a fractional-N synthesizer and how to minimize them in the ADF4355-3. Much faster lock times than those detailed in this data sheet are possible; contact Analog Devices, Inc., for more information. The timeout and synthesizer lock timeout variables programmed in Register 9 select the length of time the DAC is allowed to settle to the final voltage before the VCO calibration process continues to the next phase, which is VCO band selection. The PFD frequency is used as the clock for this logic, and the duration is set by (Timeout × Synthesizer Lock Timeout)/fPFD Integer Boundary Spurs The calculated time must be greater than or equal to 20 µs. One mechanism for fractional spur creation is the interactions between the RF VCO frequency and the reference frequency. When these frequencies are not integer related (the purpose of a fractional-N synthesizer), spur sidebands appear on the VCO output spectrum at an offset frequency that corresponds to the beat note or the difference in frequency between an integer multiple of the reference and the VCO frequency. These spurs are attenuated by the loop filter and are more noticeable on channels close to integer multiples of the reference where the difference frequency can be inside the loop bandwidth (thus the name, integer boundary spurs). VCO Band Selection Reference Spurs Reference spurs are generally not a problem in fractional-N synthesizers because the reference offset is far outside the loop bandwidth. However, any reference feedthrough mechanism that bypasses the loop may cause a problem. Feedthrough of low levels of on-chip reference switching noise, through the prescaler back to the VCO, can result in reference spur levels as high as −80 dBc. (17) Use the PFD frequency again as the clock for the band selection process. Calculate this value by fPFD/(VCO Band Selection × 16) < 150 kHz (18) The band selection takes 11 cycles of the previously calculated value. Calculate the duration by 11 × (VCO Band Selection × 16)/fPFD (19) PLL Low-Pass Filter Settling Time The time taken for the loop to settle is inversely proportional to the low-pass filter bandwidth. The settling time is also modeled in the ADIsimPLL design tool. The total lock time for changing frequencies is the sum of the three separate times (synthesizer lock, VCO band selection, and PLL settling time), all of which are modeled in the ADIsimPLL design tool. Rev. B | Page 31 of 34 ADF4355-3 Data Sheet APPLICATIONS INFORMATION The LO ports of the ADL5375 can be driven differentially from the complementary RFOUTA+/RFOUTA− outputs of the ADF4355-3. A differential drive gives better second-order distortion performance than a single-ended LO driver and eliminates the use of a balun to convert from a single-ended LO input to the more desirable differential LO input for the ADL5375. DIRECT CONVERSION MODULATOR Direct conversion architectures are used to implement base station transmitters. Figure 40 shows how to use Analog Devices devices to implement such a system. The circuit block diagram shows the AD9761 TxDAC® being used with the ADL5375. The use of a dual integrated DAC, such as the AD9761, ensures minimum error contribution (over temperature) from this portion of the signal chain. The ADL5375 accepts LO drive levels from −6 dBm to +6 dBm. The optimum LO power can be software programmed on the ADF4355-3, which allows levels from −4 dBm to +5 dBm from each output. The local oscillator (LO) is implemented using the ADF4355-3. The low-pass filter was designed using the ADIsimPLL design tool for a PFD of 61.44 MHz and a closed-loop bandwidth of 20 kHz. 51Ω REFIO MODULATED DIGITAL DATA 51Ω IOUTA LOW-PASS FILTER IOUTB AD9761 The RF output is designed to drive a 50 Ω load; however, it must be ac-coupled, as shown in Figure 40. If the I and Q inputs are driven in quadrature by 2 V p-p signals, the resulting output power from the ADL5375 modulator is approximately 2 dBm. TxDAC QOUTA LOW-PASS FILTER QOUTB FSADJ 51Ω 51Ω 2kΩ VVCO VDD FREFIN 17 25 26 10 5 4 6 27 16 VVCO VP AV DD DVDD AV DD CE PDBRF VRF CREG1 100nF LOCK DETECT 32 30 CREG2 MUXOUT RFOUTB+ 14 1nF 1nF FREFIN RFOUTB– 15 28 REFINB 7.5nH 7.5nH 1nF 2 DATA SPI-COMPATIBLE SERIAL BUS IBBN VOUT 1 CLK RFOUTA+ 11 ADF4355-3 3 LE LOIP LPF LOIN RFOUTA– 12 1nF 5.1kΩ QBBP 33nF 1500pF CPGND SDGND AGND A GNDRF A GNDVCO VREGVCO 31 9 13 18 21 10pF 19 VREF VBIAS 23 24 0.1µF 10pF RFOUT DSOP 3.3kΩ CPOUT 7 22 RSET QUADRATURE PHASE SPLITTER LPF VTUNE 20 8 ADL5375 IBBP 29 REF A IN 390pF QBBN 1kΩ 0.1µF 10pF 0.1µF Figure 40. Direct Conversion Modulator Rev. B | Page 32 of 34 13345-044 1nF 1nF 100nF Data Sheet ADF4355-3 POWER SUPPLIES Take care with the RF output traces to minimize discontinuities and ensure the best signal integrity. Via placement and grounding are critical. The ADF4355-3 contains four multiband VCOs that together cover an octave range of frequencies. To ensure best performance, it is vital to connect a low noise regulator, such as the ADM7150, to the VVCO pin. Connect the same regulator to VVCO, VREGVCO, VRF, and VP. OUTPUT MATCHING The low frequency output can simply be ac-coupled to the next circuit, if desired; however, if higher output power is required, use a pull-up inductor to increase the output power level. For the 3.3 V supply pins, use one or two ADM7150 regulators. Figure 42 shows the recommended connections. VRF PRINTED CIRCUIT BOARD (PCB) DESIGN GUIDELINES FOR A CHIP-SCALE PACKAGE 7.5nH Figure 41. Optimum Output Stage When differential outputs are not needed, terminate the unused output or combine it with both outputs using a balun. The bottom of the chip-scale package has a central exposed thermal pad. The thermal pad on the PCB must be at least as large as the exposed pad. On the PCB, there must be a minimum clearance of 0.25 mm between the thermal pad and the inner edges of the pad pattern. This clearance ensures the avoidance of shorting. For lower frequencies below 2 GHz, it is recommended to use a 100 nH inductor on the RFOUTA+/RFOUTA− pins. The RFOUTA+/RFOUTA− pins are a differential circuit. Provide each output with the same (or similar) components where possible, such as the same shunt inductor value, bypass capacitor, and termination. To improve the thermal performance of the package, use thermal vias on the PCB thermal pad. If vias are used, incorporate them into the thermal pad at the 1.2 mm pitch grid. The via diameter must be between 0.3 mm and 0.33 mm, and the via barrel must be plated with 1 oz. of copper to plug the via. The auxiliary frequency output, RFOUTB+/RFOUTB−, can be treated the same as the RFOUTA+/RFOUTA− output. If unused, leave both RFOUTB+/RFOUTB− pins open. For a microwave PLL and VCO synthesizer, such as the ADF4355-3, take care with the board stack-up and layout. Do not use FR4 material because it is too lossy above 3 GHz. Instead, Rogers 4350, Rogers 4003, or Rogers 3003 dielectric material is suitable. ON OFF EN VOUT ADM7150 COUT 1µF 100nF REF BYP CBYP 1µF VOUT = 3.3V VREG CREG 10µF 10 6 VVCO VP VRF 17 REF_SENSE GND FREF IN FREF IN 1nF 1nF LOCK DETECT 100nF 25 30 CREG1 MUXOUT 5 26 4 27 32 16 AV DD DVDD AVDD CE PDB RF CREG2 29 REF INA RFOUTB+ 14 1nF 1nF RFOUTB– 15 28 REF INB 7.5nH VIN CIN 1µF ON OFF CBYP 1µF EN VOUT ADM7150 REF BYP VREG CREG 10µF REF_SENSE GND VOUT = 3.3V COUT 1µF SPI-COMPATIBLE SERIAL BUS 1 CLK VIN = 6.0V VOUT 7.5nH 1nF 2 DATA RFOUTA+ 11 ADF4355-3 3 LE RFOUTA– 12 1nF VTUNE 20 1kΩ CPOUT 7 22 RSET 5.1kΩ 2700pF CPGND SDGND AGND AGNDRF AGNDVCO 8 31 9 13 18 VREGVCO 21 19 10pF Figure 42. Power Supplies Rev. B | Page 33 of 34 680pF 360kΩ VREF VBIAS 23 47nF 24 0.1µF 10pF 0.1µF 10pF 0.1µF 13345-045 VIN CIN 1µF 50Ω 13345-046 The lands on the 32-lead lead frame chip-scale package are rectangular. The PCB pad for these lands must be 0.1 mm longer than the package land length and 0.05 mm wider than the package land width. Center each land on the pad to maximize the solder joint size. VIN = 6.0V 100pF RFOUTA+ ADF4355-3 Data Sheet OUTLINE DIMENSIONS 0.30 0.25 0.18 32 25 1 24 0.50 BSC 3.75 3.60 SQ 3.55 EXPOSED PAD 17 TOP VIEW 0.80 0.75 0.70 TOP VIEW PKG-004570 SEATING PLANE 0.50 0.40 0.30 PIN 1 INDIC ATOR AREA OPTIONS (SEE DETAIL A) 8 16 9 BOTTOM VIEW 0.05 MAX 0.02 NOM COPLANARITY 0.08 0.20 REF 0.25 MIN FOR PROPER CONNECTION OF THE EXPOSED PAD, REFER TO THE PIN CONFIGURATION AND FUNCTION DESCRIPTIONS SECTION OF THIS DATA SHEET. COMPLIANT TO JEDEC STANDARDS MO-220-WHHD-5. 02-22-2017-B PIN 1 INDICATOR DETAIL A (JEDEC 95) 5.10 5.00 SQ 4.90 Figure 43. 32-Lead Lead Frame Chip Scale Package [LFCSP] 5 mm × 5 mm Body and 0.75 mm Package Height (CP-32-12) Dimensions shown in millimeters ORDERING GUIDE Model1 ADF4355-3BCPZ ADF4355-3BCPZ-RL7 EV-ADF4355-3SD1Z 1 Temperature Range −40°C to +105°C −40°C to +105°C Package Description 32-Lead Lead Frame Chip Scale Package [LFCSP] 32-Lead Lead Frame Chip Scale Package [LFCSP] Evaluation Board Z = RoHS Compliant Part. ©2015–2017 Analog Devices, Inc. All rights reserved. Trademarks and registered trademarks are the property of their respective owners. D13345-0-8/17(B) Rev. B | Page 34 of 34 Package Option CP-32-12 CP-32-12
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