TPA6136A2YFFR

TPA6136A2 www.ti.com ........................................................................................................................................................ SLOS621A – JULY 2009 – REVISED AUGUST 2009 25-mW DIRECTPATH™ STEREO HEADPHONE AMPLIFIER WITH POP SUPPRESSION FEATURES 1 • Patented DirectPath™ Technology Eliminates Need for DC-Blocking Capacitors – Outputs Biased at 0 V – Excellent Low Frequency Fidelity • Active Click and Pop Suppression • HI-Z Output Mode Allows Sharing Output Jack • 2.1 mA Typical Supply Current • Fully Differential Inputs Reduce System Noise – Also Configurable as Single-Ended Inputs • SGND Pin Eliminates Ground Loop Noise • Constant Maximum Output Power from 2.3 V to 5.5 V Supply – Simplifies Design to Prevent Acoustic Shock • MicrosoftTM Windows VistaTM Compliant • 100 dB Power Supply Noise Rejection • Wide Power Supply Range: 2.3 V to 5.5 V • Gain Settings: 0 dB and 6 dB • Short-Circuit and Thermal-Overload Protection • ±8 kV HBM ESD Protected Outputs • Small Package Available – 16-Ball, 1.6 x 1.6 mm, 0.4 mm Pitch WCSP 23 APPLICATIONS • • • • Smart Phones / Cellular Phones Portable Media / MP3 Players Notebook Computers Portable Gaming The TPA6136A2 (TPA6136) features fully differential inputs with an integrated low pass filter to reduce system noise pickup between the audio source and the headphone amplifier and to reduce DAC out-of-band noise. The high power supply noise rejection performance and differential architecture provides increased RF noise immunity. For single-ended input signals, connect INL+ and INR+ to ground. The device has built-in pop suppression circuitry to completely eliminate disturbing pop noise during turn-on and turn-off. The amplifier outputs have short-circuit and thermal-overload protection along with ±8 kV HBM ESD protection, simplifying end equipment compliance to the IEC 61000-4-2 ESD standard. The TPA6136A2 (TPA6136) operates from a single 2.3 V to 5.5 V supply with 2.1 mA of typical supply current. Shutdown mode reduces supply current to less than 1 µA. OUTR+ INR+ OUTR- INR- OUTL+ INL+ OUTL- INL- CODEC OUTR TPA6136A2 OUTL SGND ENABLE GAIN EN GAIN HI-Z MODE VBAT HI-Z VDD GND HPVSS HPVDD CPP CPN DESCRIPTION The TPA6136A2 (sometimes referred to as TPA6136) is a DirectPath™ stereo headphone amplifier that eliminates the need for external dc-blocking output capacitors. Differential stereo inputs and built-in resistors set the device gain, further reducing external component count. Gain is selectable at 0 dB or 6 dB. The amplifier drives 25 mW into 16 Ω speakers from a single 2.3 V supply. The TPA6136A2 (TPA6136) provides a constant maximum output power independent of the supply voltage, thus facilitating the design for prevention of acoustic shock. 1 2 3 Please be aware that an important notice concerning availability, standard warranty, and use in critical applications of Texas Instruments semiconductor products and disclaimers thereto appears at the end of this data sheet. DirectPath is a trademark of Texas Instruments. Windows Vista is a trademark of Microsoft Corporation. PRODUCTION DATA information is current as of publication date. Products conform to specifications per the terms of the Texas Instruments standard warranty. Production processing does not necessarily include testing of all parameters. Copyright © 2009, Texas Instruments Incorporated TPA6136A2 SLOS621A – JULY 2009 – REVISED AUGUST 2009 ........................................................................................................................................................ www.ti.com These devices have limited built-in ESD protection. The leads should be shorted together or the device placed in conductive foam during storage or handling to prevent electrostatic damage to the MOS gates. FUNCTIONAL BLOCK DIAGRAM VDD HPVDD Supply Control 2.2 mF GND HPVDD – INL+ Resistor Array OUTL + INL- Short-Circuit Protection HPVSS Thermal Protection HPVDD Resistor Array OUTR + INR+ – INR- HPVDD HPVSS CPP GAIN Click-and-Pop Suppression Control HI-Z Charge Pump 1 mF CPN HPVSS 2.2 mF SGND EN 2 Copyright © 2009, Texas Instruments Incorporated Product Folder Link(s) :TPA6136A2 TPA6136A2 www.ti.com ........................................................................................................................................................ SLOS621A – JULY 2009 – REVISED AUGUST 2009 DEVICE PINOUT WCSP PACKAGE (TOP VIEW) A1 A2 A3 A4 EN VDD OUTL INL- B1 B2 B3 B4 GND CPP HPVDD INL+ C1 C2 C3 C4 CPN HPVSS SGND INR+ D1 D2 D3 D4 HI-Z GAIN OUTR INR- PIN FUNCTIONS PIN NAME WCSP I/O/P PIN DESCRIPTION INL- A4 I Inverting left input for differential signals; left input for single-ended signals INL+ B4 I Non-inverting left input for differential signals. Connect to ground for single-ended input applications INR+ C4 I Non-inverting right input for differential signals. Connect to ground for single-ended input applications INR- D4 I Inverting right input for differential signals; right input for single-ended signals OUTR D3 O Right headphone amplifier output. Connect to right terminal of headphone jack HI-Z D1 I Output impedance select. Set to logic LOW for normal operation and to logic HIGH for high output impedance GAIN D2 I Gain select. Set to logic LOW for a gain of 0dB and to logic HIGH for a gain of 6dB HPVSS C2 P Charge pump output and negative power supply for output amplifiers; connect 1µF capacitor to GND CPN C1 P Charge pump negative flying cap. Connect to negative side of 1µF capacitor between CPP and CPN GND B1 P Ground CPP B2 P Charge pump positive flying cap. Connect to positive side of 1µF capacitor between CPP and CPN HPVDD B3 P Positive power supply for headphone amplifiers. Connect to a 2.2µF capacitor. Do not connect to VDD EN A1 I Amplifier enable. Connect to logic low to shutdown; connect to logic high to activate VDD A2 P Positive power supply for TPA6136A2 SGND C3 I Amplifier reference voltage. Connect to ground terminal of headphone jack OUTL A3 O Left headphone amplifier output. Connect to left terminal of headphone jack 3 Copyright © 2009, Texas Instruments Incorporated Product Folder Link(s) :TPA6136A2 TPA6136A2 SLOS621A – JULY 2009 – REVISED AUGUST 2009 ........................................................................................................................................................ www.ti.com BOARD LAYOUT CONCEPT Battery Supply Enable Control A1 A2 A3 A4 EN VDD OUTL INL- B1 B2 B3 B4 GND CPP HPVDD INL+ C1 C2 C3 C4 CPN HPVSS SGND INR+ D1 D2 D3 D4 Hi-Z GAIN OUTR INR- Audio Inputs – Matched board layout for differential input signals High-Z Gain Headphone Connector ABSOLUTE MAXIMUM RATINGS over operating free-air temperature range, TA = 25°C (unless otherwise noted) VALUE / UNIT VI Supply voltage, VDD –0.3 V to 6.0 V Headphone amplifier supply voltage, HPVDD (do not connect to external supply) –0.3 V to 1.9 V Input voltage (INR+, INR–, INL+, INL–) 1.4 VRMS Output continuous total power dissipation See Dissipation Rating Table TA Operating free-air temperature range –40°C to 85°C TJ Operating junction temperature range –40°C to 150°C Tstg Storage temperature range –65°C to 150°C ESD Protection – HBM OUTL, OUTR 8 kV All Other Pins 2 kV ORDERING GUIDE (1) (2) TA PACKAGED DEVICES (1) –40°C to 85°C 16–ball, 1.6 mm × 1.6 mm WCSP PART NUMBER (2) TPA6136A2YFFR TPA6136A2YFFT SYMBOL AOWI For the most current package and ordering information, see the Package Option Addendum at the end of this document, or see the TI Web site at www.ti.com. The YFF package is only available taped and reeled. The suffix “R” indicates a reel of 3000; the suffix “T” indicates a reel of 250. 4 Copyright © 2009, Texas Instruments Incorporated Product Folder Link(s) :TPA6136A2 TPA6136A2 www.ti.com ........................................................................................................................................................ SLOS621A – JULY 2009 – REVISED AUGUST 2009 DISSIPATION RATINGS TABLE TA ≤ 25°C POWER RATING YFF (WCSP) 1250 mW (1) PACKAGE DERATING FACTOR (1) 10 mW/°C TA = 70°C POWER RATING TA = 85°C POWER RATING 800 mW 650 mW See JEDEC Standard 51-3 for Low-K board, JEDEC Standard 51-7 for High-K board, and JEDEC Standard 51-12 for using package thermal information. See JEDEC document page for downloadable copies: http://www.jedec.org/download/default.cfm. RECOMMENDED OPERATING CONDITIONS MIN MAX Supply voltage, VDD 2.3 5.5 VIH High-level input voltage; EN, GAIN, HI-Z 1.3 VIL Low-level input voltage; EN, GAIN, HI-Z TA UNIT V V 0.6 V V Voltage applied to Output; OUTR, OUTL (when EN = 0 V) –0.3 3.6 Voltage applied to Output; OUTR, OUTL (when EN ≥ 1.3 V and HI–Z ≥ 1.3 V) –1.8 1.8 V Operating free-air temperature –40 85 °C TYP MAX ELECTRICAL CHARACTERISTICS TA = 25°C (unless otherwise noted) PARAMETER TEST CONDITIONS Output offset voltage Power supply rejection ratio MIN –0.5 VDD = 2.3 V to 5.5 V 0.5 100 UNIT mV dB High-level output current (EN, GAIN, HI-Z) 1 µA Low-level output current (EN, GAIN, HI-Z) 1 µA Supply Current Shutdown Supply Current VDD = 2.3 V, No load, EN = VDD 2.1 2.8 VDD = 3.6 V, No load, EN = VDD 2.1 2.8 VDD = 5.5 V, No load, EN = VDD 2.2 2.9 VDD = 2.3 V to 5.5 V, No load, EN = HI-Z = V, 0.7 1.2 EN = 0 V, VDD = 2.3 V to 5.5 V 0.7 1.2 mA µA 5 Copyright © 2009, Texas Instruments Incorporated Product Folder Link(s) :TPA6136A2 TPA6136A2 SLOS621A – JULY 2009 – REVISED AUGUST 2009 ........................................................................................................................................................ www.ti.com OPERATING CHARACTERISTICS VDD = 3.6 V , TA = 25°C, RL = 16 Ω (unless otherwise noted) PARAMETER PO Output power (1) (Outputs in phase) VO Output voltage(1) (Outputs in phase) AV Closed-loop voltage gain (OUT / IN–) ΔAv Gain matching Input impedance (per input pin) RIN Input impedance in shutdown (per input pin) VCM TEST CONDITIONS MIN 25 THD = 1%, f = 1 kHz, RL = 32 Ω 22 THD = 1%, VDD = 3.6 V, f = 1 kHz, RL = 100 Ω 1.1 VRMS –1.0 –1.05 GAIN ≥ 1.3 V (6 dB) –1.95 –2.0 –2.05 Between Left and Right channels UNIT mW –0.95 V/V 1% GAIN = 0 V (0 dB) 19.8 GAIN ≥ 1.3 V (6 dB) 13.2 EN = 0 V kΩ 10 –0.5 EN = HI-Z ≥ 1.3 V, f = 10 kHz 1.5 V 40 EN = HI-Z ≥ 1.3 V, f = 1 MHz 4.5 EN = HI-Z ≥ 1.3 V, f = 10 MHz 0.75 EN = 0 V (shutdown mode) Input-to-output attenuation in shutdown MAX GAIN = 0 V, (0 dB) Input common-mode voltage range Output Impedance TYP THD = 1%, f = 1 kHz EN = 0 V 200 mVpp ripple, f = 217 Hz –80 kΩ 25 Ω 80 dB -100 AC PSRR AC-power supply rejection ratio THD+N Total harmonic distortion plus noise (2) SNR Signal-to-noise ratio PO = 20 mW; GAIN = 0 V, (AV = 0 dB) 100 dB En Noise output voltage A-weighted 5.5 µVRMS fosc Charge pump switching frequency tON Start-up time from shutdown Crosstalk Thermal shutdown (1) (2) 200 mVpp ripple, f = 10 kHz dB -90 PO = 20 mW, f = 1 kHz 0.02% PO = 25 mW into 32 Ω, VDD = 5.5 V, f = 1 kHz 0.01% 1200 1275 1350 kHz 5 ms PO = 20 mW, f = 1 kHz –80 dB Threshold 150 °C Hysteresis 20 °C Per output channel A-weighted 6 Copyright © 2009, Texas Instruments Incorporated Product Folder Link(s) :TPA6136A2 TPA6136A2 www.ti.com ........................................................................................................................................................ SLOS621A – JULY 2009 – REVISED AUGUST 2009 TYPICAL CHARACTERISTICS TA = 25°C, VDD = 3.6 V, Gain = 0 dB, EN = 3.6 V, CHPVDD = CHPVSS = 2.2 µF, CINPUT = CFLYING = 1 µF, Outputs in Phase TOTAL HARMONIC DISTORTION + NOISE vs OUTPUT POWER TOTAL HARMONIC DISTORTION + NOISE vs OUTPUT POWER 10 THD+N - Total Harmonic Distortion + Noise - % THD+N - Total Harmonic Distortion + Noise - % 10 RL = 16 W, f = 1kHz VDD = 2.5 V, In Phase VDD = 3.6 V, In Phase 1 VDD = 2.5 V, Out of Phase VDD = 3.6 V, Out of Phase 0.1 0.01 0.1 1 10 PO - Output Power per Channel - mW VDD = 3.6 V, In Phase 1 VDD = 2.5 V, Out of Phase VDD = 3.6 V, Out of Phase 0.1 1 10 PO - Output Power per Channel - mW 50 Figure 1. Figure 2. TOTAL HARMONIC DISTORTION + NOISE vs FREQUENCY TOTAL HARMONIC DISTORTION + NOISE vs FREQUENCY 1 THD+N - Total Harmonic Distortion + Noise - % THD+N - Total Harmonic Distortion + Noise - % VDD = 2.5 V, In Phase 0.01 0.1 50 1 RL = 16 W, VDD = 2.5 V PO = 1 mW per Channel 0.1 0.01 PO = 4 mW per Channel PO = 10 mW per Channel 0.001 20 100 1k f - Frequency - Hz 10k RL = 16 W, VDD = 3.6 V PO = 1 mW per Channel 0.1 PO = 20 mW per Channel 0.01 PO = 10 mW per Channel 0.001 20 20k 100 1k f - Frequency - Hz 10k 20k Figure 3. Figure 4. TOTAL HARMONIC DISTORTION + NOISE vs FREQUENCY TOTAL HARMONIC DISTORTION + NOISE vs FREQUENCY 1 1 THD+N - Total Harmonic Distortion + Noise - % THD+N - Total Harmonic Distortion + Noise - % RL = 32 W, f = 1kHz RL = 16 W, VDD = 5 V PO = 1 mW per Channel 0.1 PO = 20 mW per Channel 0.01 PO = 10 mW per Channel 0.001 20 100 1k f - Frequency - Hz 10k 20k RL = 32 W, VDD = 2.5 V PO = 1 mW per Channel 0.1 PO = 4 mW per Channel 0.01 0.001 20 Figure 5. PO = 10 mW per Channel 100 1k f - Frequency - Hz 10k 20k Figure 6. 7 Copyright © 2009, Texas Instruments Incorporated Product Folder Link(s) :TPA6136A2 TPA6136A2 SLOS621A – JULY 2009 – REVISED AUGUST 2009 ........................................................................................................................................................ www.ti.com TYPICAL CHARACTERISTICS (continued) TOTAL HARMONIC DISTORTION + NOISE vs FREQUENCY TOTAL HARMONIC DISTORTION + NOISE vs FREQUENCY 1 THD+N - Total Harmonic Distortion + Noise - % THD+N - Total Harmonic Distortion + Noise - % 1 RL = 32 W, VDD = 3.6 V PO = 1 mW per Channel 0.1 PO = 10 mW per Channel 0.01 PO = 20 mW per Channel 0.001 20 100 1k f - Frequency - Hz 10k 20k RL = 32 W, VDD = 5 V PO = 1 mW per Channel 0.1 PO = 20 mW per Channel 0.01 PO = 10 mW per Channel 0.001 20 100 Figure 7. 10k 20k Figure 8. OUTPUT POWER vs SUPPLY VOLTAGE OUTPUT POWER vs SUPPLY VOLTAGE 50 50 RL = 16 W 45 45 PO - Output Power per Channel - mW PO - Output Power per Channel - mW 1k f - Frequency - Hz 40 THD+N = 10% 35 30 THD+N = 1% 25 20 15 10 5 RL = 32 W 40 35 THD+N = 10% 30 25 THD+N = 1% 20 15 10 5 0 2.5 3 3.5 4 4.5 VDD - Supply Voltage - V 5 0 2.5 5.5 3 Figure 9. 3.5 4 4.5 VDD - Supply Voltage - V 5 5.5 Figure 10. OUTPUT POWER vs LOAD RESISTANCE OUTPUT POWER vs LOAD RESISTANCE 30 40 VDD = 3.6 V, 10% THD+N 10 VDD = 2.5 V, 10% THD+N VDD = 2.5 V, 1% THD+N VDD = 3.6 V, 1% THD+N 25 HPVSS and Flying Cap = 2.2 mF 20 15 HPVSS and Flying Cap = 0.47 mF 10 5 THD+N = 1%, VDD = 3.6 V f = 1 kHz 1 10 PO - Output Power per Channel - mW PO - Output Power per Channel - mW HPVSS and Flying Cap = 1 mF 100 RL - Load Resistance - W 1000 0 10 100 200 RL - Load Resistance - W Figure 11. Figure 12. 8 Copyright © 2009, Texas Instruments Incorporated Product Folder Link(s) :TPA6136A2 TPA6136A2 www.ti.com ........................................................................................................................................................ SLOS621A – JULY 2009 – REVISED AUGUST 2009 TYPICAL CHARACTERISTICS (continued) OUTPUT VOLTAGE vs SUPPLY VOLTAGE SUPPLY VOLTAGE REJECTION RATIO vs FREQUENCY 2 VO - Output Voltage - Vrms 1.6 1.4 Load = 600 W 1.2 1 Load = 32 W 0.8 0.6 Load = 16 W 0.4 0.2 0 2.5 3 3.5 4 4.5 5 -10 Ksvr - Supply Voltage Rejection Ratio - dB f = 1 kHz, THD+N = 1% 1.8 5.5 RL = 16 W -30 -50 -70 VDD = 5 V VDD = 2.5 V VDD = 3.6 V -90 -110 20 100 VDD - Supply Voltage - V 1k f - Frequency - Hz Figure 13. 10k 20k Figure 14. SUPPLY VOLTAGE REJECTION RATIO vs FREQUENCY QUIESCENT SUPPLY CURRENT vs SUPPLY VOLTAGE -10 9 RL = 32 W -30 -50 -70 VDD = 3.6 V VDD = 5 V VDD = 2.5 V -90 EN = 1.3 V, No Load 8 Quiescent Supply Current - mA Ksvr - Supply Voltage Rejection Ratio - dB 10 7 6 5 4 3 2 1 -110 20 100 1k f - Frequency - Hz 10k 0 2.5 20k 3 3.5 4 4.5 VDD - Supply Voltage - V Figure 15. 5.5 Figure 16. SUPPLY CURRENT vs TOTAL OUTPUT POWER SUPPLY CURRENT vs TOTAL OUTPUT POWER 100 100 RL = 16 W, f = 1kHz RL = 32 W, f = 1kHz IDD - Supply Current - mA VDD = 3 V IDD - Supply Current - mA 5 VDD = 5 V 10 VDD = 2.5 V VDD = 5 V 10 VDD = 3.6 V VDD = 3 V VDD = 3.6 V 1 0.001 0.01 VDD = 2.5 V 0.1 1 PO - Total Output Power - mW 10 50 1 0.001 Figure 17. 0.01 0.1 1 PO - Total Output Power - mW 10 50 Figure 18. 9 Copyright © 2009, Texas Instruments Incorporated Product Folder Link(s) :TPA6136A2 TPA6136A2 SLOS621A – JULY 2009 – REVISED AUGUST 2009 ........................................................................................................................................................ www.ti.com TYPICAL CHARACTERISTICS (continued) CROSSTALK vs FREQUENCY OUTPUT SPECTRUM vs FREQUENCY 0 -10 RL = 16 W, Power = 15 mW, VDD = 3.6 V -30 VO - Output Amplitude - dBV -20 -40 Crosstalk - dB Single Channel, Load = 16 W, VDD = 3.6 V -60 -80 -100 -50 -70 -90 -110 -130 -120 -140 20 100 1k f - Frequency - Hz 10k -150 0 20k 5000 10000 f - Frequency - Hz Figure 19. 20000 Figure 20. HI-Z OUTPUT IMPEDANCE vs FREQUENCY STARTUP WAVEFORMS vs TIME 5 100k VDD = 3.6 V, EN = 3.6 V, HiZ = 3.6 V 4 EN 3 Right Channel 10k V - Voltage - V ZO - H-Z Output Impedance - W 15000 Left Channel 2 1 VOUT 0 1k -1 Load = 16 W, VDD = 3.6 V, VI = 0.5 VRMS at 1 kHz -2 100 10 -3 100 1000 10k 100k 1M 10M 100M 0 2 4 6 t - Time - ms f - Frequency - Hz Figure 21. 8 10 Figure 22. SHUTDOWN WAVEFORMS vs TIME 5 Load = 16 W, VDD = 3.6 V, VI = 0.5 VRMS at 20 kHz 4 EN V - Voltage - V 3 2 1 VOUT 0 -1 -2 -3 0 50 100 t - Time - ms 150 200 Figure 23. 10 Copyright © 2009, Texas Instruments Incorporated Product Folder Link(s) :TPA6136A2 TPA6136A2 www.ti.com ........................................................................................................................................................ SLOS621A – JULY 2009 – REVISED AUGUST 2009 APPLICATION INFORMATION APPLICATION CIRCUIT 0.22 µF x 4 INR+ OUTR INRTPA2012D2 INL+ OUTL INL- 0.22 µF x 4 ABB or TLV320AIC33 TLV320AIC3104 TLV320DAC32 PCM1774 OUTR+ INR+ OUTR– INR- OUTR OUTL+ INL+ OUTL OUTL– INL- TPA6136A2 SGND ENABLE GAIN HI-Z MODE VBAT 2.2 µF EN GND GAIN HI-Z VDD HPVSS HPVDD CPP CPN 1 µF 2.2 µF 1 µF Figure 24. Typical Application Configuration with Differential Input Signals 1 µF RIGHT IN INRINR+ OUTR LEFT IN 1 µF INL- TPA6136A2 OUTL INL+ SGND ENABLE GAIN EN HI-Z MODE HI-Z VBAT VDD 2.2 µF GND GAIN HPVDD HPVSS CPP CPN 1 µF 2.2 µF 1 µF Figure 25. Typical Application Configuration with Single-Ended Input Signals 11 Copyright © 2009, Texas Instruments Incorporated Product Folder Link(s) :TPA6136A2 TPA6136A2 SLOS621A – JULY 2009 – REVISED AUGUST 2009 ........................................................................................................................................................ www.ti.com GAIN CONTROL The TPA6136A2 has two gain settings which are controlled with the GAIN pin. The following table gives an overview of the gain function. GAIN VOLTAGE AMPLIFIER GAIN ≤ 0.6 V 0 dB ≥ 1.3 V 6 dB Table 1. Windows Vista™ Premium Mobile Mode Specifications Device Type Requirement Windows Premium Mobile Vista Specifications TPA6136A2 Typical Performance THD+N ≤ –65 dB FS [20 Hz, 20 kHz] –75 dB FS [20 Hz, 20 kHz] Analog Speaker Line Jack [RL = 10 kΩ, FS = 0.707 Vrms] Dynamic Range with Signal Present ≤ –80 dB FS A-Weight –100 dB FS A-Weight Analog Headphone Out Jack [RL = 32Ω, FS = 0.300 Vrms] Line Output Crosstalk ≤ –60 dB [20 Hz, 20 kHz] –90 dB [20 Hz, 20 kHz] THD+N ≤ –45 dB FS [20 Hz, 20 kHz] –65 dB FS [20 Hz, 20 kHz] Dynamic Range with Signal Present ≤ –80 dB FS A-Weight –94 dB FS A-Weight Headphone Output Crosstalk ≤ –60 dB [20 Hz, 20 kHz] –90 dB [20 Hz, 20 kHz] HIGH OUTPUT IMPEDANCE The TPA6136A2 has a HI-Z control pin that increases output impedance while muting the amplifier. Apply a voltage greater than 1.3 V to the HI-Z and EN pin to activate the HI-Z mode. This feature allows the headphone output jack to be shared for other functions besides audio. For example, sharing of a headphone jack between audio and video as shown in Figure 26. The TPA6136A2 output impedance is high enough to prevent attenuating the video signal. Enable Voltage HI-Z Voltage Output Impedance ≤ 0.6 V ≤ 0.6 V 20 Ω – 30 Ω ≤ 0.6 V ≥ 1.3 V 20 Ω –30 Ω ≥ 1.3 V ≤ 0.6 V Maximum External Voltage Applied to the Output Pins Comments –0.3 V to 3.3 V (1) Shutdown Mode – Active Mode –1.8 V to 1.8 V HI-Z Mode ≤1Ω 40 kΩ @ 10 kHz ≥ 1.3 V ≥ 1.3 V 4.5 kΩ @ 1 MHz 750 Ω @ 10 MHz (1) If VDD is < 3.3 V, then maximum allowed external voltage applied is VDD in this mode Video Buffer/Amp (i.e: THS7375) + 75 W – TPA6136A2 OUTR OUTL Figure 26. Sharing One Connector Between Audio and Video Signals Example 12 Copyright © 2009, Texas Instruments Incorporated Product Folder Link(s) :TPA6136A2 TPA6136A2 www.ti.com ........................................................................................................................................................ SLOS621A – JULY 2009 – REVISED AUGUST 2009 GROUND SENSE FUNCTION The ground sense pin, SGND, reduces ground-loop noise when the audio output jack is connected to a different ground reference than codec and amplifier ground. Always connect the SGND pin to the headphone jack. This reduces output offset voltage and eliminates turn-on pop. Figure 27 shows how to connect SGND when an FM radio antenna function is implemented on the headphone wire. The nH coil and capacitor separate the RF signal from the audio GND signal. In this case, SGND is used to eliminate the offset voltage that is generated from the audio signal current and the RF coil low-frequency impedance. The voltage difference between SGND and AGND cannot be greater than ±300 mV. The amplifier performance degrades if the voltage difference between SGND and AGND is greater than ±300 mV. OUTR+ INR+ OUTR- INR- OUTL+ INL+ OUTL- INL- CODEC OUTR TPA6136A2 OUTL SGND ENABLE GAIN EN GAIN HI-Z MODE VBAT HI-Z VDD FM Tuner GND nH Coil HPVSS HPVDD CPP CPN Figure 27. Typical Application Circuit Using Ground Sense Function HEADPHONE AMPLIFIERS Single-supply headphone amplifiers typically require dc-blocking capacitors to remove dc bias from their output voltage. The top drawing in Figure 28 illustrates this connection. If dc bias is not removed, large dc current will flow through the headphones which wastes power, clips the output signal, and potentially damages the headphones. These dc-blocking capacitors are often large in value and size. Headphone speakers have a typical resistance between 16 Ω and 32 Ω. This combination creates a high-pass filter with a cutoff frequency as shown in Equation 1, where RL is the load impedance, CO is the dc-block capacitor, and fC is the cutoff frequency. 1 fc = 2pRLCO (1) For a given high-pass cutoff frequency and load impedance, the required dc-blocking capacitor is found as: CO = 1 2p ¦C RL (2) Reducing fC improves low frequency fidelity and requires a larger dc-blocking capacitor. To achieve a 20 Hz cutoff with 16 Ω headphones, CO must be at least 500 µF. Large capacitor values require large packages, consuming PCB area, increasing height, and increasing cost of assembly. During start-up or shutdown the dc-blocking capacitor has to be charged or discharged. This causes an audible pop on start-up and power-down. Large dc-blocking capacitors also reduce audio output signal fidelity. Two different headphone amplifier architectures are available to eliminate the need for dc-blocking capacitors. The Capless amplifier architecture provides a reference voltage to the headphone connector shield pin as shown in the middle drawing of Figure 28. The audio output signals are centered around this reference voltage, which is typically half of the supply voltage to allow symmetrical output voltage swing. 13 Copyright © 2009, Texas Instruments Incorporated Product Folder Link(s) :TPA6136A2 TPA6136A2 SLOS621A – JULY 2009 – REVISED AUGUST 2009 ........................................................................................................................................................ www.ti.com When using a Capless amplifier do not connect the headphone jack shield to any ground reference or large currents will result. This makes Capless amplifiers ineffective for plugging non-headphone accessories into the headphone connector. Capless amplifiers are useful only with floating GND headphones. Conventional CO VOUT CO GND Capless VOUT GND VBIAS DirectPath™ VDD GND VSS Figure 28. Amplifier Applications The DirectPath™ amplifier architecture operates from a single supply voltage and uses an internal charge pump to generate a negative supply rail for the headphone amplifier. The output voltages are centered around 0 V and are capable of positive and negative voltage swings as shown in the bottom drawing of Figure 28. DirectPath amplifiers require no output dc-blocking capacitors. The headphone connector shield pin connects to ground and will interface with headphones and non-headphone accessories. The TPA6136A2 is a DirectPath amplifier. ELIMINATING TURN-ON POP AND POWER SUPPLY SEQUENCING The TPA6136A2 has excellent noise and turn-on / turn-off pop performance. It uses an integrated click-and-pop suppression circuit to allow fast start-up and shutdown without generating any voltage transients at the output pins. Typical start-up time from shutdown is 5 ms. DirectPath technology keeps the output dc voltage at 0 V even when the amplifier is powered up. The DirectPath technology together with the active pop-and-click suppression circuit eliminates audible transients during start up and shutdown. Use input coupling capacitors to ensure inaudible turn-on pop. Activate the TPA6136A2 after all audio sources have been activated and their output voltages have settled. On power-down, deactivate the TPA6136A2 before deactivating the audio input source. The EN pin controls device shutdown: Set to 0.6 V or lower to deactivate the TPA6136A2; set to 1.3 V or higher to activate. 14 Copyright © 2009, Texas Instruments Incorporated Product Folder Link(s) :TPA6136A2 TPA6136A2 www.ti.com ........................................................................................................................................................ SLOS621A – JULY 2009 – REVISED AUGUST 2009 RF AND POWER SUPPLY NOISE IMMUNITY The TPA6136A2 employs a new differential amplifier architecture to achieve high power supply noise rejection. Power supply noise is common in modern electronics. Although power supply noise frequencies are much higher than the 20 kHz audio band, signal modulation often falls in-band. This, in turn, modulates the supply voltage, allowing a coupling path into the audio amplifier. A common example is the 217 Hz GSM frame-rate buzz often heard from an active speaker when a cell phone is placed nearby during a phone call. The TPA6136A2 has excellent rejection of power supply noise, preventing audio signal degradation. CONSTANT MAXIMUM OUTPUT POWER AND ACOUSTIC SHOCK PREVENTION Typically the output power increases with increasing supply voltage on an unregulated headphone amplifier. The TPA6136A2 maintains a constant output power independent of the supply voltage. Thus the design for prevention of acoustic shock (hearing damage due to exposure to a loud sound) is simplified since the output power will remain constant, independent of the supply voltage. This feature allows maximizing the audio signal at the lowest supply voltage. INPUT COUPLING CAPACITORS Input coupling capacitors block any dc bias from the audio source and ensure maximum dynamic range. Input coupling capacitors also minimize TPA6136A2 turn-on pop to an inaudible level. The input capacitors are in series with TPA6136A2 internal input resistors, creating a high-pass filter. Equation 3 calculates the high-pass filter corner frequency. The input impedance, RIN, is dependent on device gain. Larger input capacitors decrease the corner frequency. See the Operating Characteristics table for input impedance values. 1 fC = 2 p RIN CIN (3) For a given high-pass cutoff frequency, the minimum input coupling capacitor is found as: 1 CIN = 2 p ¦ C RIN (4) Example: Design for a 20 Hz corner frequency with a TPA6136A2 gain of +6 dB. The Operating Characteristics table gives RIN as 13.2 kΩ. Equation 4 shows the input coupling capacitors must be at least 0.6 µF to achieve a 20 Hz high-pass corner frequency. Choose a 0.68 µF standard value capacitor for each TPA6136A2 input (X5R material or better is required for best performance). Input capacitors can be removed provided the TPA6136A2 inputs are driven differentially with less than ±1 VRMS and the common-mode voltage is within the input common-mode range of the amplifier. Without input capacitors turn-on pop performance may be degraded and should be evaluated in the system. CHARGE PUMP FLYING CAPACITOR AND HPVSS CAPACITOR The TPA6136A2 uses a built-in charge pump to generate a negative voltage supply for the headphone amplifiers. The charge pump flying capacitor connects between CPP and CPN. It transfers charge to generate the negative supply voltage. The HPVSS capacitor must be at least equal in value to the flying capacitor to allow maximum charge transfer. Use low equivalent-series-resistance (ESR) ceramic capacitors (X5R material or better is required for best performance) to maximize charge pump efficiency. Typical values are 1 µF to 2.2 µF for the HPVSS and flying capacitors. Although values down to 0.47 µF can be used, total harmonic distortion (THD) will increase. OPERATION WITH DACs AND CODECs AND INPUT RF NOISE REJECTION When using amplifiers with CODECs and DACs, sometimes there is an increase in the output noise floor from the audio amplifier. This occurs when the output out–of–band noise of the CODEC/DAC folds back into the audio frequency due to the limited gain bandwidth product of the audio amplifier. Single–ended RF noise can also fold back into the audio band thus degrading the audio signal even further. 15 Copyright © 2009, Texas Instruments Incorporated Product Folder Link(s) :TPA6136A2 TPA6136A2 SLOS621A – JULY 2009 – REVISED AUGUST 2009 ........................................................................................................................................................ www.ti.com The TPA6136A2 has a built-in low-pass filter to reduce CODEC/DAC out–of–band noise and RF noise, that could fold back into the audio frequency. POWER SUPPLY AND HPVDD DECOUPLING CAPACITORS AND CONNECTIONS The TPA6136A2 DirectPath headphone amplifier requires adequate power supply decoupling to ensure that output noise and total harmonic distortion (THD) remain low. Use good low equivalent-series-resistance (ESR) ceramic capacitors (X5R material or better is required for best performance). Place a 2.2 µF capacitor within 5 mm of the VDD pin. Reducing the distance between the decoupling capacitor and VDD minimizes parasitic inductance and resistance, improving TPA6136A2 supply rejection performance. Use 0402 or smaller size capacitors if possible. Ensure that the ground connection of each of the capacitors has a minimum length return path to the device. Failure to properly decouple the TPA6136A2 may degrade audio or EMC performance. For additional supply rejection, connect an additional 10 µF or higher value capacitor between VDD and ground. This will help filter lower frequency power supply noise. The high power supply rejection ratio (PSRR) of the TPA6136A2 makes the 10 µF capacitor unnecessary in most applications. Connect a 2.2 µF capacitor between HPVDD and ground. This ensures the amplifier internal bias supply remains stable and maximizes headphone amplifier performance. WARNING: DO NOT connect HPVDD directly to VDD or an external supply voltage. The voltage at HPVDD is generated internally. Connecting HPVDD to an external voltage can damage the device. PACKAGE INFORMATION Package Dimensions The package dimensions for this YFF package are shown in the table below. See the package drawing at the end of this data sheet for more details. Table 2. YFF Package Dimensions Packaged Devices D E TPA6136A2YFF Min = 1530µm Max = 1590µm Min = 1530µm Max = 1590µm LAYOUT RECOMMENDATIONS GND CONNECTIONS The SGND pin is an input reference and must be connected to the headphone ground connector pin. This ensures no turn-on pop and minimizes output offset voltage. Do not connect more than ±0.3 V to SGND. GND is a power ground. Connect supply decoupling capacitors for VDD, HPVDD, and HPVSS to GND. BOARD LAYOUT In making the pad size for the WCSP balls, it is recommended that the layout use non-solder-mask defined (NSMD) land. With this method, the solder mask opening is made larger than the desired land area, and the opening size is defined by the copper pad width. Figure 29 and Table 3 shows the appropriate diameters for a WCSP layout. For improved RF immunity it is recommended that all signal traces are routed in the middle layers of the multi-layer PCB. The top and bottom layers are used for the supply voltage plane and the GND plane. 16 Copyright © 2009, Texas Instruments Incorporated Product Folder Link(s) :TPA6136A2 TPA6136A2 www.ti.com ........................................................................................................................................................ SLOS621A – JULY 2009 – REVISED AUGUST 2009 Copper Trace Width Solder Pad Width Solder Mask Opening Solder Mask Thickness Copper Trace Thickness Figure 29. Land Pattern Dimensions Table 3. Land Pattern Dimensions (1) SOLDER PAD DEFINITIONS Non-solder-mask defined (NSMD) (1) (2) (3) (4) (5) (6) (7) COPPER PAD SOLDER MASK (5) OPENING 230 µm (+0.0, –25 µm) 310 µm (+0.0, –25 µm) (2) (3) (4) COPPER THICKNESS STENCIL (6) (7) OPENING STENCIL THICKNESS 1 oz max (32 µm) 275 µm × 275 µm Sq. (rounded corners) 100 µm thick Circuit traces from NSMD defined PWB lands should be 75 µm to 100 µm wide in the exposed area inside the solder mask opening. Wider trace widths reduce device stand off and impact reliability. Best reliability results are achieved when the PWB laminate glass transition temperature is above the operating the range of the intended application Recommend solder paste is Type 3 or Type 4. For a PWB using a Ni/Au surface finish, the gold thickness should be less 0,5 mm to avoid a reduction in thermal fatigue performance. Solder mask thickness should be less than 20 µm on top of the copper circuit pattern Best solder stencil performance is achieved using laser cut stencils with electro polishing. Use of chemically etched stencils results in inferior solder paste volume control. Trace routing away from WCSP device should be balanced in X and Y directions to avoid unintentional component movement due to solder wetting forces. TRACE WIDTH Recommended trace width at the solder balls is 75 µm to 100 µm to prevent solder wicking onto wider PCB traces. For high current pins (VDD, HPVDD, HPVSS, CPP, CPN, OUTL, and OUTR) of the TPA6136A2, use 100 µm trace widths at the solder balls and at least 500 µm PCB traces to ensure proper performance and output power for the device. For the remaining signals of the TPA6136A2, use 75 µm to 100 µm trace widths at the solder balls. The audio input pins (INL–, INL+, INR– and INR+) must run side-by-side to maximize common-mode noise cancellation. 17 Copyright © 2009, Texas Instruments Incorporated Product Folder Link(s) :TPA6136A2 PACKAGE OPTION ADDENDUM www.ti.com 10-Dec-2020 PACKAGING INFORMATION Orderable Device Status (1) Package Type Package Pins Package Drawing Qty Eco Plan (2) Lead finish/ Ball material MSL Peak Temp Op Temp (°C) Device Marking (3) (4/5) (6) TPA6136A2YFFR ACTIVE DSBGA YFF 16 3000 RoHS & Green SNAGCU Level-1-260C-UNLIM -40 to 85 AOW1 TPA6136A2YFFT ACTIVE DSBGA YFF 16 250 RoHS & Green SNAGCU Level-1-260C-UNLIM -40 to 85 AOW1 (1) The marketing status values are defined as follows: ACTIVE: Product device recommended for new designs. LIFEBUY: TI has announced that the device will be discontinued, and a lifetime-buy period is in effect. NRND: Not recommended for new designs. Device is in production to support existing customers, but TI does not recommend using this part in a new design. PREVIEW: Device has been announced but is not in production. Samples may or may not be available. OBSOLETE: TI has discontinued the production of the device. (2) RoHS: TI defines "RoHS" to mean semiconductor products that are compliant with the current EU RoHS requirements for all 10 RoHS substances, including the requirement that RoHS substance do not exceed 0.1% by weight in homogeneous materials. Where designed to be soldered at high temperatures, "RoHS" products are suitable for use in specified lead-free processes. TI may reference these types of products as "Pb-Free". RoHS Exempt: TI defines "RoHS Exempt" to mean products that contain lead but are compliant with EU RoHS pursuant to a specific EU RoHS exemption. Green: TI defines "Green" to mean the content of Chlorine (Cl) and Bromine (Br) based flame retardants meet JS709B low halogen requirements of