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TPS65014
SLVS551A – DECEMBER 2004 – REVISED SEPTEMBER 2015
TPS65014 Power- and Battery-Management IC for Li-Ion Powered Systems
1 Features
3 Description
•
The TPS65014 device is an integrated power- and
battery-management IC for applications powered by
one Li-ion or Li-polymer cell and which require
multiple power rails. The TPS65014 provides two
highly efficient, step-down converters targeted at
providing the core voltage and peripheral I/O rails in a
processor-based system. Both step-down converters
enter a low-power mode at light load for maximum
efficiency across the widest possible range of load
currents. The LOW_PWR pin allows the core
converter to lower its output voltage when the
application processor goes into deep sleep. The
TPS65014 also integrates two 200-mA LDO voltage
regulators, which are enabled through the serial
interface. Each LDO operates with an input voltage
range of 1.8 V to 6.5 V, thus allowing them to be
supplied from one of the step-down converters or
directly from the battery.
1
•
•
•
•
•
•
•
•
•
•
Linear Charger Management for Single Li-Ion or
Li-Polymer Cells
Dual Input Ports for Charging From USB or From
Wall Plug, Handles 100-mA and 500-mA USB
Requirements
Charge Current Programmable Through External
Resistor
1-A, 95% Efficient Step-Down Converter for I/O
and Peripheral Components (VMAIN)
400-mA, 90% Efficient Step-Down Converter for
Processor Core (VCORE)
2× 200-mA LDOs for I/O and Peripheral
Components, LDO Enable Through Bus
Serial Interface Compatible With I2C, Supports
100-kHz, 400-kHz Operation
LOW_PWR Pin to Lower or Disable Processor
Core Supply Voltage in Deep-Sleep Mode
70-µA Quiescent Current
1% Reference Voltage
Thermal-Shutdown Protection
Device Information(1)
PART NUMBER
TPS65014
•
•
All Single Li-Ion Cell-Operated Products Requiring
Multiple Supplies Including:
– PDAs
– Cellular and Smart Phones
– Internet Audio Players
– Digital Still Cameras
Digital Radio Players
Split-Supply DSP and µP Solutions
BODY SIZE (NOM)
7.00 mm × 7.00 mm
(1) For all available packages, see the orderable addendum at
the end of the data sheet.
2 Applications
•
PACKAGE
VQFN (48)
Functional Block Diagram
MAX(AC,USB,VBAT)
AC
VBAT
USB
PG
Linear Charge Controller
ISET
TS
SCLK
SDAT
AGND2
Serial
Interface
IFLSB
Thermal
Shutdown
VINMAIN
PS_SEQ
LOW_PWR
PB_ONOFF
BATT_COVER
HOT_RESET
TPOR
VMAIN
Control
Step-Down
Converter
RESPWRON
MPU_RESET
VCC
AGND3
VINCORE
INT
PWRFAIL
GPIO1
GPIO2
GPIO3
GPIO4
VIB
L1
VMAIN
DEFMAIN
PGND1
UVLO
VREF
OSC
L2
VCORE
VCORE
Step-Down
Converter
DEFCORE
PGND2
GPIOs
VINLDO1
VLDO1
200-mA LDO
VLDO1
VFB_LDO1
AGND1
LED2
VINLDO2
VLDO2
VLDO2
200-mA LDO
1
An IMPORTANT NOTICE at the end of this data sheet addresses availability, warranty, changes, use in safety-critical applications,
intellectual property matters and other important disclaimers. PRODUCTION DATA.
TPS65014
SLVS551A – DECEMBER 2004 – REVISED SEPTEMBER 2015
www.ti.com
Table of Contents
1
2
3
4
5
6
Features ..................................................................
Applications ...........................................................
Description .............................................................
Revision History.....................................................
Pin Configuration and Functions .........................
Specifications.........................................................
6.1
6.2
6.3
6.4
6.5
6.6
6.7
6.8
6.9
6.10
7
1
1
1
2
3
5
Absolute Maximum Ratings ...................................... 5
ESD Ratings.............................................................. 5
Recommended Operating Conditions....................... 5
Thermal Information .................................................. 6
Electrical Characteristics........................................... 6
Electrical Characteristics: Battery Charger ............... 9
Dissipation Ratings ................................................. 11
Serial Interface Timing Requirements..................... 12
Switching Characteristics ........................................ 12
Typical Characteristics .......................................... 13
Detailed Description ............................................ 18
7.1 Overview ................................................................. 18
7.2 Functional Block Diagram ....................................... 19
7.3 Feature Description................................................. 20
7.4 Device Functional Modes........................................ 37
7.5 Register Maps ......................................................... 38
8
Application and Implementation ........................ 51
8.1 Application Information............................................ 51
8.2 Typical Application ................................................. 51
9
Power Supply Recommendations...................... 56
9.1 Battery Charger....................................................... 56
9.2 LDO1 Output Voltage Adjustment........................... 59
10 Layout................................................................... 59
10.1 Layout Guidelines ................................................. 59
10.2 Layout Example .................................................... 60
11 Device and Documentation Support ................. 61
11.1
11.2
11.3
11.4
11.5
Device Support......................................................
Community Resources..........................................
Trademarks ...........................................................
Electrostatic Discharge Caution ............................
Glossary ................................................................
61
61
61
61
61
12 Mechanical, Packaging, and Orderable
Information ........................................................... 61
4 Revision History
NOTE: Page numbers for previous revisions may differ from page numbers in the current version.
Changes from Original (December 2004) to Revision A
•
2
Page
Added ESD Ratings table, Feature Description section, Device Functional Modes, Application and Implementation
section, Power Supply Recommendations section, Layout section, Device and Documentation Support section, and
Mechanical, Packaging, and Orderable Information section. ................................................................................................ 1
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5 Pin Configuration and Functions
LOW_PWR
INT
PWRFAIL
RESPWRON
MPU_RESET
HOT_RESET
SCLK
SDAT
IFLSB
TPOR
GPIO1
GPIO2
RGZ Package
48-Pin VQFN
Top View
36 35 34 33 32 31 30 29 28 27 26 25
37
24
38
23
39
22
40
21
41
20
42
19
43
18
44
17
45
16
46
15
47
14
48
13
1 2 3 4 5 6 7 8 9 10 11 12
VLDO1
VFB_LDO1
VINLDO1
AGND1
VLDO2
VINLDO2
GPIO3
GPIO4
PGND1_B
PGND1_A
PS_SEQ
VMAIN
DEFCORE
LED2
VIB
L2
VINCORE
VCC
VINMAIN_A
VINMAIN_B
L1_A
L1_B
PG
DEFMAIN
ISET
TS
BATT_COVER
AC
VBAT_A
VBAT_B
USB
AGND2
AGND3
PGND2
PB_ONOFF
VCORE
NC − No internal connection
Pin Functions
PIN
NAME
NO.
I/O
DESCRIPTION
Charger input voltage from AC adapter. The AC pin can be left open or can be connected to
ground if the charger is not used.
CHARGER SECTION
AC
40
I
AGND2
44
—
ISET
37
I
External charge current setting resistor connection for use with AC adapter
PG
11
O
Indicates when a valid power supply is present for the charger (open-drain)
TS
38
I
Battery temperature sense input
USB
43
I
Charger input voltage from USB port. The USB pin can be left open or can be connected to
ground if the charger is not used.
VBAT_A
41
I
Sense input for the battery voltage. Connect directly with the battery.
VBAT_B
42
O
Power output of the battery charger. Connect directly with the battery.
Thermal Pad
—
—
Connect the thermal pad to GND
Analog ground connection. All analog ground pins are connected internally on the chip.
SWITCHING REGULATOR SECTION
AGND3
L1_A, L1_B
L2
PGND1_A,
PGND1_B
PGND2
45
—
Analog ground connection. All analog ground pins are connected internally on the chip.
9, 10
—
Switch pin of VMAIN converter. The VMAIN inductor is connected here.
4
—
Switch pin of VCORE converter. The VCORE inductor is connected here.
15, 16
—
Power ground for VMAIN converter
46
—
Power ground for VCORE converter
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Pin Functions (continued)
PIN
NAME
NO.
I/O
DESCRIPTION
SWITCHING REGULATOR SECTION (continued)
VCC
6
I
Power supply for digital and analog circuitry of MAIN and CORE DC-DC converters. This
must be connected to the same voltage supply as VINCORE and VINMAIN. Also supplies
serial interface block
VCORE
48
I
VCORE feedback voltage sense input, connect directly to VCORE
VMAIN
13
I
VMAIN feedback voltage sense input, connect directly to VMAIN
VINMAIN_A,
VINMAIN_B
7, 8
I
Input voltage for VMAIN step-down converter. This must be connected to the same voltage
supply as VINCORE and VCC.
5
I
Input voltage for VCORE step-down converter. This must be connected to the same voltage
supply as VINMAIN and VCC.
VINCORE
LDO REGULATOR SECTION
AGND1
21
—
VFB_LDO1
23
I
Analog ground connection. All analog ground pins are connected internally on the chip.
Feedback input from external resistive divider for LDO1
VINLDO1
22
I
Input voltage for LDO1
VINLDO2
19
I
Input voltage for LDO2
VLDO1
24
O
Output voltage for LDO1
VLDO2
20
O
Output and feedback voltage for LDO2
LED2
2
O
LED driver, with blink rate programmable through the serial interface
VIB
3
O
Vibrator driver, enabled through the serial interface
DRIVER SECTION
CONTROL AND I2C SECTION
BATT_COVER
39
I
Indicates if battery cover is in place
DEFCORE
1
I
Input signal indicating default VCORE voltage, 0 = 1.5 V, 1 = 1.8 V
DEFMAIN
12
I
Input signal indicating default VMAIN voltage, 0 = 3 V, 1 = 3.3 V
GPIO1
26
I/O
General-purpose open-drain input/output
GPIO2
25
I/O
General-purpose open-drain input/output
GPIO3
18
I/O
General-purpose open-drain input/output
GPIO4
17
I/O
General-purpose open-drain input/output
HOT_RESET
31
I
Push-button reset input used to reboot or wake up processor through the TPS65014
IFLSB
28
I
LSB of serial interface address used to distinguish two devices with the same address
INT
35
O
Indicates a charge fault or termination, or if any of the regulator outputs are below the lower
tolerance level, active low (open-drain)
LOW_PWR
36
I
Input signal indicating deep sleep mode, VCORE is lowered to predefined value or disabled
MPU_RESET
32
O
Open-drain reset output generated by user activated HOT_RESET
PB_ONOFF
47
I
Push-button enable pin, also used to wake up processor from low power mode
PS_SEQ
14
I
Sets power-up/down sequence of step-down converters
PWRFAIL
34
O
Open-drain output. Active low when UVLO comparator indicates low VBAT condition or when
shutdown is about to occur due to an overtemperature condition or when the battery cover is
removed (BATT_COVER has gone low).
RESPWRON
33
O
Open-drain system reset output, generated according to the state of the VMAIN output
voltage. If the main output is disabled, RESPWRON is active (in other words, low).
SCLK
30
I
Serial interface clock line
SDAT
29
I/O
TPOR
27
I
4
Serial interface data/address
Sets the reset delay time at RESPWRON. TPOR = 0: Tn(RESPWRON) = 100 ms.
TPOR = 1: Tn(RESPWRON) = 1 s.
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6 Specifications
6.1 Absolute Maximum Ratings
over operating free-air temperature range unless otherwise noted (1)
MIN
MAX
UNIT
20
V
7
V
1800
mA
Peak current at all other pins
1000
mA
Continuous power dissipation
See Dissipation
Ratings
Input voltage on VAC pin with respect to AGND
Input voltage range on all other pins except AGND/PGND pins with respect to
AGND
–0.3
Current at AC, VBAT, VINMAIN, L1, PGND1
Operating free-air temperature, TA
–40
Maximum junction temperature, TJ
Storage temperature, Tstg
–65
Lead temperature 1,6 mm (1/16 inch) from case for 10 seconds
(1)
85
°C
125
°C
150
°C
260
°C
Stresses beyond those listed under Absolute Maximum Ratings may cause permanent damage to the device. These are stress ratings
only, and functional operation of the device at these or any other conditions beyond those indicated under Recommended Operating
Conditions is not implied. Exposure to absolute-maximum-rated conditions for extended periods may affect device reliability.
6.2 ESD Ratings
VALUE
V(ESD)
(1)
(2)
(3)
Electrostatic discharge
Human-body model (HBM), per ANSI/ESDA/JEDEC JS-001 (1) (2)
±1000
Charged-device model (CDM), per JEDEC specification JESD22C101 (3) (2)
±1000
UNIT
V
JEDEC document JEP155 states that 500-V HBM allows safe manufacturing with a standard ESD control process. Manufacturing with
less than 500-V HBM is possible with the necessary precautions. Pins listed as ±1000 V may actually have higher performance.
At pins VIB, PG, and LED2
JEDEC document JEP157 states that 250-V CDM allows safe manufacturing with a standard ESD control process. Manufacturing with
less than 250-V CDM is possible with the necessary precautions. Pins listed as ±1000 V may actually have higher performance.
6.3 Recommended Operating Conditions
MIN
NOM
MAX
UNIT
V(AC)
Supply voltage from AC adapter
4.5
6.5
V
V(USB)
Supply voltage from USB
4.4
5.25
V
V(BAT)
Voltage at battery
2.5
4.2
V
VI(MAIN),VI(CORE),VCC
Input voltage range step-down converters
2.5
6.0
V
VI(LDO1), VI(LDO2)
Input voltage range for LDOs
1.8
6.5
V
TA
Operating ambient temperature
-40
85
°C
TJ
Operating junction temperature
-40
125
°C
R(CC)
Resistor from VI(main),VI(core) to VCC used for
filtering, CI(VCC) = 1 µF
100
Ω
10
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6.4 Thermal Information
TPS65014
THERMAL METRIC (1)
RGZ (VQFN)
UNIT
48 PINS
RθJA
Junction-to-ambient thermal resistance
27.0
°C/W
RθJC(top)
Junction-to-case (top) thermal resistance
14.3
°C/W
RθJB
Junction-to-board thermal resistance
4.6
°C/W
ψJT
Junction-to-top characterization parameter
0.2
°C/W
ψJB
Junction-to-board characterization parameter
4.6
°C/W
RθJC(bot)
Junction-to-case (bottom) thermal resistance
1.1
°C/W
(1)
For more information about traditional and new thermal metrics, see the Semiconductor and IC Package Thermal Metrics application
report, SPRA953.
6.5 Electrical Characteristics
VI(MAIN) = VI(CORE) = VCC = VI(LDO1) = VI(LDO2) = 3.6 V, TA = –40°C to 85°C, typical values are at TA = 25°C battery charger
specifications are valid in the range 0°C < TA < 85°C unless otherwise noted
PARAMETER
TEST CONDITIONS
MIN
TYP
MAX
UNIT
2
VCC
V
0
0.8
V
1
µA
0.8 VCC
6
V
0
0.4
CONTROL SIGNALS: LOW_PWR, SCLK, SDAT (INPUT)
VIH
High-level input voltage
IIH = 20 µA
VIL
Low-level input voltage
IIL = 10 µA
IIB
Input bias current
(1)
0.01
CONTROL SIGNALS: PB_ONOFF, HOT_RESET, BATT_COVER
VIH
High-level input voltage
IIH = 20 µA (1)
VIL
Low-level input voltage
IIL = 10 µA
R(pb_onoff)
Pulldown resistor at PB_ONOFF
1000
kΩ
R(hot_reset)
Pullup resistor at HOT_RESET,
connected to VCC
1000
kΩ
R(batt_cover)
Pulldown resistor at BATT_COVER
2000
kΩ
V
CONTROL SIGNALS: MPU_RESET, PWRFAIL, RESPWRON, INT, SDAT (OUTPUT)
VOH
High-level output voltage
VOL
Low-level output voltage
IIL = 10 mA
0
6
V
0.3
V
70
µA
25
µA
SUPPLY PIN: VCC
I(Q)
IO(SD)
(1)
6
Operating quiescent current
VI = 3.6 V, current into Main + Core + VCC
Shutdown supply current
VI = 3.6 V, BATT_COVER = GND,
Current into Main + Core + VCC
15
If the input voltage is higher than VCC, an additional input current, limited by an internal 10-kΩ resister, flows.
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Electrical Characteristics (continued)
VI(MAIN) = VI(CORE) = VCC = VI(LDO1) = VI(LDO2) = 3.6 V, TA = –40°C to 85°C, typical values are at TA = 25°C battery charger
specifications are valid in the range 0°C < TA < 85°C unless otherwise noted
PARAMETER
TEST CONDITIONS
MIN
TYP
MAX
UNIT
VMAIN STEP-DOWN CONVERTER
VI
Input voltage range
IO
Maximum output current
2.5
IO(SD)
Shutdown supply current
BATT_COVER = GND
0.1
1
µA
rDS(on)
P-channel MOSFET on-resistance
VI(MAIN) = VGS = 3.6 V
110
210
mΩ
Ilkg(p)
P-channel leakage current
V(DS) = 6 V
1
µA
rDS(on)
N-channel MOSFET on-resistance
VI(MAIN) = VGS = 3.6 V
110
200
mΩ
Ilkg(N)
N-channel leakage current
V(DS) = 6 V
1
µA
IL
P-channel current limit
2.5 V< VI(MAIN) < 6 V
1.4
1.75
2.1
A
fS
Oscillator frequency
1
1.25
1.5
MHz
2.5 V
2.75 V
VO(MAIN)
Fixed output voltage
3.0 V
3.3 V
R(VMAIN)
6
1000
VI(MAIN) = 2.7 V to 6 V; IO = 0 mA
0%
3%
VI(MAIN) = 2.7 V to 6 V;
0 mA ≤ IO ≤ 1000 mA
3%
3%
VI(MAIN) = 2.95 V to 6 V; IO = 0 mA
0%
3%
VI(MAIN) = 2.95 V to 6 V;
0 mA ≤ IO ≤ 1000 mA
3%
3%
VI(MAIN) = 3.2 V to 6 V; IO= 0 mA
0%
3%
VI(MAIN) = 3.2 V to 6 V;
0 mA ≤ IO ≤ 1000 mA
3%
3%
VI(MAIN) = 3.5 V to 6 V; IO= 0 mA
0%
3%
VI(MAIN) = 3.5 V to 6 V;
0 mA ≤ IO ≤ 1000 mA
3%
3%
Line regulation
VI(MAIN) = VO(MAIN) + 0.5 V (min. 2.5 V) to 6 V,
IO = 10 mA
Load regulation
IO = 10 mA to 1000 mA
VMAIN discharge resistance
V
mA
0.5
%/V
0.12
%/A
400
Ω
VCORE STEP-DOWN CONVERTER
VI
Input voltage range
2.5
IO
Maximum output current
400
6
IO(SD)
Shutdown supply current
BATT_COVER = GND
0.1
1
µA
rDS(on)
P-channel MOSFET on-resistance
VI(CORE) = VGS = 3.6 V
275
530
mΩ
Ilkg(p)
P-channel leakage current
VDS = 6 V
0.1
1
µA
rDS(on)
N-channel MOSFET on-resistance
VI(CORE) = VGS = 3.6 V
275
500
mΩ
Ilkg(N)
N-channel leakage current
VDS = 6 V
IL
P-channel current limit
2.5 V < VI(CORE) < 6 V
fS
Oscillator frequency
0.1
1
µA
600
700
900
mA
1
1.25
1.5
MHz
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mA
7
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Electrical Characteristics (continued)
VI(MAIN) = VI(CORE) = VCC = VI(LDO1) = VI(LDO2) = 3.6 V, TA = –40°C to 85°C, typical values are at TA = 25°C battery charger
specifications are valid in the range 0°C < TA < 85°C unless otherwise noted
PARAMETER
TEST CONDITIONS
MIN
TYP
MAX
UNIT
VCORE STEP-DOWN CONVERTER (continued)
0.85 V
1.0 V
1.1 V
VO(CORE)
Fixed output voltage
1.2 V
1.3 V
1.4 V
1.5 V
1.8 V
R(VCORE)
VI(CORE) = 2.5 V to 6 V;
IO = 0 mA, CO = 22 µF
0%
3%
VI(CORE) = 2.5 V to 6 V;
0 mA ≤ IO ≤ 400 mA, CO = 22 µF
3%
3%
VI(CORE) = 2.5 V to 6 V;
IO = 0 mA, CO = 22 µF
0%
3%
VI(CORE) = 2.5 V to 6 V;
0 mA ≤ IO ≤ 400 mA, CO = 22 µF
3%
3%
VI(CORE) = 2.5 V to 6 V;
IO= 0 mA, CO = 22 µF
0%
3%
VI(CORE) = 2.5 V to 6 V;
0 mA ≤ IO ≤ 400 mA, CO = 22 µF
3%
3%
VI(CORE) = 2.5 V to 0 V; IO = 0 mA
0%
3%
VI(CORE) = 2.5 V to 6 V; 0 mA ≤ IO≤ 400 mA
3%
3%
VI(CORE) = 2.5 V to 6 V; IO= 0 mA
0%
3%
VI(CORE) = 2.5 V to 6 V;
0 mA ≤ IO ≤ 400 mA
3%
3%
VI(CORE) = 2.5 V to 6 V; IO= 0 mA
0%
3%
VI(CORE) = 2.5 V to 6 V;
0 mA ≤ IO≤ 400 mA
3%
3%
VI(CORE) = 2.5 V to 6 V; IO = 0 mA
0%
3%
VI(CORE) = 2.5 V to 6 V;
0 mA ≤ IO ≤ 400 mA
3%
3%
VI(CORE) = 2.5 V to 6 V; IO= 0 mA
0%
3%
VI(CORE) = 2.5 V to 6 V;
0 mA ≤ IO ≤ 400 mA
3%
3%
Line regulation
VI(CORE) = VO(MAIN) + 0.5 V
(min. 2.5 V) to 6 V, IO = 10 mA
Load regulation
IO = 10 mA to 400 mA
1
%/V
0.002
VCORE discharge resistance
%/mA
Ω
400
VLDO1 and VLDO2 LOW-DROPOUT REGULATORS
LD01
1.8
6.5
LD02
1.8
VCC
VI
Input voltage range
VO
LDO1 output voltage range
0.9
Vref
Reference voltage
485
VO
LDO2 output voltage range
VINLDO1
500
1.8
Full-power mode
200
Low-power mode
30
IO
Maximum output current
I(SC)
LDO1 and LDO2 short-circuit current
limit
VLDO1 = GND, VLDO2 = GND
Dropout voltage
IO = 200 mA, VINLDO1,2 = 1.8 V
V
515
mV
3.3
V
mA
Total accuracy
650
mA
300
mV
±3%
Line regulation
VINLDO1,2 = VLDO1,2 + 0.5 V
(min. 2.5 V) to 6.5 V, IO = 10 mA
Load regulation
IO = 10 mA to 200 mA
Regulation time
V
0.75
%/V
0.011
%/mA
Load change from 10% to 90%
0.1
Low-power mode
0.1
ms
I(QFP)
LDO quiescent current (each LDO)
Full-power mode
16
30
µA
I(QLPM)
LDO quiescent current (each LDO)
Low-power mode
12
18
µA
IO(SD)
LDO shutdown current (each LDO)
0.1
1
µA
Ilkg(FB)
Leakage current feedback
0.01
0.1
µA
8
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6.6 Electrical Characteristics: Battery Charger
VO(REG) + V(DO-MAX) ≤ V(CHG) = V(AC) or V(USB), I(TERM) < IO ≤ 1 A, 0°C < TA < 85°C
PARAMETER
TEST CONDITIONS
MIN
TYP
MAX
UNIT
VLDO1 and VLDO2 LOW-DROPOUT REGULATORS (continued)
V(AC)
Input voltage range
4.5
6.5
V(USB)
Input voltage range
4.35
5.25
ICC(VCHG)
Supply current
V(CHG) > V(CHG)min
ICC(SLP)
Sleep current
Sum of currents into VBAT pin,
V(CHG) < V(SLP-ENTRY),
0°C ≤ TJ ≤ 85°C
ICC(STBY)
Standby current
V
1.2
2
mA
2
5
µA
200
400
Current into USB pin
45
Current into AC pin
V
µA
VOLTAGE REGULATOR
VO
VDO
Output voltage
V(CHG)min ≥ 4.5 V
4.20
4.25
Dropout voltage (V(AC) – VBAT)
VO(REG) + V(DO-MAX) ≤ V(CHG),
IO(OUT) = 1 A
500
800
Dropout voltage (V(USB) – VBAT)
VO(REG) + V(DO-MAX)≤ V(CHG),
IO(OUT) = 0.5 A
300
500
Dropout voltage (V(USB) – VBAT)
VO(REG) + V(DO-MAX) ≤ V(CHG),
IO(OUT) = 0.1 A
100
150
4.15
V
mV
CURRENT REGULATION
Output current range for ac operation (1)
IO(AC)
VCHG ≥ 4.5 V, VI(OUT) > V(LOWV),
V(AC) - VI(BAT)> V(DO-MAX)
Output current set voltage for ac operation
at ISET pin. 100% output current I2C
register CHGCONFIG = 11
75% output current I2C register
CHGCONFIG = 10
V(SET)
2.50
2.55
1.83
1.91
1.99
1.23
1.31
1.39
0.76
0.81
0.86
100 mA < IO < 1000 mA
310
330
350
10 mA < IO < 100 mA
300
340
380
32% output current I2C register
CHGCONFIG = 00
KSET
IO(USB)
R(ISET)
Output current set factor for ac operation
Output current range for USB operation
1000
2.45
Vmin ≥ 4.5 V, VI(BAT) > V(LOWV), V(AC) VI(BAT) > V(DO-MAX)
50% output current I2C register
CHGCONFIG = 01
100
mA
V
V(CHG)min ≥ 4.35 V, VI(BAT) > V(LOWV),
V(USB) - VI(BAT) > V(DO-MAX),
I2C register CHGCONFIG = 0
80
100
V(CHG)min ≥ 4.5 V, VI(BAT) > V(LOWV),
VUSB - VI(BAT) > V(DO-MAX),
I2C register CHGCONFIG = 1
400
500
825
8250
Ω
3.2
V
100
mA
270
mV
mA
Resistor range at ISET pin
PRECHARGE CURRENT REGULATION, SHORT-CIRCUIT CURRENT, AND BATTERY DETECTION CURRENT
V(LOWV)
Precharge to fast-charge transition
threshold,
voltage on VBAT pin.
I(PRECHG)
Precharge current
I(DETECT)
Battery detection current
V(SET-PRECHG)
Voltage at ISET pin
(2)
2.8
0 ≤ VI(OUT) < V(LOWV), t < t(PRECHG)
10
3
200
0 ≤ VI(OUT) < V(LOWV), t < t(PRECHG)
240
255
µA
KSET × V
(SET)
R
(ISET)
KSET × V
(SET_PRECHG)
I
=
(PRECHG)
R
(ISET)
I
(1)
(2)
V(CHG) min ≥ 4.5 V
O(AC) =
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Electrical Characteristics: Battery Charger (continued)
VO(REG) + V(DO-MAX) ≤ V(CHG) = V(AC) or V(USB), I(TERM) < IO ≤ 1 A, 0°C < TA < 85°C
PARAMETER
TEST CONDITIONS
MIN
TYP
MAX
UNIT
100
mA
CHARGE TAPER AND TERMINATION DETECTION
(3)
I(TAPER)
Taper current detect range
VI(OUT) > V(RCH), t < t(TAPER)
10
V(SET_TAPER)
Voltage at ISET pin for charge TAPER
detection
VI(OUT) > V(RCH), t < t(TAPER)
235
250
265
mV
V(SET_TERM)
Voltage at ISET pin for charger termination
detection (4)
VI(OUT) > V(RCH)
11
18
25
mV
TEMPERATURE COMPARATOR
V(LTF)
Low (cold) temperature threshold
2.475
2.50
2.525
V(HTF)
High (hot) temperature threshold
0.485
0.5
0.515
V
V
I(TS)
TS current source
95
102
110
µA
VO(REG) –
0.115
VO(REG) –
0.1
VO(REG) –
0.085
V
V(CHG)≤
VI(OUT)
+150 mV
V
BATTERY RECHARGE THRESHOLD
V(RCH)
V(CHG)min ≥ 4.5 V
Recharge threshold
SLEEP AND STANDBY
V(SLP-ENTRY)
Sleep-mode entry threshold,
PG output = high
2.3 V ≤ VI(OUT) ≤ VO(REG)
V(SLP_EXIT)
Sleep-mode exit threshold,
PG output = low
2.3 V ≤ VI(OUT)≤ VO(REG)
V(CHG) ≥
VI(OUT) +
250 mV
V
CHARGER POWER-ON-RESET, UVLO, AND V(IN) RAMP RATE
V(CHGUVLO)
Charger undervoltage lockout
V(CHG) decreasing
2.27
Hysteresis
V(CHGOVLO)
2.5
27
Charger overvoltage lockout
6.5
2.75
V
mV
V
CHARGER OVERTEMPERATURE SUSPEND
T(suspend)
Temperature at which charger suspends
operation
T(hyst)
Hysteresis of suspend threshold
(4)
KSET × V
(SET_TAPER)
R
(ISET)
KSET × V
(SET_TERM)
=
I
(TERM)
R
(ISET)
10
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I
(3)
145
°C
20
°C
(TAPER) =
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Electrical Characteristics: Battery Charger (continued)
VO(REG) + V(DO-MAX) ≤ V(CHG) = V(AC) or V(USB), I(TERM) < IO ≤ 1 A, 0°C < TA < 85°C
PARAMETER
TEST CONDITIONS
MIN
TYP
MAX
UNIT
V
LOGIC SIGNALS DEFMAIN, DEFCORE, PS_SEQ, IFLSB
VIH
High-level input voltage
IIH = 20 µA
VCC – 0.5
VCC
VIL
Low-level input voltage
IIL = 10 µA
0
0.4
V
IIB
Input bias current
1
µA
0.3
V
0.01
LOGIC SIGNALS GPIO1-4
VOL
Low-level output voltage
IOL = 1 mA, configured as an
open-drain output
VOH
High-level output voltage
Configured as an open-drain output
VIL
Low -level input voltage
VIH
High-level input voltage
II
Input leakage current
rDS(on)
Internal NMOS
6
V
0
0.8
V
2
(5)
V
1
µA
VOL = 0.3 V
VCC
Ω
150
LOGIC SIGNALS PG, LED2
VOL
Low-level output voltage
VOH
High-level output voltage
V(PG)
IOL = 20 mA
0.5
V
6
V
V(BAT) + xx
mV
PG threshold voltage USB and AC
V
VIBRATOR DRIVER VIB
VOL
Low-level output voltage
VOH
High-level output voltage
IOL = 100 mA
0.3
0.5
V
6
V
THERMAL SHUTDOWN
T(SD)
Thermal shutdown
Increasing junction temperature
160
°C
UNDERVOLTAGE LOCKOUT
Undervoltage lockout
threshold.
The default value for
UVLO is 2.75 V
V(UVLO)
V(UVLO_HYST)
V(UVLO) 2.5 V
-3%
3%
V(UVLO) 2.75 V
-3%
3%
-3%
3%
V(UVLO) 3.0 V
Filter resistor = 10R in series
with VCC, VCC decreasing
V(UVLO) 3.25 V
-3%
UVLO comparator hysteresis
VCC rising
Decreasing rail voltage
Increasing rail voltage
3%
350
400
450
VMAIN, VCORE, VLDO1, VLDO2
decreasing
–12%
–10%
–8%
VMAIN, VCORE, VLDO1, VLDO2
increasing
–7%
–5%
–3%
mV
POWER GOOD
(5)
If the input voltage is higher than VCC an additional current flows, limited by an internal 10-kΩ resistor.
6.7 Dissipation Ratings
See
(1)
AMBIENT
TEMPERATURE
(1)
(2)
MAX POWER DISSIPATION
FOR Tj = 125°C (2)
25°C
3W
55°C
2.1 W
DERATING FACTOR
ABOVE TA= 55°C
30 mW/°C
The TPS65014 is housed in a 48-pin QFN package with exposed leadframe on the underside. This 7-mm × 7-mm package exhibits a
thermal impedance (junction-to-ambient) of 33 K/W when mounted on a JEDEC high-k board.
Consideration needs to be given to the maximum charge current when the assembled application board exhibits a thermal impedance
which differs significantly from the JEDEC high-k board.
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6.8 Serial Interface Timing Requirements
MIN
Clock frequency, fMAX
Clock high time, twH(HIGH)
Clock low time, twL(LOW)
MAX
UNIT
400
kHz
600
ns
1300
ns
DATA and CLK rise time, tR
300
ns
DATA and CLK fall time, tF
300
ns
Hold time (repeated) START condition (after this period the first clock pulse is generated), th(STA)
600
ns
Setup time for repeated START condition, th(DATA)
600
ns
0
ns
100
ns
600
ns
1300
ns
Data input hold time, th(DATA)
Data input setup time, tsu(DATA)
STOP condition setup time, tsu(STO)
Bus free time, t(BUF)
6.9 Switching Characteristics
over operating free-air temperature range (unless otherwise noted)
PARAMETER
TEST CONDITIONS
MIN
TYP
MAX
UNIT
38
56
77
ms
1.68
2.4
3.2
ms
CONTROL SIGNALS: PB_ONOFF, HOT_RESET, BATT_COVER
t(glitch)
Deglitch time at all 3 pins
t(batt_cover)
Delay after t(glitch) (PWRFAIL goes
low) before supplies are disabled
when BATT_COVER goes low.
CONTROL SIGNALS: MPU_RESET, PWRFAIL, RESPWRON, INT, SDAT (OUTPUT)
td(mpu_nreset)
Duration of low pulse at
MPU_RESET
td(nrespwron)
Duration of low pulse at
RESPWRON after VMAIN is in
regulation
td(uvlo)
td(overtemp)
100
µs
TPOR = 0
80
100
120
TPOR = 1
800
1000
1200
Time between UVLO going active
(PWRFAIL going low) and supplies
being disabled
1.68
2.4
3.2
ms
Time between chip
overtemperature condition being
recognized (PWRFAIL going low)
and supplies being disabled
1.68
2.4
3.2
ms
ms
PRECHARGE CURRENT REGULATION, SHORT-CIRCUIT CURRENT, AND BATTERY DETECTION CURRENT
Deglitch time
V(CHG) min ≥ 4.5 V, VI(OUT)
decreasing below threshold; 100-ns
fall time, 10-mV overdrive
8.8
23
60
ms
CHARGE TAPER AND TERMINATION DETECTION
Deglitch time for I(TAPER)
V(CHG) min ≥ 4.5V, charging current
increasing or decreasing above and
below; 100-ns fall time, 10-mV
overdrive
8.8
23
60
ms
Deglitch time for I(TERM)
V(CHG) min ≥ 4.5 V, charging current
decreasing below;100-ns fall time,
10-mV overdrive
8.8
23
60
ms
8.8
23
60
ms
8.8
23
60
ms
TEMPERATURE COMPARATOR
Deglitch time for temperature fault
BATTERY RECHARGE THRESHOLD
Deglitch time
12
V(CHG)min ≥ 4.5 V, VI(OUT)
decreasing below threshold; 100-ns
fall time,
10-mV overdrive
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Switching Characteristics (continued)
over operating free-air temperature range (unless otherwise noted)
PARAMETER
TEST CONDITIONS
MIN
TYP
MAX
UNIT
TIMERS
t(PRECHG)
Precharge timer
V(CHG)min ≥ 4.5 V
1500
1800
2160
s
t(TAPER)
Taper timer
V(CHG)min ≥ 4.5 V
1500
1800
2160
s
t(CHG)
Charge timer
V(CHG)min ≥ 4.5 V
15000
18000
21600
s
8.8
23
60
SLEEP AND STANDBY
Deglitch time for sleep mode entry
and exit
t(USB_DEL)
AC or USB decreasing below
threshold; 100-ns fall time, 10-mV
overdrive
Delay between valid USB voltage
being applied and start of charging
process from USB
ms
5
ms
6.10 Typical Characteristics
Table 1. Table of Graphs
FIGURE
Efficiency
vs Output current
Figure 1,
Figure 2
Quiescent current
vs Input voltage
Figure 3
Switching frequency
vs Temperature
Figure 4
LDO1 Output voltage
vs Output current
Figure 5Figure 8
LDO2 Output voltage
vs Output current
Figure 9
Line transient response (main)
Figure 9
Line transient response (core)
Figure 10
Line transient response (LDO1)
Figure 11
Line transient response (LDO2)
Figure 12
Load transient response (main)
Figure 13
Load transient response (core)
Figure 14
Load transient response (LDO1)
Figure 15
Load transient response (LDO2)
Figure 16
Output voltage ripple (PFM)
Figure 17
Output voltage ripple (PWM)
Figure 18
Start-up timing
Figure 19
Dropout voltage
vs Output current
Figure 20,
Figure 21
PSRR (LDO1 and LDO2)
vs Frequency
Figure 22
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100
100
Main:
VI = 3.8 V,
TA = 25°C,
PFWM = 1
90
80
90
80
70
VO = 3.3 V
60
Efficiency − %
70
Efficiency − %
VO = 1.6 V
Core:
VI = 3.8 V,
TA = 25°C,
PFWM = 1
VO = 2.5 V
50
40
50
30
20
20
10
10
0.10
1
10
100
1k
VO = 0.85 V
40
30
0
0.01
VO = 1.2 V
60
0
0.01
10 k
IO − Output Current − mA
0.10
1
10
Figure 1. Efficiency vs Output Current
1.230
60
VI = 4.2 V
1.225
TA = 85°C
f - Switching Frequency - MHz
Quiescent Current - mA
VCC, + Vcore,+ Vmain
50
40
TA = -40°C
TA = 25°C
30
20
10
0
2.5
3
3.5
4
4.5
5
VI - Input Voltage - V
5.5
3.401
1.220
1.215
1.210
1.205
1.200
Figure 4. Switching Frequency vs Temperature
1.652
TA = 25°C
3.381
1.642
3.361
VO − LDO1 Output Voltage − V
VO − LDO1 Output Voltage − V
TA = 25°C
3.341
VI = 3.3 V
1.632
VI = 6 V
VI = 3.6 V
1.622
VI = 5 V
3.321
1.612
3.301
1.602
3.281
VI = 4.2 V
1.592
1.582
VI = 4.2 V
3.241
1.572
VI = 3.6 V
3.221
10
100
1k
10 k
VI = 5 V
1.562
VI = 3.3 V
100 k
1.552
0
IO Output Current − mA
VI = 6 V
10
100
1k
10 k
100 k
IO Output Current − mA
Figure 5. LD01 Output Voltage vs Output Current
14
VI = 3.3 V
1.195
-40 -30 -20 -10 0 10 20 30 40 50 60 70 80 85
TA - Free-Air Temperature - °C
6
Figure 3. Quiescent Current vs Input Voltage
3.201
0
1k
Figure 2. Efficiency vs Output Current
70
3.261
100
IO − Output Current − mA
Figure 6. LD01 Output Voltage vs Output Current
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3.1
VO = 2.8 V
VO = 3 V
2.9
2.80
VO - LDO2 Output Voltage - V
2.70
VO = 2.5 V
2.60
2.50
2.40
2.30
2.20
VI LDO1 = 3.8 V
TA = 25°C
2.10
2
0.01
0.1
10
100
1
IO Output Current - mA
1000
2.5
VOLDO2 = 3.8 V
TA = 25°C
2.3
2.1
1.9
1.7
0.01
VO = 1.8 V
0.1
1
10
100
1000
IO - Output Current - mA
Figure 8. LDO2 Output Voltage vs Output Current
VI = 3.6 V to 4.2 V, VO = 1.6 V,
IL = 400 mA, TA = 25°C
500 mV/div
Figure 7. LDO1 Output Voltage vs Output Current
CH1 = VI
2.7
CH1 = VI
500 mV/div
VO - LDO1 Output Voltage - V
3
2.90
CH2 = VO
50 mV/div
500 µs/div
500 µs/div
Figure 10. Line Transient Response (Core)
VI = 3.3 to 3.8 V, VO = 1.8 V,
RL = 100 mA to 1000 mA,
TA = 25°C
VI = 3.3 to 3.8 V, VO = 2.8 V,
IL = 100 mA, TA = 25°C
CH1 = VI
500 mV/div
CH1 = VI
CH2 = VO
10 mV/div
CH2 = VO
500 µs/div
500 mV/div
Figure 9. Line Transient Response (Main)
10 mV/div
CH2 = VO
50 mV/div
VI = 3.6 to 4.2 V, VO = 3.3 V,
IL = 500 mA TA = 25°C
500 µs/div
Figure 11. Line Transient Response (LDO1)
Figure 12. Line Transient Response (LDO2)
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500 mA/div
VI = 3.8 V, VO = 1.6 V,
IL = 40 mA to 400 mA,
TA = 25°C
VI = 3.8 V, VO = 3.3 V,
IL = 100 mA to 1000 mA,
TA = 25°C
CH2 = VO
200 mV/div
CH2 = VO
100 µs/div
100 µs/div
200 mA/div
CH4 = IO
100 µs/div
100 µs/div
Figure 16. Load Transient Response (LDO2)
CH3 = Iinductor Main
CH4 = Iinductor Core
20 mV/div
CH2 = VO Core
100 mA/div
50 mV/div
200 mA/div
CH1 = VO Main
CH1 = VO Main
5 ms/div
VI = 3.8 V, TA = 25°C
VO Main = 3.3 V IL Main = 100 mA,
VO Core = 1.6 V, IL Core = 40 mA
CH2 = VO Core
CH4 = Iinductor Core
500 ns/div
VI = 3.8 V, TA = 25°C
VO Main = 3.3 V RL Main = 500 mA,
VO Core = 1.6 V, RL Core = 400 mA
Figure 17. Output Ripple (PFM)
16
100 mA/div
20 mV/div
Figure 15. Load Transient Response (LDO1)
50 mV/div
100 mV/div
CH2 = VO
100 mA/div
VI = 3.8 V, VI LDO = 3.3 V,
VO = 2.8 V, IL = 2 mA to 180 mA,
TA = 25°C
CH2 =VO
100 mV/div
CH4 = IO
VI = 3.8 V, VI LDO = 3.3 V,
VO = 1.8 V, IL = 2 mA to 180 mA,
TA = 25°C
200 mA/div
Figure 14. Load Transient Response (Core)
Figure 13. Load Transient Response (Main)
CH3 = Iinductor Main
CH4 = IO
100 mV/div
CH4 = IO
500 mA/div
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Figure 18. Output Ripple (PWM)
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0.25
LDO1 VO = 2.5 V
CH1 = VO Main
0.2
Dropout Voltage - V
CH3 = Icoil Main
CH2 = VO Core
CH4 = Icoil Core
LDO2 VO = 1.8 V
LDO2 VO = 3 V
0.15
0.1
LDO1 VO = 2.8 V
0.05
Normal Mode
TA = 25°C
0
0
500 ms/div
Figure 19. Start-Up Timing
80
0.045
70
LDO2 VO = 1.8 V
60
LDOIN = 3.3 V
LDO Output Current 10 mA
LDO2 VO = 3 V
0.035
0.03
LDO1 VO = 2.8 V
0.025
50
PSRR - dB
Dropout Voltage - V
Figure 20. Dropout Voltage vs Output Current
0.05
0.04
20 40 60 80 100 120 140 160 180 200
IO - Output Current - mA
VI = 3.8 V, VO Main = 3.3 V,
RL Main = 1 A, V O Core = 1.6 V,
RL Core = 400 mA, TA = 25°C
0.02
40
30
LDO1 VO = 2.5 V
0.015
20
0.01
Low Power Mode
TA = 25°C
0.005
10
0
0
3
6
LDO Output Current 200 mA
0
1k
9 12 15 18 21 24 27 30
IO - Output Current - mA
Figure 21. Dropout Voltage vs Output Current
10k
100k
1M
10M
f - Frequency - Hz
Figure 22. PSRR (LDO1, LDO2) vs Frequency
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7 Detailed Description
7.1 Overview
The TPS65014 has a highly integrated and flexible Li-Ion linear charger and system power management. It offers
an integrated USB port and AC-adapter supply management with autonomous power-source selection, power
FET and current sensor, high accuracy current and voltage regulation, charge status, and charge termination.
The TPS65014 charger automatically selects the USB port or the AC adapter as the power source for the
system. In the USB configuration, the host can increase the charge current from the default value of maximum
100 mA to 500 mA through the interface. In the AC adapter configuration, an external resistor sets the maximum
value of charge current.
The battery is charged in three phases: conditioning, constant current, and constant voltage. Charge is normally
terminated based on minimum current. An internal charge timer provides a safety backup for charge termination.
The TPS65014 automatically restarts the charge if the battery voltage falls below an internal threshold. The
charger automatically enters sleep mode when both supplies are removed.
The serial interface can be used for dynamic voltage scaling, for collecting information on and controlling the
battery charger status, for optionally controlling 2-LED driver outputs, a vibrator driver, masking interrupts, or for
disabling, enabling, and setting the LDO output voltages. The interface is compatible with the fast- and standardmode I2C specification, thus allowing transfers up to 400 kHz.
18
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7.2 Functional Block Diagram
MAX(AC,USB,VBAT)
AC
VBAT
USB
PG
Linear Charge Controller
ISET
TS
SCLK
SDAT
AGND2
Serial
Interface
Thermal
Shutdown
IFLSB
VINMAIN
PS_SEQ
LOW_PWR
PB_ONOFF
BATT_COVER
HOT_RESET
TPOR
VMAIN
Step-Down
Converter
Control
RESPWRON
MPU_RESET
VCC
AGND3
VINCORE
INT
PWRFAIL
GPIO1
GPIO2
GPIO3
GPIO4
L1
VMAIN
DEFMAIN
PGND1
L2
UVLO
VREF
OSC
VCORE
VCORE
Step-Down
Converter
DEFCORE
PGND2
GPIOs
VINLDO1
VIB
VLDO1
200-mA LDO
VLDO1
VFB_LDO1
AGND1
LED2
VINLDO2
VLDO2
VLDO2
200-mA LDO
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7.3 Feature Description
7.3.1 Step-Down Converters, VMAIN and VCORE
The TPS65014 incorporates two synchronous step-down converters operating typically at 1.25-MHz fixed
frequency pulse width modulation (PWM) at moderate to heavy load currents. At light load currents, the
converters automatically enter power-save mode and operate with pulse frequency modulation (PFM). The main
converter is capable of delivering 1-A output current and the core converter is capable of delivering 400 mA.
The converter output voltages are programmed through the VDCDC1 and VDCDC2 registers in the serial
interface. The main converter defaults to 3-V or 3.3-V output voltage depending on the DEFMAIN configuration
pin, if DEFMAIN is tied to ground, the default is 3 V; if it is tied to VCC, the default is 3.3 V. The core converter
defaults to either 1.5 V or 1.8 V, depending on whether the DEFCORE configuration pin is tied to GND or to VCC,
respectively. Both the main and core output voltages can subsequently be reprogrammed after start-up through
the serial interface. In addition, the LOW_PWR pin can be used either to lower the core voltage to a value
defined in the VDCDC2 register when the application processor is in deep sleep mode, or to disable the core
converter. An active signal at LOW_PWR is ignored if the ENABLE_LP bit is not set in the VDCDC1 register.
The step-down converter outputs (when enabled) are monitored by power-good comparators, the outputs of
which are available through the serial interface. The outputs of the DC-DC converters can be optionally
discharged when the DC-DC converters are disabled.
During PWM operation, the converters use a fast response voltage-mode controller scheme with input voltage
feed-forward to achieve good line and load regulation, allowing the use of small ceramic input and output
capacitors. At the beginning of each clock cycle, initiated by the clock signal, the P-channel MOSFET switch is
turned on, and the inductor current ramps up until the comparator trips and the control logic turns off the switch.
The current limit comparator also turns off the switch if the current limit of the P-channel switch is exceeded.
After the dead time preventing current shoot through, the N-channel MOSFET rectifier is turned on, and the
inductor current ramps down. The next cycle is initiated by the clock signal, again turning off the N-channel
rectifier and turning on the P-channel switch.
The error amplifier, together with the input voltage, determines the rise time of the saw-tooth generator, and
therefore any change in input voltage or output voltage directly controls the duty cycle of the converter, giving a
good line and load transient regulation.
The two DC-DC converters operate synchronized to each other, with the MAIN converter as the master. A 270°
phase shift between the MAIN switch turnon and the CORE switch turnon decreases the input RMS current, and
smaller input capacitors can be used. This is optimized for a typical application where the MAIN converter
regulates a Li-ion battery voltage of 3.7 V to 3.3 V and the CORE from 3.7 V to 1.5 V.
7.3.1.1 Forced PWM
The core and main converters are forced into PWM mode by setting bit 7 in the VDCDC1 register. This feature is
used to minimize ripple on the output voltages.
7.3.1.2 Dynamic Voltage Positioning
As described in the power-save mode operation sections and as detailed in Figure 11, the output voltage is
typically 1.2% above the nominal output voltage at light load currents, as the device is in power-save mode. This
gives additional headroom for the voltage drop during a load transient from light load to full load. During a load
transient from full load to light load, the voltage overshoot is also minimized due to active regulation turning on
the N-channel rectifier switch.
7.3.1.3 Soft-Start
Both converters have an internal soft-start circuit that limits the inrush current during start-up. The soft start is
implemented as a digital circuit, increasing the switch current in 4 steps up to the typical maximum switch current
limit of 700 mA (core) and 1.75 A (main). Therefore, the start-up time mainly depends on the output capacitor
and load current.
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Feature Description (continued)
7.3.1.4 100% Duty Cycle Low Dropout Operation
The TPS65014 converters offer a low input to output voltage difference while maintaining operation with the use
of the 100% duty cycle mode. In this mode, the P-channel switch is constantly turned on. This is particularly
useful in battery-powered applications to achieve longest operation time by taking full advantage of the whole
battery voltage range. The minimum input voltage to maintain regulation depends on the load current and output
voltage and is calculated in Equation 1:
V
I(min)
+V
O(max)
)I
O(max)
ǒrDS(on) max ) RLǓ
where
•
•
•
•
IO(max) = maximum output current plus inductor ripple current
rDS(on)max = maximum P-channel switch rDSon
RL = DC resistance of the inductor
VO(max) = nominal output voltage plus maximum output voltage tolerance
(1)
7.3.1.5 Active Discharge When Disabled
When the CORE and MAIN converters are disabled, due to an UVLO, BATT_COVER, or OVERTEMP condition,
it is possible to actively pull down the outputs. This feature is disabled per default and is individually enabled
through the VDCDC1 and VDCDC2 registers in the serial interface. When this feature is enabled, the core and
main outputs are discharged by a 400-Ω (typical) load.
7.3.1.6 Power-Good Monitoring
Both the MAIN and CORE converters have power-good comparators. Each comparator indicates when the
relevant output voltage has dropped 10% below its target value, with 5% hysteresis. The outputs of these
comparators are available in the REGSTATUS register through the serial interface. A maskable interrupt is
generated when any voltage rail drops below the 10% threshold. The comparators are disabled when the
converters are disabled. The status of the power-good comparator for VMAIN is used to generate the
RESPWRON signal.
7.3.1.7 Overtemperature Shutdown
The MAIN and CORE converters are automatically shut down if the temperature exceeds the trip point (see
Electrical Characteristics). This detection is only active if the converters are in PWM mode, either by setting
FPWM = 1, or if the output current is high enough that the device runs in PWM mode automatically.
7.3.2 Low-Dropout Voltage Regulators
The low-dropout voltage regulators are designed to operate with low value ceramic input and output capacitors.
They operate with input voltages down to 1.8 V. The LDOs offer a maximum dropout voltage of 300 mV at rated
output current. Each LDO has a current limit feature. Both LDOs are enabled per default; both LDOs can be
disabled or programmed through the serial interface using the VREGS1 register. The LDO outputs (when
enabled) are monitored by power-good comparators, the outputs of which are available through the serial
interface. The LDOs also have reverse conduction prevention when disabled. This allows the possibility to
connect external regulators in parallel in systems with a backup battery.
7.3.2.1 Power-Good Monitoring
Both the LDO1 and LDO2 linear regulators have power-good comparators. Each comparator indicates when the
relevant output voltage has dropped 10% below its target value, with 5% hysteresis. The outputs of these
comparators are available in the REGSTATUS register through the serial interface. An interrupt is generated
when any voltage rail drops below the 10% threshold. The LDO2 comparator is disabled when LDO2 is disabled.
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Feature Description (continued)
7.3.2.2 Enabling and Sequencing
Enabling and sequencing of the DC-DC converters and LDOs are described in the power-up sequencing section.
The OMAP1510 processor from Texas Instruments requires that the core power supply is enabled before the I/O
power supply, which means that the CORE converter should power up before the MAIN converter. This is
achieved by connecting PS_SEQ to GND.
7.3.3 Undervoltage Lockout
The undervoltage lockout circuit for the four regulators on TPS65014 prevents the device from malfunctioning at
low input voltages and from excessive discharge of the battery. Basically, it prevents the converter from turning
on the power switch or rectifier FET under undefined conditions. The undervoltage threshold voltage is set by
default to 2.75 V. After power up, the threshold voltage can be reprogrammed through the serial interface. The
undervoltage lockout comparator compares the voltage on the VCC pin with the UVLO threshold. When the VCC
voltage drops below this threshold, the TPS65014 sets the PWRFAIL pin low and after a time t(UVLO) disables the
voltage regulators in the sequence defined by PS_SEQ. The same procedure is followed when the TPS65014
detects that its junction temperature has exceeded the overtemperature threshold, typically 160°C, with a delay
t(overtemp). The TPS65014 automatically restarts when the UVLO (or overtemperature) condition is no longer
present.
The battery charger circuit has a separate UVLO circuit with a threshold of typically 2.5 V, which is compared
with the voltage on AC and USB supply pins.
7.3.4 Power-Up Sequencing
The TPS65014 power-up sequencing is designed to allow the maximum flexibility without generating excessive
logistical or system complexity. The relevant control pins are described in Table 2.
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Feature Description (continued)
Table 2. Control Pins
PIN NAME
INPUT/OUTPUT
FUNCTION
PS_SEQ
I
Input signal indicating power-up and power-down sequence of the switching converters. PS_SEQ = 0
forces the core regulator to ramp up first and down last. PS_SEQ = 1 forces the main regulator to ramp up
first and down last.
DEFCORE
I
Defines the default voltage of the VCORE switching converter. DEFCORE = 0 defaults VCORE to 1.5 V,
DEFCORE = VCC defaults VCORE to 1.8 V.
DEFMAIN
I
Defines the default voltage of the VMAIN switching converter. DEFMAIN = 0 defaults VMAIN to 3 V,
DEFMAIN = VCC defaults VMAIN to 3.3 V.
I
The LOW_PWR pin is used to lower VCORE to the preset voltage in the VDCDC2 register when the
processor is in deep sleep mode. Alternatively, VCORE can be disabled in low power mode if the
LP_COREOFF bit is set in the VDCDC2 register. LOW_PWR is ignored if the ENABLE LP bit is not set in
the VDCDC1 register. The TPS65014 uses the rising edge of the internal signal formed by a logical AND
of LOW_PWR and ENABLE LP to enter low power mode. TPS65014 is forced out of low power mode by
deasserting LOW_PWR, by resetting ENABLE LP to 0, by activating the PB_ONOFF pin or by activating
the HOT_RESET pin. There are two ways to get the device back into low power mode: a) toggle the
LOW_PWR pin, or b) toggle the low power bit when the LOW_PWR pin is held high. The LOW_PWR pin
is also used to set the TPS65014 into WAIT mode. If USB or AC is present, the AUA bit (CHCONFIG)
must be set to enter the WAIT mode, see Figure 23.
PB_ONOFF
I
PB_ONOFF can be used to exit the low power mode and return the core voltage to the value before low
power mode was entered. If PB_ONOFF is used to exit the low power mode, then the low power mode
can be reentered by toggling the LOW_PWR pin or by toggling the low power bit when the LOW_PWR pin
is held high. A 1-MΩ pulldown resistor is integrated in TPS65014. PB_ONOFF is internally de-bounced by
the TPS65014. A maskable interrupt is generated when PB_ONOFF is activated.
HOT_RESET
I
The HOT_RESET pin has a similar functionality to the PB_ONOFF pin. In addition, it generates a reset
(MPU_RESET) for the MPU when the VCORE voltage is in regulation. HOT_RESET does not alter any
TPS65014 settings unless low power mode was active in which case it is exited. A 1-MΩ pullup resistor to
VCC is integrated in TPS65014. HOT_RESET is internally de-bounced by the TPS65014.
BATT_COVER
I
The BATT_COVER pin is used as an early warning that the main battery is about to be removed.
BATT_COVER = VCC indicates that the cover is in place, BATT_COVER = 0 indicates that the cover is not
in place. TPS65014 generates a maskable interrupt when the BATT_COVER pin goes low. PWRFAIL is
also held low when BATT_COVER goes low. This feature may be disabled by tying BATT_COVER
permanently to VCC. The TPS65014 shuts down the main and the core converter and sets the LDOs into
low power mode. A 2-MΩ pulldown resistor is integrated in the TPS65014 at the BATT_COVER pin.
BATT_COVER is internally de-bounced by the TPS65014.
RESPWRON
O
RESPWRON is held low while the switching converters (and any LDOs defined as default on) are starting
up. It is determined by the state of MAIN's output voltage; when the voltage is higher than the power-good
comparator threshold; then RESPWRON is high when VMAIN is low; then RESPWRON is low.
RESPWRON is held low for tn(RESPWRON) seconds after VMAIN has settled.
MPU_RESET
O
MPU_RESET can be used to reset the processor if the user activates the HOT_RESET button. The
MPU_RESET output is active for t(MPU_nRESET) sec. It also forces TPS65014 to leave low power mode.
MPU_RESET is also held low as long as RESPWRON is held low.
PWRFAIL
O
PWRFAIL indicates when VCC < V(UVLO), when the TPS65014 is about to shut down due to an internal
overtemperature condition or when BATT_COVER is low. PWRFAIL is also held low as long as
RESPWRON is held low.
TPOR
I
TPOR is used to set the delay time for the RESPWRON reset signal.
TPOR = 0 sets the delay time to 100 ms. TPOR = 1 sets the delay time to 1 s.
LOW_PWR
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Figure 23 shows the state diagram for TPS65014 power sequencing. The charger function is not shown in the
state diagram because this function is independent of these states.
Monitored Permanently
No
Power
AC and/or USB
Power Applied.
Main Battery Power
Applied
VMAIN
Voltage
Enabled and
Good?
Monitored Permanently
Yes
TPS65011
RESPWRON,
PWRFAIL, INT,
MPU_RESET Low.
Reset
RESPWRON Timer
Yes
VCC>UVOL,
TjUVLO ?
BATT_COVER
High ?
UVLO_TEMP
Timer Done ?
No
VCC>UVLO ?
BATT_COVER
High ?
Release
RESPWRON,
PWRFAIL, INT,
MPU_RESET
Yes
Yes
Value
PS_SEQ ?
1
0
Shutdown VCORE,
VMAIN + LDOs
According to
PS_SEQ
Yes
Boot VCORE
Converter + LDOs
Boot VMAIN
Converter + LDOs
Boot VCORE
Converter
Boot VCORE
Converter
LOW_PWR
De-asserted,
PB_ONOFF
Button Pressed
Processor Initiated
Shutdown ∗3
LOW_
POWER
Mode
LOW_PWR
Asserted ∗2
ON
HOT_RESET
Button Pressed
∗1: All registers are reset to their default values in WAIT Mode
∗2: ENABLE_LP bit, VDCDC1 Must be set.
If AC or USB power is present, AUA bit, CHGCONFIG must also be set.
Raise the low power pin to enter low power mode.
∗3: ENABLE_SUPPLY bit, VDCDC1 must be cleared.
ENABLE_LP bit, VDCDC1 must be set.
LDO2OFF/SLP and LDO1OFF/SLP must be set or LDOs and voltage
reference remain enabled and registers not reset.
If AC or USB power is present, AUA bit, CHGCONFIG must also be set.
Raise the low power pin to enter low power mode.
ENABLE_LP default: cleared
ENABLE_SUPPLY default: set
AUA default: cleared
LDO1OFF/SLP default: cleared
LDO2OFF/SLP default: cleared
No
Release
MPU_RESET
VCORE Voltage
Good ?
Yes
Yes
MPU_RESET
Timer Done ?
Set MPU_RESET
Low, Start
MPU_RESET Timer
No
Figure 23. TPS65014 Power-On State Diagram
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7.3.4.1 TPS65014 Power State Descriptions
7.3.4.1.1 State 1: No Power
No batteries are connected to the TPS65014. When main power is applied, the bandgap reference, LDOs, and
UVLO comparator start up. The RESPWRON, PWRFAIL, INT, and MPU_RESET signals are held low. When
BATT_COVER goes high (de-bounced internally by the TPS65014), indicating that the battery cover has been
put in place and if VCC > UVLO, the power supplies are ramped in the sequence defined by PS_SEQ.
RESPWRON, PWRFAIL, INT, and MPU_RESET are released when the RESPWRON timer has timed out after
tn(RESPWRON) seconds. If VCC remains valid and no OVERTEMP condition occurs, then the TPS65014 arrives in
State 2: ON. If VCC < UVLO, the TPS65014 keeps the bandgap reference and UVLO comparator active such
that when VCC>UVLO (during battery charge), the supplies are automatically activated.
7.3.4.1.2
State 2: ON
In this state, the TPS65014 is fired up and ready for operation. The switching converter output voltages can be
programmed. The LDOs can be disabled or programmed. The TPS65014 can exit this state due to an
overtemperature condition, an undervoltage condition at VCC, BATT_COVER going low, or by the processor
programming low power mode. State 2 is left temporarily if the user activates the HOT_RESET pin.
7.3.4.1.3
State 3: Low-Power Mode
This state is entered through the processor setting the ENABLE_LP bit in the serial interface and then raising the
LOW_PWR pin. The TPS65014 uses the rising edge of the internal signal formed by a logical AND of the
LOW_PWR and ENABLE LP signals to enter low power mode. The VMAIN switching converter remains active,
but the VCORE converter may be disabled in low power mode through the serial interface by setting the
LP_COREOFF bit in the VDCDC2 register. If left enabled, the VCORE voltage is set to the value predefined by
the CORELP0/1 bits in the VDCDC2 register. The LDO1OFF/nSLP and LDO2OFF/nSLP bits in the VREGS1
register determine whether the LDOs are turned off or put in a reduced power mode (transient speed-up circuitry
disabled in order to minimize quiescent current) in low power mode. All TPS65014 features remain addressable
through the serial interface. The TPS65014 can exit this state either due to an undervoltage condition at VCC,
due to BATT_COVER going low, due to an OVERTEMP condition, by the processor deasserting the
LOW_POWER pin, or by the user activating the HOT_RESET pin or the PB_ONOFF pin.
7.3.4.1.4
State 4: Shutdown
There are two scenarios for entering this state. The first is from State 1: No Power. As soon as main battery
power is applied, the device automatically enters the WAIT mode.
The second scenario occurs when the device is in ON mode and the processor initiates a shutdown by resetting
the ENABLE SUPPLY bit in the VDCDC1 register (ENABLE_LP must be high), and then raising the LOW_PWR
pin. When this happens, the power rails are ramped down in the predefined sequence, and all circuitry is then
disabled. In this state, the TPS65014 waits for the PB_ONOFF or HOT_RESET pin to be activated before
enabling any of the supply rails. When the PB_ONOFF or HOT_RESET pin is activated, the TPS65014 powers
up the supplies according to the same constraints as at the initial application of power. Complete shutdown is
only achieved by setting the LDO1OFF/nSLP and LDO2OFF/nSLP bits high in the VREGS1 register before
activating the shutdown.
In this case, the I2C interface is deactivated, and the registers are reset to their default value after leaving the
WAIT mode.
To enter the WAIT mode when USB or AC is present, set the AUA bit (CHCONFIG). The WAIT mode is
automatically left if bit 7 in register CHCONFIG is set to 0 (default), and a voltage is present at either the AC pin
or the USB pin in the appropriate range for charging, and the voltage at VCC is above the UVLO threshold. This
feature allows the converters to start up automatically if the device is plugged in for charging.
If all supplies are turned off in WAIT mode, the internal bandgap is switched off, and the internal registers are
reset to their default state when the device returns to ON mode.
Table 3 lists possible configurations in LOW POWER mode and WAIT mode.
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Table 3. TPS65014 Possible Configurations (1)
(1)
CONVERTER
MAIN
CORE
LDO1
LDO2
LOW POWER mode
1
0/1
0/1
0/1
WAIT mode
0
0
0/1
0/1
0 = converter is disabled
1 = converter is enabled
Table 4 indicates the typical quiescent-current consumption in each power state.
Table 4. TPS65014 Typical Current Consumption
STATE
26
TOTAL QUIESCENT
CURRENT
QUIESCENT CURRENT BREAKDOWN
1
0
2
30 µA–70 µA
VMAIN (12 µA) + VCORE (12 µA) + LDOs (20 µA each, max 2) + UVLO + reference +
PowerGood
3
30 µA–55 µA
VMAIN (12 µA) + VCORE (12 µA) + LDOs (10 µA each, max 2) + UVLO + reference +
PowerGood
4
13 µA
UVLO + reference circuitry
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VCC
BATT
COVER
BATT COVER
DEG*
t(GLITCH)
PB_ONOFF
REFSYS
EN*
t(GLITCH)
UVLO*
ENABLE
SUPPLIES*
VCORE
98%
VCORE
VMAIN
95%
VMAIN
VLDO1
VLDO2
RESPWRON
MPU_RESET
PWREFAIL
INT
tn(RESPWRON)
*Internal Signal
Note:
Valid for LDO1 supplied from VMAIN as described earlier in this Application Section.
Figure 24. State 1 to State 2 Transition (PS_SEQ = 0, VCC > VUVLO + HYST)
If 2.4 ms after application VCC is still below the default UVLO threshold (3.15 V for VCC rising), then start up is as
shown in Figure 25.
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AC (or USB)
VCC
UVLO Threshold
BATT COVER
t(GLITCH)
BAT COVER
DEG *
REFSYS
EN*
UVLO*
ENABLE
SUPPLIES*
VCORE
98%
VCORE
VMAIN
95%
VMAIN
VLDO1
VLDO2
RESPWRON
MPU_RESET
PWRFAIL
INT
tn(RESPWRON)
* Internal Signal
Note:
Valid for LDO1 supplied from VMAIN as described earlier in this Application Section
Figure 25. State 1 to State 4 to State 2 Transition (Power-Up Behavior When Charge Voltage is Applied)
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VCC
UVLO Threshold With 400 mV Hysteresis
UVLO*
PWPFAIL
INT
tUVLO
ENABLE
SUPPLIES*
VCORE
VMAIN
VMAIN
~0.8 V
VLDO1
VLDO2
RESPWRON
MPU_RESET
* Internal Signal
Note:
Valid for LDO1 supplied from VMAIN as described earlier in this Application Section
Figure 26. State 2 to State 4 Transition
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ENABLE
LOW_POWER
LDO2
OFF/SLP
LOW_POWER
VMAIN
VCORE
95% VCORE
VLDO1
VLDO2
95% VLDO2
INT
Note:
VCORE Lowered, LDO2 Disabled
Note:
Subsequent State 3 to State 2 Transition When LOW POWER Is Deasserted.
Figure 27. State 2 to State 3 Transition
30
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PB_ONOFF
PB_ONOFF
DEGLITCH
tGLITCH
VCORE
VMAIN
VLDO1
VLDO2
INT
Note:
PB_ONFF Activated (See Interrupt Management for INT Behavior)
Figure 28. State 3 to State 2 Transition
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HOT_RESET
HOT_RESET
DEGLITCH
VCORE
t(GLITCH)
95% VCORE
VMAIN
VLDO1
VLDO2
95% VLDO2
INT
MPU_RESET
Note:
t(MPU_RESET)
HOT_RESET Activated (See Interrupt Management for INT Behavior)
Figure 29. State 3 to State 2 Transition
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ENABLE
LOW
POWER*
LDO1
OFF/SLP*
LDO2
OFF/SLP*
MAIN
DISCHARGE*
ENABLE
SUPPLY*
LOW POWER
VMAIN
VMAIN < ca 0.8 V
VCORE
VCORE < ca 0.4 V
VLDO1
VLDO2
RESPWRON
MPU_RESET
PWRFAIL
INT
REFSYS
ENABLE*
* Internal Signal
Figure 30. State 1 to State 4 Transition
7.3.5 System Reset and Control Signals
The RESPWRON signal is used as a global reset for the application. It is an open-drain output. The
RESPWRON signal is generated according to the power good comparator linked to VMAIN and remains low for
tn(RESPWRON) seconds after VMAIN has stabilized. When RESPWRON is low, PWRFAIL, MPU_RESET, and INT
are also held low.
If the output voltage of MAIN is less than 90% of its nominal value, as RESPWRON is generated, and if the
output voltage of MAIN is programmed to a higher value, which causes the output voltage to fall out of the 90%
window, then a RESPWRON signal is generated.
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The PWRFAIL signal indicates when VCC < UVLO or when the TPS65014 junction temperature has exceeded a
reliable value or if BATT_COVER is taken low. This open-drain output can be connected at a fast interrupt pin for
immediate attention by the application processor. All supplies are disabled t(uvlo), t(overtemp), or t(batt_cover) seconds
after PWRFAIL has gone low, giving time for the application processor to shut down cleanly.
BATT_COVER is used to detect whether the battery cover is in place or not. If the battery cover is removed, the
TPS65014 generates a warning to the processor that the battery is likely to be removed and that it may be
prudent to shut down the system. If not required, this feature may be disabled by connecting the BATT_COVER
pin to the VCC pin. BATT_COVER is de-bounced internally. Typical de-bounce time is 56 ms. BATT_COVER
has an internal 2-MΩ pulldown resistor.
The HOT_RESET input is used to generate an MPU_RESET signal for the application processor. The
HOT_RESET pin could be connected to a user-activated button in the application. It can also be used to exit low
power mode. In this case, the TPS65014 waits until the VCORE voltage has stabilized before generating the
MPU_RESET pulse. The MPU_RESET pulse is active low for t(mpu_nreset) seconds. HOT_RESET has an internal
1-MΩ pullup resistor to VCC.
The PB_ONOFF input can be used to exit LOW POWER MODE. It is typically driven by a user-activated
pushbutton in the application. Both HOT_RESET and PB_ONOFF are de-bounced internally by the TPS65014.
Typical debounce time is 56 ms. PB_ONOFF has an internal 1-MΩ pulldown resistor.
PB_ONOFF, BATT_COVER and UVLO events also cause a normal, maskable interrupt to be generated and are
noted in the REGSTATUS register.
7.3.6 Vibrator Driver
The VIB open-drain output is provided to drive a vibrator motor, controlled through the serial interface register
VDCDC2. It has a maximum dropout of 0.5 V at 100-mA load. Typically, an external resistor is required to limit
the motor current and a freewheel diode to limit the VIB overshoot voltage at turnoff.
7.3.7 LED2 Output
The LED2 output can be programmed in the same way as the PG output to blink or to be permanently on or off.
The LED2_ON and LED2_PER registers are used to control the blink rate. For both PG and LED2, the minimum
blink-on time is 10 ms, and this can be increased in 127 10-ms steps to 1280 ms. For both PG and LED2, the
minimum blink period is 100 ms, and this can be increased in 127 100-ms steps to 12800 ms.
7.3.8 Interrupt Management
The open-drain INT pin is used to combine and report all possible conditions through a single pin. Battery and
chip temperature faults, precharge timeout, charge timeout, taper timeout, and termination current are each
capable of setting INT low, that is, active. INT can also be activated if any of the regulators are below the
regulation threshold. Interrupts can also be generated by any of the GPIO pins programmed to be inputs. These
inputs can be programmed to generate an interrupt either at the rising or falling edge of the input signal. It is
possible to mask an interrupt from any of these conditions individually by setting the appropriate bits in the
MASK1, MASK2, or MASK3 registers. By default, all interrupts are masked. Interrupts are stored in the
CHGSTATUS, REGSTATUS, and DEFGPIO registers in the serial interface. CHGSTATUS and REGSTATUS
interrupts are acknowledged by reading these registers. If a 1 is present in any location, then the TPS65014
automatically sets the corresponding bit in the ACKINT1 or ACKINT2 registers and releases the INT pin. The
ACKINT register contents are self-clearing when the condition, which caused the interrupt, is removed. The
applications processor should not normally need to access the ACKINT1 or ACKINT2 registers.
Interrupt events are always captured; thus when an interrupt source is unmasked, INT may immediately go active
due to a previous interrupt condition. This can be prevented by first reading the relevant STATUS register before
unmasking the interrupt source.
If an interrupt condition occurs, then the INT pin is set low. The CHGSTATUS, REGSTATUS, and DEFGPIO
registers should be read. Bit positions containing a 1 (or possibly a 0 in DEFGPIO) are noted by the CPU and the
corresponding situation resolved. The reading of the CHGSTATUS and REGSTATUS registers automatically
acknowledges any interrupt condition in those registers and blocks the path to the INT pin from the relevant bits.
No interrupt should be missed during the read process because this process starts by latching the contents of
the register before shifting them out at SDAT. Once the contents have been latched (which takes a couple of
nanoseconds), the register is free to capture new interrupt conditions. Thus, for practical purposes the probability
of missing anything is zero.
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The following describes how registers 0x01 (CHGSTATUS) and 0x02 (REGSTATUS) are handled:
• CHGSTATUS(5,0) are positive edge set. Read of set CHGSTATUS(5,0) bits sets ACKINT1(5,0) bits.
• CHGSTATUS(7-6,4-1) are level set. Read of set CHGSTATUS(7-6,4-1) bits sets ACKINT1(7-6,4-1) bits.
• CHGSTATUS(5,0) clear when input signal low, and ACKINT1(5,0) bits are already set.
• CHGSTATUS(7-6,4-1) clear when input signal is low.
• ACKINT1(7-0) clear when CHGSTATUS(7-0) is clear.
• REGSTATUS(7-5) are positive edge set. Read of set REGSTATUS(7-5) bits sets ACKINT2(7-5) bits.
• REGSTATUS(3-0) are level set. Read of set REGSTATUS(3-0) bits sets ACKINT2(3-0) bits.
• REGSTATUS(7-5) clear when input signal low, and ACKINT1(7-5) bit are already set.
• REGSTATUS(3-0) clear when input signal is low.
• ACKINT2(7-0) clear when REGSTATUS(7-0) is clear.
The following describes the function of the 0x05 (ACKINT1) and 0x06 (ACKINT2) registers. These are not
usually written to by the CPU because the TPS65014 internally sets/clears these registers:
• ACKINT1(7:0): Bit is set when the corresponding CHGSTATUS set bit is read through I2C.
• ACKINT1(7:0): Bit is cleared when the corresponding CHGSTATUS set bit clears.
• ACKINT2(7:0): Bit is set when the corresponding REGSTATUS set bit is read through I2C.
• ACKINT2(7:0): Bit is cleared when the corresponding REGSTATUS set bit clears.
• ACKINT1(7:0): A bit set masks the corresponding CHGSTATUS bit from INT.
• ACKINT2(7:0): A bit set masks the corresponding REGSTATUS bit from INT.
The following describes the function of the 0x03 (MASK1), 0x04 (MASK2) and 0x0F (MASK3) registers:
• MASK1(7:0): A bit set in this register masks CHGSTATUS from INT.
• MASK2(7:0): A bit set in this register masks REGSTATUS from INT.
• MASK3(7:4): A bit set in this register detects a rising edge on GPIO.
• MASK3(7:4): A bit cleared in this register detects a falling edge on GPIO.
• MASK3(3:0): A bit set in this register clears GPIO Detect signal from INT.
GPIO interrupts are located by reading the 0x10 (DEFGPIO) register. The application CPU stores, or can read
from DEFGPIO, which GPIO is set to input or output. This information together with the information on
which edge the interrupt was generated (the CPU either knows this or can read it from MASK3) determines
whether the CPU is looking for a 0 or a 1 in DEFGPIO. A GPIO interrupt is blocked from the INT pin by
setting the relevant MASK3 bit; this must be done by the CPU, there is no auto-acknowledge for the GPIO
interrupts.
7.3.9 Serial Interface
The serial interface is compatible with the standard and fast mode I2C specifications, allowing transfers at up to
400 kHz. The interface adds flexibility to the power supply solution, enabling most functions to be programmed to
new values depending on the instantaneous application requirements and charger status to be monitored.
Register contents remain intact as long as VCC remains above 2 V. The TPS65014 has a 7-bit address with the
LSB set by the IFLSB pin; this allows the connection of two devices with the same address to the same bus. The
6 MSBs are 100100. Attempting to read data from register addresses not listed in this section results in FFh
being read out.
For normal data transfer, DATA is allowed to change only when CLK is low. Changes when CLK is high are
reserved for indicating the start and stop conditions. During data transfer, the data line must remain stable
whenever the clock line is high. There is one clock pulse per bit of data. Each data transfer is initiated with a start
condition and terminated with a stop condition. When addressed, the TPS65014 device generates an
acknowledge bit after the reception of each byte. The master device (microprocessor) must generate an extra
clock pulse that is associated with the acknowledge bit. The TPS65014 device must pull down the DATA line
during the acknowledge clock pulse so that the DATA line is a stable low during the high period of the
acknowledge clock pulse. The DATA line is a stable low during the high period of the acknowledge-related clock
pulse. Setup and hold times must be taken into account. During read operations, a master must signal the end of
data to the slave by not generating an acknowledge bit on the last byte that was clocked out of the slave. In this
case, the slave TPS65014 device must leave the data line high to enable the master to generate the stop
condition.
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The I2C interface accepts data as soon as the voltage at VCC is higher than the undervoltage lockout threshold
and one power rail of the converter (main, core, or one of the LDOs) is operating. Therefore, the I2C interface is
not operating after applying the battery voltage as the device automatically enters the WAIT mode with all rails
off.
When the device is in WAIT mode, the I2C registers are reset to their default values if all voltage rails are off. If
the device is in WAIT mode and one power rail is left on, the I2C interface is operating and the registers are not
reset after leaving the WAIT mode.
DATA
CLK
Change
of Data
Allowed
Data Line
Stable
Data Valid
Figure 31. Bit Transfer on the Serial Interface
CE
DATA
CLK
S
P
START Condition
STOP Condition
Figure 32. START and STOP Conditions
...
SCLK
A6
SDAT
A5
A4
...
...
A0
R/W
ACK
0
R6
... R0
R5
0
ACK
D7
D6
... D0
D5
0
Slave Address
Start
Note:
R7
...
ACK
0
Register Address
Data
Stop
SLAVE = TPS65014
Figure 33. Serial Interface WRITE to TPS65014 Device
...
SCLK
A6
SDAT
Start
Note:
..
...
A0
R/W
ACK
0
0
Slave Address
R7
..
...
R0
Register
Address
ACK
A6
..
A0
0
...
R/W
ACK
1
0
Slave Address
D7
..
D0
Slave
Drives
The Data
ACK
Master
Stop
Drives
ACK and Stop
SLAVE = TPS65014
Figure 34. Serial Interface READ From TPS65014: Protocol A
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...
SCLK
SDAT
A6
A0
R/W
ACK
0
0
..
R7
...
..
R0
Register
Address
Slave Address
Start
Note:
..
...
A6
ACK
0
Stop Start
..
A0
R/W
ACK
1
0
Slave Address
D7
..
D0
Slave
Drives
The Data
ACK
Master
Stop
Drives
ACK and Stop
SLAVE = TPS65014
Figure 35. Serial Interface READ From TPS65014: Protocol B
DATA
t(BUF)
th(STA)
t(LOW)
tr
tf
CLK
th(STA)
STO
t(HIGH)
th(DATA)
STA
tsu(STA)
tsu(STO)
tsu(DATA)
STA
STO
Figure 36. Serial Interface Timing Diagram
7.4 Device Functional Modes
7.4.1 Power Save Mode Operation
As the load current decreases, the converter enters the power-save mode operation. During power-save mode,
the converter operates with reduced switching frequency in PFM mode and with a minimum quiescent current to
maintain high efficiency.
To optimize the converter efficiency at light load, the average current is monitored; if in PWM mode, the inductor
current remains below a certain threshold, and then power-save mode is entered. The typical threshold can be
calculated as in Equation 2:
V
V
I(MAIN)
I(CORE)
I
+
I
+
(skipmain)
(skipcore)
17 W
42 W
(2)
During the power-save mode, the output voltage is monitored with the comparator by the thresholds comp low
and comp high. As the output voltage falls below the comp low threshold, set to typically 0.8% above the nominal
Vout, the P-channel switch turns on. The converter then runs at 50% of the nominal switching frequency. If the
load is below the delivered current, then the output voltage rises until the comp high threshold is reached,
typically 1.6% above the nominal Vout. At this point, all switching activity ceases, thus reducing the quiescent
current to a minimum until the output voltage has dropped below comp low again. If the load current is greater
than the delivered current, then the output voltage falls until it crosses the nominal output voltage threshold
(comp low 2 threshold), whereupon power-save mode is exited, and the converter returns to PWM mode.
These control methods reduce the quiescent current typically to 12 µA per converter and the switching frequency
to a minimum, achieving the highest converter efficiency. Setting the comparator thresholds to typically 0.8% and
1.6% above the nominal output voltage at light load current results in a dynamic voltage positioning achieving
lower absolute voltage drops during heavy load transient changes. This allows the converters to operate with a
small output capacitor of just 10 µF for the core and 22 µF for the main output and still have a low absolute
voltage drop during heavy load transient changes. See Figure 37 for detailed operation of the power-save mode.
The power-save mode can be disabled through the I2C interface to force the converters to stay in fixed frequency
PWM mode.
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Device Functional Modes (continued)
PFM Mode at Light Load
1.6%
Comp High
0.8%
Comp Low
VO
Comp Low 2
PFM Mode at Medium to Full Load
Figure 37. Power-Save Mode Thresholds and Dynamic Voltage Positioning
7.4.2 Sleep Mode
The TPS65014 charger enters the low-power sleep mode if both input sources are removed from the circuit. This
feature prevents draining the battery during the absence of input power.
7.5 Register Maps
7.5.1 CHGSTATUS Register (offset = 01h) (reset: 00h)
Bits 1-4 may be reset through the serial interface in order to force a reset of the charger. Any attempt to write to
Bit 0 and Bits 5-7 is ignored. A 1 in sets the INT pin active unless the corresponding bit in the MASK
register is set.
Figure 38. CHGSTATUS Register
7
USB Charge
6
AC Charge
R-0
R-0
5
Thermal
Suspend
R-0
4
Term Current
3
Taper Timeout
2
Chg Timeout
1
Prechg Timeout
R-0
R/W-0
R/W-0
R/W-0
0
BattTemp
Error
R-0
LEGEND: R/W = Read/Write; R = Read only; -n = value after reset
Table 5. CHGSTATUS Register Field Descriptions
BIT
7
FIELD
TYPE
RESET
DESCRIPTION
USB charge
R
0h
0h = Inactive
1h = USB source is present and in the range valid for charging.
B7 remains active as long as the charge source is present.
6
AC charge
R
0h
0h = Wall plug source is not present and/or not in the range
valid for charging
1h = Wall plug source is present and in the range valid for
charging. B6 remains active as long as the charge source is
present.
5
Thermal suspend
R
0h
0h = Charging is allowed
1h = Charging is momentarily suspended due to excessive
power dissipation on chip.
4
Term current
R
0h
0h = Charging, charge termination current threshold has not
been crossed.
1h = Charge termination current threshold has been crossed and
charging has been stopped. This can be due to a battery
reaching full capacity, or to a battery removal condition.
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Table 5. CHGSTATUS Register Field Descriptions (continued)
BIT
3
FIELD
TYPE
RESET
DESCRIPTION
Taper Timeout
R/W
0h
If CHCONFIG=0: Bit 3 equals the output of the taper voltage
comparator directly, without any timer delay.
If CHCONFIG=1: there is a delay of 30 minutes because the
timers have to time out first.
0h = Charging, timers did not time out
1h = One of the timers has timed out and charging has been
terminated.
2
Chg Timeout
R/W
0h
If CHCONFIG=0: Bit 3 equals the output of the taper voltage
comparator directly, without any timer delay.
If CHCONFIG=1: there is a delay of 30 minutes because the
timers have to time out first.
0h = Charging, timers did not time out
1h = One of the timers has timed out and charging has been
terminated.
1
Prechg Timeout
R/W
0h
If CHCONFIG=0: Bit 3 equals the output of the taper voltage
comparator directly, without any timer delay.
If CHCONFIG=1: there is a delay of 30 minutes because the
timers have to time out first.
0h = Charging, timers did not time out
1h = One of the timers has timed out and charging has been
terminated.
0
BattTempError
R
0h
Battery temperature error
•
0 = Battery temperature is inside the allowed range and that
charging is allowed.
•
1 = Battery temperature is outside of the allowed range and
that charging is suspended.
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7.5.2 REGSTATUS Register (offset = 02h) (reset: 00h)
A rising edge in the REGSTATUS register contents causes INT to be driven low if it is not masked in the MASK2.
Figure 39. REGSTATUS Register
7
PB_ONOFF
R-0
6
BATT_COVER
R-0
5
UVLO
R-0
4
Rsvd
R-0
3
PGOOD LDO2
R-0
2
PGOOD LDO1
R-0
1
PGOOD MAIN
R-0
0
PGOOD CORE
R-0
LEGEND: R/W = Read/Write; R = Read only; -n = value after reset
Table 6. REGSTATUS Register Field Descriptions
BIT
7
FIELD
TYPE
RESET
DESCRIPTION
PB_ONOFF
R
0h
0h = Inactive
1h = User activated the PB_ONOFF switch to request that all
rails are shut down.
6
BATT_COVER
R
0h
5
UVLO
R
0h
0h = BATT_COVER pin is high
1h = BATT_COVER pin is low
0h = Voltage at the VCC pin above UVLO threshold
1h = Voltage at the VCC pin has dropped below the UVLO
threshold
4
Reserved
R
0h
3
PGOOD LDO2
R
0h
2
PGOOD LDO1
R
0h
1
PGOOD MAIN
R
0h
0
PGOOD CORE
R
0h
0h = LDO2 output in regulation, or LDO2 disabled with VREGS1
= 0
1h = LDO2 output out of regulation
0h = LDO1 output in regulation, or LDO1 disabled with VREGS1
= 0
1h = LDO1 output out of regulation
0h = Main converter output in regulation
1h = Main converter output out of regulation
0h = Core converter output in regulation
1h = Core converter output out of regulation, or VDCDC2 =
1 in low power mode
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7.5.3 MASK1 Register (offset = 03h) (reset: FFh)
The MASK1 register is used to mask all or any of the conditions in the corresponding CHGSTATUS
positions indicated at the INT pin. Default is to mask all.
Figure 40. MASK1 Register
7
Mask USB
6
Mask AC
R/W-1
R/W-1
5
Mask Thermal
Suspend
R/W-1
4
Mask Term
3
Mask Taper
2
Mask Chg
1
Mask Prechg
0
Mask BattTemp
R/W-1
R/W-1
R/W-1
R/W-1
R/W-1
LEGEND: R/W = Read/Write; R = Read only; -n = value after reset
Table 7. MASK1 Register Field Descriptions
BIT
FIELD
TYPE
RESET
DESCRIPTION
7
Mask USB
R/W
1h
INT Mask for Bit 7 in CHGSTATUS register. Refer to Table 5.
6
Mask AC
R/W
1h
INT Mask for Bit 6 in CHGSTATUS register. Refer to Table 5.
5
Mask Thermal Suspend
R/W
1h
INT Mask for Bit 5 in CHGSTATUS register. Refer to Table 5.
4
Mask Term
R/W
1h
INT Mask for Bit 4 in CHGSTATUS register. Refer to Table 5.
3
Mask Taper
R/W
1h
INT Mask for Bit 3 in CHGSTATUS register. Refer to Table 5.
2
Mask Chg
R/W
1h
INT Mask for Bit 2 in CHGSTATUS register. Refer to Table 5.
1
Mask Prechg
R/W
1h
INT Mask for Bit 1 in CHGSTATUS register. Refer to Table 5.
0
Mask BattTemp
R/W
1h
INT Mask for Bit 0 in CHGSTATUS register. Refer to Table 5.
7.5.4 MASK2 Register (offset = 04h) (reset: FFh)
The MASK2 register is used to mask all or any of the conditions in the corresponding REGSTATUS
positions indicated at the INT pin. Default is to mask all.
Figure 41. MASK2 Register
7
Mask
PB_ONOFF
R/W-1
6
Mask
BATT_COVER
R/W-1
5
Mask UVLO
4
Rsvd
R/W-1
R/W-1
3
Mask PGOOD
LDO2
R/W-1
2
Mask PGOOD
LDO1
R/W-1
1
Mask PGOOD
MAIN
R/W-1
0
Mask PGOOD
CORE
R/W-1
LEGEND: R/W = Read/Write; R = Read only; -n = value after reset
Table 8. MASK2 Register Field Descriptions
BIT
FIELD
TYPE
RESET
DESCRIPTION
7
Mask PB_ONOFF
R/W
1h
INT Mask for Bit 7 in REGSTATUS register. Refer to Table 6.
6
Mask BATT_COVER
R/W
1h
INT Mask for Bit 6 in REGSTATUS register. Refer to Table 6.
5
Mask UVLO
R/W
1h
INT Mask for Bit 5 in REGSTATUS register. Refer to Table 6.
4
Reserved
R/W
1h
Reserved
3
Mask PGOOD LDO2
R/W
1h
INT Mask for Bit 3 in REGSTATUS register. Refer to Table 6.
2
Mask PGOOD LDO1
R/W
1h
INT Mask for Bit 2 in REGSTATUS register. Refer to Table 6.
1
Mask PGOOD MAIN
R/W
1h
INT Mask for Bit 1 in REGSTATUS register. Refer to Table 6.
0
Mask PGOOD CORE
R/W
1h
INT Mask for Bit 0 in REGSTATUS register. Refer to Table 6.
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7.5.5 ACKINT1 Register (offset = 05h) (reset: 00h)
The ACKINT1 register is internally used to acknowledge any of the interrupts in the corresponding
CHGSTATUS positions. When this is done, the acknowledged interrupt is no longer fed through to the INT
pin and so the INT pin becomes free to indicate the next pending interrupt. If none exists, then the INT pin goes
high, else it will remain low. A 1 at any position in ACKINT1 is automatically cleared when the corresponding
interrupt condition in CHGSTATUS is removed. The application processor should not normally need to access
the ACKINT1 register.
Figure 42. ACKINT1 Register
7
Ack USB
6
Ack AC
R-0
R-0
5
Ack Thermal
Shutdown
R-0
4
Ack Term
3
Ack Taper
2
Ack Chg
1
Ack Prechg
0
Ack BattTemp
R-0
R-0
R-0
R-0
R-0
LEGEND: R/W = Read/Write; R = Read only; -n = value after reset
Table 9. ACKINT1 Register Field Descriptions
BIT
FIELD
TYPE
RESET
DESCRIPTION
7
Ack USB
R
0h
Internal ack for Bit 7 in CHGSTATUS register. Refer to Table 5.
6
Ack AC
R
0h
Internal ack for Bit 6 in CHGSTATUS register. Refer to Table 5.
5
Ack Thermal Shutdown
R
0h
Internal ack for Bit 5 in CHGSTATUS register. Refer to Table 5.
4
Ack Term
R
0h
Internal ack for Bit 4 in CHGSTATUS register. Refer to Table 5.
3
Ack Taper
R
0h
Internal ack for Bit 3 in CHGSTATUS register. Refer to Table 5.
2
Ack Chg
R
0h
Internal ack for Bit 2 in CHGSTATUS register. Refer to Table 5.
1
Ack Prechg
R
0h
Internal ack for Bit 1 in CHGSTATUS register. Refer to Table 5.
0
Ack BattTemp
R
0h
Internal ack for Bit 0 in CHGSTATUS register. Refer to Table 5.
7.5.6 ACKINT2 Register (offset: 06h) (reset: 00h)
The ACKINT2 register is internally used to acknowledge any of the interrupts in the corresponding
REGSTATUS positions. When this is done, the acknowledged interrupt is no longer fed through to the INT
pin and so the INT pin becomes free to indicate the next pending interrupt. If none exists, then the INT pin goes
high, else it will remain low. A 1 at any position in ACKINT2 is automatically cleared when the corresponding
interrupt condition in REGSTATUS is removed. The application processor should not normally need to access
the ACKINT2 register.
Figure 43. ACKINT2 Register
7
Ack
PB_ONOFF
R-0
6
Ack BATT_
COVER
R-0
5
Ack UVLO
4
Rsvd
R-0
R-0
3
Ack PGOOD
LDO2
R-0
2
Ack PGOOD
LDO1
R-0
1
Ack PGOOD
MAIN
R-0
0
Ack PGOOD
CORE
R-0
LEGEND: R/W = Read/Write; R = Read only; -n = value after reset
Table 10. ACKINT2 Register Field Descriptions
BIT
42
FIELD
TYPE
RESET
DESCRIPTION
7
Ack PB_ONOFF
R
0h
Internal ack for Bit 7 in REGSTATUS register. Refer to Table 6.
6
Ack BATT_
COVER
R
0h
Internal ack for Bit 6 in REGSTATUS register. Refer to Table 6.
5
Ack UVLO
R
0h
Internal ack for Bit 5 in REGSTATUS register. Refer to Table 6.
4
Reserved
R
0h
Reserved
3
Ack PGOOD LDO2
R
0h
Internal ack for Bit 3 in REGSTATUS register. Refer to Table 6.
2
Ack PGOOD LDO1
R
0h
Internal ack for Bit 2 in REGSTATUS register. Refer to Table 6.
1
Ack PGOOD MAIN
R
0h
Internal ack for Bit 1 in REGSTATUS register. Refer to Table 6.
0
Ack PGOOD CORE
R
0h
Internal ack for Bit 0 in REGSTATUS register. Refer to Table 6.
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7.5.7 CHGCONFIG Register (offset: 07h) (reset: 1Bh)
The CHGCONFIG register is used to configure the charger.
Figure 44. CHGCONFIG Register
7
AUA
6
Charger reset
R/W-0
R/W-0
5
Fast charge
timer + taper
timer enabled
R/W-0
4
MSB charge
current
3
LSB charge
current
2
USB / 100 mA
500 mA
1
USB charge
allowed
0
Charge
enable
R/W-1
R/W-1
R/W-0
R/W-1
R/W-1
LEGEND: R/W = Read/Write; R = Read only; -n = value after reset
Table 11. CHGCONFIG Register Field Descriptions
BIT
7
FIELD
TYPE
RESET
DESCRIPTION
AUA
R/W
0h
0h = If a voltage is present at AC or USB in the appropriate
range for charging, and if VCC > UVLO, the TPS65014 is forced
into ON mode. The WAIT mode is disabled.
1h = If a voltage source at AC or USB is present, the WAIT
mode is enabled, and the TPS65014 does not automatically turn
on the converters.
6
Charger reset
R/W
0h
Clears all the timers in the charger and forces a restart of the
charge algorithm.
0/1 = This bit must be set and then reset through the serial
interface.
5
Fast charge timer + taper timer
enabled
R/W
0h
0h = Fast charge timer disabled (default), CHSTATUS =
status of the taper detect comparator output.
1h = Enables the fast charge timer and taper timer. CHSTATUS
= status of the taper timer.
4
MSB charge current
R/W
1h
Used to set the constant current in the current regulation phase.
See Table 12.
3
LSB charge current
R/W
1h
Used to set the constant current in the current regulation phase.
See Table 12.
2
USB / 100 mA 500 mA
R/W
0h
0h = Sets the USB charging current to max 100 mA.
1h = Sets the USB charging current to max 500 mA. B2 is
ignored if B1 = 0.
1
USB charge allowed
R/W
1h
0
Charge
enable
R/W
1h
0h = Prevents any charging from the USB input.
1h = Charging from the USB input is allowed.
0h = Charging is not allowed.
1h = Charger is free to charge from either of the two input
sources. If both sources are present and valid, the TPS65014
charges from the AC pin source.
Table 12. Charge Current Rate
B4:B3
CHARGE CURRENT RATE
11
Maximum current set by the external resistor at the ISET pin
10
75% of maximum
01
50% of maximum
00
25% of maximum
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7.5.8 LED1_ON Register (offset: 08h) (reset: 00h)
The LED1_ON and LED1_PER registers can be used to take control of the PG open-drain output normally
controlled by the charger.
Figure 45. LED1_ON Register
7
PG1
R/W-0
6
LED1 ON6
R/W-0
5
LED1 ON5
R/W-0
4
LED1 ON4
R/W-0
3
LED1 ON3
R/W-0
2
LED1 ON2
R/W-0
1
LED1 ON1
R/W-0
0
LED1 ON0
R/W-0
LEGEND: R/W = Read/Write; R = Read only; -n = value after reset
Table 13. LED1_ON Register Field Descriptions
BIT
7
6-0
FIELD
TYPE
RESET
DESCRIPTION
PG1
R/W
0h
Control of the PG pin is determined by PG1 and PG2 according
to the table under LED1_PER register
LED1 ONx
R/W
0h
LED1_ON[6:0] are used to program the on-time of the opendrain output transistor at the PG pin. The minimum on-time is
typically 10 ms and one LSB corresponds to a 10-ms step
change in the on-time.
7.5.9 LED1_PER Register (offset: 09h) (reset: 00h)
Figure 46. LED1_PER Register
7
PG2
R/W-0
6
LED1 PER6
R/W-0
5
LED1 PER5
R/W-0
4
LED1 PER4
R/W-0
3
LED1 PER3
R/W-0
2
LED1 PER2
R/W-0
1
LED1 PER1
R/W-0
0
LED1 PER0
R/W-0
LEGEND: R/W = Read/Write; R = Read only; -n = value after reset
Table 14. LED1_PER Register Field Descriptions
BIT
7
6-0
FIELD
TYPE
RESET
DESCRIPTION
PG2
R/W
0h
Control of the PG pin is determined by PG1 and PG2 according
to Table 15. Default shown in bold.
LED1 PERx
R/W
0h
LED1_PER are used to program the time period of the
open-drain output transistor at the PG pin. The minimum period
is typically 100 ms and one LSB corresponds to a 100-ms, step
change in the period.
Table 15. Control of the PG Pin
44
PG1
PG2
BEHAVIOR OF PG OPEN-DRAIN OUTPUT
0
0
Under charger control
0
1
Blink
1
0
Off
1
1
Always On
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7.5.10 LED2_ON Register (offset: 0Ah) (reset: 00h)
The LED2_ON and LED2_PER registers are used to control the LED2 open-drain output.
Figure 47. LED2_ON Register
7
LED21
R/W-0
6
LED2 ON6
R/W-0
5
LED2 ON5
R/W-0
4
LED2 ON4
R/W-0
3
LED2 ON3
R/W-0
2
LED2 ON2
R/W-0
1
LED2 ON1
R/W-0
0
LED2 ON0
R/W-0
LEGEND: R/W = Read/Write; R = Read only; -n = value after reset
Table 16. LED2_ON Register Field Descriptions
BIT
FIELD
TYPE
RESET
DESCRIPTION
7
LED21
R/W
0h
Control is determined by LED21 and LED22 according to
Table 18.
LED2 ONx
R/W
0h
LED2_ON are used to program the on-time of the opendrain output transistor at the LED2 pin. The minimum on-time is
typically 10 ms and one LSB corresponds to a 10-ms, step
change in the on-time.
6-0
7.5.11 LED2_PER (offset: 0Bh) (reset: 00h)
Figure 48. LED2_PER Register
7
LED22
R/W-0
6
LED2 PER6
R/W-0
5
LED2 PER5
R/W-0
4
LED2 PER4
R/W-0
3
LED2 PER3
R/W-0
2
LED2 PER2
R/W-0
1
LED2 PER1
R/W-0
0
LED2 PER0
R/W-0
LEGEND: R/W = Read/Write; R = Read only; -n = value after reset
Table 17. LED2_PER Register Field Descriptions
BIT
FIELD
TYPE
RESET
DESCRIPTION
7
LED22
R/W
0h
Control is determined by LED21 and LED22 according to
Table 18.
LED2 PERx
R/W
0h
LED2_ON are used to program the on-time of the opendrain output transistor at the LED2 pin. The minimum on-time is
typically 100 ms and one LSB corresponds to a 100-ms, step
change in the on-time.
6-0
Table 18. LED Control
LED21
LED22
BEHAVIOR OF LED2 OPEN-DRAIN OUTPUT
0
0
Off
0
1
Blink
1
0
Off
1
1
Always On
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7.5.12
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VDCDC1 Register (offset: 0Ch) (reset: 32h/33h)
The VDCDC1 register is used to program the VMAIN switching converter.
Figure 49. VDCDC1 Register
7
FPWM
6
UVLO1
5
UVLO0
R/W-0
R/W-0
R/W-0
4
ENABLE
SUPPLY
R/W-0
3
ENABLE LP
R/W-0
2
MAIN
DISCHARGE
R/W-0
1
MAIN1
0
MAIN0
R/W-0
R/W-0
LEGEND: R/W = Read/Write; R = Read only; -n = value after reset
Table 19. VDCDC1 Register Field Descriptions
BIT
FIELD
TYPE
RESET
DESCRIPTION
7
FPWM
R/W
0h
Forced PWM mode for DC-DC converters.
0h = MAIN and the CORE DC-DC converter are allowed to
switch into PFM mode.
1h = MAIN and the CORE DC-DC converter operate with forced
fixed-frequency PWM mode and are not allowed to switch into
PFM mode, at light load.
6-5
4
UVLOx
R/W
0h
The undervoltage threshold voltage is set by UVLO1 and
UVLO0 according to Table 20, with the default value in bold.
ENABLE SUPPLY
R/W
1h
Selects between LOW POWER mode and WAIT mode
0h = WAIT mode allowed, activated when LOW_PWR pin = 1
and VDCDC1 = 1.
1h = The TPS65014 enters LOW POWER mode when
LOW_PWR pin = 1 and VDCDC1 = 1
3
ENABLE LP
R/W
0h
2
MAIN DISCHARGE
R/W
0h
0h = Disables the low power function of the LOW_PWR pin
1h = Enables the low power function of the LOW_PWR pin.
0h = disables the active discharge of the VMAIN converter
output.
1h = enables the active discharge of the VMAIN converter
output, when the converter is disabled (that is, in WAIT mode).
1-0
MAINx
R/W
1h
The VMAIN converter output voltages are set according to
Table 21, with the default values in bold set by the DEFMAIN
pin. The default voltage can subsequently be overwritten through
the serial interface after start-up.
Table 20. Undervoltage Threshold Voltage
UVLO1
UVLO0
VUVLO
0
0
2.5 V
0
1
2.75 V
1
0
3.0 V
1
1
3.25 V
Table 21. VMAIN Converter Output Voltage
46
MAIN1
MAIN0
0
0
2.5 V
0
1
2.75 V
1
0
3.0 V
1
1
3.3 V
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7.5.13 VDCDC2 Register (offset: 0Dh) (reset: 60h/70h)
The VDCDC2 register is used to program the VCORE switching converter output voltage. It is programmable in 8
steps between 0.85 V and 1.8 V. The default value is governed by the DEFCORE pin; DEFCORE=0 sets an
output voltage of 1.5 V. DEFCORE=1 sets an output voltage of 1.8 V.
Figure 50. VDCDC2 Register
7
LP_COREOFF
6
CORE2
5
CORE1
4
CORE0
3
CORELP1
2
CORELP0
1
VIB
R/W-0
R/W-1
R/W-1
R/WDEFCORE
R/W-1
R/W-0
R/W-0
0
CORE
DISCHARGE
R/W-0
LEGEND: R/W = Read/Write; R = Read only; -n = value after reset
Table 22. VDCDC2 Register Field Descriptions
BIT
FIELD
TYPE
RESET
DESCRIPTION
LP_COREOFF
R/W
0h
0h = VCORE converter is enabled in low power mode.
6-5
COREx
R/W
1h
4
CORE0
R/W
DEFCORE Table 23 shows all possible values of VCORE. The default value
can subsequently be overwritten through the serial interface
after start-up.
3
CORELP1
R/W
1h
CORELP1 and CORELP0 can be used to set the VCORE
voltage in low power mode. In low power mode, CORE2 is
effectively 0, and CORE1, CORE0 take on the values
programmed at CORELP1 and CORELP0, default 10 giving
VCORE = 1.1 V as default in low power mode. When low power
mode is exited, VCORE reverts to the value set by CORE2,
CORE1, and CORE0.
2
CORELP0
R/W
0h
CORELP1 and CORELP0 can be used to set the VCORE
voltage in low power mode. In low power mode, CORE2 is
effectively 0, and CORE1, CORE0 take on the values
programmed at CORELP1 and CORELP0, default 10 giving
VCORE = 1.1 V as default in low power mode. When low power
mode is exited, VCORE reverts to the value set by CORE2,
CORE1, and CORE0.
1
VIB
R/W
0h
0h = Disables the VIB output transistor
7
1h = VCORE converter is disabled in low power mode.
Table 23 shows all possible values of VCORE. The default value
can subsequently be overwritten through the serial interface
after start-up.
1h = Enables the VIB output transistor to drive the vibrator
motor.
0
CORE
DISCHARGE
R/W
0h
0h = Disables the active discharge of the VCORE converter
output.
1h = Enables the active discharge of the VCORE converter
output in WAIT mode, or if VDCDC2 = 1 in LOW POWER
mode.
Table 23. VCORE Values
CORE2
CORE1
CORE0
VCORE
0
0
0
0.85 V
0
0
1
1.0 V
0
1
0
1.1 V
0
1
1
1.2 V
1
0
0
1.3 V
1
0
1
1.4 V
1
1
0
1.5 V
1
1
1
1.8 V
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7.5.14 VREGS1 Register (offset: 0Eh) (reset: 88h)
The VREGS1 register is used to program and enable LDO1 and LDO2 and to set their behavior when low power
mode is active. The LDO output voltages can be set either on the fly, while the relevant LDO is disabled, or
simultaneously when the relevant enable bit is set. Note that both LDOs are per default ON.
Figure 51. VREGS1 Register
7
LDO2 enable
R/W-0
6
LDO2 OFF/
nSLP
R/W-0
5
LDO21
4
LDO20
3
LDO1 enable
R/W-0
R/W-0
R/W-0
2
LDO1 OFF/
nSLP
R/W-0
1
LDO11
0
LDO10
R/W-0
R/W-0
LEGEND: R/W = Read/Write; R = Read only; -n = value after reset
Table 24. VREGS1 Register Field Descriptions
BIT
FIELD
TYPE
RESET
DESCRIPTION
7
LDO2 enable
R/W
1h
The function of the LDO2 enable and LDO2 OFF/nSLP bits is
shown in Table 25. See the power-on sequencing section for
details of low power mode.
6
LDO2 OFF / nSLP
R/W
0h
The function of the LDO2 enable and LDO2 OFF/nSLP bits is
shown in Table 25. See the power-on sequencing section for
details of low power mode.
LDO2x
R/W
0h
LDO2 has a default output voltage of 1.8 V. If desired, this can
be changed at the same time as it is enabled through the serial
interface. See Table 26.
3
LDO1 enable
R/W
1h
The function of the LDO1 enable and LDO1 OFF/nSLP bits is
shown in Table 27. See the power-on sequencing section for
details of low-power mode. Note that programming LDO1 to a
higher voltage may force a system power-on reset if the
increase is in the 10% or greater range.
2
LDO1 OFF / nSLP
R/W
0h
The function of the LDO1 enable and LDO1 OFF/nSLP bits is
shown in Table 27. See the power-on sequencing section for
details of low-power mode. Note that programming LDO1 to a
higher voltage may force a system power-on reset if the
increase is in the 10% or greater range.
LDO1x
R/W
0h
The LDO1 output voltage is per default set externally. If so
desired, this can be changed through the serial interface. See
Table 28.
5-4
1-0
Table 25. LDO2 Enable and LDO2 OFF/nSLP Functions
48
LDO2 ENABLE
LDO2 OFF / nSLP
LDO STATUS IN NORMAL MODE
0
X
OFF
OFF
1
0
ON, full power
ON, reduced power and performance
1
1
ON, full power
OFF
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Table 26. LDO21/LDO20
LDO21
LDO20
VLDO2
0
0
1.8 V
0
1
2.5 V
1
0
3.0 V
1
1
3.3 V
Table 27. LDO1 Enable and LDO1 OFF/nSLP Functions
LDO1 ENABLE
LDO1 OFF / nSLP
LDO STATUS IN NORMAL MODE
LDO STATUS IN LOW-POWER MODE
0
X
OFF
OFF
1
0
ON, full power
ON, reduced power and performance
1
1
ON, full power
OFF
Table 28. LDO11/LDO10
LDO11
LDO10
0
0
VLDO1
ADJ
0
1
2.5 V
1
0
2.75 V
1
1
3.0 V
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7.5.15 MASK3 Register (offset: 0Fh) (reset: 00h)
The MASK3 register must be considered when any of the GPIO pins are programmed as inputs.
Figure 52. MASK3 Register
7
Edge trigger
GPIO4
R/W-0
6
Edge trigger
GPIO3
R/W-0
5
Edge trigger
GPIO2
R/W-0
4
Edge trigger
GPIO1
R/W-0
3
Mask GPIO4
2
Mask GPIO3
1
Mask GPIO2
0
Mask GPIO1
R/W-0
R/W-0
R/W-0
R/W-0
LEGEND: R/W = Read/Write; R = Read only; -n = value after reset
Table 29. MASK3 Register Field Descriptions
BIT
FIELD
TYPE
RESET
DESCRIPTION
7-4
Edge trigger GPIOx
R/W
0h
Determines whether the respective GPIO generates an interrupt
at a rising or a falling edge.
0h = Falling edge triggered.
1h = Rising edge triggered.
3-0
7.5.16
Mask GPIOx
R/W
0h
Used to mask the corresponding interrupt. Default is unmasked
(mask GPIOx = 0).
DEFGPIO Register (offset = 10h) (reset: 00h)
The DEFGPIO register is used to define the GPIO pins to be either input or output.
Figure 53. DEFGPIO Register
7
IO4
R/W-0
6
IO3
R/W-0
5
IO2
R/W-0
4
IO1
R/W-0
3
Value GPIO4
R/W-0
2
Value GPIO3
R/W-0
1
Value GPIO2
R/W-0
0
Value GPIO1
R/W-0
LEGEND: R/W = Read/Write; R = Read only; -n = value after reset
Table 30. DEFGPIO Register Field Descriptions
BIT
FIELD
TYPE
RESET
DESCRIPTION
7-4
IOx
R/W
0h
0h = Sets the corresponding GPIO to be an input.
1h = Sets the corresponding GPIO to be an output.
3-0
Value GPIOx
R/W
0h
If a GPIO is programmed to be an output, then the signal output
is determined by the corresponding bit. The output circuit for
each GPIO is an open-drain NMOS requiring an external pullup
resistor.
1h = Activates the relevant NMOS, hence forcing a logic low
signal at the GPIO pin.
0h = Turns the open-drain transistor OFF, hence the voltage at
the GPIO pin is determined by the voltage to which the pullup
resistor is connected.
If a particular GPIO is programmed to be an input, then the
contents of the relevant bit in B3-0 is defined by the logic level at
the GPIO pin. A logic low forces a 0 and a logic high forces a 1.
If a GPIO is programmed to be an input, then any attempt to
write to the relevant bit in B3-0 is ignored.
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8 Application and Implementation
NOTE
Information in the following applications sections is not part of the TI component
specification, and TI does not warrant its accuracy or completeness. TI’s customers are
responsible for determining suitability of components for their purposes. Customers should
validate and test their design implementation to confirm system functionality.
8.1 Application Information
The TPS65014 is an integrated power- and battery-management IC designed to pair with various application
processors powered by one Li-ion or Li-polymer cell and which require multiple rails.
8.2 Typical Application
The VCORE and VMAIN converter are always enabled in a typical application. The VCORE output voltage can
be disabled or reduced from 1.5 V to a lower, preset voltage under processor control. When the processor enters
the sleep mode, a high signal on the LOW_PWR pin initiates the change.
VCORE typically supplies the digital part of the audio codec. When the processor is in sleep or low-power mode,
the audio codec is powered off, so the VCORE voltage can be programmed to lower voltages without a problem.
A typical audio codec (such as the TI AIC23) consumes about 20-mA to 30-mA current from the VCORE power
supply.
Supply LDO1 from VMAIN as shown in Figure 54. If this is not done, then subsequent to a UVLO, OVERTEMP,
or BATT_COVER = 0 condition, the RESPWRON signal goes high before the VCORE rail has ramped and
stabilized. Therefore, the processor core does not receive a power-on-reset signal.
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Typical Application (continued)
AC Adapter
AC
BATT+
1 µF
X5R
VBAT
USB port
0.1 µF
BATT−
USB
1 µF
X5R
TPS65014
ISET
TS
TEMP
PG
GND
CHARGER
POWER GOOD
PS_SEQ
GND
DEFCORE
VBAT
DEFMAIN
VBAT
LED2
VCC
10 R
1 µF
X5R
BATT_COVER
VINCORE
TPOR
VCORE 1.5 V
VBAT
PB_ONOFF
GND
HOT_RESET
L2
10 µH
10 µF
X5R
VCORE
LOW_PWR
22 µF
X5R
VINMAIN
VMAIN 3.3 V
VBAT
L1
6.2 µH
22 µF
X5R
VMAIN
GPIO1
INT
GPIO2
GPIO3
nPOR
RESPWRON
GPIO4
MPU_RESET
VIB
VBAT
1 µF
X5R
VMAIN
0.1 µF
VINLDO1
VMAIN
0.1 µF
VINLDO2
GND/VCC
CHARGER/REG INTERRUPT
PWRFAIL
VLDO2
RESET to MPU
Battery Fail, Battery Cover
Removed, Over Temp.
2.2 µF
X5R
1 MΩ Each
VLDO1
2.2 µF
X5R
IFLSB
VFB_LDO1
SDAT
SCL
SDA
SCLK
PGND
AGND
Figure 54. Typical Application Circuit
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Typical Application (continued)
AC Adapter
Touchscreen
Controller
AC
BATT+
VBAT
USB port
BATT−
USB
USB DP, Camera i/f
TPS65014
ISET
TS
TEMP
PG
VBAT
CHARGER
POWER GOOD
TPOR
GND
PS_SEQ
GND
VBAT
DEFCORE
DEFMAIN
LED2
VCC
OMAP1510
VBAT
BATT_COVER
VBAT
PB_ONOFF
GND
HOT_RESET
VINCORE
VCORE 1.5V
L2
VDD, VDD1,
VDD2, VDD3
VCORE
VINMAIN
LOW_PWR
VBAT
VMAIN 3.3V
VDDSHV2,8
L1
VMAIN
GPIO1
INT
CHARGER/REG INTERRUPT
GPIO
GPIO2
GPIO3
RESPWRON
GPIO4
MPU_RESET
VBAT
VIB
VMAIN
VINLDO1
VMAIN
VINLDO2
GND/VCC
PWRFAIL
nPOR
RESPWRON
RESET to MPU
MPU_RESET
Battery Fail, Battery Cover
Removed, Overtemp.
FIQ_PWRFAIL
VLDO2
VDDSHV4,5
VLDO1
VDDSHV1,3,6,7,9
IFLSB
VFB_LDO1
SDAT
SCL
SDA
SCLK
PGND
ARMIO_5/LOW_POWER
AGND
ARMIO,LCD,
Keyboard, USB
Host, SDIO
SDRAM, FLASH i/f
@ 1.8 V/2.8 V
Figure 55. Typical Application Circuit in Low-Power Mode
8.2.1 Design Requirements
Each DC-DC converter requires an external inductor and filter capacitor, capable of sustaining the intended
current with an acceptable voltage ripple. LDOs must have external filter capacitors, and LDO1 requires an
external feedback network for regulation. Every input supply rail requires a decoupling capacitor close to the pin.
To avoid unintended states, logic inputs without internal resistors must not be left floating.
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Typical Application (continued)
8.2.2 Detailed Design Procedure
8.2.2.1 Inductor Selection for the Main and the Core Converter
The main and the core converters in the TPS65014 typically use a 6.2-µH and a 10-µH output inductor,
respectively. Larger or smaller inductor values can be used to optimize the performance of the device for specific
operation conditions. The selected inductor must be rated for its DC resistance and saturation current. The DC
resistance of the inductance influences directly the efficiency of the converter. Therefore, an inductor with lowest
DC resistance is selected for highest efficiency.
Equation 3 calculates the maximum inductor current under static load conditions. The saturation current of the
inductor must be rated higher than the maximum inductor current as calculated with Equation 3. This is
necessary because during heavy load transient, the inductor current rises above the value calculated in
Equation 4.
V
1– O
V
I
DI + V
L
O
L ƒ
(3)
DI
I
+I
) L
L(max)
O(max)
2
where
•
•
•
•
f = Switching frequency (1.25-MHz typical)
L = Inductor value
ΔIL= Peak-to-peak inductor ripple current
ILmax = Maximum inductor current
(4)
The highest inductor current occurs at maximum VI.
Open core inductors have a soft saturation characteristic, and they can usually handle higher inductor currents
versus a comparable shielded inductor.
A more conservative approach is to select the inductor current rating just for the maximum switch current of the
TPS65014 (2 A for the main converter and 0.8 A for the core converter). The core material from inductor to
inductor differs and has an impact on the efficiency, especially at high switching frequencies.
See Table 31 and the typical applications for possible inductors
Table 31. Tested Inductors
DEVICE
INDUCTOR VALUE
DIMENSIONS
COMPONENT SUPPLIER
10 µH
6 mm × 6 mm × 2 mm
Sumida CDRH5D18-100
Core converter
Main converter
10 µH
5 mm × 5 mm × 3 mm
Sumida CDRH4D28-100
4.7 µH
5.5 mm × 6.6 mm x 1 mm
Coilcraft LPO1704-472M
4.7 µH
5 mm × 5 mm × 3 mm
Sumida CDRH4D28C-4.7
4.7 µH
5.2 mm × 5.2 mm × 2.5 mm
Coiltronics SD25-4R7
5.3 µH
5.7 mm × 5.7 mm × 3 mm
Sumida CDRH5D28-5R3
6.2 µH
5.7 mm × 5.7 mm × 3 mm
Sumida CDRH5D28-6R2
6 µH
7 mm × 7 mm × 3 mm
Sumida CDRH6D28-6R0
8.2.2.2 Output Capacitor Selection
The advanced fast response voltage-mode control scheme of the inductive converters implemented in the
TPS65014 allows the use of small ceramic capacitors with a typical value of 22 µF for the main converter and
10 µF for the core converter, without having large output voltage undershoots and overshoots during heavy load
transients. TI recommends ceramic capacitors with low ESR values and the lowest output voltage ripple. If
required, tantalum capacitors with an ESR < 100 Ω may be used as well.
See Table 32 for recommended components.
54
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If ceramic output capacitors are used, the capacitor RMS ripple current rating always meet the application
requirements. For completeness, the RMS ripple current is calculated as in Equation 5:
V
1– O
V
I
1
I
+V
RMSC(out)
O
L ƒ
2 Ǹ3
(5)
At nominal load current, the inductive converters operate in PWM mode, and the overall output voltage ripple is
the sum of the voltage spike caused by the output capacitor ESR plus the voltage ripple caused by charging and
discharging the output capacitor, as in Equation 6:
V
1– O
V
I
1
DV + V
) ESR
O
O
8 C
ƒ
L ƒ
O
(6)
ǒ
Ǔ
Where the highest output voltage ripple occurs at the highest input voltage VI.
At light load currents, the converters operate in power save mode and the output voltage ripple is independent of
the output capacitor value. The output voltage ripple is set by the internal comparator thresholds. The typical
output voltage ripple is 1% of the nominal output voltage. If the output voltage for the core converter is
programmed to its lowest voltage of 0.85 V, the output capacitor must be increased to 22 µF for low output
voltage ripple. This is because the current in the inductor decreases slowly during the off-time and further
increases the output voltage, even when the PMOS is off. This effect increases with low output voltages.
8.2.2.3 Input Capacitor Selection
A pulsating input current is the nature of the buck converter. Therefore, a low ESR input capacitor is required for
best input voltage filtering. It also minimizes the interference with other circuits caused by high input voltage
spikes. The main converter requires a 22-µF ceramic input capacitor, and the core converter requires a 10-µF
ceramic capacitor. The input capacitor for the main and the core converter can be combined and one 22-µF
capacitor can be used instead, because the two converters operate with a phase shift of 270 degrees. The input
capacitor can be increased without any limit for better input voltage filtering. The VCC pin should be separated
from the input for the main and the core converter. A filter resistor of up to 100 Ω and a 1-µF capacitor is used for
decoupling the VCC pin from switching noise.
Table 32. Possible Capacitors
CAPACITOR VALUE
CASE SIZE
COMPONENT SUPPLIER
COMMENTS
22 µF
22 µF
1206
TDK C3216X5R0J226M
Ceramic
1206
Taiyo Yuden JMK316BJ226ML
22 µF
Ceramic
1210
Taiyo Yuden JMK325BJ226MM
Ceramic
8.2.3 Application Curves
100
90
100
VO = 1.6 V
90
80
80
60
VO = 0.85 V
50
40
30
VO = 2.5 V
60
50
40
30
Core:
VI = 3.8 V,
TA = 25°C,
FPWM = 0
20
10
0
0.01
VO = 3.3 V
70
VO = 1.2 V
Efficiency - %
Efficiency - %
70
0.10
1
10
100
Main:
VI = 3.8 V,
TA = 25°C,
FPWM = 0
20
10
1k
IO - Output Current - mA
0
0.01
0.10
1
10
100
1k
10 k
IO - Output Current - mA
Figure 56. Efficiency vs Output Current
Figure 57. Efficiency vs Output Current
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9 Power Supply Recommendations
9.1 Battery Charger
The TPS65014 supports a precision Li-ion or Li-polymer charging system suitable for single cells with either coke
or graphite anodes. Charging the battery is possible even without the application processor being powered up.
The TPS65014 starts charging when an input voltage on either AC or USB input is present, which is greater than
the charger UVLO threshold. See Figure 58 for a typical charge profile.
PreConditioning
Phase
Current Regulation
Phase
Voltage Regulation and Charge
Termination Phase
Regulation Voltage
Regulation Current
Charge Voltage
Minimum Charge
Voltage
Charge Current
Preconditioning
and Taper Detect
t(PRECHG)
t(CHG)
t(TAPER)
Figure 58. Typical Charging Profile
9.1.1 Autonomous Power Source Selection
By default, the TPS65014 attempts to charge from the AC input. If AC input is not present, USB is selected. If
both inputs are available, the AC input has priority. The charge current is initially limited to 100 mA when
charging from the USB input. This can be increased to 500 mA through the serial interface. The charger can be
completely disabled through the interface or from the USB port. The start of the charging process from the USB
port is delayed to allow the application processor time to disable USB charging, for instance if a USB OTG port is
recognized. The recommended input voltage for charging from the AC input is 4.5 V < VAC < 6.5 V. However,
the TPS65014 is capable of withstanding (but not charging from) up to 20 V. Charging is disabled if VAC is
greater than typically 7 V.
9.1.2 Temperature Qualification
The TPS65014 continuously monitors battery temperature by measuring the voltage between the TS and AGND
pins. An internal current source provides the bias for most common 10K negative-temperature coefficient
thermistors (NTC) (see Figure 59). The IC compares the voltage on the TS pin against the internal V(LTF) and
V(HTF) thresholds to determine if charging is allowed. Once a temperature outside the V(LTF) and V(HTF) thresholds
is detected, the IC immediately suspends the charge. The IC suspends charge by turning off the power FET and
holding the timer value (that is, timers are not reset). Charge is resumed when the temperature returns to the
normal range.
The allowed temperature range for a 103-A T-type thermistor is 0°C to +45°C. However, the user may modify
these thresholds by adding two external resistors (see Figure 60).
56
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Battery Charger (continued)
bqTINY II
I(TS)
TS
LTF
Pack+
V(LTF)
HTF
+
Pack–
V(HTF)
NTC
TEMP
Battery Pack
Figure 59. TS Pin Configuration
bqTINY II
I(TS)
TS
LTF
Pack+
V(LTF)
HTF
+
Pack–
V(HTF)
RT1 TEMP
RT2
NTC
Battery Pack
Figure 60. TS Pin Threshold
9.1.3 Battery Preconditioning
On power up, if the battery voltage is below the V(LOWV) threshold, the TPS65014 applies a precharge current,
I(PRECHG), to the battery. This feature revives deeply discharged cells. The charge current during this phase is one
tenth of the value in current regulation phase, which is set with IO(out) = KSET × V(SET) / R(SET). The load current in
the preconditioning phase must be lower than I(PRECHG) and must allow the battery voltage to rise above V(LOWV)
within t(Prechg). VBAT_A is the sense pin to the voltage comparator for the battery voltage. This allows a power-on
sense measurement if the VBAT_A and VBAT_B pins are connected together at the battery.
The TPS65014 activates a safety timer, t(PRECHG), during the conditioning phase. If V(LOWV) threshold is not
reached within the timer period, the TPS65014 turns off the charger and indicates the fault condition in the
CHGSTATUS register. In the case of a fault condition, the TPS65014 reduces the current to I(DETECT). I(DETECT) is
used to detect a battery replacement condition. Fault condition is cleared by POR or battery replacement or
through the serial interface.
9.1.4 Battery Charge Current
The TPS65014 offers on-chip current regulation. When charging from an AC adapter, a resistor connected
between the ISET1 and AGND pins determines the charge rate. A maximum of 1-A charger current from the AC
adapter is allowed. When charging from a USB port, either a 100-mA or 500-mA charge rate can be selected
through the serial interface; default is 100-mA maximum. Two bits are available in the CHGCONFIG register in
the serial interface to reduce the charge current in 25% steps. These only influence charging from the AC input,
and may be of use if charging is often suspended due to excessive junction temperature in the TPS65014 (such
as at high AC input voltages) and low battery voltages.
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Battery Charger (continued)
9.1.5 Battery Voltage Regulation
The voltage regulation feedback is through the VBAT pin. This pin is tied directly to the positive side of the
battery pack. The TPS65014 monitors the battery-pack voltage between the VBAT and AGND pins. The
TPS65014 is offered in a fixed-voltage version of 4.2 V.
As a safety backup, the TPS65014 also monitors the charge time in the fast-charge mode. If taper current is not
detected within this time period, t(CHG), the TPS65014 turns off the charger and indicates FAULT in the
CHGSTATUS register. In the case of a FAULT condition, the TPS65014 reduces the current to I(DETECT). I(DETECT)
is used to detect a battery replacement condition. Fault condition is cleared by POR through the serial interface.
The safety timer is reset if the TPS65014 is forced out of the voltage regulation mode. The fast-charge timer is
disabled by default to allow charging during normal operation of the end equipment. It is enabled through the
CHGCONFIG register.
9.1.6 Charge Termination and Recharge
The TPS65014 monitors the charging current during the voltage regulation phase. Once the taper threshold,
I(TAPER), is detected, the TPS65014 initiates the taper timer, t(TAPER). Charge is terminated after the timer expires.
The TPS65014 resets the taper timer in the event that the charge current returns above the taper threshold,
I(TAPER). After a charge termination, the TPS65014 restarts the charge once the voltage on the VBAT pin falls
below the V(RCH) threshold. This feature keeps the battery at full capacity at all times. The fast charge timer and
the taper timer must be enabled by programming CHGCONFIG(5)=1. A thermal suspend suspends the fastcharge and taper timers.
In addition to the taper current detection, the TPS65014 terminates charge in the event that the charge current
falls below the I(TERM) threshold. This feature allows for quick recognition of a battery removal condition. When a
full battery is replaced with an empty battery, the TPS65014 detects that the VBAT voltage is below the recharge
threshold and starts charging the new battery. The taper and termination bits are cleared in the CHGSTATUS
register and if the INT pin is still active due to these two interrupt sources, then it is de-asserted. Depending on
the transient seen at the VCC pin, all registers may be set to their default values and require reprogramming with
any nondefault values required, such as enabling the fast-charge timer and taper termination; this should only
happen if VCC drops below approximately 2 V.
9.1.7
PG Output
The open-drain, power-good (PG) output indicates when a valid power supply is present for the charger. This can
be either from the AC adapter input or from the USB. The output turns ON when a valid voltage is detected. A
valid voltage is detected whenever the voltage on either pin AC or pin USB rises above the voltage on VBAT
plus 100 mV. This output is turned off in the sleep mode. The PG pin can be used to drive an LED or
communicate to the host processor. A voltage greater than the V(CHGOVLO) threshold (typ 7-V) at the AC input is
not valid and does not activate the PG output. The PG output is held in high impedance state if the charger is in
reset by programming CHGCONFIG(6)=1.
The PG output can also be programmed through the LED1_ON and LED1_PER registers in the serial interface.
It can then be programmed to be permanently on, off, or to blink with defined on- and period-times. PG is
controlled by default through the charger.
9.1.8 Thermal Considerations for Setting Charge Current
The TPS65014 is housed in a 48-pin QFN package with exposed leadframe on the underside. This 7-mm ×
7-mm package exhibits a thermal impedance (junction-to-ambient) of 33 K/W when mounted on a JEDEC high-k
board with zero air flow. Refer to Table 33 for maximum charge current considerations.
Table 33. Power Dissipation Limitations
AMBIENT TEMPERATURE
58
MAX POWER DISSIPATION FOR Tj = 125°C
25°C
3W
55°C
2.1 W
Above 55°C
30 mW/°C
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Consideration must be given to the maximum charge current when the assembled application board exhibits a
thermal impedance, which differs significantly from the JEDEC high-k board. The charger has a thermal
shutdown feature, which suspends charging if the TPS65014 junction temperature rises above a threshold of
145°C. This threshold is set 15°C below the threshold used to power down the TPS65014 completely.
9.2 LDO1 Output Voltage Adjustment
The output voltage of LDO1 is set with a resistor divider at the feedback pin. The sum of the two resistors must
not exceed 1 MΩ to minimize voltage changes due to leakage current into the feedback pin. The output voltage
for LDO1 after start-up is the voltage set by the external resistor divider. It can be reprogrammed with the I2C
interface to the three other values defined in the register VREGS1.
10 Layout
10.1 Layout Guidelines
•
•
•
•
•
•
•
•
The input capacitors for the DC-DC converters must be placed as close as possible to the VINMAIN,
VINCORE, and VCC pins.
The inductor of the output filter must be placed as close as possible to the device to provide the shortest
switch node possible, thus reducing the noise emitted into the system and increasing the efficiency.
Sense the feedback voltage from the output at the output capacitors to ensure the best DC accuracy.
Feedback must be routed away from noisy sources such as the inductor. If possible, route on the opposite
side from the switch node and inductor, and place a GND plane between the feedback and the noisy sources
or keepout underneath them entirely.
Place the output capacitors as close as possible to the inductor to reduce the feedback loop. This ensures
best regulation at the feedback point.
Place the device as close as possible to the most demanding or sensitive load. The output capacitors must
be placed close to the input of the load, which ensures the best AC performance possible.
The input and output capacitors for the LDOs must be placed close to the device for best regulation
performance.
Use vias to connect the thermal pad to the ground plane.
TI recommends using the common ground plane for the layout of this device. The AGND can be separated
from the PGND, but a large low-parasitic PGND is required to connect the PGNDx pins to the CIN and
external PGND connections. If the AGND and PGND planes are separated, have one connection point to
reference the grounds together. Place this connection point close to the IC.
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10.2 Layout Example
L2 Feedback
L2 to Inductor
L2 Filter Cap
L1 Filter Cap
L1 to Inductor
Connect
PowerPAD to
GND layer
with vias
L1 Feedback
Figure 61. Layout Recommendation
60
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11 Device and Documentation Support
11.1 Device Support
11.1.1 Third-Party Products Disclaimer
TI'S PUBLICATION OF INFORMATION REGARDING THIRD-PARTY PRODUCTS OR SERVICES DOES NOT
CONSTITUTE AN ENDORSEMENT REGARDING THE SUITABILITY OF SUCH PRODUCTS OR SERVICES
OR A WARRANTY, REPRESENTATION OR ENDORSEMENT OF SUCH PRODUCTS OR SERVICES, EITHER
ALONE OR IN COMBINATION WITH ANY TI PRODUCT OR SERVICE.
11.2 Community Resources
The following links connect to TI community resources. Linked contents are provided "AS IS" by the respective
contributors. They do not constitute TI specifications and do not necessarily reflect TI's views; see TI's Terms of
Use.
TI E2E™ Online Community TI's Engineer-to-Engineer (E2E) Community. Created to foster collaboration
among engineers. At e2e.ti.com, you can ask questions, share knowledge, explore ideas and help
solve problems with fellow engineers.
Design Support TI's Design Support Quickly find helpful E2E forums along with design support tools and
contact information for technical support.
11.3 Trademarks
E2E is a trademark of Texas Instruments.
All other trademarks are the property of their respective owners.
11.4 Electrostatic Discharge Caution
These devices have limited built-in ESD protection. The leads should be shorted together or the device placed in conductive foam
during storage or handling to prevent electrostatic damage to the MOS gates.
11.5 Glossary
SLYZ022 — TI Glossary.
This glossary lists and explains terms, acronyms, and definitions.
12 Mechanical, Packaging, and Orderable Information
The following pages include mechanical, packaging, and orderable information. This information is the most
current data available for the designated devices. This data is subject to change without notice and revision of
this document. For browser-based versions of this data sheet, refer to the left-hand navigation.
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PACKAGE OPTION ADDENDUM
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10-Dec-2020
PACKAGING INFORMATION
Orderable Device
Status
(1)
Package Type Package Pins Package
Drawing
Qty
Eco Plan
(2)
Lead finish/
Ball material
MSL Peak Temp
Op Temp (°C)
Device Marking
(3)
(4/5)
(6)
TPS65014RGZT
ACTIVE
VQFN
RGZ
48
250
RoHS & Green
NIPDAU
Level-2-260C-1 YEAR
-40 to 85
TPS65014
(1)
The marketing status values are defined as follows:
ACTIVE: Product device recommended for new designs.
LIFEBUY: TI has announced that the device will be discontinued, and a lifetime-buy period is in effect.
NRND: Not recommended for new designs. Device is in production to support existing customers, but TI does not recommend using this part in a new design.
PREVIEW: Device has been announced but is not in production. Samples may or may not be available.
OBSOLETE: TI has discontinued the production of the device.
(2)
RoHS: TI defines "RoHS" to mean semiconductor products that are compliant with the current EU RoHS requirements for all 10 RoHS substances, including the requirement that RoHS substance
do not exceed 0.1% by weight in homogeneous materials. Where designed to be soldered at high temperatures, "RoHS" products are suitable for use in specified lead-free processes. TI may
reference these types of products as "Pb-Free".
RoHS Exempt: TI defines "RoHS Exempt" to mean products that contain lead but are compliant with EU RoHS pursuant to a specific EU RoHS exemption.
Green: TI defines "Green" to mean the content of Chlorine (Cl) and Bromine (Br) based flame retardants meet JS709B low halogen requirements of
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